CN117394019A - Co-location six-polarization antenna based on dual-mode three-ring structure - Google Patents
Co-location six-polarization antenna based on dual-mode three-ring structure Download PDFInfo
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- H—ELECTRICITY
- H01—ELECTRIC ELEMENTS
- H01Q—ANTENNAS, i.e. RADIO AERIALS
- H01Q1/00—Details of, or arrangements associated with, antennas
- H01Q1/50—Structural association of antennas with earthing switches, lead-in devices or lightning protectors
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- H—ELECTRICITY
- H01—ELECTRIC ELEMENTS
- H01Q—ANTENNAS, i.e. RADIO AERIALS
- H01Q1/00—Details of, or arrangements associated with, antennas
- H01Q1/36—Structural form of radiating elements, e.g. cone, spiral, umbrella; Particular materials used therewith
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- H—ELECTRICITY
- H01—ELECTRIC ELEMENTS
- H01Q—ANTENNAS, i.e. RADIO AERIALS
- H01Q1/00—Details of, or arrangements associated with, antennas
- H01Q1/52—Means for reducing coupling between antennas; Means for reducing coupling between an antenna and another structure
- H01Q1/521—Means for reducing coupling between antennas; Means for reducing coupling between an antenna and another structure reducing the coupling between adjacent antennas
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- H—ELECTRICITY
- H01—ELECTRIC ELEMENTS
- H01Q—ANTENNAS, i.e. RADIO AERIALS
- H01Q21/00—Antenna arrays or systems
- H01Q21/24—Combinations of antenna units polarised in different directions for transmitting or receiving circularly and elliptically polarised waves or waves linearly polarised in any direction
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- H—ELECTRICITY
- H01—ELECTRIC ELEMENTS
- H01Q—ANTENNAS, i.e. RADIO AERIALS
- H01Q5/00—Arrangements for simultaneous operation of antennas on two or more different wavebands, e.g. dual-band or multi-band arrangements
- H01Q5/10—Resonant antennas
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- H—ELECTRICITY
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- H01Q—ANTENNAS, i.e. RADIO AERIALS
- H01Q5/00—Arrangements for simultaneous operation of antennas on two or more different wavebands, e.g. dual-band or multi-band arrangements
- H01Q5/50—Feeding or matching arrangements for broad-band or multi-band operation
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Abstract
The invention discloses a co-location hexapolarized antenna based on a dual-mode tricyclic structure, which comprises a first radiation unit, a second radiation unit and a third radiation unit; the three radiating units are respectively and mutually orthogonally distributed on three coordinate axis planes of x, y and z, the centers of the three radiating units are all located at the origin of coordinates, and each radiating unit is excited by using two feed structures to respectively realize two orthogonal working modes of an electric dipole and a magnetic dipole; the third radiating unit is arranged in the first radiating unit and the second radiating unit, and the six feed ports work in a common frequency band; the size of each radiating element and the overall size of the co-located hexapolarized antenna are less than half a wavelength; the six-polarization antenna can simultaneously have the advantages of co-point orthogonality, low coupling, size smaller than half wavelength, ideal electric dipole radiation mode and ideal magnetic dipole radiation mode.
Description
Technical Field
The invention relates to the field of antennas in communication technology, in particular to a co-located six-polarized antenna based on a dual-mode three-ring structure.
Background
The contradiction between limited spectrum resources and increasing application demands is a major bottleneck restricting the popularity of various emerging services in future communication systems. The use of Multiple-input Multiple-output (MIMO) technology in a wireless communication system can greatly increase system capacity, increase spectrum utilization efficiency, and improve system communication quality. The MIMO technology uses multiple antennas at both transmitting and receiving ends of a communication system at the same time, so that the spatial degree of freedom of a multipath channel can be fully utilized, and the transmission rate and channel capacity of the wireless communication system can be improved. Polarization diversity is an important technology in MIMO systems, and has the advantage that the dimension of the polarization domain of electromagnetic waves can be utilized outside the time, frequency and space to further increase the channel capacity of a wireless communication system.
In recent years, with the development of massive MIMO technology in 5G and future wireless communications, there is a strict requirement for the volume and size of mobile communication terminals and base station equipment, and antennas are being developed to be miniaturized and compact. The multi-polarized antenna is also called vector antenna, can realize polarization diversity by using a plurality of co-located antenna units, and can fully utilize all electromagnetic fields E in space x ，E y ，E z ，H x ，H y ，H z The characteristics of the components can be detected simultaneously, so that the volume limitation of the traditional MIMO system can be overcome, and the freedom degree of the wireless system in a limited space is greatly improved. Therefore, the multi-polarized antenna adopting the polarization diversity technology becomes an important component unit in future wireless communication, sensing and other systems, and can effectively improve the performances of the wireless communication, target identification, electromagnetic source positioning and other systems.
Because of the challenges of implementing low-coupling, mode-orthogonal, co-point, compact multi-polarized antennas, most of the currently available multi-polarized antennas are designed for dual-polarized and tri-polarized antennas, while multi-polarized antennas of four or more are designed less.
Patent application 201480084047.9 discloses a six-port six-polarized antenna, in which six polarizations are directly combined by six separate single polarized antennas, and is realized by an upper, middle and lower three-layer structure, the bottom layer is composed of a loop antenna to form a magnetic radiating element, the middle layer is composed of two orthogonal magnetic radiating elements and a vertical electric radiating element, and the upper layer is composed of two orthogonal electric radiating elements. The six-port six-polarized antenna of the invention comprises six polarizations of three electric field components and three magnetic field components. In order to reduce antenna coupling, the hexapolarized antenna adopts a three-layer structure, the geometric centers of all radiation elements are mutually dispersed in the three-layer structure, the co-point orthogonality among all polarization components of the hexapolarized antenna can not be truly realized, and the transverse dimension of the hexapolarized antenna unit size is far greater than half wavelength.
Patent application 202310166430.X discloses an RFID multi-polarized antenna device, wherein the multi-polarized antenna device is composed of a first polarized antenna and a third polarized antenna in a horizontal polarization direction, a vertical direction is composed of a second polarized antenna and a fourth polarized antenna, a fifth polarized antenna is between the first polarized antenna and the third polarized antenna and forms 45 ° with the polarization direction thereof, and a sixth polarized antenna is between the second polarized antenna and the fourth polarized antenna and forms 45 ° with the polarization direction thereof. Thus constituting a hexapolarized antenna. Since the hexapolarized antenna is composed of the same type of electric dipole antenna, the entire electromagnetic field component in space cannot be fully utilized, and the condition of mutual orthogonality between the antenna elements is not satisfied.
In summary, the current multi-polarized antenna mainly includes the following disadvantages:
(1) Most of the existing multi-polarization antennas are mainly polarized by electric field components. The ideal electric field component polarization can be realized through a plurality of electric dipole antennas or monopole antennas, the structure is simple and easy to realize, and the multi-polarization antenna comprising the combination of the ideal magnetic field component polarization component and the electric field polarization component is difficult to realize, because the antenna of the ideal magnetic field component polarization is usually realized through a loop antenna, the multi-polarization antenna is required to be combined with the electric dipole antenna, in order to realize the electric field component and the magnetic field component which are mutually co-point orthogonal, the geometric centers of the loop antenna and the electric dipole antenna are required to be mutually overlapped, so that higher coupling is generated between the antennas of different polarization components, in order to realize low coupling, the multi-polarization antenna is often in a distributed structure, and the size of an antenna unit is often larger because the centers of the polarized antennas are not positioned at the same spatial point.
(2) The electrical polarization element in the existing multi-polarization antenna basically has an ideal electric dipole radiation mode, but the radiation characteristics of the magnetic polarization element have a certain gap from the ideal magnetic dipole antenna, and the radiation characteristics mainly show that the directional patterns of some magnetic field component polarizations have certain directivity, the radiation range is smaller, the omnidirectional radiation of the ideal magnetic dipole magnetic field cannot be realized, and the lack of the electromagnetic component polarizations in certain space angles is caused.
Therefore, there is still a great challenge in designing a multi-polarized antenna that is simultaneously co-point orthogonal, low-coupling, compact (less than half a wavelength in size), easy to process, and capable of achieving all electromagnetic components of an ideal electromagnetic and magnetic dipole omnidirectional radiation.
Disclosure of Invention
The invention aims to: in order to solve the problems that the existing multi-polarized antenna cannot simultaneously have the common-point orthogonal, low-coupling, size smaller than half wavelength, easy processing and cannot realize the full electromagnetic component of the ideal electromagnetic and magnetic dipole omnidirectional radiation, the invention provides a common-address six-polarized antenna based on a dual-mode three-ring structure, and the antenna simultaneously has the common-point orthogonal, low-coupling, size smaller than half wavelength, ideal electric dipole radiation mode and ideal magnetic dipole radiation mode, and can be used in the fields of large-scale MIMO antenna arrays, wireless communication, target identification, electromagnetic source positioning and the like.
The technical scheme is as follows: the utility model provides a six polarized antennas of co-location based on bimodulus tricyclic structure which characterized in that: comprising the following steps: a first radiating element, a second radiating element, and a third radiating element; the three radiating units are respectively and mutually orthogonally distributed on three coordinate axis planes of x, y and z, the centers of the three radiating units are all located at the origin of coordinates, and each radiating unit is excited by using two feed structures to respectively realize two orthogonal working modes of an electric dipole and a magnetic dipole;
the first radiation unit comprises a first feed port, a second feed port, a first zero phase shift annular transmission line, a first coplanar waveguide, a first metal microstrip line and a first metal microstrip line feed network; the first zero phase shift annular transmission line is excited by the first metal microstrip line at the feed port to realize a magnetic dipole H z An operating mode; the second feeding port is connected to the first zero phase shift annular transmission line through a first metal microstrip line feeding network, and realizes an electric dipole E under the action of a first coplanar waveguide when the second feeding port is excited x An operating mode;
the second radiation unit comprises a feeding port III, a feeding port IV, a second zero phase shift annular transmission line, a second coplanar waveguide, a second metal microstrip line and a second metal microstrip line feeding network; the third feed port excites a second zero phase shift annular transmission line through a second metal microstrip line to realize a magnetic dipole H y An operating mode; the fourth feeding port is connected to the second zero phase shift annular transmission line through a second metal microstrip line feeding network, and when the fourth feeding port is excited, an electric dipole E is realized under the action of a second coplanar waveguide z An operating mode;
wherein the third radiating element comprises: a fifth feed port, a sixth feed port, a third dielectric plate, an outer multi-section annular transmission line, an inner multi-section annular transmission line, a third metal microstrip line feed network, a third metal microstrip line, a back multi-section annular transmission line and a third coplanar waveguide; the outer-layer multi-section annular transmission line is arranged on the front surface of the third dielectric plate, the inner-layer multi-section annular transmission line is arranged on the front surface of the third dielectric plate and is positioned in the outer-layer multi-section annular transmission line, and the back multi-section annular transmission line is arranged on the back surface of the third dielectric plate; the fifth feeding port is connected with the outer multi-section annular transmission line and the inner multi-section annular transmission line through a third metal microstrip line, and when the fifth feeding port is excited, the magnetic dipole H is realized x An operating mode; the feed port six is connected to the outer multi-section annular transmission line through a third metal microstrip line feed network, and when the feed port six is excited, an electric dipole E is realized under the action of a third coplanar waveguide y An operating mode;
the third radiating unit is arranged in the first radiating unit and the second radiating unit, and the six feed ports work in a common frequency band;
the size of each radiating element is smaller than half a wavelength, and the size of a co-located hexapolarized antenna based on a dual-mode tricyclic structure (49.5 mm 46.3mm 49mm = 0.4125λ) 0 *0.386λ 0 *0.4084λ 0 ) Less than half a wavelength.
In order to realize the six-polarization antenna with completely co-point orthogonality, the third radiating element is miniaturized, namely, only when the size of the third radiating element is smaller than that of the first radiating element and the second radiating element, the third radiating element can be combined with the first radiating element and the second radiating element, so that the size of the third radiating element is smaller than that of the first radiating element and the second radiating element and has the same working frequency band through the adjustment of the sizes and the relative positions of the outer multi-section annular transmission line, the inner multi-section annular transmission line and the back multi-section annular transmission line, and the third radiating element can be arranged in the first radiating element and the second radiating element, thereby realizing that six polarized ports work in a common frequency band and have larger public bandwidth; meanwhile, the coupling between the third radiation unit and the first and second radiation units is adjusted through the change of parameters such as width, length and the like of the outer-layer multi-section annular transmission line, the inner-layer multi-section annular transmission line and the back multi-section annular transmission line, namely the low coupling radiation characteristic of each polarization mode can be realized without increasing the distance between the radiation units or adding any decoupling structure on the premise of ensuring that the total precision co-point orthogonality of the radiation centers of each polarization; meanwhile, the metal microstrip line feed network is combined with the coplanar waveguide, so that the coupling between the radiating units is effectively reduced, and the size of the six-polarization antenna is effectively reduced, so that the size is smaller than half wavelength. The structural designs of the co-located six-polarized antenna are matched with each other to influence each other, so that the six-polarized antenna which has the advantages of co-point orthogonality, low coupling, size smaller than half wavelength, ideal electric dipole radiation mode and ideal magnetic dipole radiation mode can be obtained.
Further, the first coplanar waveguide, the second coplanar waveguide and the third coplanar waveguide are all coplanar waveguides with microstrip balun structures.
Further, the circumference of the first zero phase shift annular transmission line and the circumference of the second zero phase shift annular transmission line are equal to the working wavelength.
Further, the first zero-phase shifted annular transmission line and the second zero-phase shifted annular transmission line are each comprised of uniformly distributed capacitive loading units. .
Further, the outer layer multi-section annular transmission line consists of a multi-section transmission line unit I; the inner layer multi-section annular transmission line consists of a multi-section transmission line unit II; the back multi-section annular transmission line is composed of a multi-section transmission line unit III.
Further, the loop width of the back multi-section loop transmission line is consistent with the loop width of the outer layer multi-section loop transmission line.
Further, the first metal microstrip line feed network, the second metal microstrip line feed network and the third metal microstrip line feed network are all zigzag multi-section microstrip feed line structures with chamfers.
Further, the outer layer multi-section annular transmission line consists of six sections of transmission line units I, and the radian of each section of transmission line unit I is 57 degrees; the inner layer multi-section annular transmission line consists of six sections of transmission line units II, and the radian of each section of transmission line unit II is 56 degrees; the back multi-section annular transmission line consists of four sections of transmission line units III, and the radian of each section of transmission line unit III is 86 degrees.
The beneficial effects are that: compared with the prior art, the invention has the following advantages:
(1) The invention adopts three radiation units to realize six orthogonal polarizations, and can realize low coupling on the premise of keeping the coposition orthogonality of each polarization, and the radiation mode of the six-polarization antenna provided by the invention comprises three electric dipole radiation modes and three magnetic dipole radiation modes, and the six radiation modes are mutually orthogonal, so that the space electromagnetic information is fully utilized;
(2) The radiating unit of the invention is composed of a radiator, a coplanar waveguide and a microstrip feeder network, on one hand, the radiating unit canRealizing two modes of electric dipole and magnetic dipole, on the other hand, effectively reducing the size of the hexapolarized antenna and enabling the size of each radiation unit and the whole hexapolarized antenna (0.4125λ) 0 *0.386λ 0 *0.4084λ 0 ) Less than half a wavelength;
(3) The third radiating unit of the invention adopts a multi-section three-ring transmission line structure, thereby further reducing the overall size (0.354 lambda) of the third radiating unit ring 0 *0.242λ 0 ) The antenna can be arranged in the first radiation unit and the second radiation unit, and the working frequency of the antenna is changed by adjusting the multi-section three-ring transmission line so that the working frequency of the antenna is close to that of the first radiation unit and the second radiation unit, thereby the overall six-polarization antenna has larger public bandwidth; in addition, the coupling between the three radiators can be regulated, so that the coupling of the whole hexapolarized antenna is lower;
(4) The six-polarization antenna can simultaneously have the advantages of co-point orthogonality, low coupling, size smaller than half wavelength, ideal electric dipole radiation mode and ideal magnetic dipole radiation mode.
Drawings
Fig. 1 is a schematic structural diagram of a hexapolarized antenna according to an embodiment of the present invention;
fig. 2 is a structure of a first radiating element of an XY plane of a hexapolarized antenna, wherein: fig. 2 (a) is a front view, and fig. 2 (b) is a rear view;
fig. 3 is a structure of a second radiating element of XZ plane of a hexapolarized antenna, wherein: fig. 3 (a) is a front view, and fig. 3 (b) is a rear view;
fig. 4 is a structure of a third radiating element of the YZ plane of the hexapolarized antenna, in which: fig. 4 (a) is a front view, and fig. 4 (b) is a rear view;
fig. 5 is a simulation result of S parameters of a hexapolarized antenna according to an embodiment of the present invention;
FIG. 6 is a simulation result of coupling between ports of a hexapolarized antenna in an embodiment of the present invention;
fig. 7 is a diagram showing the current distribution on the zero-phase shift loop transmission line on the first radiating element when the first and second feed ports are excited by the hexapolarized antenna according to the embodiment of the present invention; wherein: fig. 7 (a) is the current distribution on the zero-phase shifted annular transmission line on the first radiating element when the first feed port is energized, and fig. 7 (b) is the current distribution on the zero-phase shifted annular transmission line on the first radiating element when the second feed port is energized;
fig. 8 is a current distribution on a zero-phase shift loop transmission line on a second radiating element when a hexapolarized antenna is excited at a third feed port and a fourth feed port in an embodiment of the present invention; wherein: fig. 8 (a) is a current distribution on a zero phase shift loop transmission line on the second radiating element when the third feed port is energized; fig. 8 (b) is the current distribution on the zero phase shift loop transmission line on the second radiating element when the fourth feed port is energized;
fig. 9 is a current distribution of a six-polarized antenna on a multi-segment loop transmission line on a third radiating element when excited at a fifth feed port and a sixth feed port in an embodiment of the present invention; fig. 9 (a) is a current distribution on the multi-segment loop transmission line on the third radiating element when the fifth feed port is energized; fig. 9 (b) is a current distribution on the multi-segment loop transmission line on the third radiating element when the sixth feed port is energized;
fig. 10 is a radiation pattern of the xoy plane and the yoz plane when the first feed port of the hexapolarized antenna is excited in the embodiment of the invention; fig. 10 (a) shows an xoy-plane radiation pattern when the first feeding port is excited, and fig. 10 (b) shows a yoz-plane radiation pattern when the first feeding port is excited;
FIG. 11 is a radiation pattern of the xoy plane and the yoz plane when the second feed port of the hexapolarized antenna is excited in an embodiment of the present invention; fig. 11 (a) shows an xoy-plane radiation pattern when the second feeding port is excited, and fig. 11 (b) shows a yoz-plane radiation pattern when the second feeding port is excited;
fig. 12 is a radiation pattern of the xoy plane and the xoz plane when the third feeding port of the hexapolarized antenna is excited in the embodiment of the present invention; fig. 12 (a) shows an xoy-plane radiation pattern when the third feeding port is excited, and fig. 12 (b) shows a xoz-plane radiation pattern when the third feeding port is excited;
fig. 13 is a radiation pattern of the xoy plane and the yoz plane when the fourth feed port of the hexapolarized antenna is excited in the embodiment of the invention; fig. 13 (a) shows the xoy-plane radiation pattern when the fourth feed port is excited; fig. 13 (b) shows a yoz radiation pattern when excited by the fourth feeding port;
fig. 14 is a radiation pattern of the xoy plane and the yoz plane when the fifth feed port of the hexapolarized antenna is excited in the embodiment of the present invention; fig. 14 (a) shows the xoy-plane radiation pattern when the fifth feeding port is excited; fig. 14 (b) shows a yoz radiation pattern when the fifth feeding port is excited;
fig. 15 is a radiation pattern of the xoy plane and the xoz plane when the sixth feed port of the hexapolarized antenna is excited in the embodiment of the present invention; fig. 15 (a) shows the xoy-plane radiation pattern when the sixth feeding port is excited; fig. 15 (b) shows a xoz radiation pattern when excited by the sixth feeding port;
fig. 16 is a schematic diagram of correlation between ports of a hexapolarized antenna according to an embodiment of the present invention.
Detailed Description
The technical scheme of the invention is further described with reference to the accompanying drawings and the embodiments.
As shown in fig. 1, the co-located hexapolarized antenna based on the dual-mode tri-loop structure of the present embodiment is composed of three co-located and mutually orthogonal radiating elements. The co-point and mutually orthogonal means that three radiating units are respectively and mutually and orthogonally distributed on three coordinate axis planes of x, y and z, the centers of the three radiating units are all located at the origin of coordinates, and each radiating unit is excited by using two feed structures, so that two orthogonal working modes of an electric dipole and a magnetic dipole can be respectively realized. Therefore, the hexapolarized antenna of the present embodiment realizes six different radiation modes including three electric dipoles (E x 、E y 、E z ) And three magnetic dipoles (H x 、H y 、H z ) The method comprises the steps of carrying out a first treatment on the surface of the As shown in fig. 1, an electric dipole (E x ) Magnetic dipole (H) z ). An electric dipole (E z ) Magnetic dipole (H) y ). An electric dipole (E y ) Magnetic dipole (H) x )。
For convenience of description, three radiating elements are denoted: a first radiating element 1, a second radiating element 2 and a third radiating element 3.
As shown in fig. 2, the first radiating element 1 is located on the antenna XoY side, and includes a first zero-phase-shift loop transmission line 4, a first feed port 5, a second feed port 6, a first dielectric plate 7, a first metal microstrip line feed network 8, a first metal microstrip line 9, and a first coplanar waveguide 10.
Wherein a first zero-phase-shift loop transmission line 4 is arranged on the front side of the first dielectric plate 7, the first zero-phase-shift loop transmission line 4 is composed of eight periodic capacitive load structural units which are uniformly distributed in space, the interval between adjacent capacitive load structural units is 45 degrees, and the maximum arc length of each unit constituting the periodic capacitive load structure of the first zero-phase-shift loop transmission line is 12 degrees. The use of the first zero-phase shifted annular transmission line 4 with a periodic structure corresponds to the introduction of a series capacitance, providing very little phase correction in adjacent capacitive loading structures, so that the current along the first zero-phase shifted annular transmission line 4 remains consistent when the circumference of the first zero-phase shifted annular transmission line 4 is comparable to the operating wavelength. The first feeding port 5 excites the first zero phase shift annular transmission line 4 through the first metal microstrip line 9, when the first feeding port 5 excites, the current on the first zero phase shift annular transmission line 4 has the same amplitude and the same direction, and realizes the magnetic dipole (H) z ) An operating mode.
The first coplanar waveguide 10 is located at the back of the first dielectric plate 7, and the first coplanar waveguide 10 in this embodiment adopts a microstrip balun structure, where the coplanar waveguide of the microstrip balun structure is a feeding structure for controlling current.
When the second feed port 6 is excited, the coplanar waveguide 10 having a microstrip balun structure (balanced to unbalanced transition structure) is connected as a microstrip feed structure to the first metal microstrip feed network 8, and connected to the first zero-phase-shift annular transmission line 4 through the first metal microstrip feed network 8, thereby realizing reverse current of the first zero-phase-shift annular transmission line 4 on both sides of the port, and thus realizing electricityDipole (E) x ) Is a function of the mode of operation of (a). The present embodiment can adjust the resonant frequency by adjusting the size of the first microstrip line feeding network 8, and effectively reduce the size of the antenna, so that the size of the first radiating element 1 (49.5 mm×37.6mm=0.4125λ) 0 *0.314λ 0 ) Less than half a wavelength.
The first dielectric plate 7 of this embodiment is epoxy FR-4 with a dielectric constant of 4.52.
As shown in fig. 3, the second radiating element 2 is located on the side of the antenna XoZ, and includes: a third feed port 11, a fourth feed port 12, a second zero phase shift loop transmission line 13, a second dielectric plate 14, a second metal microstrip feed network 15, a second metal microstrip 16 and a second coplanar waveguide 17.
Wherein the second zero-phase-shift loop transmission line 13 is arranged on the front surface of the second dielectric plate 14, the second zero-phase-shift loop transmission line 13 is composed of eight capacitive loading units which are uniformly distributed in space, the interval between adjacent capacitive loading structural units is 45 degrees, and the maximum arc length of each unit of the periodic capacitive loading structures forming the zero-phase-shift transmission line on the loop is 12 degrees. The use of the second zero-phase shifted annular transmission line 13 with a periodic structure corresponds to the introduction of a series capacitance that provides little phase correction in adjacent capacitive loading structures so that the current along the second zero-phase shifted annular transmission line 13 remains consistent when the circumference of the second zero-phase shifted annular transmission line 13 is comparable to the operating wavelength. The third feeding port 11 excites the second zero phase shift annular transmission line 13 through the second metal microstrip line 16, when the third feeding port 11 excites, equal-amplitude and same-direction current is excited on the second zero phase shift annular transmission line 13, and a magnetic dipole (H) is realized y ) An operating mode.
The second coplanar waveguide 17 is located at the back of the second dielectric plate 14, and the second coplanar waveguide 17 in this embodiment adopts a microstrip balun structure, where the coplanar waveguide of the microstrip balun structure is a feeding structure for controlling current. When the fourth feed port 12 is excited, the coplanar waveguide 17 having a microstrip balun structure (balanced to unbalanced transition structure) is connected as a microstrip feed structure to the second metal microstrip feed network 15, and is connected to the second zero phase shift through the second metal microstrip feed network 15On the loop transmission line 13, the reverse of the current of the second zero-phase shift loop transmission line 13 on both sides of the feed port is achieved, thus an electric dipole (E z ) Is a function of the mode of operation of (a).
In this embodiment, the size of the second microstrip feed network 15 can be adjusted to achieve the adjustment of the resonant frequency, and the size of the antenna can be effectively reduced, so that the size (49 mm×38mm= 0.4084 λ0×0.31666 λ0) of the second radiating element 2 is smaller than half wavelength.
The second dielectric plate 14 of this embodiment is epoxy FR-4 with a dielectric constant of 4.52.
As shown in fig. 4, the third radiating element 3 is located on the antenna YoZ surface, and includes a fifth feeding port 18, a sixth feeding port 19, a third dielectric plate 20, an outer multi-segment annular transmission line 21, an inner multi-segment annular transmission line 22, a third metal microstrip line feeding network 23, a third metal microstrip line 24, a back multi-segment annular transmission line 25, and a third coplanar waveguide 26. The outer layer multi-section annular transmission line 21, the inner layer multi-section annular transmission line 22 and the back multi-section annular transmission line 25 jointly realize the basic function of a zero phase shift transmission line, the outer layer multi-section annular transmission line 21 and the inner layer multi-section annular transmission line 22 are used on the front surface of the third dielectric plate 20, the back multi-section annular transmission line 25 is used on the back surface of the third dielectric plate 20, which is equivalent to the introduction of a series capacitor and a parallel capacitor in a transmission line loop, and the third metal microstrip line 24 is connected with the outer layer multi-section annular transmission line 21 and the inner layer multi-section annular transmission line 22, so that the regulation and control of current distribution on the transmission line can be realized.
The outer multi-section annular transmission line 21 consists of six sections of transmission line units, the radian of each section of transmission line unit is 57 degrees, the inner multi-section annular transmission line 22 also consists of six sections of transmission line units, the radian of each section of transmission line unit is 56 degrees, the back multi-section annular transmission line 25 consists of four sections of transmission line units, and the radian of each section of transmission line unit is 86 degrees. The radian of each transmission line unit is adjusted, so that the adjustment of the resonant frequency is realized. The loop width of the back multi-segment loop transmission line 25 in this embodiment is identical to the loop width of the outer multi-segment loop transmission line 21, and the resonant frequency can be greatly adjusted and the size of the third radiation unit 3 can be greatly reduced by arranging the relative positions of the two. The present embodiment can achieve resonance frequency adjustment and improve impedance bandwidth by adjusting the size of the transmission line units constituting the inner layer multi-segment loop transmission line 22.
Wherein the fifth feeding port 18 is connected to the outer multi-section annular transmission line 21 and the inner multi-section annular transmission line 22 through a third metal microstrip line 24, the sixth feeding port 19 is connected to the outer multi-section annular transmission line 21 through a third metal microstrip line feeding network 23, when the fifth feeding port 18 is excited, a current similar to a constant-amplitude and same-direction current is generated on the outer multi-section annular transmission line 21, thereby realizing a magnetic dipole (H x ) An operating mode. When the sixth feed port 19 is excited, reverse currents are excited at both sides of the feed port of the outer multi-section annular transmission line 21 under the action of the third coplanar waveguide 26, thereby realizing an electric dipole (E) y ) An operating mode.
For the third radiating element 3, by adjusting the size of the third metal microstrip line feed network 23, on the one hand, adjustment of the resonance frequency can be achieved, and on the other hand, the third radiating element size can be reduced so that the size of the third radiating element 3 is smaller than half a wavelength.
The third dielectric plate 20 of this embodiment is epoxy FR-4 with a dielectric constant of 4.52.
In this embodiment, an outer multi-segment annular transmission line 21 and an inner multi-segment annular transmission line 22 are used on the front surface of the third dielectric plate 20, and a back multi-segment annular transmission line 25 is used on the back surface of the third dielectric plate 20, and the functions thereof include:
(1) Two orthogonal working modes of an electric dipole and a magnetic dipole are realized;
(2) Has the antenna miniaturization function: in order to make the third radiating element 3 capable of being combined with the first radiating element 1 and the second radiating element 2 to realize a six-polarized antenna with completely co-point orthogonal, the third radiating element 3 needs to be miniaturized, and the size of the third radiating element 3 can be smaller than that of the first radiating element and the second radiating element and has the same working frequency range by adjusting the sizes and the relative positions of the front multi-layer multi-section annular transmission line and the back annular transmission line, so that the third radiating element 3 can be placed inside the first radiating element 1 and the second radiating element 2 based on the structure;
(3) By adjusting the sizes and the relative positions of the front multilayer multi-section annular transmission line and the back annular transmission line, on the basis of keeping the miniaturization of the radiation unit, frequency adjustment can be realized, so that a plurality of six-polarization ports work at the same frequency and have larger public bandwidth.
(4) The multi-layer multi-section transmission line structure can adjust the coupling between the third radiation unit 3 and the first radiation unit 1 and the second radiation unit 2 through the change of parameters such as width, length and the like, thereby obtaining a low-coupling six-polarization antenna structure.
In addition, the port excitation feeder structure of the corresponding electric dipole in the three radiating units is optimized, namely, a metal microstrip line feeder network with a zigzag multi-section microstrip feeder structure and a chamfer structure is adopted, and the metal microstrip line feeder network of the structure and the coplanar waveguide jointly act to realize current distribution regulation and control on the radiating units and reduce coupling between ports. And by adjusting the sizes of the metal microstrip line feed network and the coplanar waveguide of the structure, proper feed points are selected, so that the coupling between the radiation units is effectively reduced, and the size of each radiation unit is effectively reduced, and the overall size of the hexapolarized antenna is smaller than half wavelength.
In summary, the six-polarized antenna structure of this embodiment reduces the number of six independent radiators required for implementing a conventional six-polarized antenna to three, which is favorable for miniaturization of the overall antenna, and more importantly, the six-polarized antenna structure of this embodiment can implement low coupling radiation characteristics of each polarization mode without increasing the distance between the radiation units or adding any decoupling structure on the premise of ensuring that the centers of polarized radiation are completely accurate and co-point orthogonal. The six-polarization antenna of the embodiment can more fully utilize the vector characteristics of electromagnetic fields in space by transmitting and receiving electromagnetic waves with six orthogonal polarization components, and six radiation modes are close to the radiation characteristics of ideal electric and magnetic dipoles, so that omnidirectional radiation in free space can be realized. Therefore, the six-polarized antenna provided by the embodiment is a full electromagnetic component multi-polarized antenna which has the advantages of being co-point orthogonal, low in coupling, compact and easy to process and has ideal electromagnetic and magnetic dipole radiation characteristics.
Fig. 5 is a reflection coefficient curve of the hexapolarized antenna of this embodiment, and it can be seen that the common bandwidth of-10 dB impedance of the hexapolarized antenna is 140MHz (2.43-2.47 GHz).
Fig. 6 shows the coupling curves of the hexapolarized antenna of this embodiment, and it can be seen that the coupling is lower than-14.25 dB in the common bandwidth of-10 dB impedance.
As can be seen from fig. 7 (a) and fig. 7 (b) are the current distribution on the first zero-phase shift transmission line loop 4 when the first feeding port 5 and the second feeding port 6 of the hexapolarized antenna of the present embodiment are excited respectively, the amplitude of the current on the first zero-phase shift transmission line loop 4 is equal when the first feeding port 5 is excited, and the directions of the current are uniform due to the phase compensation relationship of the first zero-phase shift transmission line loop 4, a ring-shaped current with equal amplitude and same direction is formed, the radiation characteristic of which can be equivalent to that of the magnetic dipole antenna H in the z direction z . When the second feeding port 6 is fed, as shown in fig. 7 (b), under the action of the coplanar waveguide 10, the current flowing to the two ends of the first zero-phase shift transmission line ring 4 is symmetrically opposite, and the radiation characteristic can be equivalent to that of an electric dipole E in the x direction x 。
As can be seen from fig. 8 (a) and fig. 8 (b) are the current distribution on the second zero-phase shift transmission line loop 13 when the third feeding port 11 and the fourth feeding port 12 of the hexapolarized antenna of the present embodiment are excited respectively, the amplitude of the current on the second zero-phase shift transmission line loop 13 is equal when the third feeding port 11 is excited, and the directions of the currents are uniform due to the phase compensation relationship of the second zero-phase shift transmission line loop 13, a ring-shaped current with equal amplitude and same direction is formed, the radiation characteristic of which can be equivalent to that of the magnetic dipole antenna H in the y direction y . When the fourth feeding port 12 feeds, as shown in fig. 8 (b), the current flowing to both ends of the second zero-phase shift transmission line loop 13 is symmetrically opposite under the action of the coplanar waveguide 17, and the radiation characteristics thereof can be equalizedEffective as electric dipole E in z direction z 。
As can be seen from fig. 9 (a) and fig. 9 (b), which are the current distribution on the outer multi-segment loop transmission line 21 when the fifth feed port 18 and the sixth feed port 19 of the six-polarized antenna of the present embodiment are excited, respectively, the magnitudes of the currents on the outer multi-segment loop transmission line 21 are approximately equal when the fifth feed port 18 is excited, and the basic principle of the zero-phase shift transmission line is realized due to the multi-segment loop transmission line structure, so that the directions of the currents on the outer multi-segment loop transmission line 21 are substantially uniform, the radiation characteristics thereof can be equivalent to the magnetic dipole antenna H in the x-direction x . When the sixth feeding port 19 feeds, as shown in fig. 9 (b), under the action of the coplanar waveguide 26, the currents flowing to the two ends of the outer multi-section annular transmission line 21 are symmetrically opposite, and the radiation characteristic can be equivalent to the electric dipole E in the y direction y 。
Fig. 10 (a) and 10 (b) are radiation patterns of the xoy plane and the yoz plane, respectively, when the first feeding port 5 of the hexapolarized antenna of the present embodiment is excited, as shown in the figure, it can be seen that when the first feeding port 5 is excited, the hexapolarized antenna obtains good horizontal polarized omnidirectional radiation on the xoy plane, obtains an "8" shaped radiation pattern on the yoz plane, and conforms to the magnetic dipole (H z ) Is a radiation characteristic of (a).
Fig. 11 (a) and 11 (b) are radiation patterns of the xoy plane and the yoz plane, respectively, when the second feeding port 6 of the hexapolarized antenna of the present embodiment is excited. As shown in the figure, the xoy plane shows a quasi-8-shaped radiation pattern, good omnidirectional radiation is obtained at yoz, and the radiation pattern conforms to an ideal electric dipole (E x ) Is a radiation pattern of (a).
Fig. 12 (a) and 12 (b) are radiation patterns of the xoy plane and the xoz plane, respectively, when the third feeding port 11 of the hexapolarized antenna of the present embodiment is excited. As shown in the figure, it can be seen that when the third feed port 11 is excited, the hexapolarized antenna of this embodiment obtains good horizontal polarized omnidirectional radiation on the xoz plane, obtains a quasi-8-shaped radiation pattern on the xoy plane, and conforms to the arrangement along the y axisMagnetic dipole (H) y ) Is a radiation characteristic of (a).
Fig. 13 (a) and 13 (b) are radiation patterns of the xoy plane and the yoz plane, respectively, when the fourth feeding port 12 of the hexapolarized antenna of the present embodiment is excited. As shown, good omnidirectional radiation is obtained at the xoy plane, and a quasi-8-shaped radiation pattern is shown at yoz plane, the radiation pattern conforming to an ideal electric dipole (E z ) Is a radiation pattern of (a).
Fig. 14 (a) and 14 (b) are radiation patterns of the xoy plane and the yoz plane, respectively, when the fifth feeding port 18 of the hexapolarized antenna of the present embodiment is excited. As shown in the figure, it can be seen that when the fifth feed port 18 is excited, the hexapolarized antenna of this embodiment obtains good horizontal polarized omnidirectional radiation on the yoz plane, obtains a quasi-8-shaped radiation pattern on the xoy plane, and conforms to the magnetic dipole (H x ) Is a radiation characteristic of (a).
Fig. 15 (a) and 15 (b) are radiation patterns of the xoy plane and the xoz plane, respectively, when the sixth feed port 19 of the hexapolarized antenna is excited. As shown in the figure, the xoy plane shows a quasi-8-shaped radiation pattern, good omnidirectional radiation is obtained at the xoz plane, and the radiation pattern is very consistent with an ideal electric dipole (E y ) Is a radiation pattern of (a).
Fig. 16 shows a correlation coefficient curve between ports of the hexapolarized antenna of this embodiment, and it can be seen that the correlation between ports is lower than 0.03 in the frequency band range of 2.40GHz-2.60 GHz. The correlation is calculated according to the following formula:
rho in ij Representing the correlation coefficient S ii Representing the reflection coefficient of port i,represent S ii Conjugation, S ij Representing the transmission coefficients of ports j to i. />Represent S ij Is a conjugate of (c).
Claims (7)
1. The utility model provides a six polarized antennas of co-location based on bimodulus tricyclic structure which characterized in that: comprising the following steps: a first radiating element, a second radiating element, and a third radiating element; the three radiating units are respectively and mutually orthogonally distributed on three coordinate axis planes of x, y and z, the centers of the three radiating units are all located at the origin of coordinates, and each radiating unit is excited by using two feed structures to respectively realize two orthogonal working modes of an electric dipole and a magnetic dipole;
the first radiation unit comprises a first feed port, a second feed port, a first zero phase shift annular transmission line, a first coplanar waveguide, a first metal microstrip line and a first metal microstrip line feed network; the first zero phase shift annular transmission line is excited by the first metal microstrip line at the feed port to realize a magnetic dipole H z An operating mode; the second feeding port is connected to the first zero phase shift annular transmission line through a first metal microstrip line feeding network, and realizes an electric dipole E under the action of a first coplanar waveguide when the second feeding port is excited x An operating mode;
the second radiation unit comprises a feeding port III, a feeding port IV, a second zero phase shift annular transmission line, a second coplanar waveguide, a second metal microstrip line and a second metal microstrip line feeding network; the third feed port excites a second zero phase shift annular transmission line through a second metal microstrip line to realize a magnetic dipole H y An operating mode; the fourth feeding port is connected to the second zero phase shift annular transmission line through a second metal microstrip line feeding network, and when the fourth feeding port is excited, an electric dipole E is realized under the action of a second coplanar waveguide z An operating mode;
wherein the third radiating element comprises: fifth and sixth feeding ports, third dielectric plate, outer multi-section annular transmission line, inner multi-section annular transmission line, third metal microstrip line feeding network, third metal microstrip line, back multi-section annular transmission line and third coplanar waveguideThe method comprises the steps of carrying out a first treatment on the surface of the The outer-layer multi-section annular transmission line is arranged on the front surface of the third dielectric plate, the inner-layer multi-section annular transmission line is arranged on the front surface of the third dielectric plate and is positioned in the outer-layer multi-section annular transmission line, and the back multi-section annular transmission line is arranged on the back surface of the third dielectric plate; the fifth feeding port is connected with the outer multi-section annular transmission line and the inner multi-section annular transmission line through a third metal microstrip line, and when the fifth feeding port is excited, the magnetic dipole H is realized x An operating mode; the feed port six is connected to the outer multi-section annular transmission line through a third metal microstrip line feed network, and when the feed port six is excited, an electric dipole E is realized under the action of a third coplanar waveguide y An operating mode;
the third radiating unit is arranged in the first radiating unit and the second radiating unit, and the six feed ports work in a common frequency band;
the size of each radiating element is smaller than half a wavelength, and the size of the co-located hexapolarized antenna based on the dual-mode tricyclic structure is smaller than half a wavelength.
2. The co-located hexapole antenna based on dual-mode tri-loop structure of claim 1, wherein: the first coplanar waveguide, the second coplanar waveguide and the third coplanar waveguide are all coplanar waveguides with microstrip balun structures.
3. The co-located hexapole antenna based on dual-mode tri-loop structure of claim 1, wherein: the perimeter of the first zero phase shift annular transmission line and the perimeter of the second zero phase shift annular transmission line are equal to the working wavelength.
4. A co-located hexapole antenna based on a dual-mode tri-loop structure as claimed in claim 3, wherein: the first zero-phase-shift loop transmission line and the second zero-phase-shift loop transmission line are each composed of uniformly distributed capacitive loading units.
5. The co-located hexapole antenna based on dual-mode tri-loop structure of claim 1, wherein: the outer layer multi-section annular transmission line consists of a multi-section transmission line unit I; the inner layer multi-section annular transmission line consists of a multi-section transmission line unit II; the back multi-section annular transmission line is composed of a multi-section transmission line unit III.
6. The co-located hexapole antenna based on dual-mode tri-loop structure of claim 1, wherein: the loop line width of the back multi-section loop transmission line is consistent with that of the outer layer multi-section loop transmission line.
7. The co-located hexapole antenna based on dual-mode tri-loop structure of claim 1, wherein: the first metal microstrip line feed network, the second metal microstrip line feed network and the third metal microstrip line feed network are all zigzag multi-section microstrip feed line structures with chamfers.
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| CN202311446091.7A CN117394019A (en) | 2023-11-02 | 2023-11-02 | Co-location six-polarization antenna based on dual-mode three-ring structure |
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