CN115173952B - Optimized receiving method of optical universal filtering multi-carrier optical access network - Google Patents
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Abstract
The invention discloses an optimized receiving method, a device, equipment and a computer storage medium of an optical universal filtering multi-carrier optical access network, which comprises the steps of carrying out odd-even subcarrier extraction on a frequency domain signal to obtain an odd subcarrier signal and an even subcarrier signal, respectively carrying out inverse fast Fourier transform on the odd subcarrier signal and the even subcarrier signal to obtain an odd time domain signal and an even time domain signal, combining the odd time domain signal and the even time domain signal to obtain a combined time domain signal, carrying out fast Fourier transform on the combined time domain signal and the even subcarrier signal after being combined linearly, carrying out matched filtering processing to obtain a frequency domain signal after being eliminated, carrying out channel estimation on the frequency domain signal after being eliminated, carrying out QAM demodulation to obtain an original signal, fully utilizing information of overflow of a data carrier to other carriers by a time domain diversity technology, improving the performance of a receiver, and further improving frequency domain average in a symbol by a traditional least square method.
Description
Technical Field
The present invention relates to the field of signal processing technologies, and in particular, to an optimized receiving method, apparatus, device, and computer storage medium for an optical universal filtering multi-carrier optical access network.
Background
With the rapid development of internet technology, a great number of new applications, such as internet of things, high-definition video, augmented reality/virtual reality, etc., bring great pressure to communication networks. The high-capacity requirement of the communication network is also sinking from a backbone network transmitted by thousands of kilometers to an access network within a range of tens of kilometers, and the communication range comprises passive optical networks such as optical fiber to the home and the like, and also comprises an edge computing center network and a 5G wireless forwarding network which are increasingly widely applied. Thus, high-speed optical access networks have become critical to support the rapid development of various internet applications.
The traditional optical access network mainly adopts a single-carrier optical switch modulation signal, so that the challenges brought by capacity upgrading are very large, on one hand, the bandwidth bottleneck effect of a high-speed electronic device is overcome, and the bandwidth of the device is increased as much as possible; on the other hand, the dispersion damage of the high-speed signal in the optical fiber transmission is overcome, and a digital signal processing algorithm related to dispersion equalization is added. Therefore, the hardware cost required for system capacity upgrades is very high. The high-speed multi-carrier system not only can utilize quadrature amplitude modulation with high frequency spectrum efficiency, but also has very strong anti-dispersion performance of low-speed sub-carriers, and becomes one of the main technologies of the next-generation optical access network.
Orthogonal Frequency Division Multiplexing (OFDM) is the most widely studied multi-carrier optical access network technology, however OFDM has major problems of high out-of-band power leakage and strict orthogonality requirements between carriers. And universal filtered multi-Carrier (Universal Filtered Multi-Carrier, UFMC) is critical to solving the above problems. The UFMC adopts subcarrier grouping to divide all carriers into different subcarrier bands, and then performs subband filtering, so that not only can the filter length be reduced, but also out-of-band power leakage and interference between subcarriers can be reduced. In addition, since UFMC utilizes subband-based filtering, it is no longer necessary to add Cyclic Prefix (CP), so that spectrum resources can be fully utilized. UFMC is therefore an efficient way to implement a new generation of multicarrier access networks.
In addition, the modulation mode with high frequency spectrum efficiency is an effective way to realize a large-capacity transmission system, because with the increase of signal modulation orders, the amount of information carried by a single symbol also increases. Multiple phase shift keying (M-PSK) and multiple quadrature amplitude modulation (M-QAM) are spectrally efficient modulation techniques. Since the M-PSK signal envelope is constant, signal demodulation becomes increasingly difficult as M increases and the phase separation between symbols decreases. In contrast, M-QAM signals have multiple amplitudes, and at each amplitude, the phase interval between symbols is larger, so that the error rate performance of the M-QAM signal is better than that of M-PSK modulation under the same system parameters and average power.
However, in a communication system, as the modulation order of a Signal increases, an Optical Signal-to-Noise Ratio (OSNR) required for a receiver to demodulate the Signal also increases. While the OSNR of the signal is subject to system hardware performance and is difficult to boost. In addition, the high-order modulated signal has a high amplitude level, and is easier to enter into the nonlinear region of the optoelectronic device, so that serious nonlinear damage is induced. A common approach is to use a higher order volterra equalizer (Volterra equalizer, VE) to mitigate nonlinear impairments of the signal, however the complexity of this approach is very high. The universal filtering multi-Carrier (UFMC) optical fiber transmission system is an effective way to implement a high-speed passive optical network, and can provide a high-speed transmission channel for constructing a high-speed edge computing center network. High-order quadrature amplitude modulation (Quadrature Amplitude Modulation, QAM) improves the spectral efficiency of the modulated signal by using a high-level signal, increasing the rate of system transmission, whereas high-order QAM signals are susceptible to system noise, resulting in failure of the receiving end to recover the original signal.
In summary, the existing multi-carrier receiving method has the problem that the high-order QAM signal is easily affected by the system noise and cannot recover the original signal.
Disclosure of Invention
The invention aims to provide an optimized receiving method, device and equipment of an optical universal filtering multi-carrier optical access network and a computer storage medium, so as to solve the problems that a high-order QAM signal is easily influenced by system noise and cannot be recovered in the prior art.
In order to solve the technical problems, the invention provides an optimized receiving method of an optical general filtering multi-carrier optical access network, which comprises the following steps:
receiving a subcarrier signal modulated by QAM;
zero padding is carried out on the subcarrier signals, and fast Fourier transformation is carried out on the subcarrier signals subjected to the zero padding so as to obtain first frequency domain signals;
odd-even subcarrier extraction is carried out on the frequency domain signals to obtain odd-numbered subcarrier signals and even-numbered subcarrier signals;
respectively carrying out inverse fast Fourier transform on the odd subcarrier signals and the even subcarrier signals to obtain odd time domain signals and even time domain signals;
combining the odd time domain signal and the even time domain signal by using nonlinear operation to obtain a combined time domain signal;
performing fast Fourier transform after linearly combining the combined time domain signal and the even subcarrier signal to obtain a second frequency domain signal;
matching and filtering the second frequency domain signal to obtain a frequency domain signal after elimination and filtering;
and carrying out channel estimation on the frequency domain signals after the elimination and filtering, and demodulating the frequency domain signals through QAM to obtain original signals transmitted by a transmitter.
Preferably, the channel estimation of the frequency domain signal after the cancellation filtering includes:
performing signal estimation on the frequency domain signal after the elimination and filtration by utilizing a pilot frequency symbol based on a least square method to obtain a channel estimation value;
and carrying out frequency domain averaging on the channel estimation value and the adjacent channel to obtain a channel frequency response, wherein the calculation formula is as follows:
wherein ,HISFA (m') is the channel frequency response of the mth sub-carrier after applying the ISFA algorithm, m max′ and mmin ' over subcarrier interval [ m ] averaged for all participating intra-symbol frequency domain averaging algorithms min ，m max ]The smallest and largest subcarrier sequence numbers, l is the moving average window size, H LS For the signal frequency response using the LS algorithm.
Preferably, after the channel estimation value is frequency-domain averaged with the adjacent channel, the channel frequency response of the mth sub-carrier is obtained by accumulating and then averaging the channel frequency responses of the sub-carrier m' and the left and right adjacent co-2l+1 sub-carriers.
Preferably, the performing zero padding processing on the subcarrier signal, and performing fast fourier transform on the subcarrier signal after the zero padding processing, to obtain a first frequency domain signal includes:
supplementing N-L+1 zeros to the subcarrier signal to obtain a subcarrier signal with a length of 2N
For the sub-carrier signal with the length of 2NPerforming fast Fourier transform to obtain a first frequency domain signal +.>The fast Fourier transform calculation formula is as follows:
wherein the FFT is a fast Fourier transform,for a length of 2N subcarrier signal, B is the number of subbands of the generic-filter multicarrier system, k is the number of subcarriers, j is the imaginary part of the fourier transform, H (k) is the 2N-point FFT of the channel impulse response of the additive white gaussian noise channel>For each sub-band S i 2N-point FFT, F of time domain signal subjected to N-point IFFT transform i (k) For the 2N-point FFT of the impulse response function of the filter for each subband, N (k) is the 2N-point FFT of the noise of the additive white gaussian noise channel.
Preferably, the odd subcarrier signal and the even subcarrier signal are respectively subjected to inverse fast fourier transform to obtain an odd time domain signal and an even time domain signal, and the inverse fast fourier transform calculation formula is as follows:
y e ＝ifft(Y e )
y o ＝ifft(Y o )
wherein ,ye is an even time domain signal, y o Is an odd time domain signal, Y e Is an odd subcarrier signal, Y o Is an even subcarrier signal.
Preferably, the combining the odd time domain signal and the even time domain signal by using a nonlinear operation to obtain a combined time domain signal, and the nonlinear operation calculation formula is:
y r ＝y e *|y o |
wherein ,yr Is a combined signal.
Preferably, the performing fast fourier transform after linearly combining the combined time domain signal and the even subcarrier signal to obtain a second frequency domain signal includes:
linearly combining the combined time domain signal with the even subcarrier signal, wherein the linear combination calculation formula is as follows:
wherein ,for the combined signal, α is a weight parameter;
performing fast Fourier transform on the combined signal to obtain a second frequency domain signal, wherein the fast Fourier transform calculation formula is as follows:
wherein ,Y* Is the second frequency domain signal.
The invention also provides an optimized receiving device of the optical universal filtering multi-carrier optical access network, which comprises the following components:
the signal receiving module is used for receiving the subcarrier signals sent by the sending end;
the time domain processing module is used for carrying out zero padding on the subcarrier signals and carrying out fast Fourier transform on the subcarrier signals subjected to the zero padding processing to obtain first frequency domain signals;
the odd-even signal extraction and division module is used for extracting odd-even subcarriers from the frequency domain signal to obtain odd-even subcarrier signals;
the fast Fourier transform module is used for respectively carrying out inverse fast Fourier transform on the odd subcarrier signals and the even subcarrier signals to obtain odd time domain signals and even time domain signals;
the nonlinear operation module is used for combining the odd time domain signals and the even time domain signals by utilizing nonlinear operation to obtain combined time domain signals;
the linear combination module is used for carrying out fast Fourier transform after the combined time domain signal and the even subcarrier signal are combined linearly to obtain a second frequency domain signal;
the frequency domain processing module is used for carrying out matched filtering on the second frequency domain signal to obtain a frequency domain signal after elimination of filtering;
and the channel estimation demodulation module is used for carrying out channel estimation on the frequency domain signals after the elimination and filtering, and then demodulating the frequency domain signals through QAM to obtain original signals transmitted by the transmitter.
The invention also provides an optimized receiving device of the optical universal filtering multi-carrier optical access network, which utilizes the optimized receiving method of the optical universal filtering multi-carrier optical access network to optimize the received subcarrier signals modulated by QAM to obtain the original signals.
The invention also provides a computer readable storage medium, wherein the computer readable storage medium stores a computer program, and the computer program realizes the optimized receiving method of the optical universal filtering multi-carrier optical access network when being executed by a processor.
The invention provides an optimized receiving method of an optical universal filtering multi-carrier optical access network, wherein odd sub-carrier signals consist of overflow of transmission signals and interference of other sub-carriers, and the original signals are recovered by fully utilizing the omitted odd sub-carrier signals in the traditional UFMC system in the receiver through a time domain diversity technology besides even-number carrier signals, thereby improving the sensitivity of the receiver, improving the signal recovery precision and realizing that the original signals can be recovered by high-order QAM signals under the conditions of system noise and interference.
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For a clearer description of embodiments of the invention or of the prior art, the drawings that are used in the description of the embodiments or of the prior art will be briefly described, it being apparent that the drawings in the description below are only some embodiments of the invention, and that other drawings can be obtained from them without inventive effort for a person skilled in the art.
Fig. 1 is a flowchart of a first specific embodiment of an optimized receiving method of an optical generic-filtering multi-carrier optical access network according to the present invention;
fig. 2 is a block diagram of a generic filtered multi-carrier reception system;
fig. 3 is a diagram of a conventional UFMC transmission system;
fig. 4 is a block pilot channel estimation framework diagram;
FIG. 5 is a diagram of an experimental device of an IM/DD optical UFMC transmission system;
fig. 6 is a graph of error rate for various 64-QAM UFMC receivers;
fig. 7 is a 64-QAM signal constellation recovered by different receivers at rop= -14 dBm;
fig. 8 is a graph of error rate for various 256-QAM UFMC receivers;
fig. 9 is a 256-QAM signal constellation recovered by different receivers at rop= -3 dBm;
fig. 10 is a graph of error rate for various 1024-QAM UFMC receivers;
fig. 11 is a 1024-QAM signal constellation recovered by different receivers at rop= -3 dBm;
FIG. 12 is a plot of BER as a function of ISFA window size;
fig. 13 is a block diagram of an optimized receiving device of an optical generic filtering multi-carrier optical access network according to an embodiment of the present invention.
Detailed Description
The core of the invention is to provide an optimized receiving method of an optical universal filtering multi-carrier optical access network, which fully utilizes the information of the data carrier overflowing to other carriers by utilizing the time domain diversity technology, improves the performance of a receiver, and increases the average frequency domain in a symbol in the traditional least square method channel estimation method, thereby further improving the performance of the receiver.
In order to better understand the aspects of the present invention, the present invention will be described in further detail with reference to the accompanying drawings and detailed description. It will be apparent that the described embodiments are only some, but not all, embodiments of the invention. All other embodiments, which can be made by those skilled in the art based on the embodiments of the invention without making any inventive effort, are intended to be within the scope of the invention.
Referring to fig. 1 and fig. 2, fig. 1 is a flowchart of a first embodiment of an optimized receiving method of an optical generic-filtering multi-carrier optical access network according to the present invention; fig. 2 is a block diagram of the general filtering multi-carrier receiving system, and the specific operation steps are as follows:
step S101: receiving a subcarrier signal modulated by QAM;
as shown in fig. 3, the transmission signal of the transmitting end of the UFMC (universal filter multi-carrier) transmission system is as follows:
at the transmitting end, the UFMC signal is composed of B sub-bands, the ith sub-band contains N i (i=1, 2, … B) consecutive subcarriers, the number of subcarriers per subband in the present invention is the same. In the UFMC system, after QAM mapping, the frequency domain signal of each subband is denoted as S i After performing N-point IFFT on the ith sub-band, obtaining a time domain signal s i
Each sub-band is subjected to band-pass filtering by using a Chebyshev filter, and the corresponding filter impulse response function of each sub-band is f i Each filter length is L. And finally, each sub-band overlaps the signals after passing through the respective filters, and the length of the transmitted signals is N+L-1. The baseband UFMC transmit signal within one symbol time interval is represented as:
wherein f is convolution operation i The impulse response function of the filter corresponding to each sub-band, B is the sub-carrier grouping number;
assuming that the UFMC transmit signal passes through an additive gaussian white noise channel with a channel impulse response h and noise η, the channel output signal may be written as:
where h is the channel impulse response of the additive white gaussian noise channel, x is the baseband UFMC transmit signal in one symbol time interval, η is the noise of the additive white gaussian noise channel, s i For each sub-band S i Time domain signal subjected to N-point IFFT transformation, f i An impulse response function of the filter for each subband.
Step S102: zero padding is carried out on the subcarrier signals, and fast Fourier transformation is carried out on the subcarrier signals subjected to the zero padding so as to obtain first frequency domain signals;
supplementing N-L+1 zeros to the subcarrier signal to obtain a subcarrier signal with a length of 2N
For the sub-carrier signal with the length of 2NPerforming fast Fourier transform to obtain a first frequency domain signal +.>The fast Fourier transform calculation formula is as follows:
wherein the FFT is a fast Fourier transform,for a length of 2N subcarrier signal, B is the number of subbands of the generic-filter multicarrier system, k is the number of subcarriers, j is the imaginary part of the fourier transform, H (k) is the 2N-point FFT of the channel impulse response of the additive white gaussian noise channel>For each sub-band S i 2N-point FFT, F of time domain signal subjected to N-point IFFT transform i (k) For the 2N-point FFT of the impulse response function of the filter for each subband, N (k) is the 2N-point FFT of the noise of the additive white gaussian noise channel.
Step S103: and carrying out odd-even subcarrier extraction on the frequency domain signal to obtain an odd-numbered subcarrier signal and an even-numbered subcarrier signal.
Step S104: respectively carrying out inverse fast Fourier transform on the odd subcarrier signals and the even subcarrier signals to obtain odd time domain signals and even time domain signals;
y e ＝ifft(Y e )
y o ＝ifft(Y o )
wherein ,ye Is an even time domain signal, y o Is an odd time domain signal, Y e Is an odd subcarrier signal, Y o Is an even subcarrier signal.
Step S105: combining the odd time domain signal and the even time domain signal by using nonlinear operation to obtain a combined time domain signal;
y r ＝y e *|y o |
wherein ,yr Is a combined signal.
Step S106: performing fast Fourier transform after linearly combining the combined time domain signal and the even subcarrier signal to obtain a second frequency domain signal;
linearly combining the combined time domain signal with the even subcarrier signal, wherein the linear combination calculation formula is as follows:
wherein ,for the combined signal, α is a weight parameter;
performing fast Fourier transform on the combined signal to obtain a second frequency domain signal, wherein the fast Fourier transform calculation formula is as follows:
wherein ,Y* Is the second frequency domain signal.
Step S107: and carrying out matched filtering on the second frequency domain signal to obtain a frequency domain signal after elimination and filtering.
Step S108: channel estimation is carried out on the frequency domain signals after the elimination and filtering, and then the original signals transmitted by the transmitter are obtained through QAM demodulation;
performing signal estimation on the frequency domain signal after the elimination and filtration by utilizing a pilot frequency symbol based on a least square method to obtain a channel estimation value;
and carrying out frequency domain averaging on the channel estimation value and the adjacent channel to obtain a channel frequency response, wherein the calculation formula is as follows:
wherein ,HISFA (m') is the channel frequency response of the mth sub-carrier after applying the ISFA algorithm, m max′ and mmin ' over subcarrier interval [ m ] averaged for all participating intra-symbol frequency domain averaging algorithms min ，m max ]The smallest and largest subcarrier sequence numbers, l is the moving average window size, H LS Signal frequency response for the LS algorithm; after the channel estimation value and the adjacent channel are subjected to frequency domain averaging, the channel frequency response of the m 'th sub-carrier is obtained by accumulating and averaging the channel frequency responses of the sub-carrier m' and the left and right adjacent co-2l+1 sub-carriers.
Through experimental tests, the optimal weight parameter alpha in the 64-QAM, 256-QAM and 1024-QAM UFMC systems is 0.8.
According to the optimized receiving method of the optical universal filtering multi-carrier optical access network, through a time domain diversity technology, even number carrier signals are utilized in a receiver, odd number subcarrier signals ignored in a traditional UFMC system are fully utilized to recover original signals, the sensitivity of the receiver is improved, the signal recovery precision is improved, the information of data carriers overflowing to other carriers is fully utilized through the time domain diversity technology, the performance of the receiver is improved, and frequency domain average in symbols is further increased in a traditional least square method channel estimation method, so that the performance of the receiver is further improved, and the effect that the original signals can be recovered under the conditions of system noise and interference of high-order QAM signals is achieved.
Based on the above embodiment, the present embodiment focuses on adding a frequency domain average emphasis description in a symbol in a least square method channel estimation method, which specifically includes the following steps:
the accuracy of channel estimation directly affects the transmission performance of UFMC multi-carrier systems, and Least Square (LS) and least mean square error (Minimum Mean Square Error, MMSE) are two classical methods of channel estimation. The LS algorithm has simple and convenient calculation and low complexity, and does not need any priori statistical characteristics of the channel, so that the traditional UFMC receiver generally adopts the LS-based channel estimation algorithm. The LS algorithm utilizes the known pilot frequency symbols to carry out periodical linear interpolation and then estimates the frequency response of the transmission channel;
knowing x is the transmit signal of the UFMC system and y is the receive signalIs a symbol of (c). X is x p and yp Then it is the transmitted and received pilot data. Channel estimation value of kth subcarrierCan be expressed as: />As can be seen from the formula, the least square method does not consider the effect of random noise in the system, and when the noise increases, the performance of LS channel estimation is degraded.
The present embodiment uses an algorithm based on intra-symbol frequency domain averaging of LS channel estimation for channel estimation. The intra-symbol frequency domain average channel estimation method is mainly applied to a coherent light OFDM system, has the advantage of effectively suppressing noise interference under the condition of not increasing system overhead, and improves the accuracy of channel estimation. Since fibre channel changes slowly, random noise on each subcarrier in each UFMC symbol can be considered a fixed value.
As shown in fig. 4, channel estimation is performed using pilot symbols by using a least square method, and 7 block pilots are inserted into 64 symbols;
and secondly, carrying out frequency domain average on the obtained channel estimation value and an adjacent channel, and improving the accuracy of the channel estimation value by utilizing the correlation among subcarriers. The channel frequency response is shown in the following formula:
after the average of the frequency domain in the symbol, the channel frequency response of the mth sub-carrier is the sub-carrier m' and the left and right adjacent 2l+1 (l>An integer of 0) the channel frequency response on the sub-carrier is accumulated and averaged. m is m min And m is equal to max Is over all participating averaged subcarrier intervals [ m ] min ,m max ]And the smallest and largest subcarrier sequence numbers are set up. If on edge sub-carriers, define H ISFA (m′)＝H LS (m). Of the formulas, the most importantThe value size of the parameter is called the moving average window size, and the window size directly influences the accuracy of channel estimation.
In this embodiment, the FFT size is 512, and the optimal l values in the 64-QAM, 256-QAM, and 1024-QAM UFMC receivers are all 1, i.e., the window sizes are all 1. Research results show that the modulation format has small dependence on the moving average window size, which is mainly limited by the size of the FFT.
The optimized receiving method of the optical general filtering multi-carrier optical access network provided by the embodiment adopts an algorithm based on the intra-symbol frequency domain average of LS channel estimation to carry out channel estimation, carries out frequency domain average on the obtained channel estimation value and an adjacent channel, and utilizes the correlation among subcarriers to improve the accuracy of the channel estimation value and effectively inhibit noise interference.
Based on the above embodiment, the performance of the optimized receiving method of the optical generic filtering multi-carrier optical access network proposed in the present embodiment is verified by measuring different QAM modulations, specifically as follows:
as shown in fig. 5, at the UFMC transmitting end, a complex signal x (t) is generated in an off-line state, and then the real part and the imaginary part of the complex signal are placed in a crossed manner, so as to generate a serial time-domain real-valued signal. The real signal is then loaded into an arbitrary waveform generator (Arbitrary waveform generator, AWG) with a sampling rate of 50GSa/s, and the AWG performs digital-to-analog conversion. Next, the analog UFMC signal is input to a Mach-Zendell modulator modulator (MZM) modulator, which modulates the analog UFMC signal onto a Continuous Wave (CW) laser, producing an optical UFMC signal having a wavelength of 1550.112nm. The experiment adopts a 30-kM single mode fiber, and an optical UFMC signal output by a modulator is transmitted to a receiving end through a standard single mode fiber. Prior to the receiving end, a combination of variable optical attenuator (variable optical attenuator, VOA 1) and erbium-doped fiber amplifier (erbium-doped fiber amplifier, EDFA) is first used to control the system noise level for error rate testing. And the power input to the optical receiver is changed by adjusting the size of the variable attenuator (VOA 2) after that. The optical signal is then sent to a Photon Detector (PD), which converts the received optical signal to an electrical signal. And finally, performing analog-digital conversion by using a real-time oscilloscope with the sampling rate of 50GSa/s, collecting signals, and performing off-line digital signal processing. In the off-line digital signal processing process, firstly, the acquired digital signals are combined, and the real parts and the imaginary parts of the signals which are placed in a crossed mode are respectively taken out to be combined into complex signals. Then, the operations of serial-parallel conversion, zero padding, 2N point FFT, odd-even sub-carrier separation, time domain diversity combination, matched filtering, zero forcing equalization, frequency domain average channel estimation in the symbol and the like shown in figure 1 are carried out, and finally, the original signal is restored through QAM demapping.
To verify the performance of the proposed UFMC optimized receiver of the present invention, different QAM modulations were measured next, including back-to-back (BTB) and 30-km single mode fiber transmission, the performance of the conventional UFMC receiver with Time Domain Diversity Combining (TDDC) only receiver, intra-symbol frequency domain averaging (ISFA) only channel estimation and the optimized receiver of the present invention. In the following experiments, the error rate curves of the conventional UFMC receiver in BTB and 30-km single mode fiber transmission are marked with solid black square lines and dashed lines, respectively. Error rate curves of the TDDC receiver and the ISFA receiver are marked with a five-pointed star and a circle, respectively. The solid and dashed lines of the asterisks mark the bit error rate curves of the UFMC-optimized receiver of the present invention for BTB and 30-km single-mode fiber transmission.
As shown in fig. 6, to reach the HD-FEC threshold (bit error rate 3.8x10-3), the Received Optical Power (ROP) required by the conventional UFMC receiver is-20.9 dBm, the Received Optical Power (ROP) required by the tddc receiver is-21.5 dBm, the Received Optical Power (ROP) required by the isfa receiver is-21.8 dBm, and the Received Optical Power (ROP) required by the UFMC optimized receiver of the present invention is-22.2 dBm. It can be seen that the receiver sensitivity can be improved by 1.3dB by using the UFMC optimized receiver of the present invention. Fig. 7 is a diagram of a 64-QAM signal constellation recovered by four different receivers at a received optical power of-14 dBm, where the recovered constellations of the other several receivers are more converged than the conventional UFMC receiver, enabling more accurate symbol decisions.
As shown in fig. 8, the conventional receiver cannot reach the HD-FEC threshold (bit error rate 3.8x10-3), while the TDDC receiver needs a Received Optical Power (ROP) of-12 dBm and the isfa receiver needs a Received Optical Power (ROP) of-8 dBm, the UFMC optimized receiver of the present invention needs a Received Optical Power (ROP) of-14.5 dBm. Fig. 9 is a diagram of a recovered 256-QAM signal constellation for four different receivers at a received optical power of-3 dBm, where the recovered constellation is more focused than for a conventional UFMC receiver, and more accurate symbol decisions can be achieved than for several other receivers, particularly the TDDC and the optimized receiver of the present invention.
As shown in fig. 10, since the received signal is more severely affected by noise, it is necessary to recover the signal by means of a soft-decision forward error correction code, and the conventional UFMC receiver cannot reach the SD-FEC threshold (bit error rate 2.4×10-2), so that the original signal cannot be recovered correctly. The ISFA receiver is not able to recover the original signal well because it is only optimized based on LS channel estimation, and is still severely affected by noise. While the TDDC receiver can reach the SD-FEC threshold, the required Received Optical Power (ROP) is-5.9 dBm, and the UFMC optimized receiver has higher receiving sensitivity, and the required Received Optical Power (ROP) is only-9 dBm. Fig. 11 shows 1024-QAM signal constellations recovered by four different receivers at a received optical power of-3 dBm, where the recovered constellations are more converged than the conventional UFMC receiver, TDDC, and the optimized receiver of the present invention, and more accurate symbol decisions can be achieved.
In the intra-symbol frequency domain average signal estimation, although increasing the window size of intra-symbol frequency domain average can suppress noise interference, increasing the window size reduces the correlation of the channel response on the subcarriers, and thus the channel estimation error also increases, thereby reducing the accuracy of the channel estimation. The window size of the intra-symbol frequency domain average needs to be optimized.
As shown in fig. 12, the intra-symbol frequency domain average window size is mainly limited by the size of the FFT. Fig. 12 shows the BER curves for different window sizes, with the black line labeled 512 sub-carrier UFMC signals and the gray line labeled 2048 sub-carrier UFMC signals. The UFMC systems all use 1/4 sub-carrier as data sub-carrier, and the system adopts 256-QAM modulation. As can be seen from fig. 12, when the FFT is 512, the optimum window value is 1, and when the FFT is increased to 2048, the optimum window value is increased to 4. Thus, depending on the application requirements, the system may choose different FFT sizes, requiring optimization of the size of the frequency domain averaging window within the symbol.
As the FFT size becomes larger, the optimum window value is not the same for different received optical powers for the same FFT size. Table 1 lists the best window values for different ROPs (dBm), with the best window size corresponding to the lowest BER. The experiment takes 2048 subcarriers as an example, wherein 1/4 is a data subcarrier, and 256-QAM modulation is adopted.
TABLE 1 comparison of different optimum window sizes at different ROP values
It can be seen from the table that the optimal window values are not the same for different received optical powers, and that optimal receiver performance cannot be obtained if a single initialization is used to determine the optimal window values. However, in the case of the commonly used 512 subcarriers, the best window values of different received optical powers have little influence, so in the present invention, 1 is uniformly selected as the best window value.
The optimal receiving method of the optical universal filtering multi-carrier optical access network provided by the embodiment can improve the sensitivity of the traditional UFMC receiver by 1.3dB in a 64-QAM system by utilizing the UFMC optimal receiver of the embodiment, and can also correctly recover 256-QAM signals and 1024-QAM signals which cannot be correctly recovered by the traditional UFMC receiver on the basis of HD-FEC and SD-FEC respectively. The invention has extremely high application value in the aspect of the large-capacity UFMC optical access network, and has guiding significance for high-order QAM optimized reception in 5G, 6G and WiFi-6 systems in the future.
Referring to fig. 13, fig. 13 is a block diagram of an optimized receiving device of an optical generic filtering multi-carrier optical access network according to an embodiment of the present invention; the specific apparatus may include:
a signal receiving module 100, configured to receive a subcarrier signal sent by a sending end;
the time domain processing module 200 is configured to perform zero padding processing on the subcarrier signal, and perform fast fourier transform on the subcarrier signal after the zero padding processing to obtain a first frequency domain signal;
the odd-even signal extraction module 300 is configured to extract odd-even subcarriers from the frequency domain signal to obtain odd-even subcarriers;
a fast fourier transform module 400, configured to perform inverse fast fourier transform on the odd subcarrier signal and the even subcarrier signal, respectively, to obtain an odd time domain signal and an even time domain signal;
a nonlinear operation module 500, configured to combine the odd time domain signal and the even time domain signal by using nonlinear operation to obtain a combined time domain signal;
a linear combination module 600, configured to perform fast fourier transform after linearly combining the combined time domain signal and the even subcarrier signal, to obtain a second frequency domain signal;
the frequency domain processing module 700 is configured to match filter the second frequency domain signal to obtain a frequency domain signal after the cancellation of the filtering;
the channel estimation demodulation module 800 is configured to perform channel estimation on the frequency domain signal after the cancellation and filtering, and then perform QAM demodulation to obtain an original signal transmitted by the transmitter.
An optical generic-filtering multi-carrier optical access network optimization receiving device of this embodiment is used to implement the foregoing optical generic-filtering multi-carrier optical access network optimization receiving method, so that the foregoing embodiments of an optical generic-filtering multi-carrier optical access network optimization receiving device can be seen from the foregoing example portions of an optical generic-filtering multi-carrier optical access network optimization receiving method, for example, the signal receiving module 100, the time domain processing module 200, the parity signal decimating module 300, the fast fourier transform module 400, the nonlinear operation module 500, the linear combination module 600, the frequency domain processing module 700, and the channel estimation demodulation module 800, which are respectively used to implement steps S101, S102, S103, S104, S105, S106, S107 and S108 in the foregoing optical generic-filtering multi-carrier optical access network optimization receiving method, so that the detailed description thereof can refer to the corresponding respective portion embodiments and will not be repeated herein.
The specific embodiment of the invention also provides an optimized receiving device of the optical universal filtering multi-carrier optical access network, which comprises the following components: a memory for storing a computer program; and the processor is used for realizing the steps of the optimized receiving method of the optical universal filtering multi-carrier optical access network when executing the computer program.
The specific embodiment of the invention also provides a computer readable storage medium, wherein the computer readable storage medium is stored with a computer program, and the computer program realizes the steps of the optimized receiving method of the optical general filtering multi-carrier optical access network when being executed by a processor.
In this specification, each embodiment is described in a progressive manner, and each embodiment is mainly described in a different point from other embodiments, so that the same or similar parts between the embodiments are referred to each other. For the device disclosed in the embodiment, since it corresponds to the method disclosed in the embodiment, the description is relatively simple, and the relevant points refer to the description of the method section.
Those of skill would further appreciate that the various illustrative elements and algorithm steps described in connection with the embodiments disclosed herein may be implemented as electronic hardware, computer software, or combinations of both, and that the various illustrative elements and steps are described above generally in terms of functionality in order to clearly illustrate the interchangeability of hardware and software. Whether such functionality is implemented as hardware or software depends upon the particular application and design constraints imposed on the solution. Skilled artisans may implement the described functionality in varying ways for each particular application, but such implementation decisions should not be interpreted as causing a departure from the scope of the present invention.
The method, the device, the equipment and the computer storage medium for optimizing the receiving of the optical universal filtering multi-carrier optical access network provided by the invention are described in detail. The principles and embodiments of the present invention have been described herein with reference to specific examples, the description of which is intended only to facilitate an understanding of the method of the present invention and its core ideas. It should be noted that it will be apparent to those skilled in the art that various modifications and adaptations of the invention can be made without departing from the principles of the invention and these modifications and adaptations are intended to be within the scope of the invention as defined in the following claims.
Claims (6)
1. An optimized receiving method of an optical general filtering multi-carrier optical access network is characterized by comprising the following steps:
receiving a subcarrier signal modulated by QAM;
zero padding is carried out on the subcarrier signals, and fast Fourier transformation is carried out on the subcarrier signals subjected to the zero padding so as to obtain first frequency domain signals;
the zero padding processing is performed on the subcarrier signal, and the fast fourier transform is performed on the subcarrier signal after the zero padding processing, so as to obtain a first frequency domain signal, which includes:
supplementing N-L+1 zeros to the subcarrier signal to obtain a subcarrier signal with a length of 2N
For the sub-carrier signal with the length of 2NPerforming fast Fourier transform to obtain a first frequency domain signal +.>The fast Fourier transform calculation formula is as follows:
wherein the FFT is a fast Fourier transform,for a length of 2N subcarrier signal, B is the number of subbands of the generic-filter multicarrier system, k is the number of subcarriers, j is the imaginary part of the fourier transform, H (k) is the 2N-point FFT of the channel impulse response of the additive white gaussian noise channel>For each sub-band S i 2N-point FFT, F of time domain signal subjected to N-point IFFT transform i (k) 2N point FFT of impulse response function of filter corresponding to each sub-band, N (k) is 2N point FFT of noise of additive Gaussian white noise channel;
odd-even subcarrier extraction is carried out on the frequency domain signals to obtain odd-numbered subcarrier signals and even-numbered subcarrier signals;
respectively carrying out inverse fast Fourier transform on the odd subcarrier signals and the even subcarrier signals to obtain odd time domain signals and even time domain signals;
combining the odd time domain signal and the even time domain signal by using nonlinear operation to obtain a combined time domain signal;
combining the odd time domain signal and the even time domain signal by using nonlinear operation to obtain a combined time domain signal, wherein the nonlinear operation calculation formula is as follows:
y r ＝y e *|y 0 |
wherein ,yr Is a combined signal;
performing fast Fourier transform after linearly combining the combined time domain signal and the even subcarrier signal to obtain a second frequency domain signal;
the performing fast fourier transform after linearly combining the combined time domain signal and the even subcarrier signal to obtain a second frequency domain signal includes:
linearly combining the combined time domain signal with the even subcarrier signal, wherein the linear combination calculation formula is as follows:
wherein ,for the combined signal, α is a weight parameter;
performing fast Fourier transform on the combined signal to obtain a second frequency domain signal, wherein the fast Fourier transform calculation formula is as follows:
wherein ,Y* Is a second frequency domain signal;
matching and filtering the second frequency domain signal to obtain a frequency domain signal after elimination and filtering;
channel estimation is carried out on the frequency domain signals after the elimination and filtering, and then the original signals transmitted by the transmitter are obtained through QAM demodulation;
the channel estimation of the frequency domain signal after the cancellation and filtering includes:
performing signal estimation on the frequency domain signal after the elimination and filtration by utilizing a pilot frequency symbol based on a least square method to obtain a channel estimation value;
and carrying out frequency domain averaging on the channel estimation value and the adjacent channel to obtain a channel frequency response, wherein the calculation formula is as follows:
wherein ,HISFA (m') is the channel frequency response of the mth sub-carrier after applying the ISFA algorithm, m max' and mmin' Over subcarrier intervals averaged for all participating intra-symbol frequency domain averaging algorithms [ m ] min ,m max ]The smallest and largest subcarrier sequence numbers, l is the moving average window size, H LS For the signal frequency response using the LS algorithm.
2. The optimized receiving method of optical general filtering multi-carrier optical access network as claimed in claim 1, wherein after said channel estimation value is frequency-domain averaged with the adjacent channel, the channel frequency response of the mth sub-carrier is obtained by accumulating and averaging the channel frequency responses of sub-carrier m' and the left and right adjacent co-2l+1 sub-carriers.
3. The optimized receiving method of optical general filtering multi-carrier optical access network as claimed in claim 1, wherein said odd subcarrier signal and said even subcarrier signal are respectively subjected to inverse fast fourier transform to obtain an odd time domain signal and an even time domain signal, and the inverse fast fourier transform calculation formula is:
y e ＝ifft(Y e )
y o ＝ifft(Y o )
wherein ,ye Is an even time domain signal, y o Is an odd time domain signal, Y e Is an odd subcarrier signal, Y o Is an even subcarrier signal.
4. An optimized receiving device of an optical general filtering multi-carrier optical access network, which is characterized by comprising:
the signal receiving module is used for receiving the subcarrier signals sent by the sending end;
the time domain processing module is used for carrying out zero padding on the subcarrier signals and carrying out fast Fourier transform on the subcarrier signals subjected to the zero padding processing to obtain first frequency domain signals;
the zero padding processing is performed on the subcarrier signal, and the fast fourier transform is performed on the subcarrier signal after the zero padding processing, so as to obtain a first frequency domain signal, which includes:
supplementing N-L+1 zeros to the subcarrier signal to obtain a subcarrier signal with a length of 2N
For the sub-carrier signal with the length of 2NNumber (number)Performing fast Fourier transform to obtain a first frequency domain signal +.>The fast Fourier transform calculation formula is as follows:
wherein the FFT is a fast Fourier transform,for a length of 2N subcarrier signal, B is the number of subbands of the generic-filter multicarrier system, k is the number of subcarriers, j is the imaginary part of the fourier transform, H (k) is the 2N-point FFT of the channel impulse response of the additive white gaussian noise channel>For each sub-band S i 2N-point FFT, F of time domain signal subjected to N-point IFFT transform i (k) 2N point FFT of impulse response function of filter corresponding to each sub-band, N (k) is 2N point FFT of noise of additive Gaussian white noise channel;
the odd-even signal extraction and division module is used for extracting odd-even subcarriers from the frequency domain signal to obtain odd-even subcarrier signals;
the fast Fourier transform module is used for respectively carrying out inverse fast Fourier transform on the odd subcarrier signals and the even subcarrier signals to obtain odd time domain signals and even time domain signals;
the nonlinear operation module is used for combining the odd time domain signals and the even time domain signals by utilizing nonlinear operation to obtain combined time domain signals;
combining the odd time domain signal and the even time domain signal by using nonlinear operation to obtain a combined time domain signal, wherein the nonlinear operation calculation formula is as follows:
y r ＝y e *|y o |
wherein ,yr Is a combined signal;
the linear combination module is used for carrying out fast Fourier transform after the combined time domain signal and the even subcarrier signal are combined linearly to obtain a second frequency domain signal;
the performing fast fourier transform after linearly combining the combined time domain signal and the even subcarrier signal to obtain a second frequency domain signal includes:
linearly combining the combined time domain signal with the even subcarrier signal, wherein the linear combination calculation formula is as follows:
wherein ,for the combined signal, α is a weight parameter;
performing fast Fourier transform on the combined signal to obtain a second frequency domain signal, wherein the fast Fourier transform calculation formula is as follows:
wherein ,Y* Is a second frequency domain signal;
the frequency domain processing module is used for carrying out matched filtering on the second frequency domain signal to obtain a frequency domain signal after elimination of filtering;
the channel estimation demodulation module is used for carrying out channel estimation on the frequency domain signals after the elimination and filtration, and then carrying out QAM demodulation to obtain original signals transmitted by the transmitter;
the channel estimation of the frequency domain signal after the cancellation and filtering includes:
performing signal estimation on the frequency domain signal after the elimination and filtration by utilizing a pilot frequency symbol based on a least square method to obtain a channel estimation value;
and carrying out frequency domain averaging on the channel estimation value and the adjacent channel to obtain a channel frequency response, wherein the calculation formula is as follows:
wherein ,HISFA (m') is the channel frequency response of the mth sub-carrier after applying the ISFA algorithm, m max' and mmin' Over subcarrier intervals averaged for all participating intra-symbol frequency domain averaging algorithms [ m ] min ,m max ]The smallest and largest subcarrier sequence numbers, l is the moving average window size, H LS For the signal frequency response using the LS algorithm.
5. An optimized receiving device of an optical general filtering multi-carrier optical access network, characterized in that the optimized receiving method of the optical general filtering multi-carrier optical access network according to any one of claims 1 to 3 is used for optimizing the received subcarrier signal after QAM modulation to obtain an original signal.
6. A computer readable storage medium, characterized in that the computer readable storage medium has stored thereon a computer program which, when executed by a processor, implements a method for optimized reception of an optical generic-filter multi-carrier optical access network according to any of claims 1 to 3.
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