CN113541833B - Signal-to-noise ratio estimation method, signal-to-noise ratio estimation device, communication equipment and storage medium - Google Patents
Signal-to-noise ratio estimation method, signal-to-noise ratio estimation device, communication equipment and storage medium Download PDFInfo
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Abstract
The embodiment of the application is applicable to the technical field of communication, and provides a signal-to-noise ratio estimation method, a signal-to-noise ratio estimation device, communication equipment and a storage medium, wherein the method comprises the following steps: acquiring power time delay distribution of a channel; evenly dividing the power time delay distribution into a plurality of distribution sections; circularly calculating the moving average values of the distribution sections to obtain a moving average value set, wherein the minimum value in the moving average value set is used for representing the noise power; determining a plurality of target location points for statistical signal power in the power delay profile; calculating a signal power based on the plurality of target location points, the signal power being equal to a sum of powers corresponding to the plurality of target location points minus a product of a number of reserved paths and the noise power; and calculating the signal-to-noise ratio of the channel based on the signal power and the noise power. By adopting the method, the accuracy of the signal-to-noise ratio estimation can be improved.
Description
Technical Field
The embodiment of the application belongs to the technical field of communication, and particularly relates to a signal-to-noise ratio estimation method, a signal-to-noise ratio estimation device, communication equipment and a storage medium.
Background
Signal to noise ratio (SNR or S/N) refers to the ratio of signal to noise in an electronic device, electronic system or channel, often expressed in decibel (dB) numbers. Generally, the larger the signal-to-noise ratio, the smaller the noise mixed in the signal, and the higher the quality of sound playback; otherwise, the opposite is true.
In a communication system applying Orthogonal Frequency Division Multiplexing (OFDM), signal-to-noise ratio estimation can be generally performed based on power-delay profile (PDP) of a channel.
However, the existing channel-based PDP methods for calculating the signal-to-noise ratio have large errors.
Disclosure of Invention
In view of this, embodiments of the present application provide a method, an apparatus, a communication device, and a storage medium for estimating a signal-to-noise ratio, so as to improve accuracy of signal-to-noise ratio estimation.
A first aspect of an embodiment of the present application provides a signal-to-noise ratio estimation method, including:
acquiring power time delay distribution of a channel;
evenly dividing the power time delay distribution into a plurality of distribution sections;
circularly calculating the sliding average values of the distribution sections to obtain a sliding average value set, wherein the minimum value in the sliding average value set is used for representing noise power;
determining a plurality of target location points for statistical signal power in the power delay profile;
calculating a signal power based on the plurality of target location points, the signal power being equal to a sum of powers corresponding to the plurality of target location points minus a product of a number of reserved paths and the noise power;
calculating a signal-to-noise ratio of the channel based on the signal power and the noise power.
A second aspect of an embodiment of the present application provides an snr estimation apparatus, including:
a power delay distribution obtaining module, configured to obtain power delay distribution of a channel;
the power time delay distribution dividing module is used for evenly dividing the power time delay distribution into a plurality of distribution sections;
the moving average calculation module is used for circularly calculating the moving average of the distribution sections to obtain a moving average set, and the minimum value in the moving average set is used for representing the noise power;
a target location point determining module, configured to determine a plurality of target location points for counting signal power in the power delay distribution;
a signal power calculation module for calculating a signal power based on the plurality of target location points, the signal power being equal to a value obtained by subtracting a product of a reserved path number and the noise power from a sum of powers corresponding to the plurality of target location points;
and the signal-to-noise ratio calculation module is used for calculating the signal-to-noise ratio of the channel based on the signal power and the noise power.
A third aspect of embodiments of the present application provides a communication device, including a memory, a processor, and a computer program stored in the memory and executable on the processor, wherein the processor, when executing the computer program, implements the signal-to-noise ratio estimation method according to the first aspect.
A fourth aspect of embodiments of the present application provides a computer-readable storage medium, which stores a computer program, which when executed by a processor implements the signal-to-noise ratio estimation method according to the first aspect.
A fifth aspect of embodiments of the present application provides a computer program product, which when run on a communication device, causes the communication device to perform the signal-to-noise ratio estimation method according to the first aspect.
Compared with the prior art, the embodiment of the application has the following advantages:
in the embodiments of the present application, noise and signal power are estimated using power delay profiles. In the actual processing process, the calculation amount in the processing process is reduced by using a mode of sectional averaging and then performing circulating averaging. Secondly, the maximum value and two adjacent values in the obtained power delay distribution are reserved during noise suppression, and the main path of the channel is guaranteed not to be lost. Thirdly, in the processing process, by distinguishing the noise, the cyclic prefix and the time offset range, compared with the prior art that the noise suppression effect is only carried out according to the threshold value, the method and the device have better noise suppression effect. Fourth, when calculating the signal power, the embodiment of the present application does not simply add the multiple paths, but subtracts the noise on each path, and the theoretical calculation result is more accurate. Thus, the final calculated signal-to-noise ratio is more accurate.
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In order to more clearly illustrate the technical solutions in the embodiments of the present application, the drawings used in the embodiments or the description of the prior art will be briefly described below. It is obvious that the drawings in the following description are only some embodiments of the application, and that for a person skilled in the art, other drawings can be derived from them without inventive effort.
Fig. 1 is a schematic flowchart illustrating steps of a signal-to-noise ratio estimation method according to an embodiment of the present application;
fig. 2 is a schematic diagram of an implementation manner of step S101 of a signal-to-noise ratio estimation method provided in an embodiment of the present application;
fig. 3 is a schematic diagram of an implementation manner of step S103 of a signal-to-noise ratio estimation method provided in an embodiment of the present application;
FIG. 4 is a schematic diagram of a segment averaging provided by an embodiment of the present application;
FIG. 5 is a schematic diagram of a sliding average provided by an embodiment of the present application;
fig. 6 is a schematic diagram of an implementation manner of step S104 of a signal-to-noise ratio estimation method provided in an embodiment of the present application;
fig. 7 is a schematic diagram of an snr estimation apparatus according to an embodiment of the present application;
fig. 8 is a schematic diagram of a communication device according to an embodiment of the present application.
Detailed Description
In the following description, for purposes of explanation and not limitation, specific details are set forth such as particular system structures, techniques, etc. in order to provide a thorough understanding of the embodiments of the present application. However, it will be apparent to one skilled in the art that the present application may be practiced in other embodiments that depart from these specific details. In other instances, detailed descriptions of well-known systems, devices, circuits, and methods are omitted so as not to obscure the description of the present application with unnecessary detail.
When performing signal-to-noise ratio estimation based on the channel PDP, the Channel Impulse Response (CIR) of the OFDM ideal can be expressed as the following formula (1):
wherein L is the number of paths of a plurality of paths passed by the signal propagation process, a L For the amplitude of each path, n l Is the time of arrival of the signal through each path.
Since there is noise in the system and the length of the CIR does not exceed the length of the Cyclic Prefix (CP) in most cases, the CIR can also be expressed by the following formula (2):
where w (n) is noise, the intra-CP representation signal is located within the cyclic prefix, and correspondingly, the extra-CP representation signal is located outside the cyclic prefix.
Accordingly, the PDP of the above channel can be represented using the following formula (3):
since the signal energy is generally larger than the noise, the signal-to-noise ratio of the channel can be calculated by considering the portion of the PDP profile outside the CP as noise and the portion inside the CP as channel energy. However, the signal-to-noise ratio calculated in this way is often in a large error.
In view of the above problems, embodiments of the present application provide a method, an apparatus, a communication device, and a storage medium for estimating an snr, where the method also performs snr estimation based on a PDP, but compared with the prior art, instead of directly considering a part located outside a CP as noise and a part inside the CP as channel energy, noise suppression is performed by distinguishing noise, a cyclic prefix, and a time offset range, and a maximum value and two adjacent values in the PDP are retained, thereby ensuring that a main path of a channel is not lost; the multipath is not simply added in the power calculation process, but noise on each path is subtracted, so that the calculation result is more accurate.
The technical solution of the present application will be described below by way of specific examples.
Referring to fig. 1, a schematic flow chart illustrating steps of a signal-to-noise ratio estimation method provided in the embodiment of the present application is shown, which specifically includes the following steps:
s101, acquiring power delay distribution of a channel.
It should be noted that the method can be applied to an OFDM system. Specifically, the execution subject of the method may be a communication device with a signal-to-noise ratio estimation function in the OFDM system, and the embodiment of the present application does not limit the specific type of the communication device.
In embodiments of the present application, the communication device may use the PDP to estimate the noise power and the signal power. A PDP, also known as a power delay profile, describes the dispersion of the channel in time, indicating the expectation of received signal power at a certain time delay.
In one possible implementation manner of the embodiment of the present application, as shown in fig. 2, the PDP for the communication device to acquire a channel may include the following sub-steps S1011 to S1013:
and S1011, performing channel estimation on the channel according to a Least Square (LS) criterion.
Channel estimation is a process of estimating model parameters of a certain assumed channel model from received data. In practical applications, the communication device may perform channel estimation by using a plurality of methods, such as non-blind channel estimation, and the like, which is not limited in this embodiment.
In the embodiment of the present application, the communication device may perform channel estimation by using an LS channel estimation method to obtain a corresponding result.
S1012, performing Inverse Fast Fourier Transform (IFFT) on the result of the channel estimation to obtain a transform result.
Fast Fourier Transform (FFT) is an efficient Discrete Fourier Transform (DFT) algorithm, and has wide application in the field of communications. The IFFT is the inverse operation of the FFT algorithm.
And S1013, sequentially carrying out modular and quadratic operation on the conversion result to obtain the power time delay distribution of the channel.
In the embodiment of the present application, according to the time-frequency domain conversion principle, the communication device may perform IFFT transformation on the result obtained by channel estimation, and then perform modulo and squaring operations on the transformation result in sequence, so as to obtain a PDP of a channel.
As an example, the above procedure of acquiring the PDP can be expressed by using equations (4), (5):
wherein H LS Shows the result obtained by LS channel estimation, IFFT (H) LS ) Is the result of the IFFT transformation.
If the length of the channel is K, the length of the PDP may be represented by the following formula (6):
in this embodiment of the present application, after obtaining the PDP, the communication device may record a maximum value PDP in the PDP max And its location point n max ：
pdp max ＝max(pdp(n))……(7)
n max ＝argmax(pdp(n))……(8)
By recording the maximum value and its location point in the PDP, the communication device can retain the maximum value when performing subsequent noise suppression processing, ensuring that it is not removed.
In one possible implementation manner of the embodiment of the present application, in addition to recording the maximum value and its location point in the PDP, the communication device may also record a location point adjacent to the maximum value, for example, a location point n before the maximum value max,L And the latter position point n max,R ：
n max,L ＝(n max -1)&(N PDP -1)……(9)
n max,R ＝(n max +1)&(N PDP -1)……(10)
Wherein N is PDP -1 indicates that the location point is located at N PDP Within the range of (a).
When the noise suppression processing is subsequently performed, the communication device may retain the position point of the maximum value in the PDP and its adjacent position points. In this way, it is ensured that the main path of the channel is not lost.
S102, evenly dividing the power time delay distribution into a plurality of distribution sections.
In the embodiment of the present application, in order to reduce the subsequent calculation amount, the communication device may equally divide the PDP into a plurality of distribution segments. Thus, the number of position points included in each distribution segment is equal.
In a specific implementation, the PDP has a length of N PDP It can be divided equally into G PDP Segments, the number of location points contained within each distribution segment can be represented as N G ＝N PDP /G PDP 。
Above G PDP The specific size of the piecewise constant can be determined according to actual needs. In general, G PDP Should satisfy the power n of 2. Exemplarily, when n =5, G PDP =32, i.e. representing the average division of the PDP into 32 segments.
S103, circularly calculating the sliding average values of the distribution sections to obtain a sliding average value set, wherein the minimum value in the sliding average value set is used for representing noise power.
In general, the PDP contains noise and multipath. Wherein the multipath is distributed over the length of the CP. The number of segments occupied by CP can be set to G CP G of the CP Should be taken to satisfy the range of positions that need to contain multipath. Thus, the number of segments occupied by noise can be correspondingly represented as G noise ＝G PDP -G CP 。
In addition, the PDP may be shifted due to the influence of the time offset, and the number of shift stages may be set to G TA The G is TA Should satisfy a range of positions that includes a time offset.
In the embodiment of the present application, in order to attempt to add all possible noise values, a sliding average calculation may be performed on a plurality of distribution segments that have been divided in an average manner, so as to obtain a sliding average value set including a plurality of sliding averages.
In a possible implementation manner of the embodiment of the present application, as shown in fig. 3, the communication device obtains a moving average value set by circularly calculating a moving average value of a plurality of distribution segments, and may include the following sub-steps S1031 to S1033:
and S1031, respectively calculating an arithmetic average value of each distribution section.
In the embodiment of the present application, in order to facilitate the calculation of the moving average, the arithmetic average of each distribution segment may be calculated first. Calculating the arithmetic mean of each distribution section, i.e. the segment averaging, for N in each distribution section G And calculating the average value of the position points. The PDP is divided into how many distribution segments, and the arithmetic mean calculated is how many. That is, the PDP is divided into G PDP Segment, then the arithmetic mean also has G PDP And (4) respectively.
Fig. 4 is a schematic diagram of segment averaging according to an embodiment of the present application. The average division of the PDP into G is shown in FIG. 4 PDP Segment averaging process when =32 segments (0,1,2, …, 31). The length of the PDP is N PDP Each segment containing N G The resulting arithmetic mean comprises 32 position points.
Specifically, the arithmetic mean of each distribution segment can be calculated using the following formula (11):
wherein S is 1 (g 1 ) Is G PDP Set of arithmetic mean values of segments, G PDP Is a section constant, i.e. the total number of the plurality of distributed sections obtained after the division, g 1 To correspond to the segment value, N G For the number of location points contained within each distribution segment.
S1032, determining a sliding starting section and a sliding ending section.
Determining the start and end of slip segments refers to determining from which segment the slip should start and to which segment the slip should end when determining the slip average.
In the embodiment of the present application, the slip start segment may be denoted as G S ＝mod(G TA ,G PDP ) The end of slide segment can be represented as G E ＝G CP +G TA -1. Where mod is the remainder operation, G TA Is the number of offset stages, G PDP Total number of segments for a plurality of distribution segments, G CP Is the number of segments occupied by the cyclic prefix.
And S1033, calculating a sliding average value in the range from the sliding starting section to the sliding ending section by taking the preset number of sections as the length based on the arithmetic average value of each distribution section to obtain the sliding average value set.
In the embodiment of the application, the preset segment number can be equal to the segment number G occupied by noise noise Equal, that is, equal to the total number of segments of the plurality of distributed segments minus the number of segments occupied by the cyclic prefix.
Fig. 5 is a schematic diagram of a sliding averaging according to an embodiment of the present disclosure. According to FIG. 5, the process of sliding averaging, i.e. from the start of the sliding segment G S Initially, each time length is calculated as G noise After each calculation is finished, the average value of the plurality of distribution sections is slid backwards by one section, and the length is calculated again to be G noise Until a section G from the end of sliding is calculated E Starting at length G noise Average of a plurality of distribution segments.
Specifically, the moving average S may be calculated using the following formula (12) 2 (g 2 )：
S above 2 (g 2 ) Is a set of moving averages.
And S104, determining a plurality of target position points for counting the signal power in the power time delay distribution.
The plurality of target location points for counting the signal power may be regarded as location points that are not removed when calculating the signal power, and the location points that need to be removed may be regarded as noise on the PDP. The plurality of target location points in the embodiment of the present application may include a location point belonging to a CP in the PDP and a location point of a maximum value in the PDP and its neighboring location points.
In a possible implementation manner of the embodiment of the present application, as shown in fig. 6, the determining, by the communication device, a plurality of target location points for counting signal power in the PDP may include the following sub-steps S1041 to S1042:
s1041, determining a position index set belonging to the cyclic prefix in the power delay distribution according to the position of the minimum value in the moving average value set.
In the embodiment of the present application, it can be considered that only noise is included in the minimum moving average result. Thus, S is as described above 2 (g 2 ) The minimum in the set can be used to characterize the noise power:
P noise ＝min(S 2 (g 2 ))……(13)
then, its position g min Can be expressed as:
thus, the position of the CP can be inferred based on the position of the noise segment.
In a particular implementation, the communication device may determine the starting position g of the noise segment based on the position of the minimum value in the set of running average values start 。
In general, if g min ＞G TA Then the starting position of the noise segment can be represented as g start ＝g min -G TA -1; if g is min ≤G TA Then the starting position of the noise segment can be represented as g start ＝G PDP +g min -G TA -1；
Wherein, g min Is the position of the minimum in the set of moving average values, G TA For the number of offset stages, G PDP The total number of segments for a plurality of distribution segments.
Note that, the PDP distribution may be shifted due to the influence of the time offset. Therefore, if g min ＞G TA Then, it represents the start position g of the actual noise segment start In the front half of the PDP; if g is min ≤G TA Then, it represents the start position g of the actual noise segment start In the second half of the PDP.
The communication device may then rely on the starting position g of the noise segment start Determining a set of position indices Idx belonging to the CP in the PDP CP Comprises the following steps:
Idx CP ＝(N G ·g start -n)&(N PDP -1)，n＝0,1,2,…,N G ·G CP -1……(15)
wherein the content of the first and second substances,&to find the intersection sign, N G ·g start Indicating the starting position of noise on the PDP, N G ·G CP Indicates the number of location points on the PDP that belong to the CP segment, N PDP -1 denotes a position index at N PDP Within the range of (a).
S1042, determining the position points belonging to the position index set and the position point of the maximum value in the power delay distribution and the adjacent position points thereof as a plurality of target position points for counting signal power.
In the embodiments of the present application, idx may be assigned CP Multiple location points in the set and location point n of the maximum value in the PDP max And its adjacent position point n max,L And n max,R A plurality of target location points for statistical signal power are determined.
In a specific implementation, the position point outside the CP may be set to zero, and the position point n of the maximum value is retained max And its adjacent position point n max,L And n max,R 。
In a possible implementation manner of the embodiment of the present application, idx may also be used for the target location point CP Deleting the position points with the power less than the threshold value from the plurality of position points in the set, wherein the threshold value is equal to the noise power P noise Is preset multiple of.
Exemplarily, can be according to P noise The following threshold values Thr are determined:
Thr＝R·P noise ……(16)
wherein R may be an empirical value.
In a specific implementation, the power may be set to zero for the position point where the power is less than the threshold.
After the above processing, the positions outside the CP and less than the threshold value in the PDP are set to zero, and the position n inside the CP and greater than the threshold value is reserved max And its adjacent position point n max,L And n max,R . The communication device may calculate the signal power from the reserved target location point.
The above process can be represented by the following code segment:
wherein N is path To preserve the diameter number.
And S105, calculating signal power based on the target position points, wherein the signal power is equal to the sum of the powers corresponding to the target position points minus the product of the reserved path number and the noise power.
In the embodiment of the present application, in calculating the signal power, the noise on each path may be subtracted on the basis of adding the signal powers of a plurality of paths. Thus, compared with the prior art that the signal power on the multipath is simply added, the calculated signal is more accurate.
In a specific implementation, N path Equal to the number of the plurality of target location points. Thus, adding the signal powers of the multiple paths may refer to adding the powers corresponding to the multiple target location points; the noise on each path that needs to be subtracted, i.e., N path And noise power P noise The product of (a) and (b).
Therefore, the signal power on the PDP can be calculated using the following equation (17):
and S106, calculating the signal-to-noise ratio of the channel by adopting the signal power and the noise power.
The calculated signal-to-noise ratio can be expressed as:
in the embodiments of the present application, the power delay profile is used to estimate the noise and signal power. In addition, in the actual processing process, the calculation amount in the processing process is reduced by using a mode of sectional averaging and then performing circulating averaging. Secondly, the maximum value and two adjacent values in the obtained power delay distribution are reserved during noise suppression, and the main path of the channel is guaranteed not to be lost. Third, in the processing process, by distinguishing noise, cyclic prefix and time offset range, the embodiment of the present application has a better noise suppression effect compared with the prior art that noise suppression is performed only according to a threshold value. Fourthly, when calculating the signal power, the embodiment of the present application does not simply add the multiple paths, but subtracts the noise on each path, and the theoretical calculation result is more accurate.
It should be noted that, the sequence numbers of the steps in the foregoing embodiments do not mean the execution sequence, and the execution sequence of each process should be determined by the function and the inherent logic of the process, and should not constitute any limitation on the implementation process of the embodiments of the present application.
Referring to fig. 7, a schematic diagram of a signal-to-noise ratio estimation apparatus provided in the embodiment of the present application is shown, and specifically, the apparatus may include a power delay distribution obtaining module 701, a power delay distribution dividing module 702, a moving average calculating module 703, a target location point determining module 704, a signal power calculating module 705, and a signal-to-noise ratio calculating module 706, where:
a power delay profile obtaining module 701, configured to obtain a power delay profile of a channel;
a power delay profile dividing module 702, configured to divide the power delay profile into a plurality of profile segments evenly;
a moving average calculation module 703, configured to calculate moving averages of the multiple distribution segments in a cyclic manner to obtain a moving average set, where a minimum value in the moving average set is used to represent noise power;
a target location point determining module 704, configured to determine a plurality of target location points for counting signal power in the power delay profile;
a signal power calculation module 705 for calculating a signal power based on the plurality of target location points, the signal power being equal to a value obtained by subtracting a product of a reserved path number and the noise power from a sum of powers corresponding to the plurality of target location points;
a signal-to-noise ratio calculating module 706, configured to calculate a signal-to-noise ratio of the channel based on the signal power and the noise power.
In the embodiment of the application, the number of the reserved paths is equal to the number of the target position points.
In this embodiment of the present application, the power delay profile obtaining module 701 is specifically configured to: performing channel estimation on the channel according to a least square criterion; performing inverse fast Fourier transform on the result of the channel estimation to obtain a transform result; and sequentially carrying out modular operation and square operation on the transformation result to obtain the power time delay distribution of the channel.
In this embodiment, the moving average calculating module 703 is specifically configured to: respectively calculating the arithmetic mean value of each distribution section; determining a sliding starting section and a sliding ending section; and calculating a sliding average value in the range from the sliding starting section to the sliding ending section by taking the preset number of sections as the length based on the arithmetic average value of each distribution section to obtain the sliding average value set.
In the embodiment of the present application, the sliding start segment may be G S ＝mod(G TA ,G PDP ) The end section of sliding can be G E ＝G CP +G TA -1, the predetermined number of segments being equal to the number of segments occupied by noise, the number of segments occupied by noise being equal to the total number of segments of the plurality of distributed segments minus the number of segments occupied by the cyclic prefix; where mod is the remainder operation, G TA For the number of offset stages, G PDP A total section of a plurality of distribution sectionsNumber, G CP Is the number of segments occupied by the cyclic prefix.
In this embodiment of the present application, the target location point determining module 704 is specifically configured to: determining a position index set belonging to the cyclic prefix in the power delay distribution according to the position of the minimum value in the moving average value set; and determining a plurality of position points belonging to the position index set, the position point of the maximum value in the power delay distribution and the adjacent position points thereof as a plurality of target position points for counting the signal power.
In this embodiment of the present application, the target location point determining module 704 is further configured to: determining the starting position of a noise section according to the position of the minimum value in the moving average value set; and determining a position index set belonging to the cyclic prefix in the power delay distribution according to the initial position of the noise section.
In the examples of the present application, if g min ＞G TA Then the starting position g of the noise section start ＝g min -G TA -1; if g is min ≤G TA Then the starting position g of the noise section start ＝G PDP +g min -G TA -1, the set of position indices of the cyclic prefix is: idx CP ＝(N G ·g start -n)&(N PDP -1)，n＝0,1,2,…,N G ·G CP -1; wherein the content of the first and second substances,&to find the intersection symbol, g min For the position of the minimum in the set of moving average values, G TA For the number of offset stages, G PDP Is the total number of segments of the plurality of distribution segments.
In this embodiment of the present application, the target location point determining module 704 is further configured to: and deleting the position points with the power smaller than a threshold value from the plurality of position points in the position index set, wherein the threshold value is equal to a preset multiple of the noise power.
For the apparatus embodiment, since it is substantially similar to the method embodiment, it is described relatively simply, and reference may be made to the description of the method embodiment section for relevant points.
Referring to fig. 8, a schematic diagram of a communication device provided in an embodiment of the present application is shown. As shown in fig. 8, the communication apparatus 800 includes: a processor 810, a memory 820, and a computer program 821 stored in the memory 820 and operable on the processor 810. The processor 810, when executing the computer program 821, implements the steps in various embodiments of the above-described signal-to-noise ratio estimation method, such as the steps S101 to S106 shown in fig. 1. Alternatively, the processor 810, when executing the computer program 821, implements the functions of the modules/units in the device embodiments, such as the functions of the modules 701 to 706 shown in fig. 7.
Illustratively, the computer program 821 may be partitioned into one or more modules/units that are stored in the memory 820 and executed by the processor 810 to accomplish the present application. The one or more modules/units may be a series of computer program instruction segments capable of performing certain functions, which may be used to describe the execution of the computer program 821 in the communication device 800. For example, the computer program 821 may be divided into a success rate delay distribution obtaining module, a power delay distribution dividing module, a moving average calculating module, a target location point determining module, a signal power calculating module, and a signal-to-noise ratio calculating module, where the specific functions of each module are as follows:
a power delay distribution obtaining module, configured to obtain power delay distribution of a channel;
the power time delay distribution dividing module is used for evenly dividing the power time delay distribution into a plurality of distribution sections;
the moving average calculation module is used for circularly calculating the moving average of the distribution sections to obtain a moving average set, and the minimum value in the moving average set is used for representing the noise power;
a target location point determining module, configured to determine a plurality of target location points for counting signal power in the power delay distribution;
a signal power calculation module for calculating a signal power based on the plurality of target location points, the signal power being equal to a value obtained by subtracting a product of a reserved path number and the noise power from a sum of powers corresponding to the plurality of target location points;
and the signal-to-noise ratio calculation module is used for calculating the signal-to-noise ratio of the channel based on the signal power and the noise power.
The communication device 800 may be a base station or a terminal. The terminal comprises a mobile phone, a tablet and a personal computer. The communication device 800 may include, but is not limited to, a processor 810, a memory 820. Those skilled in the art will appreciate that fig. 8 is merely an example of a communication device 800 and does not constitute a limitation of communication device 800 and may include more or fewer components than illustrated, or some components may be combined, or different components, e.g., communication device 800 may also include input-output devices, network access devices, buses, etc.
The Processor 810 may be a Central Processing Unit (CPU), other general purpose Processor, a Digital Signal Processor (DSP), an Application Specific Integrated Circuit (ASIC), an off-the-shelf Programmable Gate Array (FPGA) or other Programmable logic device, discrete Gate or transistor logic device, discrete hardware component, etc. A general purpose processor may be a microprocessor or the processor may be any conventional processor or the like.
The storage 820 may be an internal storage unit of the communication device 800, such as a hard disk or a memory of the communication device 800. The memory 820 may also be an external storage device of the communication device 800, such as a plug-in hard disk, a Smart Media Card (SMC), a Secure Digital (SD) Card, a Flash memory Card (Flash Card), and so on, provided on the communication device 800. Further, the memory 820 may also include both internal storage units and external storage devices of the communication device 800. The memory 820 is used for storing the computer program 821 and other programs and data required by the communication device 800. The memory 820 may also be used to temporarily store data that has been output or is to be output.
The embodiment of the present application further discloses a communication device, which includes a memory, a processor, and a computer program stored in the memory and executable on the processor, and when the processor executes the computer program, the signal-to-noise ratio estimation method according to the foregoing embodiments is implemented.
The embodiment of the present application further discloses a computer-readable storage medium, in which a computer program is stored, and when the computer program is executed by a processor, the method for estimating a signal-to-noise ratio as described in the foregoing embodiments is implemented.
The embodiment of the present application further discloses a computer program product, which when running on a communication device, causes the communication device to execute the signal-to-noise ratio estimation method described in the foregoing embodiments.
The above-mentioned embodiments are only used for illustrating the technical solutions of the present application, and not for limiting the same. Although the present application has been described in detail with reference to the foregoing embodiments, it should be understood by those of ordinary skill in the art that: the technical solutions described in the foregoing embodiments may still be modified, or some technical features may be equivalently replaced; such modifications and substitutions do not depart from the spirit and scope of the embodiments of the present application, and they should be construed as being included in the present application.
Claims (10)
1. A method for estimating a signal-to-noise ratio, comprising:
acquiring power time delay distribution of a channel;
evenly dividing the power time delay distribution into a plurality of distribution sections;
circularly calculating the sliding average values of the distribution sections to obtain a sliding average value set, wherein the minimum value in the sliding average value set is used for representing noise power;
determining a plurality of target position points for counting signal power in the power time delay distribution;
calculating a signal power based on the plurality of target location points, the signal power being equal to a sum of powers corresponding to the plurality of target location points minus a product of a number of reserved paths and the noise power;
calculating a signal-to-noise ratio of the channel based on the signal power and the noise power;
wherein the determining a plurality of target location points for statistical signal power in the power delay profile comprises:
determining a position index set belonging to a cyclic prefix in the power delay distribution according to the position of the minimum value in the moving average value set;
and determining a plurality of position points belonging to the position index set, the position point of the maximum value in the power delay distribution and the adjacent position points thereof as a plurality of target position points for counting the signal power.
2. The method of claim 1, wherein the number of reserved paths is equal to the number of target location points.
3. The method of claim 1, wherein the loop calculates a moving average of the plurality of distribution segments, resulting in a set of moving averages, comprising:
respectively calculating the arithmetic mean value of each distribution section;
determining a sliding starting section and a sliding ending section;
and calculating a sliding average value in the range from the sliding starting section to the sliding ending section by taking the preset number of sections as the length based on the arithmetic average value of each distribution section to obtain the sliding average value set.
4. A method according to claim 3, wherein the slip initiation section isG S =mod(G TA ,G PDP )The sliding end section isG E =G CP +G TA -1The predetermined number of segments is equal to the number of segments occupied by noise, and the noise stationThe number of the occupied sections is equal to the total number of the distributed sections minus the number of the sections occupied by the cyclic prefix; wherein the content of the first and second substances,modin order to carry out the operation of the remainder,G TA in order to offset the number of stages,G PDP is the total number of the plurality of distribution segments,G CP the number of segments occupied by the cyclic prefix.
5. The method of claim 1, wherein the determining the set of position indices in the power delay profile belonging to the cyclic prefix according to the position of the minimum value in the set of moving average values comprises:
determining the starting position of a noise section according to the position of the minimum value in the moving average value set;
and determining a position index set belonging to the cyclic prefix in the power delay distribution according to the initial position of the noise section.
6. The method of claim 5, wherein the determining the set of position indices in the power delay profile belonging to the cyclic prefix according to the position of the minimum value in the set of moving average values comprises:
if it isg min ＞G TA Then the starting position of the noise sectiong start =g min -G TA -1(ii) a If it isg min ≤G TA Then the starting position of the noise sectiong start =G PDP +g min -G TA -1；
The position index set of the cyclic prefix is as follows:
Idx
CP
=(N
G
·g
start
-n)&( N
PDP
-1)，n=0,1,2,…, N
G
·G
CP
-1
wherein the content of the first and second substances,&in order to find the intersection symbols,g min for the position of the minimum in the set of running average values,G TA in order to offset the number of stages,G PDP is the total number of the plurality of distribution segments,N G indicating the number of location points contained within each distribution segment,N G ·g start to representPDPThe start position of the upper noise is determined,PDPit is shown that the power delay profile,N G ·G CP to representPDPThe number of location points of the segment belonging to the cyclic prefix,N PDP -1indicating that the position is indexed atN PDP Within the range of (a) to (b),N PDP to representPDPLength of (d).
7. The method according to claim 1, wherein after determining a plurality of position points belonging to the position index set and a position point of a maximum value in the power delay profile and its neighboring position points as a plurality of target position points for statistical signal power, further comprising:
and deleting the position points with the power smaller than a threshold value from the plurality of position points in the position index set, wherein the threshold value is equal to a preset multiple of the noise power.
8. The method of claim 7, wherein the threshold is equal to a product of the noise power and an empirical value.
9. A signal-to-noise ratio estimation apparatus, comprising:
a power delay distribution obtaining module, configured to obtain power delay distribution of a channel;
the power time delay distribution dividing module is used for evenly dividing the power time delay distribution into a plurality of distribution sections;
the moving average calculation module is used for circularly calculating the moving average of the distribution sections to obtain a moving average set, and the minimum value in the moving average set is used for representing the noise power;
a target location point determining module, configured to determine a plurality of target location points for counting signal power in the power delay distribution;
a signal power calculation module for calculating a signal power based on the plurality of target location points, the signal power being equal to a value obtained by subtracting a product of a reserved path number and the noise power from a sum of powers corresponding to the plurality of target location points;
a signal-to-noise ratio calculation module, configured to calculate a signal-to-noise ratio of the channel based on the signal power and the noise power;
wherein the target location point determining module is specifically configured to: determining a position index set belonging to a cyclic prefix in the power delay distribution according to the position of the minimum value in the moving average value set; determining a plurality of position points belonging to the position index set, a position point of the maximum value in the power time delay distribution and adjacent position points thereof as a plurality of target position points for counting the signal power
A communication device comprising a memory, a processor and a computer program stored in the memory and executable on the processor, wherein the processor implements the signal-to-noise ratio estimation method according to any one of claims 1 to 8 when executing the computer program.
10. A computer-readable storage medium, in which a computer program is stored which, when being executed by a processor, carries out a signal-to-noise ratio estimation method according to any one of claims 1 to 8.
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