CN112467399B - Positive-feed excitation multi-frequency-point novel circularly polarized millimeter wave broadband planar reflection array antenna - Google Patents
Positive-feed excitation multi-frequency-point novel circularly polarized millimeter wave broadband planar reflection array antenna Download PDFInfo
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Abstract
A positive feed excitation multi-frequency point novel circular polarization millimeter wave broadband planar reflection array antenna belongs to the technical field of microwaves. The micro-strip n x n petal reflection array comprises a dielectric substrate, a grounding plate, a feed source and a micro-strip n x n petal reflection array; the micro-strip n x n petal reflection array comprises n x n single-layer tightly-coupled petal units, the n x n single-layer tightly-coupled petal units meet the recursion relation and are uniformly arranged on the upper surface of the medium substrate and are in rotary distribution at a certain angle, and the micro-strip n x n petal reflection array faces the feed source; each close-coupled petal unit comprises 2M regular polygon open resonance rings which are equal in size in pairs and surround regular 2M polygonal gaps, and the regular polygon open resonance rings with different sizes respectively work at different frequencies to form a multi-resonance unit; the back of the dielectric substrate is provided with a grounding plate, and the contour of the grounding plate is rectangular. The millimeter wave antenna can work in different millimeter wave bands, comprises a 5G standard, is designed according to requirements, has good radiation performance, and is simple in structure, low in cost and easy to realize in engineering.
Description
Technical Field
The invention belongs to the technical field of microwaves, and particularly relates to a novel positive-feed excitation multi-frequency-point circularly polarized millimeter wave broadband planar reflection array antenna.
Background
Conventional high gain antennas mainly include a reflector antenna represented by a large parabolic antenna and a microstrip patch array antenna represented by a phased array antenna. The large reflector antenna has the advantages of simple design, theoretically infinite gain bandwidth, high efficiency and strong directivity, but is large in size, difficult to deploy and needs a complex waiting system, the curved surface structure has high requirements on processing precision, especially millimeter wave bands, and in addition, the beam scanning can be realized only through mechanical rotation. Microstrip patch array antennas often have low profile, the PCB etching technology is mature, phase shift is used for independently adjusting the phase and amplitude of a radiation unit, beam scanning is easy to realize, but for a super-large-scale array, the feed network design is complex, the cost of a T/R assembly required by electric scanning is high, and the millimeter wave band loss is increased sharply. Under the background, the microstrip reflective array antenna has come forward, combines the advantages of a parabolic antenna, such as high gain, high efficiency and low cost of a microstrip low section, and once the microstrip reflective array antenna is put forward, the microstrip reflective array antenna can be widely concerned by experts and scholars at home and abroad, becomes a first choice of a novel high-gain antenna, and shows a wide application prospect.
From the perspective of an antenna excitation mode, the circularly polarized antenna can radiate and receive electromagnetic waves with any polarization, so that polarization loss is avoided, and the circularly polarized antenna is just the reason for generally using the circularly polarized antenna in applications such as electronic reconnaissance and the like; the rotation direction of the reflected wave is reversed, so that the interference of rain and fog weather and multipath reflection can be inhibited; in addition, based on the polarization orthogonality of the circularly polarized antenna, the electromagnetic wave distortion of an ionized layer caused by Faraday rotation can be eliminated. Because of these incomparable advantages, the circularly polarized antenna has been widely used in polarization diversity of radar communication and navigation systems.
Reference documents:
[1]LIU J W,CHOU H T.Phase-only synthesis of convex metallic reflectarray antennas for multi-beam radiations via steepest descent method[C]；proceedings of the 2017International Applied Computational Electromagnetics Society Symposium-Italy(ACES),2017.
[2]Xue F,Wang H J,Yi M,et al.Design of a Broadband Single-Layer Linearly Polarized Reflectarray Using Four-Arm Spiral Elements[J].IEEE Antennas&Wireless Propagation Letters,2016,16(99):1-1.
[3] scheifei broadband dual-frequency microstrip reflective array and broadband transmissive array antenna research [ J ].2017.
[4]Guo L,Min M,Che W,et al.A Novel Miniaturized Planar Ultra-Wideband Antenna[J].IEEE Access,2018:1-1.
[5]Fan C,Che W,Yang W,et al.A Novel PRAMC-Based Ultralow-Profile Transmitarray Antenna by Using Ray Tracing Principle[J].IEEE Transactions on Antennas and Propagation,2017,65(4):1779-1787.
[6]Fan C,Che W,Yang W,et al.A polarization-rotation AMC-based low-profile transmitarray antenna[C]//2016Asia-Pacific Microwave Conference(APMC).IEEE,2016.
[7]Amin M H A S M,Ghaemi K,Behdad N.Ultra-Wideband,True-Time-Delay Reflectarray Antennas Using Ground-Plane-Backed,Miniaturized-Element Frequency Selective Surfaces[J].IEEE Transactions on Antennas and Propagation,2015,63(2):534-542.
[8]H.Yu,L.Guo,W.Che and W.Yang,"A Broadband Folded Reflectarray Using Single-Layer Three-Dipole Elements,"2019IEEE MTT-S International Wireless Symposium(IWS),Guangzhou,China,2019,pp.1-3.
[9]Hussain S,Qu S W.A Compact Wideband,Wide-Scan Millimeter-Wave Antenna Array for 5G Wireless Applications[C].ICC 2019-2019IEEE International Conference on Communications(ICC).IEEE,2019.
[10]Nayeri P,Yang F,Elsherbeni A Z.Reflectarray Antennas:Theory,Designs,and Applications[M].2018.
[11]Yang F,Deng R,Xu S,et al.Design and Experiment of a Near-Zero-Thickness High-Gain Transmit-Reflect-Array Antenna Using Anisotropic Metasurface[J].IEEE Transactions on Antennas&Propagation,2018:1-1.
Disclosure of Invention
The invention aims to provide a novel feed-forward excitation multi-frequency point circularly polarized millimeter wave (26/52GHz) broadband planar reflection array antenna which has the performances of high gain, low side lobe and low cross polarization and can be widely applied to 5G millimeter wave communication.
The invention comprises a dielectric substrate, a grounding plate and a microstrip n x n petal reflection array; the micro-strip n x n petal reflection array comprises n x n single-layer tightly-coupled petal units, the n x n single-layer tightly-coupled petal units meet the recursion relation and are uniformly arranged on the upper surface of the medium substrate and are in rotary distribution at a certain angle, and the micro-strip n x n petal reflection array faces the feed source; each close-coupled petal unit comprises 2M regular polygon open resonance rings which are equal in size in pairs and surround regular 2M polygonal gaps, and the regular polygon open resonance rings with different sizes respectively work at different frequencies to form a multi-resonance unit; the back of the dielectric substrate is provided with a grounding plate, and the contour of the grounding plate is rectangular.
The sizes of the different-order tightly-coupled petal units have a digital recursive effect. By controlling the angle psi of counter-clockwise rotation of the tightly coupled petal units along the centre of each petal itselfmnRealizing reflection phase delay, and obtaining the required compensation phase from phase distribution according to aperture field superposition method
Then obtaining the corresponding tightly coupled petal unit rotation angle psi according to the tightly coupled petal unit phase shift curvemnSo that each tightly coupled petal unit is in rotary distribution at a certain angle. The tightly coupled petal unit structure is composed of 2M sub petal structures which are in two-by-two equal sizes and are symmetrically distributed according to the center, the tightly coupled petal unit structure can be extended step by step according to 1, 2 and 3 … 8 by adjusting the number of the sub petals, namely the number of the sides of the central gap 2M, and is composed by recursion according to the 2 sub petal structures which are more than the upper step according to the lower step, the regular polygonal open petal resonant rings corresponding to different orders M can respectively work on different frequencies to form a multi-resonance unit, the first-order, second-order, third-order and fourth-order structures respectively correspond to microstrip n petal reflection arrays with single frequency points, double frequency points, three frequency points and four frequency points, and the multi-resonance unit structure is designed into microstrip n petal reflection arrays with different types according to requirements.
The medium substrate layer is a high-performance low-consumption millimeter wave medium substrate, the dielectric constant of the medium substrate can be 2.2-8.0, the outline of the tightly-coupled petal units is square, the side length P of the square outline is 4-6 mm, and the thickness H1 of the medium substrate is 0.7-1 mm.
The feed source uses a horn antenna as positive feed excitation, the beam direction points to the direction of the surface of the microstrip n x n petal reflection array perpendicularly, the target deviation angles of two emergent beams of the microstrip n x n petal reflection array are respectively Phi 90 degrees, Theta 30 degrees, Phi 90 degrees and Theta-30 degrees, and the distance between the horn antenna feed source and the tight coupling petal unit reflection surface is 50-60 mm.
The upper surface metal layer of tight coupling petal unit is the copper layer, and the desirable scope of thickness H of copper layer is 0.03 ~ 0.125 mm.
The corresponding side lengths of the 2M regular polygon opening resonance rings which are equal in size in pairs and surround the regular 2M polygonal slits are L1～LMThe value range of M is that M is more than or equal to 2; wherein L is1The preferable range is 0.5-2.45 mm, the value of the coefficient KS is 0.02, and the coefficient KL0Is 0.54, coefficient KL2Is 0.8, coefficient KW1Is 0.21, coefficient KW20.1, and the value of the gap S between two adjacent regular polygon open-ended resonant rings is L1KS; side length L of regular polygon opening resonant ring gaps with different sizes0Has a value of L1 KL0；L2Has a value of L1 KL2(ii) a Side length of L1Width W of regular polygon open resonator ring1Value of L1 KW1(ii) a Side length of L2Width W of regular polygon open resonator ring2Value of L1 KW2(ii) a M is increased, the coefficient KL is increased3,KW3...KLM,KWMAnd by analogy, adjusting the coefficient according to the actual working frequency requirement.
The length of the side of the basic tightly-coupled petal unit of the microstrip n x n petal reflection array antenna in different orders meets the optimized ratio, and when the order of the microstrip n x n petal reflection array antenna unit is M, the length of the side L of all positive 2 x M polygonal slots of the basic tightly-coupled petal unit structure of the antenna is LP0＝L0*pM-1Wherein the optimized ratio p is 0.8-1, the method can be used for adjusting the working frequency, and the side length base number is L0The antenna is 0.8-1 mm and used for controlling the gain of the microstrip n x n petal reflection array antenna; in the same way, whenWhen the order of the close coupling petal unit of the antenna is M, the side length L of the resonance ring of the regular polygon openingP1＝L1*pM-1The optimization ratio p is 0.8-1, and the side length base number L1The antenna is 0.5-2.45 mm and is used for controlling the working frequency of the microstrip n x n petal reflection array antenna. Coefficient KLM＝KL2*PM-2,KWM＝KW2*PM-2The optimized ratio p is 0.8-1; length L of square edge dug out at centerP0Coefficient of petal size KLMHas a decisive effect on the resonance frequency point, LP0The influence on the low frequency point is larger than that of the high frequency point, KLMMainly affecting the spacing of the high and low resonance frequency points.
The value range of the microstrip n x n petal reflection array antenna n is that n is more than or equal to 2.
A is the antenna aperture, and P is the side length of the tightly coupled petal unit. The microstrip n x n petal reflection array unit is formed by obtaining the required compensation phase from the phase field distribution obtained by the obtained wave beam according to the aperture field superposition method
I.e. the compensation phase of the (m, n) th cell, assuming the feed bit-vector as
The (m, n) -th unit bit vector is
Target beam pointing
Should satisfy
By pairs
The adjustment of (2) can be carried out to meet the above formula, so that the reflection array with the main beam in any direction can be designed. Followed by close coupling of petalsCell phase shift curve derivation
Angle psi of counter-clockwise rotation of corresponding tightly coupled petal units along petal centersmnWherein the petal units are tightly coupled at a rotation angle psimnThe range of (a) is 0 to 180 degrees.
The invention can perform phase modulation, improve gain, control side lobe, low cross polarization and other effects by controlling the type and the rotation angle of the tight coupling petal type tight coupling petal unit. The M-order micro-strip tightly-coupled petal units of the petal type are optimized according to a certain recursion proportion, and the side length range L of the nth orderP1＝L1*pM-1The recursion ratio p is 0.8 to 1. The control of the recursive ratio can regularly adjust the bandwidth and the working frequency point of the antenna to obtain the balanced and flat microstrip antenna characteristic. The positive-feed excitation multi-frequency-point novel circularly polarized millimeter wave broadband planar reflection array antenna has a simple and uniform structure, only needs to rotate the tightly-coupled petal units, is easy to process and manufacture and has low cost; the adoption of the form of tight coupling can enhance resonance, improve bandwidth and stability to oblique incidence, and is beneficial to the small-sized and compact design of the multi-resonance unit. The microstrip n x n petal reflection array antenna provided by the invention has the advantages that the grid period of the single-layer tight coupling petal units and other size parameters of the units are reasonably set, the mutual coupling influence among different frequencies is fully considered, the antenna can work in different wavebands of millimeter waves including 5G standard, and can be designed into single-frequency, double-frequency, three-frequency, four-frequency point and other types as required, so that the caliber of the microstrip n x n petal reflection array antenna is multiplexed, the microstrip n x n petal reflection array antenna has good radiation performance, the designed antenna has a simple structure and low cost, and the design is easy for engineering realization.
Drawings
FIG. 1 is a diagram illustrating an overall system configuration according to an embodiment of the present invention;
FIG. 2 is a front view of a different type of rotary multi-resonant close-coupled petal unit configuration according to an embodiment of the present invention;
FIG. 3 is a side view of a different type of rotary multi-resonant close-coupled petal cell configuration according to an embodiment of the present invention;
FIG. 4 is a plot of return loss (S11 parameter) for a tightly coupled petal unit;
FIG. 5 is a graph of reflection phase versus angle of incidence for a tightly coupled petal unit;
FIG. 6 is a phase distribution plot calculated to produce dual beams using aperture field superposition;
FIG. 7 is a diagram of a unit rotation angle distribution for dual beam generation using aperture field superposition;
FIG. 8 is a top view of a dual beam reflectarray of an embodiment of the present invention;
FIG. 9 is a petal dual beam array radiation pattern for a rotary phase modulation scheme;
FIG. 10 is a plot of petal dual beam array gain versus axial ratio bandwidth for a rotary phase modulation scheme;
fig. 11 is a 3D effect diagram of petal symmetry dual beam for the rotary phase modulation scheme.
Detailed Description
The following examples will further illustrate the present invention with reference to the accompanying drawings.
As shown in fig. 1 to 3, the embodiment of the invention is provided with a dielectric substrate 3, the upper surface of the dielectric substrate 3 is provided with a microstrip n x n petal reflection array 2, the back surface of the dielectric substrate is provided with a grounding plate 4, and the contour of the grounding plate 4 is rectangular; the micro-strip n x n petal reflection arrays which meet the recursive relationship and are uniformly arranged are distributed on the upper surface in a rotary mode at a certain angle, and the surfaces of the micro-strip n x n petal reflection arrays face the horn antenna feed source 1. By controlling the angle psi of counter-clockwise rotation of the tightly coupled petal units along the centre of each petal itselfmnThe purpose of reflecting phase delay can be realized, and the required compensation phase is obtained from the phase distribution according to the aperture field superposition method
Then obtaining the corresponding tightly coupled petal unit rotation angle psi according to the tightly coupled petal unit phase shift curvemn. The n x n tightly coupled petal unit structure consists of 2 x M sub petal structures which are of the same size in pairs and are symmetrically distributed according to the center, and the number of the sub petals can be adjusted through the tightly coupled petal unit structureThe number of sides 2M of the central slot is measured, the central slot extends step by step according to 1, 2 and 3 … 8, the central slot is formed by recursion according to 2 sub-petal structures which are more than the upper step according to the pressing step, regular polygon open resonant rings corresponding to different orders M can respectively work on different frequencies to form a multi-resonant unit, the first-order, second-order, third-order and fourth-order structures respectively correspond to microstrip n petal reflective arrays with single frequency point, double frequency point, three frequency point and four frequency point, and the microstrip n petal reflective arrays with different types can be designed according to requirements.
The dielectric substrate layer is made of a high-performance dielectric material substrate, the dielectric constant of the high-performance dielectric material substrate can be 2.2-8.0, the outline of the tightly-coupled petal units is square, the side length P of the square outline is 4-6 mm, and the thickness H1 of the dielectric substrate is 0.7-1 mm. The antenna uses a horn antenna as positive feedback excitation, the beam direction points to the direction of the surface of the microstrip n x n petal reflection array perpendicularly, the target deviation angles of two emergent beams of the microstrip n x n petal reflection array are respectively Phi 90 degrees, Theta 30 degrees, Phi 90 degrees and Theta-30 degrees, and the distance between the horn antenna feed source and the tight coupling petal unit reflection surface is 50-60 mm. The corresponding side lengths of the 2M regular polygon open-ended resonant rings with the same size in pairs are respectively L1～LMThe value range of M is that M is more than or equal to 2; wherein L is1The preferable range is 0.5-2.45 mm, the value of the coefficient KS is 0.02, and the coefficient KL0Is 0.54, coefficient KL2Is 0.8, coefficient KW1Is 0.21, coefficient KW20.1, and the value of the gap S between two adjacent regular polygon open-ended resonant rings is L1KS; side length L of regular polygon opening resonant ring gaps with different sizes0Has a value of L1 KL0；L2Has a value of L1 KL2(ii) a Side length of L1Width W of regular polygon open resonator ring1Value of L1 KW1(ii) a Side length of L2Width W of regular polygon open resonator ring2Value of L1 KW2(ii) a M is increased, the coefficient KL is increased3,KW3...KLM,KWMAnd by analogy, adjusting the coefficient according to the actual working frequency requirement.
As a preferred scheme, the overall size of the antenna of the implementation example is 55mThe single-layer dielectric substrate with the thickness of m multiplied by 55mm multiplied by 1mm and bearing the tightly coupled petal unit reflecting surface 2 and the grounding plate 4 adopts Rossgers RT5880(lossy), and the dielectric constant is epsilonr2.2, and a loss tangent σ of 0.002. The side length P of the square outline of the tightly coupled petal unit is 5mm, and the thickness H1 of the medium substrate is 0.787 mm.
The feed source in the embodiment of the invention adopts a short conical horn with E, H surfaces having high symmetry, the structure is simple, and the waveguide port adopts two TE11 waves with orthogonal phases for feeding, so that high-purity circularly polarized waves with the axial ratio approximate to 0 are excited. The 26GHz horn structure antenna parameters include that the waveguide diameter is 9.8009mm, the waveguide length is 2.8826mm, the coaxial inner diameter is 15.281mm, the coaxial outer diameter is 19.025mm, the cavity depth is 2.6520mm, the edge depth is 2.8826mm, and the opening angle is 66 degrees. Gain 13.1dB at center frequency 26Hz, half power lobe width 41.8 °. E. The H-plane radiation patterns are highly coincident and cross polarization is very low.
The preferred embodiments of the invention are detailed below:
in the embodiment, adopt rotary-type two resonance close coupling petal unit structures, get M promptly 2, then the opening resonance ring that gap and size two liang equal is the square, and two liang of opening resonance rings that equal of two different sizes correspond two resonance points and apply circular polarization ripples, and the current centralized distribution is inboard in big square ring in low frequency department, and the current is then concentrated in little square ring in high frequency department, when work is 26GHz, the current evenly distributed on the big square ring, petal unit structure with optimize the size as follows: side length L of larger unit of square opening resonant ring1The preferable range is 0.5-2.45 mm, the value of the coefficient KS is 0.02, and the coefficient KL0Is 0.54, coefficient KL2Is 0.8, coefficient KW1Is 0.21, coefficient KW20.1, and the value of the gap S between two adjacent square open-ended resonant rings is L1KS; side length L of gaps of square opening resonant rings with different sizes0Has a value of L1 KL0(ii) a Side length L of smaller unit of square opening resonant ring2Has a value of L1 KL2(ii) a Side length of L1Width W of square split ring resonator1Value of L1 KW1(ii) a Side length of L2Width W of square split ring resonator2Value of L1 KW2(ii) a When L is1When 1.59mm is taken, S is 0.318mm, L0Is 0.8586mm, L2Is 1.272mm, W10.3339mm, W2Is 0.159 mm. The side length coefficient KL of a square is dug out at the center0And small petal size factor KL2Has a decisive effect on the resonance frequency point, KL0The influence on the low frequency point is larger than that of the high frequency point, KL2Mainly affecting the spacing of the high and low resonance frequency points.
Preferably, the focal length ratio F/D is 1.14, the period P of the tightly-coupled petal unit is 5mm, the radiation radius D is 50mm, and the distance between the horn antenna feed 1 and the reflecting surface 2 of the tightly-coupled petal unit is 57 mm.
The single-feed-source dual-beam reflection array is designed by adopting a rotary type close-coupled petal unit, positive-feed excitation is carried out by a horn antenna, and the target deflection angles of two emergent beams of the micro-strip n x n petal reflection array are Phi 90 degrees, Theta 30 degrees, Phi 90 degrees and Theta-30 degrees respectively.
Referring to fig. 4, the circularly polarized bandwidth of the tightly-coupled petal microstrip tightly-coupled petal unit antenna satisfying the 15dB amplitude determination condition is (25.2-26.7 GHz).
Referring to fig. 5, when the oblique incidence angle is 45 degrees, the reflection loss of the tightly-coupled petal microstrip tightly-coupled petal unit is increased dramatically, the tightly-coupled petal microstrip tightly-coupled petal unit is insensitive to the incidence angle smaller than 45 degrees, and the tightly-coupled petal unit has good reflection phase and amplitude response under the oblique incidence condition of 0-30 degrees.
The antenna efficiency was calculated to be 40%, a ═ NP2≈2648.6761mm2Considering that the dual beams can disperse partial radiation energy of the feed source, 11 × 11 units are adopted in design, the array size is 55 × 55mm, and the distribution of the phase of the generated dual beams and the rotation angle of the tightly coupled petal units is calculated by using an aperture field superposition method, see fig. 6 and 7. A top view of the dual beam reflectarray is seen in fig. 8.
Referring to fig. 9, the direction theta of the reflective dual-beam array is strictly equal to +/-30 degrees, the gain at the central frequency point is 18.03dB, the sidelobe level is-8.7 dB, the beam axial ratios pointing to +/-30 degrees are almost coincident, the circularly polarized bandwidth of the array is 11.1% (24.695-27.582 Hz), and the cross polarization at the central frequency is-21.200 dB.
Figure 10 is a plot of petal dual beam array gain versus axial ratio bandwidth for the rotary phasing scheme.
Fig. 11 is a 3D effect diagram of petal symmetry dual beam for the rotary phase modulation scheme.
In summary, the close-coupled petal units of the positive-feed excitation multi-frequency-point novel circular polarization millimeter wave broadband planar reflection array antenna comprise n single-layer close-coupled petal units which are uniformly arranged on the upper surface of a medium substrate, the close-coupled petal units are regular polygon open resonance rings which comprise 2M regular polygon open resonance rings with the same size in pairs and surround regular 2M polygon gaps, and the regular polygon open resonance rings with different sizes respectively work on different frequencies to form a multi-resonance unit. The sizes of the different-order tightly-coupled petal units have a digital recursive effect. The millimeter wave 5G frequency band can be designed to be single-frequency, double-frequency, triple-frequency, four-frequency and the like according to requirements so as to cover different millimeter wave 5G frequency bands. The adjacent units are not arranged in the same direction, the current direction between the adjacent units is irregular, and the superposition effect on a far field is offset, so that the cross polarization performance of the array is greatly reduced by adopting rotary phase modulation. Compared with the traditional microstrip plane reflection array antenna, the microstrip plane reflection array antenna can simultaneously optimize the radiation performance of high gain and low side lobe; and the structure is uniform, the processing and the manufacturing are easy, and the cost is low, so the invention has wide application prospect. The broadband unit is used for realizing multi-frequency points, the bandwidth of each obtained wave beam is about 3GHz, and the practicability of the single-feed multi-frequency point microstrip reflective array in a communication system is enhanced.
Table 1 shows the characteristics of the effect of the manufacturing process error of the present invention on the antenna.
TABLE 1
Note: the data in table 1 have certain redundancy, and each parameter has certain relevance, so that the structural parameters can be optimized as required to complete special design.
Claims (7)
1. The novel positive-feed excitation multi-frequency-point circularly polarized millimeter wave broadband planar reflection array antenna is characterized by comprising a dielectric substrate, a grounding plate and a micro-strip n x n petal reflection array; the micro-strip n x n petal reflection array comprises n x n tightly-coupled petal units, the n x n tightly-coupled petal units meet the recursion relationship and are uniformly arranged on the upper surface of the medium substrate and are in rotary distribution at a certain angle, and the micro-strip n x n petal reflection array faces to the feed source; the close-coupled petal units comprise 2M regular polygon open resonance rings which are equal in two by two and surround regular 2M polygonal gaps, and the regular polygon open resonance rings with different sizes respectively work at different frequencies to form a multi-resonance unit; the back of the dielectric substrate is provided with an earth plate, and the outline of the earth plate is rectangular;
the n x n tightly-coupled petal units are composed of 2 x M regular polygon open-ended resonant rings which are equal in size in pairs and surround a regular 2 x M polygonal slot according to a central symmetrical sub-petal structure, the tightly-coupled petal unit structure extends step by step according to 1, 2 and 3 … 8 by adjusting the number of the sub-petals, namely the number of the edges of the central slot 2 x M, and is composed by recursion according to a structure that 2 sub-petals are added to the upper step according to the lower step, the regular polygon open-ended resonant rings corresponding to different orders M respectively work on different frequencies to form a multi-resonant unit, and the first-order, second-order, third-order and fourth-order structures respectively correspond to single-frequency, double-frequency, three-frequency and four-frequency point microstrip n petal reflective arrays and are designed into different types of microstrip n x n petal reflective arrays according to needs;
the corresponding side lengths of the 2M regular polygon opening resonance rings which are equal in size in pairs and surround the regular 2M polygonal slits are L1～LMThe value range of M is that M is more than or equal to 2; wherein L is1The value range of (A) is 0.5-2.45 mm, the value of coefficient KS is 0.02, and the coefficient KL0Is 0.54, coefficient KL2Is 0.8, coefficient KW1Is 0.21, coefficient KW20.1, and the value of the gap S between two adjacent regular polygon open-ended resonant rings is L1KS; side length L of regular polygon opening resonant ring gaps with different sizes0Has a value of L1 KL0；L2Has a value of L1 KL2(ii) a Side length of L1Width W of regular polygon open resonator ring1Value of L1 KW1(ii) a Side length of L2Width W of regular polygon open resonator ring2Value of L1 KW2(ii) a M is increased, the coefficient KL is increased3,KW3...KLM,KWMIn this way, the coefficient is adjusted according to the actual working frequency requirement;
the length of the side of the basic tightly-coupled petal unit of the microstrip n x n petal reflection array antenna in different orders meets the optimized ratio, and when the order of the antenna is M, the length of the side L of all the regular 2 x M polygonal slots of the basic tightly-coupled petal unit structure of the antenna is LP0＝L0*pM-1Wherein the optimization ratio p is 0.8-1, and the base number of the side length is L00.8-1 mm; regular polygon opening resonant ring unit side length LP1＝L1*pM-1The optimization ratio p is 0.8-1, and the side length base number L10.5-2.45 mm; coefficient KLM＝KL2*PM-2,KWM＝KW2*PM-2The optimized ratio p is 0.8-1, and the coefficient KL2Radix number 0.8, coefficient KW2Radix is 0.1; the value range of the microstrip n x n petal reflection array unit n is more than or equal to 2.
2. The feed-forward excited multi-frequency-point novel circularly polarized millimeter wave broadband planar reflection array antenna as claimed in claim 1, wherein said distribution is of angular rotation type by controlling the angle ψ of the tightly coupled petal units rotated counterclockwise along the center of each petal itselfmnTo realize the purpose of reflecting phase delay, the required compensation phase is obtained from the phase distribution according to the aperture field superposition method
Then obtaining the corresponding tightly coupled petal unit rotation angle psi according to the tightly coupled petal unit phase shift curvemn。
3. The feed forward excitation multi-frequency novel circularly polarized millimeter wave broadband planar reflection array antenna as claimed in claim 1, wherein the dielectric substrate layer is a high-performance low-consumption millimeter wave dielectric substrate, the dielectric constant of the dielectric substrate is 2.2-8.0, the outline of the tightly coupled petal units is square, the side length P of the square outline is 4-6 mm, and the thickness H1 of the dielectric substrate is 0.7-1 mm.
4. The positive-feed excitation multi-frequency-point novel circular polarization millimeter wave broadband planar reflection array antenna of claim 1, wherein the feed source uses a horn antenna for positive-feed excitation, the beam direction is vertically directed to the direction of the microstrip n x n petal reflection array plane, the target departure angles of two emergent beams of the microstrip n x n petal reflection array are Phi 90 °, Theta 30 °, Phi 90 °, Theta-30 °, and the distance between the horn antenna feed source and the tight coupling petal unit reflection plane is 50-60 mm.
5. The feed-forward excitation multi-frequency-point novel circularly polarized millimeter-wave broadband planar reflection array antenna as claimed in claim 1, wherein the upper surface metal layer of the close-coupled petal units is a copper layer, and the thickness H of the copper layer is 0.03-0.125 mm.
6. The feed forward excitation multi-frequency-point novel circularly polarized millimeter wave broadband planar reflection array antenna as claimed in claim 1, wherein the close-coupled petal units form a rotational symmetric structure by a plurality of different petals, the different petals respectively correspond to resonance points with different frequencies, namely 2 petals, 4 petals, 6 petals and 8 petals, the corresponding frequencies are sequentially increased to 24/52GHz, and the antenna is designed to be single-frequency, double-frequency, three-frequency and four-frequency-point types to cover different millimeter wave 5G frequency bands as required.
7. The feed-forward excitation multi-frequency-point novel circularly polarized millimeter wave broadband planar reflection array antenna as claimed in claim 1, wherein the microstrip n x n petal reflection array unit is formed by obtaining the required compensation phase from the phase field distribution of the obtained wave beam according to aperture field superposition
I.e. the compensation phase of the (m, n) th cell, assuming the feed bit-vector as
The (m, n) -th unit bit vector is
Target beam pointing
Should satisfy
By pairs
Adjusting to design a reflecting array with the main beam in any direction according to the formula; then obtaining a phase shift curve according to the tightly coupled petal units
Angle psi of counter-clockwise rotation of corresponding tightly coupled petal units along petal centersmnWherein the cell is rotated by an angle psimnThe range of (a) is 0 to 180 degrees.
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