CN111884692B - Transmit-receive terminal combined spatial modulation transmission method enabled by radio frequency reflector - Google Patents

Transmit-receive terminal combined spatial modulation transmission method enabled by radio frequency reflector Download PDF

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CN111884692B
CN111884692B CN202010736000.3A CN202010736000A CN111884692B CN 111884692 B CN111884692 B CN 111884692B CN 202010736000 A CN202010736000 A CN 202010736000A CN 111884692 B CN111884692 B CN 111884692B
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CN111884692A (en
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刘超文
边嘉慧
马季
董艺华
卢光跃
刘伯阳
万鹏武
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Xian University of Posts and Telecommunications
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    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B7/00—Radio transmission systems, i.e. using radiation field
    • H04B7/02—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas
    • H04B7/04—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas
    • H04B7/0413—MIMO systems
    • H04B7/0456—Selection of precoding matrices or codebooks, e.g. using matrices antenna weighting
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B7/00—Radio transmission systems, i.e. using radiation field
    • H04B7/02—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas
    • H04B7/04—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas
    • H04B7/0413—MIMO systems
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Abstract

The invention discloses a receiving and transmitting end combined spatial modulation method enabled by a radio frequency reflector, which mainly solves the problems of configuration constraint and high hardware cost of the existing receiving and transmitting antenna. The technical scheme is as follows: configuring a plurality of radio frequency reflectors around the transmitting antenna, and activating one transmitting antenna to transmit signals; then, the transmitter completes the design of an alternate zero-space beam forming preprocessing matrix with zero forcing function of the similar transmitter according to the acquired channel information of different radio frequency reflector activating combination patterns, and completes the preprocessing of the transmitting signals based on the element weighting of the preprocessing matrix in the symbol sub-time slot of different radio frequency reflector activating combinations; and finally, the receiver respectively carries out maximum likelihood detection and suboptimal multi-stage detection based on received power sequencing on the signal observation. The invention can effectively reduce the realization cost of the joint spatial modulation of the transmitting and receiving ends and improve the reliability and the application flexibility of the joint spatial modulation of the transmitting and receiving ends; furthermore, there are inherent advantages of the invention in terms of signal transmission.

Description

Transmit-receive terminal combined spatial modulation transmission method enabled by radio frequency reflector
Technical Field
The invention belongs to the technical field of communication, in particular to a transmitting-receiving end combined spatial modulation transmission method enabled by a radio frequency reflector, which can be used for a 5G mobile communication MIMO communication system.
Background
The wireless Multiple-Input Multiple-Output (MIMO) technology has the advantages of expanding system capacity and increasing transmission rate, and has become one of the most widely applied technologies in modern communication systems. However, with the increasing of the antenna scale, the implementation cost and complexity of the MIMO system increase, and there are inherent technical defects such as inter-channel interference, inter-antenna synchronization, and multi-radio frequency link consumption.
The Spatial Modulation (SM) technique is a novel MIMO transmission technique, and can realize an ideal compromise between spatial multiplexing and spatial diversity by modulating and transmitting extra information bits with indexes of active antennas, and at the same time, overcome the inherent technical defects in the conventional MIMO. In each symbol transmission time slot, the SM-MIMO transmitter splits the information bits into two parts, one part of the information bits is used for modulating the information bits into baseband amplitude phase modulation symbols to be transmitted, and the other part of the information bits is used for activating the transmitting antennas corresponding to the indexes to transmit the baseband symbols. Based on the realization mechanism, the SM-MIMO better realizes the compromise between the system energy efficiency and the spectrum efficiency.
Different from SM, the core design idea of precoding assisted Spatial modulation psm (precoding assisted Spatial modulation) is to converge the energy of a transmitted signal to a certain receiving antenna to achieve the purpose of "activation" by using a transmitter precoding scheme, thereby realizing the purpose of encoding and transmitting additional information by using the index number of the receiving antenna. Based on the assistance of the transmitter precoding technology, the PSM-MIMO system can effectively reduce the detection complexity of a receiving end, can obtain the transmission diversity gain, and effectively improves the reliability of wireless transmission. However, conventional PSM-MIMO systems typically cannot achieve multiplexing gain as well as receive diversity gain.
For future communication requirements, when a large-scale MIMO system assisted by PSM is configured with a large number of transmitting antennas, the system cost caused by the precoding operation of the transmitted signal will be very significant, which is not beneficial to practical implementation. For this situation, designing a PSM based on transmit antenna subset selection can significantly reduce system implementation complexity while obtaining additional multiplexing gain. Further, a Joint Transmitter-Receiver Spatial Modulation (JSM) scheme is proposed, which is designed to utilize the index of the subset of transmit antennas to modulate and transmit the extra information, and the technical advantages of SM and PSM can be achieved by a single MIMO system at the same time. The existing JSM-MIMO system can simultaneously obtain the transmission diversity, the receiving diversity and the spatial multiplexing gain, but the configuration of a transmitting antenna and a receiving antenna is restricted, so that the application flexibility of JSM is limited to a certain extent.
Media-based Modulation (MBM) is a Modulation technique that uses a wireless channel to carry different information, and is implemented by including the transmitted information in the transmission medium and using the randomness and uniqueness of the channel to transmit different messages. In the MBM system, a radio frequency reflector is arranged around a transmitting antenna, and the radio frequency radiation characteristic between the transmitting antenna and a receiving antenna changes along with the change of the opening and closing state combination of the radio frequency reflector, so that the real-time channel state between a transmitter and a receiver is changed, and the modulation transmission of information in channels with different states is realized.
In the conventional transceiving end-associated spatial modulation system, during signal transmission, a transmitting end needs to activate multiple transmitting antennas for transmit diversity, and there is a strict limitation between the activated transmitting antenna patterns and the number of precoding receiving antennas, so that information is transmitted between multiple radio frequency links, the spectral efficiency and flexibility of the system are low, and additional hardware cost is increased. In addition, the transmitter zero forcing based preprocessing scheme brings low diversity gain, and therefore, the detection error performance of the receiver is to be improved.
Disclosure of Invention
The invention aims to provide a receiving and transmitting end combined spatial modulation transmission method based on a radio frequency reflector, aiming at overcoming the defects of the prior art, and solving the problems of high cost, limited adaptive range, low diversity gain order and the like of the conventional receiving and transmitting end combined spatial modulation hardware.
The basic idea for realizing the invention is as follows: a plurality of radio frequency reflectors with two modes of switches are arranged around a transmitting antenna, so that a series of mutually independent channels are created, and in each time slot, alternate null space beam forming preprocessing is carried out aiming at different channel states, so that corresponding preprocessing vectors are obtained, and therefore the error code performance of the system is reduced and the channel capacity of the system is improved.
In order to achieve the purpose, the technical scheme of the invention comprises the following steps:
1) setting a transmitter in a multi-input multi-output system to comprise M transmitting antennas, and a receiver provided with N receiving antennas, wherein L radio frequency reflectors are respectively arranged on each transmitting antenna of the transmitter;
2) calculating the number U of the types of the radio frequency reflector activation patterns associated with each transmitting antenna:
U＝2L；
3) setting the number L of radio frequency reflectors to be more than or equal to log2(N-D), and M, N-D and D are both non-negative integer powers of 2; d is the number of receiving antennas for realizing receiving diversity enhancement, and the receiver uses front N-D antennas to realize receiving of precoding space modulation symbols;
4) in a time division duplex communication mode, a receiver sends pilot frequency information for channel estimation to a transmitter, and the transmitter completes the estimation of equivalent combined channels between the ith transmitting antenna and N receiving antennas by controlling the opening and closing of radio frequency reflectors of different transmitting antennas to obtain channel state information Wi：
Figure BDA0002605060350000031
Wherein, i belongs to {1,2, …, M };
5) in each transmission timeslot, the transmitter divides the information bits to be transmitted into three parts:
the first part is a transmitting space bit and is used for selecting and activating one transmitting antenna in the M transmitting antennas;
the second part is a symbol modulation bit used for mapping to obtain an amplitude phase modulation symbol set, and the order of each phase modulation symbol in the set is recorded as MmAnd M ism＝2n；
The third part is a receiving space bit and is used for selecting and activating one antenna in the front N-D receiving antennas to realize symbol receiving;
6) the transmitter utilizes the channel state information W obtained in the step 4)iObtaining an alternating null-space beamforming pre-processing vector tij；
6.1) removing channel State information WiJ row in (1), obtaining a channel matrix
Figure BDA0002605060350000032
Figure BDA0002605060350000033
Wherein j ∈ {1, 2., N-D }, [ · is]TRepresenting a transpose operation;
6.2) channel matrix pair
Figure BDA0002605060350000034
Singular value decomposition is carried out to obtain a channel matrix
Figure BDA0002605060350000035
Post v ═ U-N + D +1 column matrix of right singular vector matrix
Figure BDA0002605060350000036
6.3) obtaining the received signal power correction factor eta by an alternate null-space beam forming preprocessing operationij：
Figure BDA0002605060350000037
Wherein, betaiRepresenting a received signal power normalization factor, | · |, non-woven phosphor-1Representing the euclidean norm;
6.4) computing an alternate null-space beamforming pre-processing vector tij：
Figure BDA0002605060350000041
Wherein 1 isvRepresents a full one vector of length v;
7) modulating each M in the symbol set with amplitude and phasemThe sending time slot of the order amplitude phase modulation symbol is averagely divided into U sub-symbol sending time slots, in the U ∈ {1, 2., U } sub-symbol sending time slot, the activated ith transmitting antenna is opened and closed through a radio frequency reflector, and a preprocessing vector t is sent on the corresponding radio frequency reflector activation patternijMiddle u element ti,j,uThe weighted sub-symbols; setting the baseband symbol to be transmitted as the mth symbol q in the amplitude phase modulation symbol setmWherein M ═ {1,2, … MmIn the duration of the u-th subsymbol, the transmitter transmits a signal of
Figure BDA0002605060350000042
Figure BDA0002605060350000043
8) The front N-D antennas and the rest D antennas at the receiver end respectively receive the U sub-symbols to obtain received signals;
9) the receiver is based on the channel state information W shared by the transmitteriThe received signal is processed with maximum likelihood detection MLD meeting the requirement of system detection complexity and suboptimal multistage detection RPSD based on received power sequencing to obtain the detection symbol of the joint space modulation at the transmitting and receiving ends, and decoding is realized.
Compared with the prior art, the invention has the following advantages:
firstly, because the radio frequency reflector is adopted at the transmitting antenna end, the transmitting mode is formed by changing a plurality of antenna patterns into a single antenna, so that the inherent constraint of the number relation of the transmitting and receiving antennas in the transmitting pattern can be effectively deactivated;
secondly, as the invention adopts the alternate null-space beam forming pretreatment to the signal, the diversity gain of the receiving and transmitting end combined spatial modulation wireless communication system is obviously enhanced, thereby improving the detection performance of the receiver;
thirdly, because the invention provides a suboptimal multi-stage detection algorithm of received power sequencing in the aspect of detection, the detection of the received signals is carried out in stages, thereby effectively reducing the complexity of detection.
Drawings
FIG. 1 is a flow chart of an implementation of the method of the present invention;
FIG. 2 is a system diagram of the message routing process of the present invention;
FIG. 3 is a graph comparing bit error rate BER simulation results for the present invention and a conventional preprocessing scheme;
FIG. 4 is a comparison graph of bit error rate BER simulation results of a suboptimal multistage detection algorithm based on received power sequencing and an existing conventional detection algorithm in the invention;
fig. 5 is a comparison diagram of simulation results of achievable capacity and capacity approximation of the MLD detection system of multicast listeners employed in the present invention.
Detailed Description
The invention is described in detail below with reference to the attached drawing figures:
the communication system model adopted by the method comprises the following steps: a transmitter, a radio frequency mirror, and a receiver. The transmitter is provided with M antennas and L radio frequency reflectors are arranged near each antenna, the receiver is provided with N receiving antennas, wherein the first N-D receiving antennas are used for coding transmission information, the remaining D redundant receiving antennas are used for acquiring receiving diversity, the number of the antennas meets the condition that M and N-D are nonnegative integer powers of 2, and the pattern U of the radio frequency reflector near each transmitting antenna is 2L＞N-D。
As shown in fig. 2, the transmitter is provided with M antennas, L rf mirrors are provided around each antenna, and only one rf link is connected to the transmitting antenna; in each transmission time slot, the transmitter divides the input information bits into three parts, the first part is called transmission space bits and is used for selecting one transmission antenna from M transmission antennas, and the second part is called modulation bits and is used for mapping to MmAn order amplitude phase modulation symbol; the third part is called receiving space bit and is used for activating one antenna in receiving antennas N-D to receive APM symbolNumber; the transmitter then transmits information to the receiver in each time slot.
Referring to fig. 1, the present invention provides a transmit-receive end combined spatial modulation transmission method enabled by a radio frequency reflector, which includes the following steps:
step 1: the transmitter in the mimo system includes M transmitting antennas, the receiver is equipped with N receiving antennas, and L rf mirrors are respectively disposed on each transmitting antenna of the transmitter, and the rf mirrors can change the open/close states, and different open/close states correspond to mutually independent fading channels, that is, the transmitter activates one transmitting antenna for transmitting information.
Step 2: calculating the number U of the types of the radio frequency reflector activation patterns associated with each transmitting antenna:
U＝2L；
and step 3: setting the number L of radio frequency reflectors to be more than or equal to log2(N-D), and M, N-D and D are both non-negative integer powers of 2; d is the number of receiving antennas for realizing receiving diversity enhancement, and the receiver uses front N-D antennas to realize receiving of precoding space modulation symbols;
and 4, step 4: in a time division duplex communication mode, before preprocessing alternate null-space beam forming, a transmitter firstly sends transmitting signal request information and pilot frequency sequence information to a receiver; the receiver sends pilot frequency information for channel estimation to the transmitter by using pre-shared pilot frequency sequence information, the transmitter completes the estimation of equivalent combined channels between the ith transmitting antenna and the N receiving antennas by controlling the opening and closing of radio frequency reflectors of different transmitting antennas, and channel state information W is obtainedi：
Figure BDA0002605060350000061
Wherein, i belongs to {1,2, …, M };
and 5: in each transmission timeslot, the transmitter divides the information bits to be transmitted into three parts:
the first part is a transmitting space bit and is used for selecting and activating one transmitting antenna in the M transmitting antennas;
the second part is a symbol modulation bit used for mapping to obtain an amplitude phase modulation symbol set, and the order of each phase modulation symbol in the set is recorded as MmAnd M ism＝2n；
The third part is a receiving space bit and is used for selecting and activating one antenna in the front N-D receiving antennas to realize symbol receiving; one antenna of the first N-D receiving antennas is selected and activated to output the largest signal power, and the signal power leakage on the other N-D-1 receiving antennas is minimized.
Step 6: after finishing estimating the channel information, the transmitter utilizes the channel state information W obtained in step 4)iObtaining an alternating null-space beamforming pre-processing vector tij：
6.1) removing channel State information WiJ row in (1), obtaining a channel matrix
Figure BDA0002605060350000062
Figure BDA0002605060350000063
Wherein j ∈ {1, 2., N-D }, [ · is]TRepresenting a transpose operation;
6.2) channel matrix pair
Figure BDA0002605060350000071
Singular value decomposition is carried out to obtain a channel matrix
Figure BDA0002605060350000072
Post v ═ U-N + D +1 column matrix of right singular vector matrix
Figure BDA0002605060350000073
For channel matrix
Figure BDA0002605060350000074
Performing singular value decomposition according to the following formula:
Figure BDA0002605060350000075
wherein [ ·]HRepresents a conjugate transpose operation;
Figure BDA0002605060350000076
is a channel matrix
Figure BDA0002605060350000077
The rear v ═ U-N + D +1 column of the right singular vector matrix, and
Figure BDA0002605060350000078
wherein each column forms a channel matrix
Figure BDA0002605060350000079
A set of orthogonal bases of null space.
6.3) obtaining the received signal power correction factor eta by an alternate null-space beam forming preprocessing operationij：
Figure BDA00026050603500000710
Wherein, betaiRepresenting a received signal power normalization factor, | · |, non-woven phosphor-1Representing the euclidean norm;
received signal power normalization factor betaiCalculated according to the following formula:
Figure BDA00026050603500000711
wherein Tr [. cndot. ] represents the trace of the matrix.
6.4) computing an alternate null-space beamforming pre-processing vector tij：
Figure BDA00026050603500000712
Wherein 1 isvRepresents a full one vector of length v;
and 7: modulating each M in the symbol set with amplitude and phasemThe sending time slot of the order amplitude phase modulation symbol is averagely divided into U sub-symbol sending time slots, in the U ∈ {1, 2., U } sub-symbol sending time slot, the activated ith transmitting antenna is opened and closed through a radio frequency reflector, and a preprocessing vector t is sent on the corresponding radio frequency reflector activation patternijMiddle u element ti,j,uThe weighted sub-symbols; setting the baseband symbol to be transmitted as the mth symbol q in the amplitude phase modulation symbol setmWherein M ═ {1,2, … MmIn the duration of the u-th subsymbol, the transmitter transmits a signal of
Figure BDA00026050603500000713
Figure BDA00026050603500000714
And 8: the front N-D antennas and the rest D antennas at the receiver end respectively receive the U sub-symbols to obtain received signals; the received signal includes two parts: received signal vector r of N-D antennas before transmitter to receiverpReceived signal vector r from transmitter to remaining D antennasd；
Figure BDA0002605060350000081
Figure BDA0002605060350000082
Wherein the content of the first and second substances,
Figure BDA0002605060350000083
activation pattern of u-th radio frequency mirror representing ith transmitting antenna to first N-DThe channel vector of the receiving antenna(s),
Figure BDA0002605060350000084
a channel vector representing the activation pattern of the u-th rf mirror for the ith transmit antenna to the remaining D receive antennas; n ispAnd ndRespectively carrying out zero-mean circularly symmetric complex Gaussian vectors of accumulated received noise at the front N-D receiving antennas and the rest D receiving antennas in the U sub-symbol transmitting time slots;
Figure BDA0002605060350000085
representing equivalent joint channels of U radio frequency reflector activation patterns corresponding to the front N-D receiving antennas;
Figure BDA0002605060350000086
representing equivalent joint channels of U radio frequency reflector activation patterns corresponding to the remaining D receiving antennas;
Figure BDA0002605060350000087
representing a pre-processing vector t based on alternating null-space beamformingijThe resulting transmitter pre-processing matrix.
And step 9: the receiver is based on the channel state information W shared by the transmitteriThe received signal is processed with maximum likelihood detection MLD meeting the requirement of system detection complexity and suboptimal multistage detection RPSD based on received power sequencing to obtain the detection symbol of the joint space modulation at the transmitting and receiving ends, and decoding is realized.
According to the received signal in step 8 and the channel information shared by the transmitter, the receiver end completes the joint spatial modulation symbol detection of the transmitting and receiving end which meets the design requirement of the system complexity: after an alternative zero space beam forming preprocessing matrix is obtained by utilizing signal information, an MLD algorithm is carried out on a received signal, and r is obtainedpAnd rdBy combining, the observation vector of N received signals of the receiver can be obtained
Figure BDA0002605060350000091
Wherein
Figure BDA0002605060350000092
According to the maximum likelihood detection algorithm:
Figure BDA0002605060350000093
wherein I ═ 1, 2., M }, J ═ 1, 2., (N-D) }, M ═ 1, 2., M ═q}. Therefore, joint detection of the transmitted spatial bits, the received spatial bits and the modulation symbol bits can be realized;
performing a suboptimal multistage detection RPSD algorithm based on received power sequencing on received signal observation: the received spatial bits are first detected, and then the transmitted spatial bits, the modulation symbol bits, are jointly detected. From rj＝λijqm+nj，rτ＝nττ ∈ {1, 2., (N-D) }, τ ≠ j, where τ ≠ j
Figure BDA0002605060350000094
rτAnd nτRespectively represent rpAnd npTo (1) aτAnd (6) rows. The joint spatial modulation symbol detection of the transmitting and receiving ends realized by adopting RPSD can be described as follows step by step:
Figure BDA0002605060350000095
Figure BDA0002605060350000096
the invention can improve the detection performance of the system by adopting an alternative null-space beam forming scheme. To set M to 2, L to 2, N ∈ {2,3,4,6}, MmFor example, fig. 2 illustrates MLD detection with redundancy when implemented using transmitter zero-forcing pre-processing and alternating zero-space beamforming pre-processing to assist the transceiver-side joint spatial modulation system, respectivelyBER performance curve with increasing number of antennas D. As can be seen from fig. 3, the alternative null-space beamforming pre-processing scheme can provide higher diversity gain, and the BER performance advantage of the corresponding system is more obvious.
In the step 9, the received signal is detected by using a maximum likelihood detection algorithm and a suboptimal multi-stage detection algorithm based on the received power sorting. To set M to 2, L to 2, N to {2,4}, MmFor example, 4(4-QAM), fig. 3 depicts BER performance comparison curves of systems using different complexity detection algorithms when the number of redundant antennas configured in the system is D ∈ {0,2 }. The result proves that in a high signal-to-noise ratio region, detection algorithms with different complexities can realize reliable receiving of the spatial modulation symbols combined at the transmitting and receiving ends, and the difference between the detection performances can be basically ignored.
To set M to 2, L to 2, N ∈ {2,4,6}, MmFig. 4 depicts the ergodic achievable capacity and capacity approximation performance curves of the system under the assumption of signal input and different parameters, for example 4 (4-QAM). Compared with the conventional transceiver-end joint spatial modulation, the results in the figure further show that the transceiver-end joint spatial modulation enabled by the radio frequency reflector can obtain more remarkable performance gain, and can be flexibly configured and realized at low cost.
The effects of the invention can be further illustrated by simulation:
A. simulation conditions
Using matlab simulation tool to simulate, assuming that the information is under rayleigh flat fading channel, the transmitter obtains all channel state information, and the specific simulation parameters are set as follows:
simulation 1: setting M to 2, L to 2, N ∈ {2,3,4,6}, Mm＝4(4-QAM)；
Simulation 2: setting M to 2, L to 2, N ∈ {2,4}, Mm＝4(4-QAM)；
Simulation 3: setting M to 2, L to 2, N ∈ {2,4,6}, Mm＝4(4-QAM)。
B. Emulated content
Simulation 1: the simulation comparison curve of the maximum likelihood detection bit error rate of the system under the pre-processing of the forced zero of the transmitter and the pre-processing of the alternate zero space beam forming, and the simulation result is shown in fig. 3;
simulation 2: bit error rate simulation comparison curves of a maximum likelihood detection algorithm under the zero forcing pretreatment and the alternate zero space beam forming pretreatment of the transmitter and a suboptimal multistage detection algorithm system based on received power sequencing are shown in the figure 4;
simulation 3: the achievable capacity and capacity based on the alternating null-space beamforming pre-processing system approximate the simulation contrast curve, and the simulation result is shown in fig. 5.
C. Simulation result
As can be seen from fig. 3, as the average signal-to-noise ratio per bit increases, the bit error rate of the rf mirror-enabled transceiver-end combined with the spatial modulation system gradually decreases. The bit error performance of the alternate null-space beamforming based preprocessing system can be significantly improved compared to transmitter zero forcing preprocessing.
As can be seen from fig. 4, when D is increased to 2, the sub-optimal multi-stage detection algorithm based on the received power ordering has worse bit error rate performance than MLD in the low to medium snr region, and reaches convergence in the high snr region. Therefore, the proposed suboptimal multi-stage detection algorithm of received power ordering can achieve low complexity detection and can replace the maximum likelihood detection scheme in the high signal-to-noise ratio region.
As can be seen from fig. 5, as the average signal-to-noise ratio per bit increases, the achievable capacity of the system gradually increases and reaches the upper limit, the achievable capacity of the system and the capacity approximation are both tight and the capacity approximation becomes more stringent as D increases from 0 to 2.
The simulation analysis proves the correctness and the effectiveness of the method provided by the invention.
The invention has not been described in detail in part of the common general knowledge of those skilled in the art.
While the invention has been particularly shown and described with reference to a preferred embodiment, it will be understood by those skilled in the art that various changes in form and detail may be made therein without departing from the spirit and scope of the invention.

Claims (6)

1. A radio frequency reflector enabled transceiving end combined spatial modulation transmission method is characterized by comprising the following steps:
1) setting a transmitter in a multi-input multi-output system to comprise M transmitting antennas, and a receiver provided with N receiving antennas, wherein L radio frequency reflectors are respectively arranged on each transmitting antenna of the transmitter;
2) calculating the number U of the types of the radio frequency reflector activation patterns associated with each transmitting antenna:
U＝2L；
3) setting the number L of radio frequency reflectors to be more than or equal to log2(N-D), and M, N-D and D are both non-negative integer powers of 2; d is the number of receiving antennas for realizing receiving diversity enhancement, and the receiver uses front N-D antennas to realize receiving of precoding space modulation symbols;
4) in a time division duplex communication mode, a receiver sends pilot frequency information for channel estimation to a transmitter, and the transmitter completes the estimation of equivalent combined channels between the ith transmitting antenna and N receiving antennas by controlling the opening and closing of radio frequency reflectors of different transmitting antennas to obtain channel state information Wi：
Figure FDA0003040189110000011
Wherein, i belongs to {1,2, …, M };
5) in each transmission timeslot, the transmitter divides the information bits to be transmitted into three parts:
the first part is a transmitting space bit and is used for selecting and activating one transmitting antenna in the M transmitting antennas;
the second part is a symbol modulation bit used for mapping to obtain an amplitude phase modulation symbol set, and the order of each phase modulation symbol in the set is recorded as MmAnd M ism＝2n；
The third part is a receiving space bit and is used for selecting and activating one antenna in the front N-D receiving antennas to realize symbol receiving;
6) the transmitter utilizes the channel state information W obtained in the step 4)iObtaining an alternating null-space beamforming pre-processing vector tij；
6.1) removing channel State information WiJ row in (1), obtaining a channel matrix
Figure FDA0003040189110000012
Figure FDA0003040189110000021
Wherein j ∈ {1, 2., N-D }, [ · is]TRepresenting a transpose operation;
6.2) channel matrix pair
Figure FDA0003040189110000022
Singular value decomposition is carried out to obtain a channel matrix
Figure FDA0003040189110000023
Post v ═ U-N + D +1 column matrix of right singular vector matrix
Figure FDA0003040189110000024
6.3) obtaining the received signal power correction factor eta by an alternate null-space beam forming preprocessing operationij：
Figure FDA0003040189110000025
Wherein, betaiRepresenting a received signal power normalization factor, | · |, non-woven phosphor-1Representing the euclidean norm;
6.4) computing an alternate null-space beamforming pre-processing vector tij：
Figure FDA0003040189110000026
Wherein 1 isvRepresents a full one vector of length v;
7) modulating each M in the symbol set with amplitude and phasemThe sending time slot of the order amplitude phase modulation symbol is averagely divided into U sub-symbol sending time slots, in the U ∈ {1, 2., U } sub-symbol sending time slot, the activated ith transmitting antenna is opened and closed through a radio frequency reflector, and a preprocessing vector t is sent on the corresponding radio frequency reflector activation patternijMiddle u element ti,j,uThe weighted sub-symbols; setting the baseband symbol to be transmitted as the mth symbol q in the amplitude phase modulation symbol setmWherein M ═ {1,2, … MmIn the duration of the u-th subsymbol, the transmitter transmits a signal of
Figure FDA0003040189110000027
Figure FDA0003040189110000028
8) The front N-D antennas and the rest D antennas at the receiver end respectively receive the U sub-symbols to obtain received signals;
9) the receiver is based on the channel state information W shared by the transmitteriThe received signal is processed with maximum likelihood detection MLD meeting the requirement of system detection complexity and suboptimal multistage detection RPSD based on received power sequencing to obtain the detection symbol of the joint space modulation at the transmitting and receiving ends, and decoding is realized.
2. The rf mirror enabled transceiving end-associated spatial modulation transmission method according to claim 1, wherein: the radio frequency reflector in step 1) can change the open-close state, and different open-close states correspond to mutually independent fading channels, namely, a transmitter activates a transmitting antenna for transmitting information.
3. The rf mirror enabled transceiving end-associated spatial modulation transmission method according to claim 1, wherein: in the step 5), one antenna in the front N-D receiving antennas is selected and activated to output the maximum signal power, and the signal power leakage on the rest N-D-1 receiving antennas is minimized.
4. The rf mirror enabled transceiving end-associated spatial modulation transmission method according to claim 1, wherein: to the channel matrix in step 6.2)
Figure FDA0003040189110000031
Performing singular value decomposition according to the following formula:
Figure FDA0003040189110000032
wherein [ ·]HRepresents a conjugate transpose operation;
Figure FDA0003040189110000033
is a channel matrix
Figure FDA0003040189110000034
The rear v ═ U-N + D +1 column of the right singular vector matrix, and
Figure FDA0003040189110000035
wherein each column forms a channel matrix
Figure FDA0003040189110000036
A set of orthogonal bases of null space.
5. The rf mirror enabled transceiving end-associated spatial modulation transmission method according to claim 1, wherein: normalization factor beta of received signal power in step 6.3)iCalculated according to the following formulaTo:
Figure FDA0003040189110000037
wherein Tr [. cndot. ] represents the trace of the matrix.
6. The rf mirror enabled transceiving end-associated spatial modulation transmission method according to claim 1, wherein: the received signal in step 8) comprises two parts: received signal vector r of N-D antennas before transmitter to receiverpReceived signal vector r from transmitter to remaining D antennasd；
Figure FDA0003040189110000041
Figure FDA0003040189110000042
Wherein the content of the first and second substances,
Figure FDA0003040189110000043
a channel vector representing the activation pattern of the u-th rf mirror for the ith transmit antenna to the first N-D receive antennas,
Figure FDA0003040189110000044
a channel vector representing the activation pattern of the u-th rf mirror for the ith transmit antenna to the remaining D receive antennas; n ispAnd ndRespectively carrying out zero-mean circularly symmetric complex Gaussian vectors of accumulated received noise at the front N-D receiving antennas and the rest D receiving antennas in the U sub-symbol transmitting time slots;
Figure FDA0003040189110000045
activation diagram for representing U radio frequency reflectors corresponding to front N-D receiving antennasAn equivalent joint channel of cases;
Figure FDA0003040189110000046
representing equivalent joint channels of U radio frequency reflector activation patterns corresponding to the remaining D receiving antennas;
Figure FDA0003040189110000047
representing a pre-processing vector t based on alternating null-space beamformingijThe resulting transmitter pre-processing matrix.
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