CN108155479B - Microwave antenna array communication system and communication method - Google Patents
Microwave antenna array communication system and communication method Download PDFInfo
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Abstract
In the microwave antenna array communication system and the communication method provided by the embodiment of the invention, the phased array antenna array replaces the existing double-sided bipolar antenna, each horizontal polarization radio frequency signal transmission device in the microwave transmission device is directly connected with each sub-array in the corresponding horizontal polarization antenna array in the phased array antenna array respectively so as to send a horizontal polarization radio frequency signal to the opposite terminal, and each vertical polarization radio frequency signal transmission device is connected with each sub-array in the corresponding vertical polarization antenna array respectively so as to send a vertical polarization radio frequency signal to the opposite terminal; the phase shifters of the horizontal polarization antenna array and the vertical polarization antenna array are directly controlled by the controller of the phased array antenna array to configure the phase shifters, so that the physical distance and the installation accuracy between the antenna arrays are not depended on, the cost and the installation difficulty can be reduced, and the reliability can be improved.
Description
Technical Field
The present invention relates to the field of microwave communications, and in particular, to a microwave antenna array communication system and a communication method.
Background
Nowadays, the demand for wireless data transmission is rapidly increasing, and wireless communication technology is rapidly developing. Several approaches that are currently in common use to increase the transmission capacity and transmission rate of wireless communication systems are frequency diversity, space diversity and the use of polarized antennas. In order to explain the technical background of the present solution, a microwave LoS MIMO system is taken as an example for explanation.
The microwave transmission has the advantages of high speed, high stability, less land resource occupation and the like. The microwave transmission generally adopts line of Sight (Light of Sight, abbreviated as LoS). The microwave spatial multiplexing mainly adopts a multi-antenna technology (also called a Multiple Input Multiple Output technology, abbreviated as MIMO in english), and is different from general MIMO, and the multi-antenna technology of the microwave system is called LoS MIMO (Line of Sight MIMO, abbreviated as LoS MIMO). LoS MIMO technology greatly improves system throughput under the existing bandwidth. Most manufacturers currently do 2x2 LoS MIMO (here, 2x2 can be understood as a broad monopole antenna array, and 4x 4MIMO in the narrow sense of a dipole antenna array). With the enhancement of technology, 4x4 (8 x8MIMO in the narrow sense of a dipole antenna array) to NxN LoS MIMO is increasingly applied.
The transmission capacity C of the MIMO system obtained according to Shannon's theorem is:
in the above formula (1): p is the signal-to-noise ratio at the receiving side, H' is a normalized matrix of channel transmission characteristics,
is nROrder unit array (.)HRepresenting the Hermitian transformation. The maximum equivalent of the transmission capacity of the system is maximized H'HThe determinant of (1) is that under the condition of the maximum capacity of the system, a channel matrix needs to meet a Van der Monte matrix, and the maximum transmission capacity can be ensured by any unitary transformation of the channel matrix. Taking 2x2 microwave LoS MIMO as an example, the channel matrix vandermonde is expressed as:
using two unitary transforms yields:
for the 2x2 MIMO description, any Tx will transmit a corresponding Tx signal to one receiving end Rx of the opposite end, and transmit a Tx signal with a phase delay of 90 ° to the other receiving end Rx. For example, referring to fig. 1, the Tx1 transmits Tx signals and Tx 'signals to the Rx1 and Rx2, respectively, at the same time, the Tx' signals being phase-delayed by 90 ° with respect to the Tx signals. Generalizing to other NxN LoS MIMO, in the process of maximizing link transmission capacity, the layout space requirements between the transmit-receive antennas are finally met, or taking 2x2 LoS MIMO in fig. 1 as an example, under the condition of a known communication distance D, h is accurately measured and antenna layout is performed, so as to determine a corresponding phase shift angle, where the corresponding relationship between h and D is as follows:
in the formula (2), λ is a wavelength. The conventional dipole antenna array implements 2x2 LoS MIMO in fig. 1 corresponding to 4x 4MIMO in a narrow sense, and the architecture of the conventional dipole array 4x 4MIMO design is shown in fig. 2-1 and fig. 2-2. In fig. 2-1 and 2-2, Site 1(Site1) and Site 2(Site2) are one-hop 4x 4MIMO links, Site1 is taken as an example, and H0, V0, H1 and V1 respectively represent four microwave transmission devices (H represents that the devices are connected to a horizontally polarized antenna and V represents that the devices are connected to a vertically polarized antenna), which all work at the same radio frequency points, H0 and V0 form a Cross-polarization Interference canceller (Cross-polarization Interference canceller), which corresponds to TX1 in fig. 1, and both of the devices are connected to an OMT (Orth-Mode transmitter, direct transceiver), and then connected to a dual-polarization antenna, which is installed on a tower shown in fig. 2-2, and is deployed in a high/low station manner, and the antenna spacing H satisfies the requirement in the above equation (2). Wherein H1 and V1 form another XPIC group (corresponding to TX2 in fig. 1), the connection mode is similar, and finally the two XPIC working groups are combined to form a 4x 4MIMO working group, and the state of Site2 is similar, and when the microwave device adopts FDD (Frequency Division duplex) working mode, it can be known that the transceiving frequencies of Site1 and Site2 are reciprocal. It can be known that in order to meet the requirement of normal operation of microwave 4x 4MIMO transmission, the center distance between two dual-polarized antennas at the Site1 side needs to satisfy the requirement of formula (2), and when the antenna is actually deployed, the requirement of MIMO station distribution is fully considered on iron towers (holding poles) at the Site1 side and the Site2 side, and after accurate measurement and calculation, the two-sided dual-polarized antennas are correctly installed at a proper distance. The antenna mounting structure has requirements on the structure and height of an iron tower (holding pole) for mounting the antenna, improves the cost of a communication system, is influenced by factors such as distance measurement accuracy and antenna mounting accuracy, has great influence on the performance of the antenna, causes poor reliability, and even cannot achieve the declared advantages of the MIMO antenna.
Disclosure of Invention
The embodiment of the invention provides a microwave antenna array communication system and a communication method, which solve the problems of high cost, high installation safety and poor reliability caused by hard requirements of the existing microwave antenna array on the installation physical distance and the installation precision between dual-polarized antennas.
An embodiment of the present invention provides a microwave antenna array communication system, including: the method comprises the steps that a phased array antenna array and microwave transmission equipment are adopted, wherein N is a bipolar antenna array order with the value larger than or equal to 4;
the phased array antenna array comprises a controller and a pair of polarized antenna arrays which correspond to the pair of microwave transmission devices one by one;
the horizontal polarization radio frequency signal transmission equipment in the microwave transmission equipment is connected with the antenna sub-arrays of the horizontal polarization antenna arrays in the corresponding polarization antenna arrays to send horizontal polarization radio frequency signals to an opposite terminal, and the vertical polarization radio frequency signal transmission equipment is connected with the antenna sub-arrays of the vertical polarization antenna arrays in the polarization antenna arrays to send vertical polarization radio frequency signals to the opposite terminal;
the controller is configured to configure, through the phase shifter of each antenna sub-array in the horizontally polarized antenna array, a phase of a horizontally polarized radio frequency signal transmitted by each antenna sub-array, and configured to configure, through the phase shifter of each antenna sub-array in the vertically polarized antenna array, a phase of a vertically polarized radio frequency signal transmitted by each antenna sub-array.
An embodiment of the present invention further provides a communication method of the microwave antenna array communication system, including:
the controller controls the phase shifters of the antenna sub-arrays of the horizontal polarization antenna array to configure the phases of the horizontal polarization radio frequency signals transmitted by the antenna sub-arrays, and controls the phase shifters of the antenna sub-arrays of the vertical polarization antenna array to configure the phases of the vertical polarization radio frequency signals transmitted by the antenna sub-arrays;
the horizontally polarized radio frequency signal transmission equipment in the microwave transmission equipment sends the signals to the opposite terminal through each antenna subarray in the corresponding horizontally polarized antenna array
A horizontally polarized RF signal and a vertically polarized RF signal transmission device for transmitting to the opposite terminal via each antenna sub-array in the corresponding vertically polarized antenna array
A vertically polarized radio frequency signal.
Has the advantages that:
according to the microwave antenna array communication system and the communication method provided by the embodiment of the invention, the phased array antenna array replaces the conventional double-sided bipolar antenna, and each horizontal polarization radio frequency signal transmission device in the microwave transmission device is directly connected with each antenna sub-array in the corresponding horizontal polarization antenna array in the phased array antenna array so as to send the signals to the opposite terminal
Each horizontal polarization radio frequency signal transmission device is respectively connected with each antenna subarray in the corresponding vertical polarization antenna array to transmit the horizontal polarization radio frequency signals to the opposite terminal
A vertically polarized radio frequency signal; for a horizontally polarized antenna array and a vertically polarized antenna array
The phase shifters of the antenna sub-arrays of the horizontal polarization antenna array and the antenna sub-arrays of the vertical polarization antenna array are directly controlled to be configured through the controller of the phased array antenna array without depending on physical distance and installation accuracy between the antenna arrays, so that the reliability of the antenna performance is improved while the engineering cost and the installation difficulty are reduced, the antenna has the advantages of an MIMO antenna as much as possible, and the satisfaction degree of user communication experience is improved.
Drawings
Fig. 1 is a schematic diagram of a 2x2 LoS MIMO architecture;
FIG. 2-1 is a schematic diagram of a conventional dual-sided bipolar 4x 4MIMO architecture;
fig. 2-2 is a schematic diagram of a conventional double-faced bipolar 4x 4MIMO iron tower;
fig. 3 is a schematic radiation diagram of an antenna element according to a second embodiment of the present invention;
fig. 4 is a schematic diagram illustrating a phase shifter connection of an antenna element according to a second embodiment of the present invention;
fig. 5-1 is a schematic diagram of an NxN MIMO antenna array according to a second embodiment of the present invention;
fig. 5-2 is a schematic diagram of an NxN MIMO iron tower according to a second embodiment of the present invention;
fig. 6 is a schematic diagram of a 4x 4MIMO antenna array according to a second embodiment of the present invention;
fig. 7 is a schematic diagram of a structure of a middle antenna carrier plate according to a second embodiment of the present invention;
fig. 8 is a schematic diagram of the connection of the vertically polarized antenna array according to the second embodiment of the present invention;
fig. 9 is a schematic diagram of signals transmitted by the local-end vertical polarization antenna array according to the second embodiment of the present invention;
FIG. 10 is a schematic diagram of a phase control process according to a second embodiment of the present invention;
fig. 11 is a schematic diagram of 4x 4MIMO signal transmission according to a third embodiment of the present invention;
FIG. 12 is a schematic flow chart of phase closed-loop control according to a third embodiment of the present invention;
fig. 13 is a schematic diagram of a minimum phased array antenna array according to a fourth embodiment of the present invention;
fig. 14 is a schematic diagram of minimum phased array antenna array connection according to a fourth embodiment of the present invention.
Detailed Description
The following describes embodiments of the present invention in further detail with reference to the accompanying drawings.
The first embodiment is as follows:
the present embodiment provides a microwave dipole antenna array communication system, and it should be understood that the microwave dipole antenna array communication system in the present embodiment may be deployed at a transmitting end, may be deployed at a receiving end, or may be directly deployed at both ends of the transmitting end and the receiving end. In the FDD mode, the transmitting end and the receiving end are opposite, that is, when the transmitting end transmits a radio frequency signal to the opposite end, the transmitting end also serves as the receiving end to receive the radio frequency signal transmitted from the opposite end. Therefore, the present embodiment is exemplified by replacing the transmitting end and the receiving end with the home end and the opposite end (which may also be referred to as a far end). The microwave dipole antenna array communication system in this embodiment may be correspondingly deployed at the local end and the opposite end at the same time.
The microwave dual-polar antenna array communication system in the embodiment comprises a phased array antenna array and
for microwave transmission equipment, wherein N is the order of the bipolar antenna array with the value of more than or equal to 4; for example, if a 4 × 4MIMO dipole antenna array is implemented, N is 4, if an 8 × 8MIMO dipole antenna array is implemented, N is taken to be 8, and so on.
The phased array antenna array in this embodiment includes a controller and
one-to-one correspondence to microwave transmission equipment
To a polarized antenna array. One pair of microwave transmission devices comprises a horizontal polarization radio frequency signal transmission device and a vertical polarization radio frequency signal transmission device; a pair of polarized antenna arrays comprising a first antenna array and a second antenna array
Horizontally polarized antenna array composed of antenna sub-arrays and antenna array composed of antenna sub-arrays
The antenna array comprises a vertical polarization antenna array formed by antenna subarrays, wherein each antenna subarray comprises at least one antenna vibration element and a phase shifter for controlling the phase of the antenna vibration element. It should be understood that in the present embodiment, among the antenna sub-arraysEach antenna element (also called radiation unit) can use one phase shifter independently, or a plurality of antenna elements can share one phase shifter, and can be flexibly set according to requirements. For example, one antenna sub-array is configured by a plurality of antenna elements, and each antenna element uses one phase shifter, that is, the antenna elements and the phase shifters correspond to each other one by one.
In this embodiment, each horizontally polarized radio frequency signal transmission device in each pair of microwave transmission devices is respectively connected to each antenna sub-array in the corresponding horizontally polarized antenna array to transmit the horizontally polarized radio frequency signal to the opposite end
Each vertical polarization radio frequency signal transmission device in each pair of microwave transmission devices is respectively connected with each antenna subarray in the corresponding vertical polarization antenna array to send the horizontal polarization radio frequency signals to the opposite end
A vertically polarized radio frequency signal.
The controller of the phased array antenna array is used for configuring the phase of the horizontally polarized radio frequency signal transmitted by each antenna sub-array of each horizontally polarized antenna array through the phase shifter of each antenna sub-array of each horizontally polarized antenna array, so that one horizontally polarized antenna array transmits the horizontally polarized radio frequency signal
The phase difference between the horizontally polarized radio frequency signals meets the requirement of the N-NMIMO bipolar antenna array; also for transmission by a vertically polarised antenna array
The phase difference between the vertically polarized radio-frequency signals is also configured by controlling the phase shifters of the antenna sub-arrays of the vertically polarized antenna array through the controller, so that the phase of the vertically polarized radio-frequency signal transmitted by one vertically polarized antenna array is configured
The phase difference between the vertically polarized radio frequency signals meets the requirements of the N-NMIMO dual-polar antenna array. For transmission from a vertically polarised antenna array
Phase difference between vertically polarized radio-frequency signals and transmission by a horizontally polarized antenna array
And determining the specific value of the phase difference between the horizontal polarization radio frequency signals according to the specific order of the N-by-N MIMO bipolar antenna array. The following is an example of a generalized monopole antenna array in conjunction with channel matrix vandermonde.
Generalized single-polarity antenna array NxN MIMO corresponds to:
the vandermonde array of a generalized 4x4 monopole antenna array (corresponding to a bipolar antenna array of 8x8MIMO) is as follows:
the following two unitary transformations are performed:
taking the first row as an example, assuming that the first row corresponds to the local and peer TX1 and RX1, 4 Txs are required for Rx1 to be in accordance with
The interval (i.e., phase difference) reaches the receiving antenna. Other high-order MIMO can be constructed continuously according to the method, for example, for the generalized unipolar antenna array NxN MIMO, the phase difference requirement is
Converted into a narrow-sense dual antenna array NxN MIMO, and the phase difference requirement is
Therefore, in this embodiment, for each horizontally polarized antenna array, the controller configures, through the phase shifter of each antenna sub-array of the horizontally polarized antenna array, the phase difference between horizontally polarized radio-frequency signals transmitted by adjacent antenna sub-arrays of the horizontally polarized antenna array to be
For each vertical polarization antenna array, the controller configures the phase difference of the vertical polarization radio frequency signals transmitted by the adjacent antenna sub-arrays of the vertical polarization antenna array to be
In the present embodiment, for the local end or the opposite end
For a polarized antenna array, this can be done
The polarized antenna array is arranged on one antenna bearing plate, so that the installation procedure can be simplified, and the installation efficiency is improved. This can also be adjusted according to the actual requirements
Each pair of polarized antenna arrays in the polarized antenna arrays are respectively arranged on an antenna bearingOn the support plate, the flexibility of antenna installation and application can be improved, and more application scenes can be met.
In this embodiment, the controller may control the phase of the radio frequency signal transmitted by each antenna sub-array of each of the flat polarization antenna arrays or the vertical polarization antenna arrays in an open-loop control manner, that is, may complete the configuration according to the above process. The phase difference is configured to be used for demodulating baseband digital signals in a Modem, so that only the local antenna and the remote antenna are considered in some cases
The requirement of phase difference may not reach the maximum gain of the system, because the phase difference is caused by the waveguide connector and the radio frequency cable used between the radio frequency unit of the microwave device and the phased array antenna array except the phase difference introduced between the antennas, and because the radio frequency transceiving channels are independent from each other, the maximum gain of the MIMO demodulation is ensured. The present embodiment may also perform phase difference adaptive adjustment through a feedback loop. Firstly, according to the above-mentioned process, the process is completed
Coarse adjustment of phase, i.e. ensuring that the corresponding flat polarized antenna array or vertical polarized antenna array between the local and remote antennas satisfies
Phase requirements, it is then expected that the system will be able to operate in MIMO mode. At this time, the controller is further configured to, after the phases of the horizontally polarized radio-frequency signals transmitted by the antenna sub-arrays of each horizontally polarized antenna array are configured according to the above requirements, obtain the receiving phase angle and the receiving phase angle of the horizontally polarized radio-frequency signal transmitted by the antenna sub-arrays of the horizontally polarized antenna array of the local terminal, which is received by the corresponding horizontally polarized antenna array of the opposite terminal
The difference between the two is judged to be larger than the deviation of the preset horizontal polarization phase angleAnd during the threshold value, adjusting the phase of the horizontally polarized radio-frequency signal transmitted by each antenna sub-array of the horizontally polarized antenna array according to the difference between the two values (the process is a phase difference fine adjustment process) until the difference between the two values is less than or equal to a preset horizontal phase angle deviation threshold value.
Similarly, the controller is further configured to, after the phase of the vertically polarized radio frequency signal transmitted by each antenna sub-array of each vertical polarized antenna array is configured according to the above process, obtain a receiving phase angle and a receiving phase angle of the vertical polarized radio frequency signal transmitted by each antenna sub-array of the local vertical polarized antenna array at the receiving end of the corresponding vertical polarized antenna array at the opposite end
And when the difference between the two values is larger than a preset vertical polarization phase angle deviation threshold value, adjusting the phase of the vertical polarization radio frequency signal transmitted by each antenna subarray of the vertical polarization antenna array according to the difference between the two values until the difference between the two values is smaller than or equal to the preset vertical phase angle deviation threshold value.
In this embodiment, the phase angle and
the difference can be calculated at the local end or at the opposite end, and the specific calculation method can adopt any existing method capable of obtaining the receiving phase angle according to the performance index of the receiving signal or directly obtaining the receiving phase angle and the receiving phase angle
The difference (i.e. the received phase angle error) is implemented in a manner that will not be described in detail herein.
The phase shifter in this embodiment may be a digital phase shifter of a discrete type, or may be an analog phase shifter of a non-discrete type. The controller may adopt a step-by-step adjustment mode during the fine adjustment process, and perform adjustment again after the opposite end updates its receiver MIMO performance index again, and if the performance index fed back by the far end reaches a certain threshold range, the adjustment is stopped, and the closed-loop phase adjustment process of the MIMO system is considered to be finished. Because the receiving and sending channels are reciprocal, after the adjustment of the local terminal is finished, the adjustment of the link from the default opposite terminal to the local terminal is also finished, and the MIMO system enters a long-term stable working state.
In this embodiment, for each horizontally polarized antenna array or vertically polarized antenna array, the controller may further adjust the transmission power of the antenna array before or after the phase configuration of the antenna array. The adjustment process is as follows:
for each horizontal polarization antenna array, acquiring the difference between the transmitting power of the horizontal polarization antenna array and the receiving power of the horizontal polarization antenna array corresponding to the opposite end and the path insertion loss to the opposite end as a horizontal polarization power difference value, and when the acquired horizontal polarization power difference value is greater than or equal to a preset horizontal polarization power difference threshold value, adjusting the main lobe radiation angle of the horizontal polarization antenna array until the horizontal polarization power difference value is less than or equal to the preset horizontal polarization power difference threshold value; of course, the transmit power of the horizontally polarized antenna array at the local end may also be directly adjusted to achieve the above-mentioned effect, or two adjustment manners may be used in combination, or the transmit power of the horizontally polarized antenna array may be adjusted from other aspects, as long as the above-mentioned effect is achieved.
For each vertical polarization antenna array, acquiring the difference between the transmitting power of the vertical polarization antenna array and the receiving power of the vertical polarization antenna array corresponding to the opposite end and the path insertion loss to the opposite end as a vertical polarization power difference value, and when the acquired vertical polarization power difference value is greater than or equal to a preset vertical polarization power difference threshold value, adjusting the main lobe radiation angle of the vertical polarization antenna array until the vertical polarization power difference value is less than or equal to the preset vertical polarization power difference threshold value; of course, the transmit power of the vertical polarization antenna array at the local end may also be directly adjusted to achieve the above-mentioned effect, or two adjustment methods may be used in combination, or the transmit power of the vertical polarization antenna array may be adjusted from other aspects, as long as the above-mentioned effect is achieved.
However, it should be understood that the above power adjustment process may be directly skipped when the initial power is already set, or may be adjusted in real time in the subsequent working process. In addition, the specific values of the various thresholds in this embodiment can be flexibly selected according to the requirements of the specific communication environment.
In this embodiment, the phased array antenna array directly replaces the existing dual-sided bipolar antenna, each horizontally polarized radio frequency signal transmission device in the microwave transmission device is respectively connected to each antenna sub-array in the corresponding horizontally polarized antenna array in the phased array antenna array to transmit a horizontally polarized radio frequency signal to the opposite terminal, and each vertically polarized radio frequency signal transmission device is respectively connected to each antenna sub-array in the corresponding vertically polarized antenna array to transmit a vertically polarized radio frequency signal to the opposite terminal; for the relationship between the phases of the radio-frequency signals sent by one horizontal polarization antenna array and one vertical polarization antenna array, the phase shifters of each antenna sub-array of the horizontal polarization antenna array and each antenna sub-array of the vertical polarization antenna array can be directly controlled by the controller of the phased array antenna array to be configured, and then corresponding signals are sent through the corresponding antenna sub-arrays of the horizontal polarization antenna array and the corresponding antenna sub-arrays of the vertical polarization antenna array. The reliability of the performance of the antenna can be improved while the engineering cost and the installation difficulty can be reduced, and the advantage of the MIMO antenna is ensured to be exerted by the antenna.
Example two:
for a better understanding of the present invention, the present embodiment is illustrated in conjunction with a specific implementation of a phased array antenna array.
The horizontal polarization antenna array and the vertical polarization antenna array of the phased array antenna array are generally defined to be composed of a group of independent antenna vibration elements, and the relative amplitude and phase relation can be ensured through related circuit design, so that the target of focusing and forming in a certain expected direction is realized, and the radiation energy of electric waves is greatly reduced (inhibited) in comparison with other directions. Any antenna element is independently and controllably uniformly distributed on a straight line, for example, as shown in fig. 3, the six antenna elements in the upper row are distributed on a straight line, the radiation sequence is that the antenna elements radiate from right to left in turn, and finally, a wave front with a phase angle can be formed, that is, the radiation main lobe angle can be adjusted by programming radiation delay. Therefore, the phased array antenna has the capability of adjusting the direction of the main radiation lobe.
One implementation of a horizontally polarized antenna array and one antenna sub-array of a vertically polarized antenna array is shown in fig. 4.
In fig. 4, the circle plus the arrow corresponds to the phase shifter, all antenna elements are non-directional, feed in phase with equal amplitude, the excitation current phase difference of adjacent antenna elements is psi, and the corresponding radiation direction angle is θ:
the vector sum of the field intensities of the radiation fields of the antenna elements at a certain point in the theta direction far zone is as follows:
E(θ)＝E0+E1+…+Ei+…+EN-1
assuming constant amplitude feeding, the radiation field strength of each antenna element at the position is characterized as follows (with the antenna element No. 0 in fig. 4 as a phase reference):
when in use
When (Ψ represents an observation angle relative to the antenna array), the components are added in phase, the field intensity radiation is maximized (the main lobe is maximized in this respect, that is, the main lobe direction is electrically controlled and adjusted):
|E(θ)|max＝NE
change of
According to the antenna receiving and transmitting reciprocity theorem, the receiving antenna also meets the corresponding conclusion. The method is popularized to a 2-dimensional planar array, and by adjusting the phase shift value of each feed source reaching the planar array,then a main lobe electro-controlled scan, such as in three dimensions of space, may be completed.
In this embodiment, a local terminal is taken as a station 1, and an opposite terminal is taken as a station 2 for example, please refer to fig. 5-1, and in fig. 5-1, microwave dual-polar antenna array communication systems are correspondingly arranged at the local terminal and the opposite terminal. In the figure, V0 and H0 form a pair of microwave transmission devices, wherein V0 is a horizontally polarized radio frequency signal transmission device, and H0 is a vertically polarized radio frequency signal transmission device. There are N pairs of microwave transmission devices at each end, V0+ H0, … …, VN + HN; n pairs of polarized antenna arrays are correspondingly disposed on the antenna carrier plate 1 at each end, and each pair of polarized antenna arrays is composed of a horizontally polarized antenna array 21 and a vertically polarized antenna array 20. The dual antenna array 2Nx2N MIMO is implemented in fig. 5-1. Corresponding to the 2Nx2N MIMO shown in fig. 5-1, the schematic diagram of iron tower installation is shown in fig. 5-2, the physical distance between the antennas during installation is not the same as the conventional double-sided polar antenna which must be accurately measured and installed, and the phase difference is mainly realized by phase shifter control, so that the practicability and reliability of the MIMO antenna system can be improved.
In fig. 5-1, the horizontally polarized antenna array completes the transceiving of the corresponding horizontally polarized radio frequency signal, and the vertically polarized antenna array completes the transceiving of the corresponding vertically polarized radio frequency signal, and for the vertical and horizontal relationship in the figure, for the ground plane, the geometric combination relationship of the corresponding array units needs to be designed according to the working frequency band, the antenna gain and the like in the practical implementation of the phased array, which is not necessarily the topology illustrated in fig. 5-1, and is only an illustration facilitating the description here. After the microwave transmission device shown in fig. 5-1 is connected to the corresponding vertical or horizontal polarized antenna array, the antenna bearing plate 1 is mounted on the iron tower (pole) through a bracket or a structural member, and a phase shifter and a controller are integrated in the antenna bearing plate 1, so that the phase adjustment and beam forming of the corresponding radiation beam can be completed through a corresponding algorithm or software, thereby meeting the requirement of LoS MIMO on the transmission channel matrix and finally realizing the improvement of transmission capacity and performance multiple.
Based on fig. 5-1, an example of implementing the dual-polarity antenna array 4x 4MIMO is described below. Referring to fig. 6, in fig. 6, two pairs of polarized antenna arrays are disposed on the antenna bearing plate 1 at two ends of the station 1 and the station 2, and two pairs of microwave transmission devices, V0+ H0 and V1+ H1, are disposed at two ends of the antenna bearing plate 1, wherein each pair of microwave transmission devices is connected to each polarized antenna array, as shown in fig. 6, V0 and V1 are connected to the corresponding vertical polarized antenna array 21, and H0 and H1 are connected to the corresponding horizontal polarized antenna array 20. Each of the horizontally polarized antenna array 21 and the vertically polarized antenna array 20 in fig. 6 contains 2 antenna sub-arrays.
Referring to fig. 7, the specific structure of the antenna carrier board 1 is shown, the black tiny rectangular module in fig. 7 represents an antenna oscillator (the antenna oscillator may specifically adopt various types of oscillators, for example, a low-cost FR4 (code of fire-resistant material grade) material PCB may be used to attach the antenna radiating oscillator), the two pairs of horizontal polarized antenna arrays 21 and vertical polarized antenna arrays 20 are respectively connected to V0, H0, V1, and H2, the horizontal polarized antenna arrays 21 and vertical polarized antenna arrays 20 both include two antenna sub-arrays, each oscillator of each antenna sub-array corresponds to a phase shifter (not shown in the figure), and each phase shifter is connected to the controller. The controller completes self-adaptive processing of radiation main lobes and power of 4 paths of signals, and specifically, corresponding setting of phases and gains of all radiation oscillator elements in any antenna array in the 4 paths of signals needs to be completed. Compared with the traditional double-sided polarized antenna array, the dual-polarized antenna has to be arranged on an iron tower (holding pole) by calculating the corresponding space distance interval according to the working frequency of equipment and the distance between one-hop microwave links through a corresponding theoretical formula. In the embodiment, the horizontal polarization antenna array 21 and the vertical polarization antenna array 20 are both already cured on the antenna carrier plate 1, the physical form is fixed, and the radio frequency signal distance relationship in the same polarization direction is also fixed, so that the remote pulling problem between antenna feeds can not be considered by using the phased array antenna array, and for different frequencies and communication distances, the MIMO transmission channel can be established by using an electrically tunable phased array. The MIMO transmission channel can be eliminated from the requirements of high difficulty and high precision in the installation of the traditional MIMO equipment, so that the MIMO can be deployed quickly, and after the related one-hop communication distance and frequency point are set to enter the equipment, the related phase shifting and MIMO transmission channel realization can be automatically carried out through the controller.
An exemplary implementation of each of the horizontally polarized antenna array 21 and the vertically polarized antenna array 20 is shown in fig. 8. Fig. 8 illustrates an implementation of the vertically polarized antenna array 20 as an example. The antenna elements in the two antenna sub-arrays 201 and 202 and the connection between the antenna elements and the phase shifter PS and the power divider are shown in fig. 8. The controller implements phase shift control and power control. The controller determines the corresponding phase shift value, and the power regulation module at the front stage completes the power control of each path of beam forming so as to realize
After the local end RF Tx Lo is divided, the local oscillator is provided to the antenna local oscillator of the lower half array after 90 ° phase shift. The implementation for the horizontally polarized antenna array 21 is the same as that shown in fig. 8.
Assuming that the RF operating band of the 4 × 4MIMO shown in fig. 6 is 15G band, and the one-hop communication distance is 5Km, taking the local station 1 as an example, referring to fig. 9, any one of the vertically polarized antenna arrays 21 is divided into two antenna sub-arrays with the same polarization, which are respectively an antenna sub-array with a radiation lobe 021 corresponding to the V0 path of the receiving array of the peer station 2 and an antenna sub-array with a radiation lobe 121 corresponding to the V1 path of the receiving array of the peer station 2. Opposite ends V0 and V1 are two groups of independent vertical polarization antenna array units, which are arranged and designed according to fixed positions in an integrated antenna, so that corresponding main lobe focusing and alignment can be realized by performing beam forming control on two antenna sub-arrays in a local end V0, and meanwhile, the most important 90-degree phase requirement of the maximum transmission capacity of the MIMO channel can also be set by performing automatic electric regulation in a phased array antenna array, wherein for example, a radiation lobe 021 is required to be ahead of the radiation lobe 12190 so as to meet the antenna spacing requirement in the traditional dual-polarization MIMO (the remaining H0, H1 and V1 at the local end are provided with two antenna sub-arrays, and the physical requirement of the lobe of the array corresponding to an opposite end site2 is consistent with the behavior relation of the V0), namely, the phase shifter in the phased array antenna array realizes the necessary working condition of the LoS MIMO with the phase difference of 90 degrees in the electric wave transmission path, which needs space to be realized in the traditional scheme, by placing the phase shifter And the phase-shifting relation can be adjusted and finely adjusted in real time according to the requirements of users, so that the LoS MIMO antenna engineering installation of the microwave equipment becomes the same simple work as the traditional single-polarization 1+0 single-polarization microwave. In this embodiment, the process of controlling the power and the phase of each of the horizontally polarized antenna array 20 and the vertically polarized antenna array 21 is shown in fig. 10, and includes:
s1001: setting a one-hop distance D between a home terminal and an opposite terminal and determining a frequency point F, acquiring transmission power Ptx (x can be selected from V0, H0, V1 and H1) corresponding to each polarized antenna array (two horizontal polarized antenna arrays 20 and vertical polarized antenna arrays 21 corresponding to V0, H0, V1 and H1) and path insertion loss Ld from the home terminal to the opposite terminal, and setting corresponding power difference thresholds (a horizontal polarized power difference threshold and a vertical polarized power difference threshold can be preset respectively corresponding to each horizontal polarized antenna array 20 and each vertical polarized antenna array 21, and the same power difference threshold can be used certainly);
s1002: obtaining the receiving power Prx (x can be selected from V0, H0, V1, and H1) corresponding to each polarized antenna array (two horizontally polarized antenna arrays 20 and vertically polarized antenna arrays 21 corresponding to V0, H0, V1, and H1) after the manual alignment of the opposite-end antenna is completed, where the step may be performed simultaneously with S1001;
s1003: judging whether Ptx-Ld-Prx is smaller than or equal to a power difference threshold value, if so, turning to S1005; otherwise, go to S1004;
s1004: adjusting the main lobe radiation angle of the polarized antenna array corresponding to the Ptx until the Ptx-Ld-Prx is less than or equal to a power difference threshold; go to S1005;
s1005: ending the current Ptx main lobe adjustment, traversing the next polarized antenna array and turning to S1003 until the traversal is finished;
s1006: phase shifters in the polarized antenna arrays are adjusted to ensure 90-degree phase shift between the sub-arrays of the receiving antennas opposite to each other.
So far, the one-hop 4x4 LoS MIMO completes the phased array antenna configuration of the local terminal, and similarly, the opposite terminal also completes the corresponding phased array antenna configuration, so as to ensure that each path of transmission signal of the local terminal meets the 90 ° phase difference requirement for constructing the maximum transmission channel after reaching the opposite terminal, then, the baseband MIMO processing function is started, and after the receiver system of the opposite terminal completes the baseband operation and processing of capturing, synchronizing and locking, the normal receiving and demodulation of each path of data are completed, thereby realizing the doubling of the transmission capacity. The processing mechanisms from the opposite end to the home end are correspondingly consistent, and are not described herein again.
Example three:
in addition to the open-loop control of the phase shifters in each polarized antenna array, as shown in the embodiments, the present embodiment provides a closed-loop precise control process. Such closed loop control is particularly useful for different one-hop communication distances and device operating frequency bands.
Still taking the dipole antenna array 4x 4MIMO as an example in the present embodiment, in order to demodulate any path of signal in the MIMO demodulation process, the baseband implements an equivalent one path of main path signal, and a receiver structure of three paths of auxiliary path signals, for example, V0 path of Rx0 shown in fig. 11 is an explanatory object, which needs to complete the filtering processing of H0, V1, and H1 paths in the main received signal to recover the data of V0, thereby implementing correct demodulation.
Fig. 11 is a 4x 4MIMO, if H0 and H1 in fig. 11 are removed first, which is the case of 2x2 MIMO under the consideration of single polarization in a broad sense, the first received signal is R0 ═ V0+ V1 ^ e j (θ 0), the second received signal is R1 ═ V1+ V0 ^ j (θ 1), taking the first reception as an example, MIMO demodulation is to be estimated (θ 0), Rx1 sends its own reception to Rx0, and the final demodulated signal in the first path is: r0-e ^ j (θ 0) (V1+ V0 ^ j (θ 1)) ═ V0-V0 ^ e ^ j (θ 0+ θ 1), and ideally θ 0 ═ θ 1 ^ 90 °, so 2R0 should be demodulated.
The θ angle is the phase angle difference, and ideally corresponds to 90 ° required in the 4 × 4MIMO case described above. Because this phase difference is finally convenient for the demodulation of baseband digital signals in the Modem, the maximum gain of the system may not be achieved only by considering the requirement of 90 ° phase difference between the local and remote antennas, because the phase difference is caused by the waveguide connector and the radio frequency cable used between the radio frequency unit of the microwave device and the phased array antenna array except for the phase difference introduced between the antennas, and because the radio frequency transceiving channels are independent from each other, the maximum gain of MIMO demodulation is ensured. Phase difference adaptive adjustment can also be performed through a feedback loop, firstly according to the process shown in the second embodiment, coarse adjustment of a 90-degree Phase is completed according to configuration in an equipment user interface, that is, it is ensured that an array unit group corresponding to the antenna at the home terminal and the opposite terminal meets the 90-degree Phase requirement, then it is expected that the system can work in an MIMO mode, because system indexes are not optimal, a closed-loop Phase fine adjustment flow is started, a link of a closed-loop control channel is established between one hop according to a lower Modulation mode (such as a QPSK (Quadrature Phase Shift Keying), a 16QAM (Quadrature Amplitude Modulation, SIGNAL-to-NOISE RATIO) and other Modulation modes requiring a lower SNR (SIGNAL-NOISE RATIO)), once the link is established, an error between a Phase angle received at the opposite terminal and an ideal angle can be estimated (a specific algorithm can adopt an existing arbitrary error estimation algorithm, no further description is given here), the observable indexes include mse (mean Square Error) and fec (forward Error correction) decoding conditions, which are sent to the local terminal through the established closed-loop control channel, after the local terminal receives the Error, the actual phase condition of the receiver at the opposite terminal is calculated according to the Error distribution condition, and after the Error is compared with the ideal 90-degree phase relationship, the actual phase condition is informed to the phased array antenna control module at the local terminal to perform the phase shift angle adjustment of the corresponding array unit group by issuing a specific phase shift control instruction, because the circuit structure in fig. 8 is used, all the phase adjustments are electrically controlled and adjustable, the phase shift relationship can be corresponded with the specific circuit, in the adjustment process, a stepping mode can be adopted, after the opposite terminal updates the MIMO performance index of the receiver again, the adjustment is performed again, if the performance index fed back by the opposite end reaches a certain threshold value range, the adjustment is stopped, and the closed-loop phase adjustment process of the MIMO system is considered to be finished. Because the receiving and sending channels are reciprocal, after the local terminal finishes the adjustment, the default link from the opposite terminal to the local terminal is also adjusted, and the LoS MIMO system enters a long-term stable working state.
The above closed-loop control process is shown in fig. 12, and includes:
s1201: setting a one-hop distance D between a home terminal and an opposite terminal and determining a frequency point F, acquiring transmission power Ptx (x can be selected from V0, H0, V1 and H1) corresponding to each polarized antenna array (two horizontal polarized antenna arrays 20 and vertical polarized antenna arrays 21 corresponding to V0, H0, V1 and H1) and path insertion loss Ld from the home terminal to the opposite terminal, and setting corresponding power difference thresholds (a horizontal polarized power difference threshold and a vertical polarized power difference threshold can be preset respectively corresponding to each horizontal polarized antenna array 20 and each vertical polarized antenna array 21, and the same power difference threshold can be used certainly);
s1202: acquiring receiving power Prx (x can be selected from V0, H0, V1 and H1) corresponding to each polarized antenna array (two horizontally polarized antenna arrays 20 and vertically polarized antenna arrays 21 corresponding to V0, H0, V1 and H1) after the opposite-end antenna is manually aligned;
s1203: judging whether the Ptx-Ld-Prx is smaller than or equal to a power difference threshold value, if so, turning to S1205; otherwise, go to S1204;
s1204: adjusting the main lobe radiation angle of the polarized antenna array corresponding to the Ptx until the Ptx-Ld-Prx is less than or equal to a power difference threshold; go to S1205;
s1205: ending the current Ptx main lobe adjustment, traversing the next polarized antenna array and turning to S1203 until the traversal is finished;
s1206: adjusting phase shifters in each polarized antenna array to ensure 90-degree phase shift between the sub-arrays of the receiving antennas opposite to each other;
s1207: the local terminal and the opposite terminal force the modulation mode to a preset modulation mode (such as QPSK), so that a closed-loop control channel is enabled;
s1208: prx carries out 90-degree phase shift fine adjustment on each polarized antenna array until the estimation error of the phase angle of each polarized antenna array is less than or equal to a set threshold, and MSE reaches an MIMO threshold;
s1209: the local terminal and the opposite terminal change the modulation mode back to the original user configuration mode and enter stable operation.
The feedback loop provided by this embodiment performs phase difference adaptive adjustment, which can further improve antenna performance and ensure reliability of the MIMO antenna array. After the phase configuration is completed based on the process, the corresponding signal can be sent to the opposite terminal, so that the engineering cost and the installation difficulty can be reduced, the reliability of the performance of the antenna can be improved, and the advantage of the MIMO antenna is ensured to be exerted by the antenna.
It will be apparent to those skilled in the art that the modules or steps of the embodiments of the invention described above may be implemented in a general purpose computing device, they may be centralized on a single computing device or distributed across a network of multiple computing devices, and alternatively, they may be implemented in program code executable by a computing device, such that they may be stored on a computer storage medium (ROM/RAM, magnetic disk, optical disk) and executed by a computing device, and in some cases, the steps shown or described may be performed in an order different than that described herein, or they may be separately fabricated into individual integrated circuit modules, or multiple ones of them may be fabricated into a single integrated circuit module. Thus, the present invention is not limited to any specific combination of hardware and software.
Example four:
as a result, the antenna carrier plate can be disposed on the same plane, and the antenna carrier plate can be disposed on the same plane. For example, for user applications, it may not be required that all scenarios are MIMO systems, that is, phased array antenna arrays integrated in physical form, and under the scenarios such as XPIC and protection, they no longer have the problem of corresponding multiplexing flexibility, and this embodiment proposes another implementation case, that is, according to the requirement of XPIC group, the original NxN antenna array is decomposed into physically independent minimum units, which include a pair of polarized antenna arrays (that is, include a horizontally polarized antenna array and a vertically polarized antenna array), as shown in fig. 13, where fig. 13 includes a horizontally polarized antenna array and a vertically polarized antenna array. In an application scenario, still according to a 15G working frequency band, taking a 5Km one-hop communication distance as an example (see fig. 6), a theoretically required dual-polarized antenna has a pitch of 7.07 m, considering an installation requirement on an iron tower (pole), a two-sided minimum phased array antenna array is installed at a distance of 1 m, because the two-sided minimum phased array antenna is not at an ideal required 7 m pitch, a two-sided phased array antenna is first required to perform 90 ° phase adjustment and equipment in the second embodiment, as shown in fig. 14, because the antenna pitch between the two-sided phased antennas is determined only at the end of an installation and engineering implementation stage and is not a fixed value, a phase difference finally shown at a receiving end may be a random angle distributed around 90 ° within a certain range, and at this time, the closed-loop phase adjustment process described in the third embodiment is completed, the phase between the radiation array units corresponding to the local terminal and the opposite terminal is automatically adjusted and finely adjusted, after the final adjustment is completed, the random antenna distance (determined by a user according to the specific installation situation) has no influence on the bipolar antenna MIMO system in the embodiment, the system automatically adjusts and converges to an optimal working state, that is, the transmission channel matrix is ensured to meet the requirements of the vandermonde matrix, and the corresponding radiation array units form an optimal phase difference relationship, so that the gain maximization of the MIMO system is realized, and the optimization is realized in the aspects of the transmission capacity and the system gain of the system. Meanwhile, the minimum phased array antenna array shown in fig. 13 can flexibly construct microwave applications such as 2+0, 2+2, 1+0 and the like when MIMO application is not performed, and the antenna array has more compact size and weight and is more optimized in the aspects of engineering installation and the like.
The foregoing is a more detailed description of embodiments of the present invention, and the present invention is not to be considered limited to such descriptions. For those skilled in the art to which the invention pertains, several simple deductions or substitutions can be made without departing from the spirit of the invention, and all shall be considered as belonging to the protection scope of the invention.
Claims (10)
1. A microwave antenna array communication system, comprising: phased array antenna array and
for microwave transmission equipment, N is the order of the bipolar antenna array with the value of more than or equal to 4;
the phased array antenna array comprises a controller and a phase control circuit connected with the controller
One-to-one correspondence to microwave transmission equipment
To the polarized antenna array;
the horizontally polarized radio frequency signal transmission equipment in the microwave transmission equipment and the horizontally polarized antenna array in the corresponding polarized antenna array
Individual antenna sub-array connections for transmitting to opposite terminals
Horizontally polarized radio frequency signal, vertically polarized radio frequency signal transmission apparatus, and vertically polarized antenna array of said polarized antenna arrays
Individual antenna sub-array connections for transmitting to opposite terminals
A vertically polarized radio frequency signal;
the controller is used for passing each antenna in the horizontally polarized antenna arrayThe phase shifters of the sub-arrays configure the phase of the horizontally polarized radio frequency signal transmitted by each antenna sub-array so that one horizontally polarized antenna array transmits
The phase difference between the horizontally polarized radio-frequency signals meets the requirement of the N-NMIMO bipolar antenna array, and the phase shifters are used for configuring the phase of the vertically polarized radio-frequency signals transmitted by each antenna sub-array in the vertically polarized antenna array, so that the vertically polarized radio-frequency signals transmitted by one vertically polarized antenna array
The phase difference between the vertically polarized radio frequency signals meets the requirements of the N-NMIMO dual-polar antenna array.
2. A microwave antenna array communication system as claimed in claim 1, wherein the controller is configured to configure phase differences of horizontally polarized radio frequency signals transmitted by adjacent antenna sub-arrays of the horizontally polarized antenna array by phase shifters of each antenna sub-array of the horizontally polarized antenna array
And the phase shifter for each antenna sub-array of the vertical polarization antenna array is used for configuring the phase difference of vertical polarization radio frequency signals transmitted by the adjacent antenna sub-arrays of the vertical polarization antenna array into
3. A microwave antenna array communication system as claimed in claim 1, wherein the antenna array is a single-chip antenna array
The pair of polarized antenna arrays is positioned on one antenna bearing plate;
or the like, or, alternatively,
the above-mentioned
Each pair of polarized antenna arrays in the pair of polarized antenna arrays is respectively positioned on one antenna bearing plate.
4. The microwave antenna array communication system of claim 2, wherein the controller is further configured to obtain a receiving phase angle of a corresponding horizontally polarized antenna array for receiving a horizontally polarized radio frequency signal transmitted by each antenna sub-array of the horizontally polarized antenna array and the receiving phase angle of the corresponding horizontally polarized antenna array for receiving the horizontally polarized radio frequency signal transmitted by each antenna sub-array of the horizontally polarized antenna array after configuring the phase of the horizontally polarized radio frequency signal transmitted by each antenna sub-array of the horizontally polarized antenna array, and the controller is further configured to obtain the receiving phase angle of the corresponding horizontally polarized antenna array for receiving the horizontally polarized radio frequency signal transmitted by each antenna sub-array of the horizontally polarized antenna array and the receiving phase angle of the corresponding horizontally polarized antenna array
When the difference is judged to be larger than the preset horizontal polarization phase angle deviation threshold value, adjusting the phase of the horizontal polarization radio frequency signal transmitted by each antenna subarray of the horizontal polarization antenna array according to the difference until the difference is smaller than or equal to the preset horizontal phase angle deviation threshold value;
the controller is further configured to, after configuring the phase of the vertically polarized radio frequency signal transmitted by each antenna sub-array of the vertically polarized antenna array, obtain a receiving phase angle at which the corresponding vertically polarized antenna array receives the vertically polarized radio frequency signal transmitted by each antenna sub-array of the vertically polarized antenna array and the received phase angle
And when the difference between the two values is larger than a preset vertical polarization phase angle deviation threshold value, adjusting the phase of the vertical polarization radio frequency signal transmitted by each antenna subarray of the vertical polarization antenna array according to the difference between the two values until the difference between the two values is smaller than or equal to the preset vertical phase angle deviation threshold value.
5. A microwave antenna array communication system as in any of claims 1-4, wherein the controller is further configured to obtain a difference between a transmission power of the horizontally polarized antenna array and a reception power of a horizontally polarized antenna array corresponding to an opposite end and a path insertion loss to the opposite end as a horizontally polarized power difference value, and when the horizontally polarized power difference value is greater than or equal to a preset horizontally polarized power difference threshold value, adjust a main lobe radiation angle of the horizontally polarized antenna array until the horizontally polarized power difference value is smaller than the preset horizontally polarized power difference threshold value;
the controller is further configured to obtain a difference between the transmission power of the vertical polarization antenna array and the reception power of the vertical polarization antenna array corresponding to the opposite end and a path insertion loss to the opposite end as a vertical polarization power difference value, and adjust a main lobe radiation angle of the vertical polarization antenna array when the vertical polarization power difference value is greater than or equal to a preset vertical polarization power difference threshold value until the vertical polarization power difference value is smaller than the preset vertical polarization power difference threshold value.
6. A microwave antenna array communication system according to any one of claims 1-4, wherein the antenna sub-array includes a plurality of antenna elements and phase shifters in one-to-one correspondence with the antenna elements.
7. A method of communicating in a microwave antenna array communication system as claimed in any one of claims 1 to 6, comprising:
the controller controls the phase shifters of the antenna sub-arrays of the horizontally polarized antenna array to configure the phase of the horizontally polarized radio frequency signal transmitted by each antenna sub-array, so that the horizontally polarized radio frequency signal is transmitted by one horizontally polarized antenna array
The phase difference between the horizontal polarization radio frequency signals meets the requirement of the N-NMIMO bipolar antenna array, and the phase shifters of the antenna sub-arrays of the vertical polarization antenna array are controlled to carry out phase shifting on the vertical polarization radio frequency signals transmitted by the antenna sub-arraysArranged so that one vertically polarised antenna array transmits
The phase difference between the vertically polarized radio frequency signals meets the requirement of the N-NMIMO bipolar antenna array;
the horizontally polarized radio frequency signal transmission equipment in the microwave transmission equipment sends the signals to the opposite terminal through each antenna subarray in the corresponding horizontally polarized antenna array
A horizontally polarized RF signal and a vertically polarized RF signal transmission device for transmitting to the opposite terminal via each antenna sub-array in the corresponding vertically polarized antenna array
A vertically polarized radio frequency signal.
8. A method for communicating in a microwave antenna array communication system as claimed in claim 7, wherein said controller controls the phase shifters of each antenna sub-array of said horizontally polarized antenna array to configure the phase difference of horizontally polarized rf signals transmitted by adjacent antenna sub-arrays of said horizontally polarized antenna array to be the same
And controlling phase shifters of each antenna sub-array of the vertically polarized antenna array to configure phase differences of horizontally polarized radio frequency signals transmitted by adjacent antenna sub-arrays of the vertically polarized antenna array to be phase differences
9. A method of communicating in a microwave antenna array communication system as recited in claim 8, further comprising:
the controller controls each antenna of the horizontally polarized antenna arrayAfter the phases of the horizontal polarization radio frequency signals transmitted by the sub-arrays are configured, the receiving phase angle of the horizontal polarization radio frequency signals transmitted by each antenna sub-array of the horizontal polarization antenna array received by the corresponding horizontal polarization antenna array and the receiving phase angle are obtained
When the difference is judged to be larger than the preset horizontal polarization phase angle deviation threshold value, adjusting the phase of the horizontal polarization radio frequency signal transmitted by each antenna subarray of the horizontal polarization antenna array according to the difference until the difference is smaller than or equal to the preset horizontal phase angle deviation threshold value;
and after the controller configures the phases of the vertical polarization radio frequency signals transmitted by the antenna sub-arrays of the vertical polarization antenna array, acquiring the receiving phase angle of the vertical polarization radio frequency signals transmitted by the antenna sub-arrays of the vertical polarization antenna array and the receiving phase angle of the vertical polarization radio frequency signals transmitted by the antenna sub-arrays of the vertical polarization antenna array, which are received by the corresponding vertical polarization antenna array at the opposite end
And when the difference between the two values is larger than a preset vertical polarization phase angle deviation threshold value, adjusting the phase of the vertical polarization radio frequency signal transmitted by each antenna subarray of the vertical polarization antenna array according to the difference between the two values until the difference between the two values is smaller than or equal to the preset vertical phase angle deviation threshold value.
10. A method of communicating in a microwave antenna array communication system as claimed in any one of claims 7 to 9, further comprising:
the controller obtains a difference between the transmitting power of the horizontally polarized antenna array, the receiving power of the horizontally polarized antenna array corresponding to an opposite terminal and the path insertion loss to the opposite terminal as a horizontally polarized power difference value, and adjusts a main lobe radiation angle of the horizontally polarized antenna array when the horizontally polarized power difference value is greater than or equal to a preset horizontally polarized power difference threshold value until the horizontally polarized power difference value is smaller than the preset horizontally polarized power difference threshold value;
and acquiring the difference between the transmitting power of the vertical polarization antenna array, the receiving power of the vertical polarization antenna array corresponding to the opposite terminal and the path insertion loss to the opposite terminal as a vertical polarization power difference value, and adjusting the main lobe radiation angle of the vertical polarization antenna array when the vertical polarization power difference value is greater than or equal to a preset vertical polarization power difference threshold value until the vertical polarization power difference value is smaller than the preset vertical polarization power difference threshold value.
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| WO2020200418A1 (en) * | 2019-04-01 | 2020-10-08 | Telefonaktiebolaget Lm Ericsson (Publ) | Transmitter for a point-to-point microwave system |
| CN110109082A (en) * | 2019-04-17 | 2019-08-09 | 天津大学 | A kind of Terahertz Active Radar imaging array of shared antenna |
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| JP4952789B2 (en) * | 2007-04-12 | 2012-06-13 | 日本電気株式会社 | Dual polarized antenna |
| CN101316130B (en) * | 2007-06-01 | 2014-06-11 | 中国移动通信集团公司 | Community antenna system and method in closed loop mode |
| CN102148425B (en) * | 2010-02-10 | 2014-07-30 | 雷凌科技股份有限公司 | Feed-in device used for smart antennas |
| JP5809482B2 (en) * | 2011-08-15 | 2015-11-11 | 株式会社Ｎｔｔドコモ | Wireless communication system, wireless base station, and wireless communication method |
| US8861646B2 (en) * | 2011-10-10 | 2014-10-14 | Lg Innotek Co., Ltd. | Terminal comprising multi-antennas and method of processing received frequency |
| WO2014033669A1 (en) * | 2012-08-30 | 2014-03-06 | Mimotech (Pty) Ltd. | A method of and system for providing diverse point to point communication links |
| BR112015010998B1 (en) * | 2012-12-03 | 2022-02-08 | Telefonaktiebolaget Lm Ericsson (Publ) | NODE IN A WIRELESS COMMUNICATION NETWORK |
| US9641215B2 (en) * | 2013-06-18 | 2017-05-02 | Telefonaktiebolaget Lm Ericsson (Publ) | Leakage cancellation for a multiple-input multiple-output transceiver |
| CN105226400B (en) * | 2015-09-16 | 2020-07-14 | 哈尔滨工业大学（威海） | Broadband dual-polarization phased array antenna and full-polarization beam forming method |
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| CN101772904A (en) * | 2007-08-02 | 2010-07-07 | 日本电气株式会社 | MIMO communication system having deterministic communication path and antenna arrangement method therefor |
| CN101916918A (en) * | 2010-07-01 | 2010-12-15 | 中国电子科技集团公司第五十四研究所 | Automatically polarized adjustment antenna system and polarization calibration method thereof |
| WO2012125190A1 (en) * | 2011-03-15 | 2012-09-20 | Intel Corporation | Mm-wave multiple-input multiple-output antenna system with polarization diversity |
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Also Published As
| Publication number | Publication date |
|---|---|
| EP3553887A1 (en) | 2019-10-16 |
| EP3553887A4 (en) | 2020-07-29 |
| WO2018103677A1 (en) | 2018-06-14 |
| CN108155479A (en) | 2018-06-12 |
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