CN106257812A - A kind of power management chip controlled based on COT containing flow equalizing function biphase Buck circuit - Google Patents

A kind of power management chip controlled based on COT containing flow equalizing function biphase Buck circuit Download PDF

Info

Publication number
CN106257812A
CN106257812A CN201610687539.8A CN201610687539A CN106257812A CN 106257812 A CN106257812 A CN 106257812A CN 201610687539 A CN201610687539 A CN 201610687539A CN 106257812 A CN106257812 A CN 106257812A
Authority
CN
China
Prior art keywords
pmos
module
grid
voltage
drain electrode
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Granted
Application number
CN201610687539.8A
Other languages
Chinese (zh)
Other versions
CN106257812B (en
Inventor
赵梦恋
张书瑜
朱波
秦政
杨艺丹
董阳涛
吴晓波
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Zhejiang University ZJU
Original Assignee
Zhejiang University ZJU
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Zhejiang University ZJU filed Critical Zhejiang University ZJU
Priority to CN201610687539.8A priority Critical patent/CN106257812B/en
Publication of CN106257812A publication Critical patent/CN106257812A/en
Application granted granted Critical
Publication of CN106257812B publication Critical patent/CN106257812B/en
Active legal-status Critical Current
Anticipated expiration legal-status Critical

Links

Classifications

    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
    • H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
    • H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/156—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
    • H02M3/157—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators with digital control
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/08—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters
    • H02M1/088—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters for the simultaneous control of series or parallel connected semiconductor devices
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/14—Arrangements for reducing ripples from dc input or output
    • H02M1/143—Arrangements for reducing ripples from dc input or output using compensating arrangements
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
    • H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
    • H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/156—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
    • H02M3/158—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load
    • H02M3/1584—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load with a plurality of power processing stages connected in parallel
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0048—Circuits or arrangements for reducing losses
    • H02M1/0054—Transistor switching losses
    • H02M1/0058—Transistor switching losses by employing soft switching techniques, i.e. commutation of transistors when applied voltage is zero or when current flow is zero
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
    • H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
    • H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/156—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
    • H02M3/158—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load
    • H02M3/1584—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load with a plurality of power processing stages connected in parallel
    • H02M3/1586—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load with a plurality of power processing stages connected in parallel switched with a phase shift, i.e. interleaved
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
    • Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes

Landscapes

  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Electronic Switches (AREA)

Abstract

The invention discloses a kind of power management chip controlled containing flow equalizing function biphase Buck circuit based on COT, it is provided with power supply input pin, output voltage foot, grounding leg and two switch SW feet.Switching tube in chip internal reference circuit module, comparator module, Voltage loop module, clock generation module, control logical AND soft-start module, constant on-time generation module, ripple compensation module, current sample module, current balance module, driving module and four sheets.Power management chip of the present invention can overcome multiple unsymmetrical factors to realize current balance efficiently, and precision is higher, can be operated under higher switching frequency, and compared with the traditional method of digital control coupling dutycycle, energy loss is less, and footprint area is less.

Description

A kind of power management chip controlled based on COT containing flow equalizing function biphase Buck circuit
Technical field
The invention belongs to technical field of integrated circuits, be specifically related to a kind of based on COT control biphase Buck Han flow equalizing function The power management chip of circuit.
Background technology
Power management class chip is that each module in system is carried out the chip of the management of power use, some power management chip meetings It is used for switching power circuit.Switching power circuit is from being broadly defined as, and all semiconductor power devices are as switch, by electricity Source Morphological Transitions becomes another form, with automatically controlling closed-loop stabilization output the circuit of protected link during transformation.Switch electricity Source circuit generally comprises control chip and peripheral circuit.The common topological structure of switching power circuit has: buck chopper (Buck), Boost chopper (Boost), inverse-excitation type, positive activation type, half-bridge and full-bridge.Wherein the control mode of Buck circuit includes: sluggish control The control of system, constant on-time (COT), voltage type PWM control and current type PWM control etc..
When load need bigger electric current time, changer can more employing heterogeneous structures, multiple branch circuit parallel connections are come to output End provides energy.Many times, heterogeneous structure is the working method using phase alternation, and the switching frequency of each branch road keeps one Causing, but phase place staggers, the frequency of output ripple then becomes switching frequency and is multiplied by circuitry number.Now heterogeneous structure can simplify Become the phase structure that switching frequency increases.Thus the heterogeneous structure that phase sequence is alternately can be greatly improved loop bandwidth, and then improve wink State response speed, meets the requirement of large current load.Owing to each branch road is required for power tube and inductance, so whole changer Switch block quantity can increase.Single from the point of view of efficiency, heterogeneous structure promotes the most further, even can bring more Many switching losses.But the maximum current that phase structure can be provided by is the most limited, the reliability of work is the highest；And it is heterogeneous Load current is evenly distributed to each branch road by structure, and output load current ability can be significantly greatly increased, and the most each branch road bears Electric current also will not be the highest, functional reliability is ensured.But heterogeneous structure needs extra current equalization circuit, make every The electric current of individual branch road is equal.
Conventional digital control biphase Buck circuit structure as it is shown in figure 1, its method using dutycycle to mate realizes, Owing to the analog circuit of tradition generation dutycycle is very sensitive to the unsymmetrical factors of branch road, in order to reach corresponding precision, need to adopt The dutycycle of coupling is produced with digital module.But, digital control meeting inevitably introduces quantization error, thus causes not Good limit cycle；Additionally, the High-accuracy direct current changer being operated under the highest switching frequency needs high-resolution and at a high speed Digital PWM generator and analog-digital converter, can cause the most again the loss of energy and the waste of area.
Summary of the invention
For the above-mentioned technical problem existing for prior art, the invention provides a kind of based on COT control merit Han current-sharing The power management chip of the biphase Buck circuit of energy, it is possible to be operated under higher switching frequency, overcome various unsymmetrical factors, will Load current is evenly distributed to each branch road, it is to avoid each phase current is unequal when causing that single-phase loss is excessive even affects work Sequence, and relatively conventional digital control method energy loss is relatively low, footprint area is less.
A kind of power management chip controlled based on COT containing flow equalizing function biphase Buck circuit, including:
Article two, switching branches, described switching branches comprises power switch pipe Mp and Mn；Wherein, the source of power switch pipe Mp The input voltage V of connection circuitIN, the drain terminal of a power switch pipe Mp phase electricity corresponding with the drain terminal of power switch pipe Mn and circuit One end of sense is connected, and the source ground connection of power switch pipe Mn, in circuit, the other end of two phase inductances is parallel with one another；
Reference circuit module, it is at input voltage VINFor during high level in sheet provide reference voltage VBG；
Ripple compensation module, the output voltage V of its sample circuitOAnd two junction points of phase inductance and corresponding switching branches Voltage, thus produce reference voltage FB and two-way compensation voltage RAMP1And RAMP2；
Voltage loop module, it is according to reference voltage FB and reference voltage VBGCompare, produce burning voltage VCON；
Current sample module, it is by flowing through power switch pipe Mp's in current mirror Cycle by Cycle two switching branches of sampling Current peak, corresponding generation is positively correlated with the current sample voltage VCS of current peak1And VCS2；
Current balance module, it is according to current sample voltage VCS1And VCS2Comparing, the electric current producing a pair difference is equal Weighing apparatus voltage VCB1And VCB2；
Two comparator module, described comparator module has two and aligns inverting input, and its outfan produces and compares letter Number；Wherein a pair of a comparator module positive inverting input meets burning voltage V respectivelyCONWith compensation voltage RAMP1, another is right Positive inverting input meets current balance voltage VCB respectively1And VCB2；The positive inverting input of a pair of another comparator module is respectively Meet burning voltage VCONWith compensation voltage RAMP2, another aligns inverting input and meets current balance voltage VCB respectively2And VCB1；
Two constant on-time generation modules, described constant on-time generation module is according to corresponding comparator module Comparison signal generates ON time signal；
Two control logical AND soft-start module, and described control logical AND soft-start module is according to corresponding constant on-time The ON time signal of generation module generates driving signal by controlling logic；
Two drive module, and described driving module makes the corresponding driving signal power controlling logical AND soft-start module amplify After in order to drive power switch pipe Mp and Mn in corresponding switching branches to carry out on-off control.
Described reference voltage FB is proportional to output voltage VODC component, compensate voltage RAMP1AC compounent direct ratio In the AC compounent of a wherein phase inductance electric current, compensate voltage RAMP2AC compounent be proportional to the friendship of another phase inductance electric current Flow component, compensates voltage RAMP1And RAMP2DC component be equal to reference voltage FB.
Described constant on-time generation module is when comparison signal is low level, and generating ON time signal is just high electricity Putting down and the pulsewidths constant of this high level, other times generate ON time signal and are low level.
Described control logical AND soft-start module when closed between signal when being high level, generating and driving signal is low electricity Flat, when closed between signal when being low level, generating and driving signal is high level.
Described driving module is when driving signal is low level so that it is power switch pipe Mp in the corresponding switching branches driven Open-minded, power switch pipe Mn turns off；When being high level when driving signal so that it is power switch pipe in the corresponding switching branches driven Mn is open-minded, and power switch pipe Mp turns off.
Described current balance module includes the trsanscondutance amplifier GM singly exported1, the trsanscondutance amplifier of dual output differential type GM2, electric capacity C or door, eight current source I1～I8, five switch S1～S5, four PMOS PM1～PM4, resistance R11～R12With R21～R22, three NMOS tube NM1～NM3, two rest-set flip-flop R1～R2, two phase inverter INV1～INV2, two chronotron Delay1～Delay2, three digit counter CA of dual input1Enumerator CA with single input2；Wherein: trsanscondutance amplifier GM1Just Phase input and inverting input meet current sample voltage VCS respectively1And VCS2, trsanscondutance amplifier GM1Outfan and electric capacity C Top crown, switch S5One end and trsanscondutance amplifier GM2Inverting input be connected, the bottom crown ground connection of electric capacity C, eight Current source I1～I8Input all meet supply voltage, current source I6Outfan and trsanscondutance amplifier GM2Normal phase input end, Switch S5The other end and NMOS tube NM1Drain and gate be connected, NMOS tube NM1Source ground, current source I1～I4's Outfan respectively with switch S1～S4One end be connected, switch S1～S4The other end and trsanscondutance amplifier GM2Positive output end, Resistance R11One end and PMOS PM1Grid be connected, resistance R11Other end ground connection, current source I5Outfan and mutual conductance Amplifier GM2Reversed-phase output, resistance R12One end and PMOS PM2Grid be connected, resistance R12Other end ground connection, Current source I7Outfan and PMOS PM1Source electrode and PMOS PM2Source electrode be connected, current source I8Outfan with PMOS PM3Source electrode and PMOS PM4Source electrode be connected, PMOS PM3Grid and PMOS PM4Grid connect respectively Current sample voltage VCS1And VCS2, PMOS PM1Drain electrode and PMOS PM3Drain electrode, resistance R21One end and NMOS tube NM2Drain electrode be connected and produce current balance voltage VCB1, PMOS PM2Drain electrode and PMOS PM4Drain electrode, resistance R22's One end and NMOS tube NM3Drain electrode be connected and produce current balance voltage VCB2, resistance R21The other end and resistance R22Another One end, NMOS tube NM2Grid and NMOS tube NM3Grid be connected, NMOS tube NM2Source electrode and NMOS tube NM3Source electrode connect Ground；Phase inverter INV1And INV2Input connect respectively two control logical AND soft-start modules generate two-way drive signals, instead Phase device INV1Outfan and chronotron Delay1Input and rest-set flip-flop R1R end, phase inverter INV2Outfan with Chronotron Delay2Input and rest-set flip-flop R2R end, chronotron Delay1Outfan and rest-set flip-flop R1S end It is connected, chronotron Delay2Outfan and rest-set flip-flop R2S end be connected, rest-set flip-flop R1Outfan and three digit counters CA1First input end and or door first input end be connected, rest-set flip-flop R2Outfan and three digit counter CA1? Two inputs and or door the second input be connected, three digit counter CA1Three outfans respectively switch S1～S3There is provided Switch controlling signal, or the outfan of door and enumerator CA2Input be connected, enumerator CA2Outfan for switch S4There is provided Switch controlling signal.
Described current source I1～I5Output size of current be respectively 1uA, 2uA, 4uA, 0.5uA and 4uA.
Described three digit counter CA1Sum counter CA2Input be rising edge trigger, wherein three digit counter CA1's First input end often receives a rising edge and adds 1, and the second input often receives a rising edge and subtracts 1, three digit counter CA1Meter Numerically lower limit is respectively 8 and 0；Enumerator CA2Count value be added to 8 after persistently export high level, otherwise output low level.
Described comparator module includes a bias current sources, 12 PMOS P1～P12With seven NMOS tube N1～N7； Wherein: PMOS P1～P8Source electrode all connect supply voltage, PMOS P1Grid and PMOS P2Grid, PMOS P1Leakage Pole, PMOS P3Grid and bias current sources input be connected, the output head grounding of bias current sources, PMOS P2's Drain electrode and PMOS P9Source electrode and PMOS P10Source electrode be connected, PMOS P3Drain electrode and PMOS P11Source electrode and PMOS P12Source electrode be connected, PMOS P4Grid and PMOS P5Grid, PMOS P4Drain electrode and NMOS tube N3's Drain electrode is connected, PMOS P5Drain electrode and PMOS P6Grid and NMOS tube N4Drain electrode be connected, PMOS P6Drain electrode with PMOS P7Grid, NMOS tube N6Grid and NMOS tube N5Drain electrode be connected, PMOS P7Drain electrode and PMOS P8's Grid, NMOS tube N7Grid and NMOS tube N6Drain electrode be connected, PMOS P8Drain electrode and NMOS tube N7Drain electrode be connected also Produce comparison signal, PMOS P10Grid and PMOS P9Grid to correspond to a pair of comparator module respectively the most anti-phase defeated Enter end, PMOS P12Grid and PMOS P11Another of grid corresponding comparator module respectively align inverting input, PMOS P9Drain electrode and NMOS tube N1Grid, NMOS tube N4Grid, PMOS P11Drain electrode and NMOS tube N1Drain electrode It is connected, PMOS P10Drain electrode and NMOS tube N2Grid, NMOS tube N3Grid, NMOS tube N5Grid, PMOS P12's Drain electrode and NMOS tube N2Drain electrode be connected, NMOS tube N1～N7Source grounding.
Described PMOS P10Breadth length ratio and PMOS P12The ratio of breadth length ratio and PMOS P9Breadth length ratio and PMOS Pipe P11The ratio of breadth length ratio to be 1:N, N be the real number more than 1.
The Advantageous Effects of power management chip of the present invention is as follows:
(1) current equalization circuit in the present invention, it is possible to be operated under higher switching frequency, overcome various asymmetric because of Asymmetric such as offset voltage, inductance, electric capacity, resistance etc. of element, it is possible to the phase sequence realizing quarter-phase circuit replaces, reliability after tested The highest, it is ensured that the stability of system, improve lifetime of system.
(2) power management chip in the present invention possesses soft start function, improves system job stability, reduces and is System switching loss.
Accompanying drawing explanation
Fig. 1 is conventionally employed numerically controlled biphase Buck electrical block diagram.
Fig. 2 is the present invention biphase Buck circuit power managing chip and the structural representation of peripheral circuit thereof.
Fig. 3 is the electrical block diagram of current balance module of the present invention.
Fig. 4 is the electrical block diagram of comparator module of the present invention.
Fig. 5 is the digital channel using current equalization circuit of the present invention work wave schematic diagram under DCM.
Detailed description of the invention
In order to more specifically describe the present invention, below in conjunction with the accompanying drawings and detailed description of the invention is to technical scheme It is described in detail.
As in figure 2 it is shown, power management chip of the present invention is for big electric current Buck circuit occasion, it is provided with power supply input pin (Vin), output voltage foot (VO), grounding leg (GND) and two switch SW foot (SW1And SW2).Chip internal has reference circuit mould Block, comparator module, Voltage loop module, clock generation module, control logical AND soft-start module, constant on-time produce mould Block, ripple compensation module, current sample module, current balance module.Drive switching tube Mp in module and four sheets1、Mp2With Mn1、Mn2。
Power supply input pin (Vin), modules in access chip, the power supply electricity that in generation chip, modules normally works Position.Grounding leg (GND), modules in access chip, the ground reference that in generation chip, modules normally works.Switch SW foot (SW1And SW2), it is connected on power switch pipe Mp respectively1、Mn1Between and Mp2、Mn2Between, level between sampled power switching tube, Simultaneously by level input ripple compensation module between switching tube.Output voltage foot (VO), also ripple compensation module in access chip.Stricture of vagina Ripple compensating module produces and compensates ripple (RAMP1And RAMP2) respectively input two branch road comparators a negative terminal, the most also produce Raw voltage feedback signal (FB) is input to Voltage loop negative terminal.It is input to the benchmark that circuit module produces on the basis of Voltage loop anode Level (VBG), Voltage loop produces burning voltage (VCON) it is input to an anode of two branch road comparator module, respectively with two benefits Repay ripple (RAMP1And RAMP2) compare.Current balance module receives the current value that two branch current sampling modules samplings obtain (VCS1And VCS2), produce current balance voltage (VCB1And VCB2), a pair input of two the branch road comparators that are added to respectively is just Negative terminal.Comparator module output accesses constant on-time generation module, is simultaneously entered going back of constant on-time generation module Having the clock signal (CLK) that clock generation circuit produces, constant on-time generation module produces fixing ON time signal, It is input to control logical AND soft-start module.It is separately input to two control logical AND soft-start modules simultaneously and also has switching signal (SW1And SW2), control logical AND soft-start module and produce output signal (D1And D2), it is separately input to the driving mould of two branch roads Block, produces and drives signal to drive switching tube Mp in two sheets in each branch road1、Mn1And Mp2、Mn2。
As typical case's application of this chip, as in figure 2 it is shown, external power supply voltage is via power supply input pin (Vin), access core Modules in sheet, the power supply potential that in generation chip, modules normally works.External ground current potential via grounding leg (GND), Modules in access chip, the ground reference that in generation chip, modules normally works.
Two switches SW foot (SW1 and SW2), are connected on respectively between power switch pipe Mp1, Mn1 and between Mp2, Mn2, adopt Level between sample power switch pipe, simultaneously by level input ripple compensation module between switching tube and control logical AND soft-start module.
Output voltage foot (VO) also ripple compensation module in access chip, ripple compensation module includes ripple compensation electricity Road, produces two and compensates ripple (RAMP1And RAMP2) it is respectively connected to a negative terminal of two comparator module, also produce electricity simultaneously Pressure feedback signal (FB) is input to the negative terminal of Voltage loop module；Wherein FB is proportional to output voltage VODC component, RAMP1's AC compounent is proportional to the AC compounent of inductance L1 electric current, RAMP2AC ripple be proportional to the AC compounent of inductance L2 electric current, RAMP1And RAMP2DC component be equal to reference voltage FB.
Reference circuit module is according to input voltage VinFor producing reference level (V during high levelBG) it is input to Voltage loop module Anode, Voltage loop module defeated generation burning voltage (VCON) it is input to an anode of two comparator module, respectively with compensation Ripple (RAMP1And RAMP2) compare.
Current sample module flows through power switch pipe Mp by the sampling of current mirror Cycle by Cycle1、Mp2Current peak, produce It is positively correlated with the current sample voltage VCS of current peak1、VCS2。
Current balance module receives the current sample voltage (VCS that two branch current sampling modules samplings obtain1With VCS2), produce current balance voltage (VCB1And VCB2), a pair input positive and negative terminal of two the branch road comparators that are added to respectively.As Shown in Fig. 3, in present embodiment, current balance modular circuit includes two two input comparator GM1And GM2, input is to pipe GMSWith GMF, switch S1～S5, resistance R11、R12、R21And R22, electric capacity C, eight current sources, wherein five be respectively 1uA, 2uA, 4uA, 0.5uA and 4uA, and three NMOS；Wherein, VCS1And VCS2Current sampling data as biphase branch road all exports GM1With GMFInput, GM1Outfan and electric capacity C and GM2Inverting input be connected, GM2Positive input connect current source Simultaneously through NMOS ground connection, the grid leak end short circuit of NMOS, switch S5Connect GM2Two inputs, switch S1～S4Connect respectively The current source of 1uA, 2uA, 4uA and 0.5uA, these four branch circuit parallel connections, end points in parallel connects GM2Positive output end and GMSInput End is simultaneously through resistance R11Ground connection, GMSAnother input connect GM2Negative output terminal and the current source of 4uA simultaneously through resistance R12 Ground connection, GMSThe drain terminal of two PMOS respectively through a NMOS ground connection, the grid end of the two NMOS is connected, resistance R21、R22Respectively By GMSThe drain terminal of two PMOS is connected with NMOS grid end, GMSIn two PMOS drain terminals and GMFIn two PMOS drain terminal respectively It is connected, junction point extracted current signal VCB respectively1、VCB2。
Comparator module (uses four input comparators, differential difference amplifier), its two couple Forward and reverse input, is for a pair current balance voltage VCB1、VCB2, a pair for compensating ripple RAMP1(or RAMP2) and stable electricity Pressure VCON, thus produce comparison signal ON1、ON2；As shown in Figure 4, in present embodiment comparator module to employ two groups of inputs right Pipe GM1And GM2, one group of (GM1) give compensation ripple signal RAMP1(or RAMP2) and burning voltage VCONUse, another group (GM2) give Current balance voltage signal VCB1And VCB2Using, structure uses common dual-stage amplifier, wherein GM1/GM2=N/1 (N > 1), Be equivalent to pipe GM2Input signal convert GM1Input after, the most original N/mono-.
Comparator module output accesses constant on-time generation module, is simultaneously entered constant on-time generation module Also having the clock signal (CLK) that clock generation circuit produces, constant on-time generation module produces fixing ON time letter Number, it is input to control logical AND soft-start module.It is separately input to two simultaneously and controls logical AND soft-start module also switch Signal (SW1And SW2),
Control logical AND soft-start module and produce output signal (D1And D2), it is input to drive module, produces and drive signal to drive Switching tube Mp1, Mn1 and Mp2, Mn2 in two sheets in dynamic each branch road, it is achieved the conversion of electric energy and transmission.Comparison signal ON1 Or ON2During for low level, the ON time signal that the constant on-time generation module of that phase corresponding generates is just high level Triggering and the pulsewidths constant of this high level, other times are low level.
The current balance module of present embodiment includes fast passage and slow channel, as shown in Figure 3.Fast on the right side of Fig. 3 In passage, the current sampling data (VCS of two branch roads1And VCS2) through inputting pipe GMFWith resistance R21、R22Change into difference ripple, It is directly superimposed to the input of comparator.Slow channel on the left of Fig. 3 is divided into again analog channel and digital channel.Wherein, simulation is logical Road is by current sampling data (VCS1And VCS2) through comparator GM1Obtain current differential information, then through electric capacity C low-pass filtering, then Through comparator GM2With resistance R11、R12Transformation of scale, after through input to pipe GMSWith fast passage is together in parallel, at resistance R21、R22Upper generation difference ripple；Digital channel is then the electric current of regulation current array, at resistance R21、R22Upper generation difference stricture of vagina Ripple.The ripple that fast passage and slow channel produce is at resistance R21、R22Upper superposition, obtains final difference ripple VCB1And VCB2, defeated Go out the input to comparator.Switch S4It it is the centre in order to the asymmetric offset voltage of comparator being set in a gear Value.When the asymmetric offset voltage of comparator is zero, two branch roads can be the most open-minded, the most only opens wherein one in the next cycle Road.It addition, switch S5A period of time can be opened, to GM when flow equalizing circuit is opened1～the output of C low pass filter provides initial value.
For the slow channel in current balance module, wherein digital channel is equivalent to coarse adjustment, and analog channel is equivalent to fine tuning. If binary system has been carried out phase sequence alternately, then digital channel will not work, and analog channel then can gradually subtract The impact of few offset voltage.Because binary system is in when being continuously turned on state, typically also achieves phase sequence and stagger.At this with disconnected Be introduced as a example by continuous duty, groundwork sequential as shown in Figure 5:
(1) declining when output, first is mutually open-minded, and enumerator receives a rising pulses, and output Q [2:0] adds 1, flows through R11Electric current increase, VCB1Reduce and VCB2Increase, be equivalent to superposition on the comparator of the first phase and bear offset voltage, second Going up the positive offset voltage of superposition mutually, so that the first phase is more difficult to open and the second phase is easier to open-minded；
(2) if output voltage declines again, second meets open-minded, and enumerator receives a falling pulse, output Q [2: 0] subtract 1, flow through R11Electric current reduce, VCB1Increase and VCB2Reduce, be equivalent to superposition on the comparator of the first phase and just lack of proper care Voltage, in the second phase, offset voltage is born in superposition, so that the first phase is easier to open and the second phase is more difficult to open-minded；
(3) when output voltage declines again, take turns to first mutually open-minded, then be the second phase, circulate successively, it is achieved thereby that Phase sequence staggers.Finally, Q [2:0] saltus step in a gear of digital channel, i.e. Q0 constantly jumps to 1 from 0, then jumps to 0 from 1.
Wherein the offset voltage waveform in Fig. 5 is switch S4Effect the asymmetric offset voltage of comparator is set Intermediate value at a gear, it is to avoid when the asymmetric offset voltage of comparator is zero, two branch roads can be the most open-minded, and next Cycle the most only opens a wherein road.So the present invention proposes corresponding half value amendment circuit, see the lower left corner of Fig. 3, if continuously Two branch roads, eight cycles simultaneously detected, then the carry flag of enumerator can jump 1, switchs S4Open-minded, by two comparators Asymmetric offset voltage be set to the intermediate value of a gear.Can be achieved with it follows that the offset voltage of digital channel adjusts Normal positive and negative saltus step.If the initial asymmetric offset voltage of two comparators is at intermediate value, it is possible to realize two Road phase sequence staggers, then switch S4It is still kept off.
The above-mentioned description to embodiment is to be understood that for ease of those skilled in the art and apply the present invention. Above-described embodiment obviously easily can be made various amendment by person skilled in the art, and described herein typically Principle is applied in other embodiments without through performing creative labour.Therefore, the invention is not restricted to above-described embodiment, ability Field technique personnel should be in protection scope of the present invention according to the announcement of the present invention, the improvement made for the present invention and amendment Within.

Claims (10)

1. the power management chip containing flow equalizing function biphase Buck circuit based on COT control, it is characterised in that including:
Article two, switching branches, described switching branches comprises power switch pipe Mp and Mn；Wherein, the source of power switch pipe Mp connects electricity The input voltage V on roadIN, the drain terminal of a power switch pipe Mp phase inductance corresponding with the drain terminal of power switch pipe Mn and circuit One end is connected, and the source ground connection of power switch pipe Mn, in circuit, the other end of two phase inductances is parallel with one another；
Reference circuit module, it is at input voltage VINFor during high level in sheet provide reference voltage VBG；
Ripple compensation module, the output voltage V of its sample circuitOAnd two junction point voltage of phase inductance and corresponding switching branches, Thus produce reference voltage FB and two-way compensation voltage RAMP1And RAMP2；
Voltage loop module, it is according to reference voltage FB and reference voltage VBGCompare, produce burning voltage VCON；
Current sample module, it is by flowing through the electric current of power switch pipe Mp in current mirror Cycle by Cycle two switching branches of sampling Peak value, corresponding generation is positively correlated with the current sample voltage VCS of current peak1And VCS2；
Current balance module, it is according to current sample voltage VCS1And VCS2Compare, produce the current balance electricity of a pair difference Pressure VCB1And VCB2；
Two comparator module, described comparator module has two and aligns inverting input, and its outfan produces comparison signal；Its In a pair positive inverting input of a comparator module meet burning voltage V respectivelyCONWith compensation voltage RAMP1, another aligns anti-phase Input meets current balance voltage VCB respectively1And VCB2；The positive inverting input of a pair of another comparator module connects stable respectively Voltage VCONWith compensation voltage RAMP2, another aligns inverting input and meets current balance voltage VCB respectively2And VCB1；
Two constant on-time generation modules, described constant on-time generation module is according to the comparison of corresponding comparator module Signal generates ON time signal；
Two control logical AND soft-start module, and described control logical AND soft-start module produces according to corresponding constant on-time The ON time signal of module generates driving signal by controlling logic；
Two drive module, and described driving module makes the corresponding driving signal power controlling logical AND soft-start module use after amplifying To drive power switch pipe Mp and Mn in corresponding switching branches to carry out on-off control.
Power management chip the most according to claim 1, it is characterised in that: described reference voltage FB is proportional to output electricity Pressure VODC component, compensate voltage RAMP1AC compounent be proportional to the AC compounent of a wherein phase inductance electric current, compensate electricity Pressure RAMP2AC compounent be proportional to the AC compounent of another phase inductance electric current, compensate voltage RAMP1And RAMP2DC component It is equal to reference voltage FB.
Power management chip the most according to claim 1, it is characterised in that: described constant on-time generation module when than When relatively signal is low level, generating the pulsewidths constant that ON time signal is just high level and this high level, other times generate ON time signal is low level.
Power management chip the most according to claim 1, it is characterised in that: described control logical AND soft-start module is when leading When logical time signal is high level, generating and driving signal is low level, when closed between signal when being low level, generate and drive letter Number it is high level.
Power management chip the most according to claim 1, it is characterised in that: described driving module is low electricity when driving signal At ordinary times so that it is in the corresponding switching branches driven, power switch pipe Mp is open-minded, and power switch pipe Mn turns off；It is high when driving signal During level so that it is in the corresponding switching branches driven, power switch pipe Mn is open-minded, and power switch pipe Mp turns off.
Power management chip the most according to claim 1, it is characterised in that: described current balance module includes single output Trsanscondutance amplifier GM1, the trsanscondutance amplifier GM of dual output differential type2, electric capacity C or door, eight current source I1～I8, five open Close S1～S5, four PMOS PM1～PM4, resistance R11～R12And R21～R22, three NMOS tube NM1～NM3, two rest-set flip-flops R1～R2, two phase inverter INV1～INV2, two chronotron Delay1～Delay2, three digit counter CA of dual input1And list The enumerator CA of input2；Wherein: trsanscondutance amplifier GM1Normal phase input end and inverting input connect current sample voltage respectively VCS1And VCS2, trsanscondutance amplifier GM1The top crown of outfan and electric capacity C, switch S5One end and trsanscondutance amplifier GM2's Inverting input is connected, the bottom crown ground connection of electric capacity C, eight current source I1～I8Input all meet supply voltage, current source I6 Outfan and trsanscondutance amplifier GM2Normal phase input end, switch S5The other end and NMOS tube NM1Drain and gate phase Even, NMOS tube NM1Source ground, current source I1～I4Outfan respectively with switch S1～S4One end be connected, switch S1~ S4The other end and trsanscondutance amplifier GM2Positive output end, resistance R11One end and PMOS PM1Grid be connected, resistance R11Other end ground connection, current source I5Outfan and trsanscondutance amplifier GM2Reversed-phase output, resistance R12One end and PMOS PM2Grid be connected, resistance R12Other end ground connection, current source I7Outfan and PMOS PM1Source electrode and PMOS PM2Source electrode be connected, current source I8Outfan and PMOS PM3Source electrode and PMOS PM4Source electrode be connected, PMOS PM3Grid and PMOS PM4Grid meet current sample voltage VCS respectively1And VCS2, PMOS PM1Drain electrode with PMOS PM3Drain electrode, resistance R21One end and NMOS tube NM2Drain electrode be connected and produce current balance voltage VCB1, PMOS Pipe PM2Drain electrode and PMOS PM4Drain electrode, resistance R22One end and NMOS tube NM3Drain electrode be connected and produce current balance Voltage VCB2, resistance R21The other end and resistance R22The other end, NMOS tube NM2Grid and NMOS tube NM3Grid phase Even, NMOS tube NM2Source electrode and NMOS tube NM3Source ground；Phase inverter INV1And INV2Input connect two controls respectively The two-way that logical AND soft-start module generates drives signal, phase inverter INV1Outfan and chronotron Delay1Input with And rest-set flip-flop R1R end, phase inverter INV2Outfan and chronotron Delay2Input and rest-set flip-flop R2R end, Chronotron Delay1Outfan and rest-set flip-flop R1S end be connected, chronotron Delay2Outfan and rest-set flip-flop R2S End is connected, rest-set flip-flop R1Outfan and three digit counter CA1First input end and or door first input end be connected, Rest-set flip-flop R2Outfan and three digit counter CA1The second input and or door the second input be connected, three countings Device CA1Three outfans respectively switch S1～S3Switch controlling signal, or the outfan of door and enumerator CA are provided2Defeated Enter end to be connected, enumerator CA2Outfan for switch S4Switch controlling signal is provided.
Power management chip the most according to claim 6, it is characterised in that: described current source I1～I5Output electric current big Little respectively 1uA, 2uA, 4uA, 0.5uA and 4uA.
Power management chip the most according to claim 6, it is characterised in that: described three digit counter CA1Sum counter CA2 Input be rising edge trigger, wherein three digit counter CA1First input end often receive a rising edge and add 1, second Input often receives a rising edge and subtracts 1, three digit counter CA1Count value bound be respectively 8 and 0；Enumerator CA2Meter Numerical value persistently exports high level, otherwise output low level after being added to 8.
Power management chip the most according to claim 1, it is characterised in that: described comparator module includes a biased electrical Liu Yuan, 12 PMOS P1～P12With seven NMOS tube N1～N7；Wherein: PMOS P1～P8Source electrode all connect supply voltage, PMOS P1Grid and PMOS P2Grid, PMOS P1Drain electrode, PMOS P3Grid and bias current sources defeated Enter end to be connected, the output head grounding of bias current sources, PMOS P2Drain electrode and PMOS P9Source electrode and PMOS P10's Source electrode is connected, PMOS P3Drain electrode and PMOS P11Source electrode and PMOS P12Source electrode be connected, PMOS P4Grid With PMOS P5Grid, PMOS P4Drain electrode and NMOS tube N3Drain electrode be connected, PMOS P5Drain electrode and PMOS P6 Grid and NMOS tube N4Drain electrode be connected, PMOS P6Drain electrode and PMOS P7Grid, NMOS tube N6Grid and NMOS tube N5Drain electrode be connected, PMOS P7Drain electrode and PMOS P8Grid, NMOS tube N7Grid and NMOS tube N6's Drain electrode is connected, PMOS P8Drain electrode and NMOS tube N7Drain electrode be connected and produce comparison signal, PMOS P10Grid and PMOS P9Grid correspond to a pair positive inverting input of comparator module, PMOS P respectively12Grid and PMOS P11 Another of grid corresponding comparator module respectively align inverting input, PMOS P9Drain electrode and NMOS tube N1Grid, NMOS tube N4Grid, PMOS P11Drain electrode and NMOS tube N1Drain electrode be connected, PMOS P10Drain electrode and NMOS tube N2 Grid, NMOS tube N3Grid, NMOS tube N5Grid, PMOS P12Drain electrode and NMOS tube N2Drain electrode be connected, NMOS Pipe N1～N7Source grounding.
Power management chip the most according to claim 9, it is characterised in that: described PMOS P10Breadth length ratio and PMOS Pipe P12The ratio of breadth length ratio and PMOS P9Breadth length ratio and PMOS P11The ratio of breadth length ratio to be 1:N, N be more than 1 Real number.
CN201610687539.8A 2016-08-17 2016-08-17 A kind of power management chip based on the COT control Buck circuits of two-phase containing flow equalizing function Active CN106257812B (en)

Priority Applications (1)

Application Number Priority Date Filing Date Title
CN201610687539.8A CN106257812B (en) 2016-08-17 2016-08-17 A kind of power management chip based on the COT control Buck circuits of two-phase containing flow equalizing function

Applications Claiming Priority (1)

Application Number Priority Date Filing Date Title
CN201610687539.8A CN106257812B (en) 2016-08-17 2016-08-17 A kind of power management chip based on the COT control Buck circuits of two-phase containing flow equalizing function

Publications (2)

Publication Number Publication Date
CN106257812A true CN106257812A (en) 2016-12-28
CN106257812B CN106257812B (en) 2018-05-22

Family

ID=57713589

Family Applications (1)

Application Number Title Priority Date Filing Date
CN201610687539.8A Active CN106257812B (en) 2016-08-17 2016-08-17 A kind of power management chip based on the COT control Buck circuits of two-phase containing flow equalizing function

Country Status (1)

Country Link
CN (1) CN106257812B (en)

Cited By (23)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN106899199A (en) * 2017-04-15 2017-06-27 深圳市广开源科技有限公司 A kind of ON-OFF control circuit
CN107590342A (en) * 2017-09-19 2018-01-16 无锡中微亿芯有限公司 A kind of impedance calibration circuit of area-saving design
CN107834653A (en) * 2017-11-28 2018-03-23 维沃移动通信有限公司 The battery control circuit and mobile terminal of a kind of mobile terminal
CN108199424A (en) * 2017-12-20 2018-06-22 成都芯源系统有限公司 Multi-phase charging circuit and control method thereof
WO2018214470A1 (en) * 2017-05-24 2018-11-29 华为技术有限公司 Current equalization circuit, array circuit and multi-phase converter
CN109039315A (en) * 2018-10-29 2018-12-18 上海艾为电子技术股份有限公司 A kind of analog switching circuit of adjustable opening time
CN109586565A (en) * 2018-11-28 2019-04-05 成都芯源系统有限公司 COT controlled multiphase direct current converter, control circuit and current sharing method
CN109742945A (en) * 2019-01-04 2019-05-10 泉芯电子技术(深圳)有限公司 Internal ripple compensation circuit and its control method based on COT control
CN110021992A (en) * 2018-01-10 2019-07-16 厦门雅迅网络股份有限公司 A kind of main secondary power switching circuit and method
CN110165875A (en) * 2019-06-26 2019-08-23 绍兴光大芯业微电子有限公司 Realize the circuit and corresponding driving method of constant on-time control model
CN111865081A (en) * 2020-07-15 2020-10-30 成都芯源系统有限公司 Phase sequence correction method and circuit of voltage converter adopting coupling inductor
CN112042094A (en) * 2018-02-24 2020-12-04 综合器件技术公司 Automatic phase shift and dynamic on-time controlled current balancing multiphase constant on-time buck converter
CN112701891A (en) * 2019-10-23 2021-04-23 北京小米移动软件有限公司 Power supply method and device, electronic equipment and storage medium
CN113078817A (en) * 2021-03-29 2021-07-06 浙江大学 Interphase current balance control system suitable for hysteresis control high-frequency two-phase Buck converter
CN113098272A (en) * 2021-04-23 2021-07-09 陕西亚成微电子股份有限公司 Control method and circuit of switching power supply
CN113300602A (en) * 2021-07-12 2021-08-24 华北电力大学 Novel staggered parallel BUCK converter and ripple wave eliminating method thereof
CN113556035A (en) * 2021-06-18 2021-10-26 华为技术有限公司 COT parallel circuit and power supply equipment
CN113556039A (en) * 2021-07-22 2021-10-26 无锡职业技术学院 Control system and method of multiphase DC-DC converter
US20220239228A1 (en) * 2021-01-25 2022-07-28 Rohm Co., Ltd. Control circuit and control method of dc/dc converter, power management circuit
CN114944748A (en) * 2022-07-20 2022-08-26 中科(深圳)无线半导体有限公司 Constant frequency control circuit and method for constant on-time control mode converter
CN115037125A (en) * 2022-06-22 2022-09-09 无锡格兰德微电子科技有限公司 High-reliability wide-voltage-range Buck controller circuit
CN115242059A (en) * 2022-09-21 2022-10-25 深圳英集芯科技股份有限公司 Multi-power-supply parallel current output device and method and electronic equipment
WO2024093595A1 (en) * 2022-11-03 2024-05-10 东南大学 Multiphase high-precision current-sharing control method applied to constant on-time control

Citations (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JPH1118415A (en) * 1997-06-27 1999-01-22 Nec Tohoku Ltd Current balance circuit of parallel operation power unit
JP2006271102A (en) * 2005-03-24 2006-10-05 Toshiba Mitsubishi-Electric Industrial System Corp Parallel multiplex chopper
CN104485816A (en) * 2014-12-15 2015-04-01 矽力杰半导体技术(杭州)有限公司 Interleaved switching power supply and control method thereof
CN105356734A (en) * 2015-11-18 2016-02-24 浙江大学 COT-control-based ripple-compensation-based buck circuit power management chip

Patent Citations (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JPH1118415A (en) * 1997-06-27 1999-01-22 Nec Tohoku Ltd Current balance circuit of parallel operation power unit
JP2006271102A (en) * 2005-03-24 2006-10-05 Toshiba Mitsubishi-Electric Industrial System Corp Parallel multiplex chopper
CN104485816A (en) * 2014-12-15 2015-04-01 矽力杰半导体技术(杭州)有限公司 Interleaved switching power supply and control method thereof
CN105356734A (en) * 2015-11-18 2016-02-24 浙江大学 COT-control-based ripple-compensation-based buck circuit power management chip

Cited By (36)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN106899199A (en) * 2017-04-15 2017-06-27 深圳市广开源科技有限公司 A kind of ON-OFF control circuit
CN106899199B (en) * 2017-04-15 2019-07-12 深圳市广开源科技有限公司 A kind of ON-OFF control circuit
WO2018214470A1 (en) * 2017-05-24 2018-11-29 华为技术有限公司 Current equalization circuit, array circuit and multi-phase converter
US11095224B2 (en) 2017-05-24 2021-08-17 Huawei Technologies Co., Ltd. Current equalization circuit, current equalization array circuit, and multiphase converter
CN107590342B (en) * 2017-09-19 2020-09-08 无锡中微亿芯有限公司 Impedance correction circuit with optimally designed area
CN107590342A (en) * 2017-09-19 2018-01-16 无锡中微亿芯有限公司 A kind of impedance calibration circuit of area-saving design
CN107834653A (en) * 2017-11-28 2018-03-23 维沃移动通信有限公司 The battery control circuit and mobile terminal of a kind of mobile terminal
CN108199424A (en) * 2017-12-20 2018-06-22 成都芯源系统有限公司 Multi-phase charging circuit and control method thereof
CN108199424B (en) * 2017-12-20 2021-06-15 成都芯源系统有限公司 Multi-phase charging circuit and control method thereof
CN110021992B (en) * 2018-01-10 2022-02-18 厦门雅迅网络股份有限公司 Main/standby power supply switching circuit and method
CN110021992A (en) * 2018-01-10 2019-07-16 厦门雅迅网络股份有限公司 A kind of main secondary power switching circuit and method
CN112042094B (en) * 2018-02-24 2021-12-10 综合器件技术公司 Automatic phase shift and dynamic on-time controlled current balancing multiphase constant on-time buck converter
CN112042094A (en) * 2018-02-24 2020-12-04 综合器件技术公司 Automatic phase shift and dynamic on-time controlled current balancing multiphase constant on-time buck converter
CN109039315B (en) * 2018-10-29 2023-09-22 上海艾为电子技术股份有限公司 Analog switch circuit for adjusting turn-on time
CN109039315A (en) * 2018-10-29 2018-12-18 上海艾为电子技术股份有限公司 A kind of analog switching circuit of adjustable opening time
CN109586565A (en) * 2018-11-28 2019-04-05 成都芯源系统有限公司 COT controlled multiphase direct current converter, control circuit and current sharing method
CN109742945B (en) * 2019-01-04 2024-03-08 泉芯电子技术(深圳)有限公司 Internal ripple compensation circuit based on COT control and control method thereof
CN109742945A (en) * 2019-01-04 2019-05-10 泉芯电子技术(深圳)有限公司 Internal ripple compensation circuit and its control method based on COT control
CN110165875A (en) * 2019-06-26 2019-08-23 绍兴光大芯业微电子有限公司 Realize the circuit and corresponding driving method of constant on-time control model
CN112701891A (en) * 2019-10-23 2021-04-23 北京小米移动软件有限公司 Power supply method and device, electronic equipment and storage medium
CN111865081B (en) * 2020-07-15 2021-05-18 成都芯源系统有限公司 Phase sequence correction method and circuit of voltage converter adopting coupling inductor
CN111865081A (en) * 2020-07-15 2020-10-30 成都芯源系统有限公司 Phase sequence correction method and circuit of voltage converter adopting coupling inductor
US20220239228A1 (en) * 2021-01-25 2022-07-28 Rohm Co., Ltd. Control circuit and control method of dc/dc converter, power management circuit
CN113078817A (en) * 2021-03-29 2021-07-06 浙江大学 Interphase current balance control system suitable for hysteresis control high-frequency two-phase Buck converter
CN113098272A (en) * 2021-04-23 2021-07-09 陕西亚成微电子股份有限公司 Control method and circuit of switching power supply
CN113556035A (en) * 2021-06-18 2021-10-26 华为技术有限公司 COT parallel circuit and power supply equipment
CN113300602B (en) * 2021-07-12 2022-01-11 华北电力大学 Novel staggered parallel BUCK converter and ripple wave eliminating method thereof
CN113300602A (en) * 2021-07-12 2021-08-24 华北电力大学 Novel staggered parallel BUCK converter and ripple wave eliminating method thereof
CN113556039A (en) * 2021-07-22 2021-10-26 无锡职业技术学院 Control system and method of multiphase DC-DC converter
CN113556039B (en) * 2021-07-22 2022-08-30 无锡职业技术学院 Control system and method of multiphase DC-DC converter
CN115037125A (en) * 2022-06-22 2022-09-09 无锡格兰德微电子科技有限公司 High-reliability wide-voltage-range Buck controller circuit
CN115037125B (en) * 2022-06-22 2024-04-26 无锡格兰德微电子科技有限公司 High-reliability wide-voltage-range Buck controller circuit
CN114944748A (en) * 2022-07-20 2022-08-26 中科(深圳)无线半导体有限公司 Constant frequency control circuit and method for constant on-time control mode converter
CN115242059A (en) * 2022-09-21 2022-10-25 深圳英集芯科技股份有限公司 Multi-power-supply parallel current output device and method and electronic equipment
CN115242059B (en) * 2022-09-21 2023-02-28 深圳英集芯科技股份有限公司 Multi-power-supply parallel current output device and method and electronic equipment
WO2024093595A1 (en) * 2022-11-03 2024-05-10 东南大学 Multiphase high-precision current-sharing control method applied to constant on-time control

Also Published As

Publication number Publication date
CN106257812B (en) 2018-05-22

Similar Documents

Publication Publication Date Title
CN106257812A (en) A kind of power management chip controlled based on COT containing flow equalizing function biphase Buck circuit
Ye et al. Improved bootstrap methods for powering floating gate drivers of flying capacitor multilevel converters and hybrid switched-capacitor converters
Saeedian et al. Step‐up switched‐capacitor module for cascaded MLI topologies
Qin et al. A high-power-density power factor correction front end based on seven-level flying capacitor multilevel converter
Abdelhakim et al. Three-phase three-level flying capacitors split-source inverters: Analysis and modulation
Zhu et al. PV isolated three-port converter and energy-balancing control method for PV-battery power supply applications
CN105356734B (en) It is a kind of that the Buck circuit power managing chips containing ripple compensation are controlled based on COT
Meyvaert et al. A light-load-efficient 11/1 switched-capacitor DC-DC converter with 94.7% efficiency while delivering 100 mW at 3.3 V
CN103197122B (en) Current detection circuit and switch-type regulator provided with same
CN105099188B (en) Dc-dc converter
Jung et al. An error-based controlled single-inductor 10-output DC-DC buck converter with high efficiency under light load using adaptive pulse modulation
CN106253671A (en) A kind of internal ripple being applicable to COT control compensates circuit
CN104901534B (en) A kind of slope compensation circuit and DC DC conversion equipments
WO2021022582A1 (en) Single-inductor multi-output dc-dc buck converter
CN102868297A (en) Deadline-fixed PFM (pulse frequency modulation) mode switching power supply controller
Upadhyay et al. Coupled‐inductor‐based high‐gain converter utilising magnetising inductance to achieve soft‐switching with low voltage stress on devices
Pulvirenti et al. 4-phase interleaved boost converter with IC controller for distributed photovoltaic systems
CN110311562A (en) A kind of DC-DC converter
Ma et al. A 1.8 V single-inductor dual-output switching converter for power reduction techniques
CA2983789A1 (en) Multi-port converter structure for dc/dc power conversion
Kapat et al. Achieving monotonic variation of spectral composition in DC–DC converters using pulse skipping modulation
CN106921294B (en) A kind of switching circuit and switching method of pulse wave modulation and the modulation of pulse hop cycle
CN113078817B (en) Interphase current balance control system suitable for hysteresis control high-frequency two-phase Buck converter
Hu et al. Synchronous high step-down ratio non-isolated LED constant current driver based on improved Watkins-Johnson topology
Lodh et al. High gain and efficient integrated flyback-Sepic DC-DC converter with leakage energy recovery mechanism

Legal Events

Date Code Title Description
C06 Publication
PB01 Publication
C10 Entry into substantive examination
SE01 Entry into force of request for substantive examination
GR01 Patent grant
GR01 Patent grant