CN105071051A - Improved Fabry-Perot resonant cavity antenna - Google Patents
Improved Fabry-Perot resonant cavity antenna Download PDFInfo
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Abstract
The invention relates to an improved Fabry-Perot resonant cavity antenna, belongs to the technical field of resonant cavity antennas, and aims at solving the problem that the present abry-Perot resonant cavity antenna is low in gain bandwidth. The antenna comprises a feed source and a portion reflecting plate, the feed source includes a rectangular patch antenna, the portion reflecting plate is arranged over the feed source in parallel, and the height of a resonant cavity body formed between the feed source and the portion reflecting plate is h; and the portion reflecting plate is of a double-layer coating structure, the upper surface of the portion reflecting plate includes a copper clad array of periodical arrangement, and the lower surface includes a hollow cross-shaped copper clad square array of periodical arrangement. A PRS structure of the portion reflecting plate enables a reflection value module value of the reflecting plate to be higher, the gain of the feed source antenna is thus improved, the phase and frequency of the reflection coefficient is positively correlated, and thus, the impedance bandwidth and the gain bandwidth are both improved.
Description
Technical field
The present invention relates to modified model Fabry-P é rot cavity antenna, belong to cavity antenna technical field.
Background technology
In recent years, the flat plane antenna of high-gain, low section is widely applied in centimeter wave, even millimeter wave communication, such as high speed wireless access, satellite receive-transmit system and point-to-point radio communication.But because the gain of individual antenna is less, bandwidth is narrower, Nowadays communication system requirements cannot be met.Array arrangement antenna can improve gain and bandwidth by coupling, but antenna feed system can be very complicated.Comparatively speaking, Fabry-P é rot cavity antenna is we provide the new method that a kind of simple raising antenna gain does not but increase feed system complexity.Traditional Fabry-P é rot cavity antenna is loaded on flat plane antenna by part reflecting plate PRS to form, and its resonant cavity height is the half of operation wavelength.
2005, AMC (artificialmagneticconductor, artificial magnetic conductor) was overlying on around plane feed antenna by the people such as Feresidis, successfully resonant cavity height is dropped to 1/4th of operation wavelength; 2014, part reflecting plate PRS was placed on the array of two flat plane antennas formation by Debogovic, achieved independently velocity of wave scanning and lobe size and controlled; Within 2013, there is Fabry-P é rot cavity antenna that can be conformal; 2014, Fabry-P é rot cavity antenna achieved function feed linear polarization mode being converted into entire physical circular polarization.Through development these years, Fabry-P é rot cavity antenna achieves a lot of function, but, after consulting relevant Fabry-P é rot cavity antenna data, we find, the 3dB gain bandwidth of traditional Fabry-P é rot cavity antenna is very low, and the Fabry-P é rot cavity antenna 3dB gain bandwidth described in above-mentioned document is no more than 2%.
Summary of the invention
The present invention seeks to, in order to solve the low problem of existing Fabry-P é rot cavity antenna gain bandwidth, to provide a kind of modified model Fabry-P é rot cavity antenna.
Modified model Fabry-P é rot cavity antenna of the present invention, it comprises feed and part reflecting plate,
Feed is rectangular patch antenna, and part reflecting plate is parallel to be placed in above feed, and the resonator height formed between feed and part reflecting plate is h;
Part reflecting plate is two-sided coat structure, and its upper surface is the deposited copper array of cycle arrangement, and lower surface is the cross deposited copper square array of hollow out of cycle arrangement;
The method making described cavity antenna obtain maximum gain is:
If the directivity function of feed is f (α), the reflection coefficient of part reflecting plate is
transmission coefficient is
the reflection coefficient on floor is set to 1e
j π, then synthesized by the wave beam being sent rear injection part sub reflector plate by feed, obtaining antenna gain G is:
001"/>
Wherein, α is feed launching beam and method phase angle, and r is the amplitude of reflection coefficient,
for reflection coefficient phase, ψ is transmission coefficient phase place;
Then determine that antenna gain G increases with the increase of part baffle reflection coefficient;
Make the beam phase of injection part sub reflector plate identical, realize superposing in the same way, then setting variable θ value is:
In formula, λ is operation wavelength;
Obtain after above formula distortion:
In formula, n is positive integer;
When resonator height be h is definite value, obtain into
for:
In formula, f is operating frequency, and c is the light velocity;
Then make reflection coefficient phase
by above formula value, and make part baffle reflection coefficient get maximum in the scope of allowing, obtain cavity antenna maximum gain.
In the deposited copper array of part reflecting plate upper surface, it is 4.12mm that middle column applies the length of side that all squares in copper apply copper, and applying all deposited copper mutual spacings in copper array is 0.88mm.
In the cross deposited copper square array of hollow out of part reflecting plate lower surface, the length of side in each cycle is 5mm, and the cross cross length of described hollow out is 4.6mm, and the cross cross width of hollow out is 2mm.
Advantage of the present invention: the present invention analyzes the reason that the traditional Fabry-P é rot cavity antenna 3dB gain bandwidth of restriction improves, and devises a kind of cavity antenna of uniqueness, meanwhile, its raising in 3dB gain bandwidth by simulating, verifying.Part reflecting plate PRS structure of the present invention, make his the amplitude of reflection coefficient comparatively large, this makes feed antenna gain be improved, and reflection coefficient phase exists positive correlation with frequency, and impedance bandwidth and gain bandwidth are all improved.
Accompanying drawing explanation
Fig. 1 is the structural representation of modified model Fabry-P é rot cavity antenna of the present invention;
Fig. 2 is the structural representation of part reflecting plate lower surface;
Fig. 3 is the structural representation of part reflecting plate upper surface;
Fig. 4 is the reflection coefficient of part reflecting plate periodic unit structure and the graph of relation of frequency;
Fig. 5 is reflection coefficient emulation and the measured result curve chart of cavity antenna;
Fig. 6 is the gain simulation result curve chart of Fabry-P é rot cavity antenna;
Fig. 7 is the emulation of 12GHz place Fabry-P é rot cavity antenna directivity factor and measured result curve chart.
Embodiment
Embodiment one: present embodiment is described below in conjunction with Fig. 1 to Fig. 3, modified model Fabry-P é rot cavity antenna described in present embodiment, it comprises feed 1 and part reflecting plate 2,
Feed 1 is rectangular patch antenna, and part reflecting plate 2 is parallel to be placed in above feed 1, and the resonator height formed between feed 1 and part reflecting plate 2 is h;
Part reflecting plate 2 is two-sided coat structure, and its upper surface is the deposited copper array of cycle arrangement, and lower surface is the cross deposited copper square array of hollow out of cycle arrangement;
The method making described cavity antenna obtain maximum gain is:
If the directivity function of feed 1 is f (α), the reflection coefficient of part reflecting plate 2 is
transmission coefficient is
the reflection coefficient on floor is set to 1e
j π, then synthesized by the wave beam being sent rear injection part sub reflector plate 2 by feed 1, obtaining antenna gain G is:
002"/>
Wherein, α is feed launching beam and method phase angle, and r is the amplitude of reflection coefficient,
for reflection coefficient phase, ψ is transmission coefficient phase place;
Then determine that antenna gain G increases with the increase of part reflecting plate 2 reflection coefficient;
Make the beam phase of injection part sub reflector plate 2 identical, realize superposing in the same way, then setting variable θ value is:
In formula, λ is operation wavelength;
Obtain after above formula distortion:
In formula, n is positive integer;
When resonator height be h is definite value, obtain into
for:
In formula, f is operating frequency, and c is the light velocity;
Then make reflection coefficient phase
by above formula value, and make part reflecting plate 2 reflection coefficient get maximum in the scope of allowing, obtain cavity antenna maximum gain.
Theory analysis in present embodiment: shown in Fig. 1, feed adopts rectangular patch, and floor is covered at back, and the acquisition basis of its antenna gain G is: suppose do not have loss, adopts simple velocity of wave light path analysis to obtain.From the expression formula of antenna gain G, part baffle reflection coefficient is larger, and the Fabry-P é rot cavity antenna gain of formation is larger.
Resonator height is the acquisition of h, needs the beam phase of setting section reflecting plate identical, to realize superposing in the same way, realizes high-gain.From the expression formula of h, the height of resonant cavity is determined by part reflecting plate lower surface reflected phase will and n value.By
expression formula known, in cavity antenna working frequency range, require that the reflected phase will of part reflecting plate increases with the increase of frequency, this successively decreases with frequency with the reflection coefficient phase of the part reflecting plate of existing Fabry-P é rot cavity antenna, causes the very low formation of bandwidth to contrast.
Embodiment two: present embodiment is described below in conjunction with Fig. 3, present embodiment is described further execution mode one, in the deposited copper array of part reflecting plate 2 upper surface, it is 4.12mm that middle column applies the length of side that all squares in copper apply copper, and applying all deposited copper mutual spacings in copper array is 0.88mm.
Embodiment three: present embodiment is described below in conjunction with Fig. 1 to Fig. 7, present embodiment is described further execution mode two, in the cross deposited copper square array of hollow out of part reflecting plate 2 lower surface, the length of side in each cycle is 5mm, the cross cross length of described hollow out is 4.6mm, and the cross cross width of hollow out is 2mm.
Each periodic unit of described part reflecting plate 2 lower surface be 5mm × 5mm, the dielectric-slab blockage of relative dielectric constant 1.5, thickness 1.5mm.
CST emulation experiment: shown in Fig. 4, known, structural design of the present invention meets expection requirement.Part baffle reflection coefficient modulus value minimum value is 0.74, when f=11.5GHz, and reflected phase will 120.02deg, when f=12.0GHz, reflected phase will 171.25deg, when f=12.5GHz, reflected phase will 171.79deg.With the increase of frequency, reflected phase will increases progressively, and can meet the phase difference caused by wave path-difference, thus realizes superposing in the same way.
Entire physical structure and emulation measured result:
Part reflecting plate of the present invention is loaded on feed antenna, used medium plate dielectric constant 2.2, thickness 1.5mm.After Computation and Simulation, determine that resonant cavity height is 12.3mm, close to the half of operation wavelength.
The reflection coefficient emulation of Fabry-P é rot cavity antenna is shown in Fig. 5 with measured result.When standing-wave ratio VSWR<2, Fabry-P é rot cavity antenna-10dB impedance bandwidth is 11.57GHz to 12.77GHz, and centre frequency is 12.17GHz, and resonance point frequency is 11.88GHz, this S
11value is-30dB, and visible energy obtains good radiation.
Frequency bandwidth is 1.20GHz, accounts for 9.8% of centre frequency.Measured result display-10dB impedance bandwidth is 11.235GHz to 13.700GHz, and centre frequency is 12.4695GHz, and frequency bandwidth 2.465GHz accounts for 19.77% of centre frequency.
The gain simulation result of Fabry-P é rot cavity antenna is shown in Fig. 6.Fabry-P é rot cavity antenna highest-gain appears at f=11.751GHz place, and when highest-gain is 16.16dB, f=11GHz, gain is 12.48dB, f=12GHz place, and gain is 14.813dB.-3dB gain bandwidth frequency range is 11.073GHz to 12.39GHz, altogether 1.317GHz, centre frequency 11.7315GHz, mutually p-3dB gain bandwidth 11.23%.Compared with traditional Fabry-P é rot cavity antenna-3dB gain bandwidth, improve 6 times, be increased to 11.23% by 2%.
The emulation of 12GHz place Fabry-P é rot cavity antenna directivity factor is shown in Fig. 7 with measured result, and matching is better, and in figure, A is measured curve, and B is simulation curve.
The very wide Fabry-P é rot cavity antenna of a kind of 3dB gain bandwidth of uniqueness is devised in invention.Antenna Entity measurement Xian Shi – 10dB impedance bandwidth range is 11.24 to 13.7GHz. maximum gain 16.16dB ， – 3dB gain bandwidth scope 11.07 to 12.39GHz, relative bandwidth 11.23%.And antenna resonance chamber height still keeps low section characteristic, resonant cavity height is close to the half of operation wavelength, and 12.33mm, result shows that this .Fabry-P é rot cavity antenna can be well suited in radio communication or satellite communication system.
The analytic process that the present invention improves gain is as follows:
Outgoing beam for part reflecting plate 2:
Wave beam 0 electric field E (0) is:
003"/>
E in formula
0for greatest irradiation field intensity;
Wave beam 1 electric field E (1) is:
Wave beam 2 electric field E (2) is:
Wave beam 3 electric field E (3) is:
Wave beam n electric field E (n) is:
Adopt the analysis of simple velocity of wave light path, the velocity of wave of injection part sub reflector plate synthesized, then has:
Sued for peace by Geometric Sequence, can obtain:
Wherein,
if the beam phase appearing PRS part reflecting plate is identical, can realizes superposing in the same way, realize high-gain, then requirement
namely
The height of visible resonant cavity has part reflecting plate lower surface reflected phase will and n value to determine.
But when resonator height one timing, have
Visible, in cavity antenna working frequency range, require that the reflected phase will of part reflecting plate increases with the increase of frequency.
Power spectral density maximum S is obtained by formula (2-7)
max:
004"/>
By the known gain size of relation of power spectral density and gain be
005"/>
S in formula
0for non-directional coefficient radiosity;
When α is very little, following formula is had to set up:
006"/>
Visible, the lower surface the amplitude of reflection coefficient of part reflecting plate is larger, and the gain of this antenna is larger.
Claims (3)
1. a modified model Fabry-P é rot cavity antenna, is characterized in that, it comprises feed (1) and part reflecting plate (2),
Feed (1) is rectangular patch antenna, and part reflecting plate (2) is parallel is placed in feed (1) top, and the resonator height formed between feed (1) and part reflecting plate (2) is h;
Part reflecting plate (2) is two-sided coat structure, and its upper surface is the deposited copper array of cycle arrangement, and lower surface is the cross deposited copper square array of hollow out of cycle arrangement;
The method making described cavity antenna obtain maximum gain is:
If the directivity function of feed (1) is f (α), the reflection coefficient of part reflecting plate (2) is
transmission coefficient is
the reflection coefficient on floor is set to 1e
j π, then synthesized by the wave beam being sent rear injection part sub reflector plate (2) by feed (1), obtaining antenna gain G is:
Wherein, α is feed launching beam and method phase angle, and r is the amplitude of reflection coefficient,
for reflection coefficient phase, ψ is transmission coefficient phase place;
Then determine that antenna gain G increases with the increase of part reflecting plate (2) reflection coefficient;
Make the beam phase of injection part sub reflector plate (2) identical, realize superposing in the same way, then setting variable θ value is:
In formula, λ is operation wavelength;
Obtain after above formula distortion:
In formula, n is positive integer;
When resonator height be h is definite value, obtain into
for:
In formula, f is operating frequency, and c is the light velocity;
Then make reflection coefficient phase
by above formula value, and make part reflecting plate (2) reflection coefficient get maximum in the scope of allowing, obtain cavity antenna maximum gain.
2. modified model Fabry-P é rot cavity antenna according to claim 1, it is characterized in that, in the deposited copper array of part reflecting plate (2) upper surface, it is 4.12mm that middle column applies the length of side that all squares in copper apply copper, and applying all deposited copper mutual spacings in copper array is 0.88mm.
3. modified model Fabry-P é rot cavity antenna according to claim 2, it is characterized in that, in the cross deposited copper square array of hollow out of part reflecting plate (2) lower surface, the length of side in each cycle is 5mm, the cross cross length of described hollow out is 4.6mm, and the cross cross width of hollow out is 2mm.
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Cited By (14)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN106876896A (en) * | 2017-02-28 | 2017-06-20 | 山东大学 | Circular polarized antenna |
| CN106876972A (en) * | 2017-02-28 | 2017-06-20 | 山东大学 | Sub-wavelength resonance cavity circularly polarized antenna |
| CN106898868A (en) * | 2017-02-28 | 2017-06-27 | 山东大学 | Large scale sub-wavelength cavity antenna based on magnetic single-negative material |
| CN107039758A (en) * | 2017-03-07 | 2017-08-11 | 广东通宇通讯股份有限公司 | Dual polarization broadband Fabry P é rot antennas |
| CN107069201A (en) * | 2017-02-28 | 2017-08-18 | 山东大学 | Sub-wavelength cavity antenna based on magnetic single-negative material |
| CN107317102A (en) * | 2017-05-26 | 2017-11-03 | 上海无线电设备研究所 | A kind of integrated high-gain band cover antenna coupled system and its design method |
| CN107369909A (en) * | 2017-06-16 | 2017-11-21 | 西安交通大学 | A kind of high scan angles high-gain Ka wave bands phased array flat-plate lens antenna |
| CN107482313A (en) * | 2017-06-19 | 2017-12-15 | 西北工业大学 | A kind of grading structure wideband resonance chamber antenna |
| CN109509990A (en) * | 2018-12-29 | 2019-03-22 | 四川睿迪澳科技有限公司 | All-metal FP cavity antenna based on choke groove and non-homogeneous coating |
| CN110534166A (en) * | 2019-08-30 | 2019-12-03 | 哈尔滨工业大学 | The method for removing Fabry-Perot puppet resonance backstepping composite material electromagnetic parameter |
| CN110808461A (en) * | 2019-11-22 | 2020-02-18 | 东南大学 | Low-profile holographic imaging antenna based on Fabry-Perot resonant cavity type structure |
| CN111226346A (en) * | 2017-10-18 | 2020-06-02 | 瑞典爱立信有限公司 | Adjustable resonant cavity |
| CN111755809A (en) * | 2020-07-30 | 2020-10-09 | 上海无线电设备研究所 | Miniaturized dual-polarized broadband Fabry-Perot resonant cavity antenna |
| CN109509990B (en) * | 2018-12-29 | 2024-05-28 | 四川睿迪澳科技有限公司 | All-metal FP resonant cavity antenna based on choke groove and non-uniform covering layer |
Citations (2)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN102769198A (en) * | 2012-06-29 | 2012-11-07 | 深圳光启创新技术有限公司 | Artificial electromagnetic material, radome and antenna system |
| CN103296348A (en) * | 2012-02-29 | 2013-09-11 | 深圳光启创新技术有限公司 | Artificial electromagnetic material and filter using same |
-
2015
- 2015-07-27 CN CN201510446373.6A patent/CN105071051A/en active Pending
Patent Citations (2)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN103296348A (en) * | 2012-02-29 | 2013-09-11 | 深圳光启创新技术有限公司 | Artificial electromagnetic material and filter using same |
| CN102769198A (en) * | 2012-06-29 | 2012-11-07 | 深圳光启创新技术有限公司 | Artificial electromagnetic material, radome and antenna system |
Non-Patent Citations (2)
| Title |
|---|
| MUDAR AL-JOUMAYLY: "A New Technique for Design of Low-Profile,Second-Order, Bandpass Frequency Selective Surfaces", 《IEEE TRANSACTIONS ON ANTENNAS AND PROPAGATION》 * |
| 张迪: "基于双层FSS的高增益微带天线", 《2015年全国微波毫米波会议论文集》 * |
Cited By (17)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN106876972A (en) * | 2017-02-28 | 2017-06-20 | 山东大学 | Sub-wavelength resonance cavity circularly polarized antenna |
| CN106898868A (en) * | 2017-02-28 | 2017-06-27 | 山东大学 | Large scale sub-wavelength cavity antenna based on magnetic single-negative material |
| CN107069201A (en) * | 2017-02-28 | 2017-08-18 | 山东大学 | Sub-wavelength cavity antenna based on magnetic single-negative material |
| CN106876896A (en) * | 2017-02-28 | 2017-06-20 | 山东大学 | Circular polarized antenna |
| CN107039758B (en) * | 2017-03-07 | 2019-09-27 | 广东通宇通讯股份有限公司 | Dual polarization broadband Fabry-P é rot antenna |
| CN107039758A (en) * | 2017-03-07 | 2017-08-11 | 广东通宇通讯股份有限公司 | Dual polarization broadband Fabry P é rot antennas |
| CN107317102B (en) * | 2017-05-26 | 2020-02-21 | 上海无线电设备研究所 | Integrated high-gain antenna coupling system with cover and design method thereof |
| CN107317102A (en) * | 2017-05-26 | 2017-11-03 | 上海无线电设备研究所 | A kind of integrated high-gain band cover antenna coupled system and its design method |
| CN107369909A (en) * | 2017-06-16 | 2017-11-21 | 西安交通大学 | A kind of high scan angles high-gain Ka wave bands phased array flat-plate lens antenna |
| CN107482313A (en) * | 2017-06-19 | 2017-12-15 | 西北工业大学 | A kind of grading structure wideband resonance chamber antenna |
| CN111226346A (en) * | 2017-10-18 | 2020-06-02 | 瑞典爱立信有限公司 | Adjustable resonant cavity |
| US11670832B2 (en) | 2017-10-18 | 2023-06-06 | Telefonaktiebolaget Lm Ericsson (Publ) | Tunable resonance cavity |
| CN109509990A (en) * | 2018-12-29 | 2019-03-22 | 四川睿迪澳科技有限公司 | All-metal FP cavity antenna based on choke groove and non-homogeneous coating |
| CN109509990B (en) * | 2018-12-29 | 2024-05-28 | 四川睿迪澳科技有限公司 | All-metal FP resonant cavity antenna based on choke groove and non-uniform covering layer |
| CN110534166A (en) * | 2019-08-30 | 2019-12-03 | 哈尔滨工业大学 | The method for removing Fabry-Perot puppet resonance backstepping composite material electromagnetic parameter |
| CN110808461A (en) * | 2019-11-22 | 2020-02-18 | 东南大学 | Low-profile holographic imaging antenna based on Fabry-Perot resonant cavity type structure |
| CN111755809A (en) * | 2020-07-30 | 2020-10-09 | 上海无线电设备研究所 | Miniaturized dual-polarized broadband Fabry-Perot resonant cavity antenna |
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