CN104253659B - Spectrum sensing method and device - Google Patents
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Abstract
The invention relates to a spectrum sensing method and a spectrum sensing device. The method comprises the following steps: S1, performing the self interference suppression calculation on received signals to obtain sampling signals; S2, calculating a decision threshold according to the number of phase adjacent differences between sampling chips of the sampling signals and the default false-alarm probability; S3, calculating the phase adjacent difference between the sampling chips, and calculating the average value of the phase adjacent differences; S4, calculating the cumulative amount of the phase adjacent differences according to the average value of the phase adjacent differences; S5, judging whether a master user exists or not according to the cumulative amount of the phase adjacent differences and the decision threshold. According to the sensing method and the spectrum sensing device, the purpose that sensing and transmission are simultaneously carried out by a full-duplex sensing method can be achieved, the sensing speed is quick, the computational complexity is low and the stability is good.
Description
Technical field
The present invention relates to wireless communication field, more particularly, to a kind of full duplex frequency spectrum detecting method based on the adjacent difference of phase place
And its device.
Background technology
The explosive increase of radio communication species and portfolio, makes frequency spectrum scarcity problem increasingly serious.But world wide
Frequency spectrum investigation find that allocated frequency spectrum resource is not used effectively.The proposition of cognitive radio technology is exactly to understand
Certainly frequency spectrum is in short supply and contradiction between the utilization of resources is insufficient.In cognitive radio, secondary user's can not made to primary user
Into mandate frequency range is dynamically accessed in the case of interference, so as to improve frequency spectrum service efficiency.In order to not interfere to primary user,
Secondary user's first to authorizing frequency range to detect will determine whether primary user takes frequency spectrum before access.So, frequency spectrum detection
Technology is one of the most key technology of cognitive radio.
Existing frequency spectrum detecting method mainly has energy measuring, cycle specificity detection and matched filter detection etc..These
Method is difficult in detection performance, and computation complexity and stability aspect all reach preferable effect, all exist in practical application
Various shortcomings.
If any the Chinese patent of an Application No. " CN 200910046690 ", a kind of feature based circulation frequency is disclosed
The frequency spectrum detecting method of rate.The method is processed using the Cyclic Spectrum that finite length is carried out to signal, by differentiating it in circulation frequency
Cyclic Spectrum numerical value at rate whether there is judging primary user's signal.It realizes that process is：First, acquisition noise sample is followed
The process of ring spectrum obtains noise circulation spectral sequence, and in conjunction with desired false-alarm probability value decision threshold is set；Then to target frequency
The signal of section is sampled, and carries out Cyclic Spectrum process；Finally, comparison object signal value and door for above setting at Cyclic Spectrum
Limit compares, if being more than thresholding, then it is assumed that the frequency range is taken by primary user, otherwise it is assumed that the frequency range is not taken by primary user,
Secondary user's can access the frequency range.Said method carries out frequency spectrum detection by using the method that characteristic cycle is composed, although can be with
The detection performance under Low SNR is effectively improved, but its computation complexity is very high, it is impossible to make detection performance and calculate multiple
Miscellaneous degree reaches preferable unification.In actual applications, particularly end side is difficult to realize.
Current frequency spectrum detection algorithm is mainly half-duplex frequency spectrum detection, and secondary user's are in the beginning of each signal frame
Frequency spectrum detection is carried out with the shorter time whether occupied to judge frequency spectrum, if not having occupied, secondary user's are in the signal
Frame in transmission information, does not otherwise transmit.If however, primary user's state (i.e. channel occupation status) the frequency spectrum detection time period it
After there occurs change, it is possible to cause congestion or the waste of frequency spectrum.For example：If detection finds that frequency spectrum is unoccupied, secondary
User's sending signal, now primary user's state change, proceed-to-send signal, this will cause same in two users of this frequency range
Shi Jinhang signal transmissions, necessarily cause congestion.In turn, if detection finds that frequency spectrum is occupied, secondary user's stop sending
Signal, now primary user's state change after detection time section, also no longer sending signal, this will subtract will the availability of frequency spectrum
It is little.
The content of the invention
The present invention provides a kind of frequency spectrum detecting method and its device, and using the frequency spectrum detecting method of work of enjoying a double blessing inspection can be realized
The purpose for carrying out simultaneously is surveyed and transmits, and its detection speed is fast, and computation complexity is low, good stability.
According to above-mentioned purpose, the invention provides a kind of frequency spectrum detecting method, methods described includes：S1, the docking collection of letters number
Carry out self-interference to suppress to calculate, obtain sampled signal；S2, according to the number of the adjacent difference of phase place of the sampling chip of the sampled signal
With default false-alarm probability, decision threshold is calculated；S3, the phase place for calculating the sampling chip is adjacent poor, and it is adjacent to calculate the phase place
Poor average；S4, according to the adjacent difference accumulation amount of mean value computation phase place of the adjacent difference of the phase place；S5, it is cumulative according to the adjacent difference of the phase place
Amount and the decision threshold judge that primary user whether there is.
Wherein, step S1 is specifically included：S11, the docking collection of letters number is modeled；S12, calculate it is described reception signal with
The degree of association of spontaneous emission signal；S13, sets up correlation matrix；S14, according to the correlation matrix linear self-interference is calculated
Value；S15, according to the value of the linear self-interference, the receipt signal model set up by step S11 is generated self-interference and is suppressed
Sampled signal afterwards.
Specifically, the sampling chip lengths of the sampled signal are required according to detection duration and sampling rate determines.
Specifically, the decision threshold is calculated according to below equation：
Wherein, N is the number of the adjacent difference of sampling chip phase of the sampled signal, PfFor the false-alarm probability, erfc-1For
Remaining compensating error functionInverse function.
Specifically, step S3 includes：
S31, calculates the phase theta of each sampling chip of the sampled signaln；
Wherein, Re (r (n)) and Im (r (n)) be respectively it is described sampling chip real part and imaginary part, () mod2 π be in order to
Ensure the phase place for calculating in the interval of [0,2 π].S32：According to the phase of each sampling chip of the sampled signal for calculating
Position, the phase place for calculating the sampling chip is adjacent poor, the adjacent difference ψ of the phase placenComputing formula be：ψn=(θn+1-θn)mod2π；
S33：Calculate the mean μ of the adjacent difference of the phase placeψ：
In addition, step S4 includes：The adjacent difference accumulation amount of the phase place is calculated according to below equation：
In addition, step S5 is specifically included：
S51：Calculate the adjacent difference accumulation amount ψ of the phase placesumWith the absolute value of the difference of N π, i.e., | ψsum-Nπ|；
S52：It is relatively more described | ψsum- N π | value and the decision thresholdNumerical values recited；
S53：IfJudge that primary user's signal is present；Otherwise judge that primary user's signal is not present.
According to another aspect of the present invention, there is provided a kind of frequency spectrum detection device, described device includes：Self-interference suppresses single
Unit, carries out self-interference and suppresses to calculate for the docking collection of letters number, obtains sampled signal；Threshold sets module, according to the sampling letter
Number sampling chip the adjacent difference of phase place number and default false-alarm probability, calculate decision threshold；The adjacent difference mean value computation mould of phase place
Block, the phase place for calculating the sampling chip is adjacent poor, and calculates the average of the adjacent difference of the phase place；The adjacent difference accumulation amount of phase place is calculated
Module, for according to the adjacent difference accumulation amount of mean value computation phase place of the adjacent difference of the phase place；Determination module, for adjacent according to the phase place
Difference accumulation amount and the decision threshold judge that primary user whether there is.
A kind of frequency spectrum detection device of the present invention, can realize detecting and passing using the frequency spectrum detecting method of work of enjoying a double blessing
It is defeated and to be suppressed by not needing the self-interference of Cyclic Prefix while the purpose for carrying out, the accuracy of frequency spectrum detection can be improved；
Meanwhile, using the frequency spectrum detecting method based on the adjacent difference of phase place, its computation complexity is greatly reduced, and Simultaneous Stabilization increases.
Description of the drawings
The features and advantages of the present invention can be more clearly understood from by reference to accompanying drawing, accompanying drawing is schematic and should not manage
Solution is to carry out any restriction to the present invention, in the accompanying drawings：
Fig. 1 shows a kind of flow chart of frequency spectrum detecting method of the present invention；
Fig. 2 shows a kind of structured flowchart of frequency spectrum detection device of the present invention；
Specific embodiment
Below in conjunction with accompanying drawing, embodiments of the present invention is described in detail.
Embodiments of the invention propose a kind of full duplex frequency spectrum detecting method based on the adjacent difference of phase place.
The basic thought of full-duplex communication is spontaneous emission signal known to receiver, therefore can eliminate self-interference to realize sending out
Penetrate, receive the same frequency band transmission of signal.The frequency spectrum detection of full-duplex communication, one is the need for the self-interference Restrainable algorithms imitated to carry
The accuracy of high detection, two be need complexity it is relatively low, detection better performances frequency spectrum detection algorithms with realize detect it is quick,
Accurately carry out.
The frequency spectrum detecting method of the present invention is described in detail below by way of specific embodiment.
Fig. 1 shows a kind of flow chart of frequency spectrum detecting method of the present invention.
As shown in figure 1, the frequency spectrum detecting method of embodiments of the invention includes step：
Step S1, the docking collection of letters number carries out self-interference and suppresses to calculate, and obtains sampled signal.
In the frequency spectrum detecting method of full duplex, self-interference suppresses to realize by two steps：Simulation is eliminated and numeral disappears
Remove.Simulation is eliminated and mainly suppressed from sending signal by following two modes：Isolation transmitting and reception antenna, in some way
Arrangement reception antenna is cancelled out each other come the signal for ensureing reception.Signal is received afterwards and is converted to digital sampled signal, now adopt
Numeral eliminates the linearity and non-linearity part for suppressing spontaneous emission signal.
In the present embodiment, the linear self-interference part in eliminating mainly for numeral is calculated.The part interference comes
Come from direct leakage from transmitting antenna to reception antenna and the impact of surrounding.
In one embodiment, the calculation procedure for suppressing to self-interference is as follows：
S11, the docking collection of letters number is modeled：
In above formula, r (k) is reception signal, siK () is the spontaneous emission signal of i-th emission source, h (l) is l paths
Direct leakage and reflection multipath component.spK () and w (k) are respectively the signal and noise for wanting to receive, L is the road of sampling
Footpath quantity.Because siK (), in receiving terminal, it is known that problem reduction is to estimate multipath component, and the problem equivalent is classical channel
Estimation problem.For the system for having known prefix, it is possible to use LMSE method.But some systems do not have prefix, i.e.,
The system for having prefix to those is made, the estimation to multipath is also limited to the length and occurrence frequency of prefix.Therefore one kind is needed not
Depend on the channel estimation method of prefix.
S12, calculates the degree of association for receiving signal and spontaneous emission signal：
Spontaneous emission signal is generally uncorrelated to signal and noise signal that hope is received, when correlation length is sufficiently large, on
Last two of formula are intended to zero.Therefore, above formula can be reduced to：
WhereinFor the auto-correlation of spontaneous emission signal.
Because spontaneous emission signal receiving end is, it is known that its auto-correlation can be obtained by calculating.Therefore, c (k) is changed into one
Unknown quantity is h (l)*, it is known that measure as the linear representation of R (k-l).
S13, sets up correlation matrix.
L paths are included in the channel response for receiving signal, therefore containing L unknown number.We can calculate 2L-1
Individual correlation coefficient is simultaneously expressed relational expression with following matrix form.
May be irreversible in view of autocorrelation matrix, the channel of estimation can be expressed as：
H'=R+*c*
R in above formula+It is the generalized inverse of autocorrelation matrix.
S14, according to correlation matrix the value of linear self-interference is calculated.
After estimator h' of channel is obtained in step S14, you can substituted into the formula of the reception signal in step S11
In, to eliminate the self-interference of secondary user's.What is be achieved in that will be primary user's signal and noise, and then primary user can be believed
Number detected.
Step S2, according to the number and default false-alarm probability of the adjacent difference of phase place of the sampling chip of sampled signal, calculating is sentenced
Certainly thresholding；
In the present embodiment, chip lengths N+1 and false-alarm probability P of sampled signalfIt is that, by outside input, sampling chip is long
Degree is required according to detection duration and sampling rate determines.
Number N of the adjacent difference of the phase place of sampling chip lengths is can determine according to chip lengths, and according to adjacent difference number N of phase place
With false-alarm probability PfTo determine decision thresholdI.e.
Wherein, erfc-1For remaining compensating error functionInverse function.
For false-alarm probability PfSetting, according to noise adjacent phase difference ψ 'n=θn+1-θnObey the triangle point of [- 2 π, 2 π]
Cloth, obtains formula：
It is ψ due to defining adjacent signal phase contrastn=(θn+1-θn) mod2 π=ψ 'nMod2 π, and for -2 π≤ψ 'n＜
0, ψ 'nMod2 π=ψ 'n+ 2 π, the then noise adjacent phase difference for defining is distributed as：
The average and variance of the adjacent difference accumulation amount of noise phase can be calculated according to above-mentioned formula:
When adjacent difference number N of phase place is very big, according to central limit theorem, the adjacent difference accumulation amount ψ of noise phasesumProbability point
Cloth is approximately average for N μψ=N π2/ 3, variance isGauss distribution.Therefore, the adjacent difference of noise phase is cumulative
The distribution of amount can be with approximate representation：
When one thresholding of settingWhen, false-alarm probability PfCan be expressed as：
Usually, decision thresholdSetting to false-alarm probability PfWith detection probability PdImpact will be produced.Due to detection
Probability PdWith the relating to parameters of primary user's signal, and these parameters are generally difficult to obtain in a practical situation, therefore in practice,
Generally according to false-alarm probability PfTo determine decision threshold.Therefore, false-alarm probability P that detection is required is being knownfAnd sampled signal
During number N of the adjacent difference of phase place of sampling chip, decision thresholdCan be calculated by formula once：
Wherein, erfc is remaining compensating error function, anderfc-1It is remaining compensating error function erfc
Inverse function.
Step S3, the phase place for calculating sampling chip is adjacent poor, and calculates the average of the adjacent difference of phase place.
Step S3 is specifically included：
S31, calculates the phase theta of each sampling chip of the sampled signaln。
In the calculating of the adjacent difference of phase place of each the sampling chip for carrying out sampled signal, sampled signal is defined as first：
Wherein, T is the sampling interval, A (nT) andIt is respectively the instantaneous amplitude and instantaneous phase of primary user's signal, fc
It is sample frequency, x (nT) and y (nT) is respectively the in-phase component and quadrature component of white Gaussian noise.And define Gauss white noise
The in-phase component and quadrature component mean μ of soundx=μy=0, variance
According to the sampled signal of definition, the phase place of each sampling chip of sampled signal is calculated：
Wherein, Re (r (n)) and Im (r (n)) are respectively the real parts and imaginary part of sampled signal, and () mod2 π are to ensure
The phase place of calculating is in the interval of [0,2 π].
Step S32, according to the phase place of each sampling chip of the sampled signal for calculating, the phase place for calculating sampling chip is adjacent
Difference, and the adjacent difference ψ of phase placenComputing formula be：
ψn=(θn+1-θn)mod2π；
S33, calculates the mean μ of the adjacent difference of phase placeψ：
Step S4, calculates adjacent signal phase contrast accumulation amount：
Step S5, judges that primary user whether there is according to the adjacent difference accumulation amount of phase place and decision threshold.
Specifically, step S5 includes：
S51：Calculate adjacent phase difference accumulation amount ψsumWith the absolute value of the difference of N π, i.e., | ψsum-Nπ|；
S52：Relatively | ψsum- N π | value and decision thresholdNumerical values recited；
S53：IfJudge that primary user's signal is present；Otherwise judge that primary user's signal is not present.
Fig. 2 shows a kind of structured flowchart of the frequency spectrum detection device using the present invention；
With reference to Fig. 2, an alternative embodiment of the invention provides a kind of fundamental frequency spectrum detection device, and the device includes：
Self-interference suppresses unit 10, carries out self-interference for the docking collection of letters number and suppresses to calculate, and obtains sampled signal；
Threshold sets module 20, it is general according to the number and default false-alarm of the adjacent difference of phase place of the sampling chip of sampled signal
Rate, calculates decision threshold；
The adjacent difference mean value computation module 30 of phase place, the phase place for calculating sampling chip is adjacent poor, and calculates the equal of the adjacent difference of phase place
Value；
The adjacent difference accumulation amount computing module 40 of phase place, for according to the adjacent difference accumulation amount of mean value computation phase place of the adjacent difference of phase place；
Determination module 50, for judging that primary user whether there is according to the adjacent difference accumulation amount of phase place and decision threshold.
A kind of frequency spectrum detecting method of the present invention and its device, can solve traditional frequency spectrum detection due to detecting and passing
The defeated relevant issues that can not be caused simultaneously, realize detection and transmit synchronous carrying out.Meanwhile, proposing in the present invention need not
The self-interference Restrain measurement of Cyclic Prefix, contributes to the realization of full duplex frequency spectrum detection mechanism.
In addition, frequency spectrum detecting method proposed by the present invention only needs the phase place of signal calculated and the statistic of test based on it
(i.e. the adjacent difference accumulation amount of phase place), computation complexity is relatively low.Meanwhile, from the calculating of decision threshold as can be seen that setting for decision threshold
Fixed it doesn't matter with noise power, therefore does not also receive that noise power is probabilistic to be affected substantially, and stability is fine.In addition, this
Invention is started with from the phase place visual angle of signal, carries out frequency spectrum detection, and under Low SNR, amplitude is compared in the change of signal phase
It is much more obvious, therefore the method detects that performance is more preferable under Low SNR.
By specific experiment, in 1000 sampled points, false-alarm probability is 1%, and signal to noise ratio is can to reach under the conditions of -7dB
99% detection probability.
Although being described in conjunction with the accompanying embodiments of the present invention, those skilled in the art can be without departing from this
Various modifications and variations are made in the case of bright spirit and scope, such modification and modification are each fallen within by claims
Within limited range.
Claims (3)
1. a kind of frequency spectrum detecting method, it is characterised in that methods described includes：
S1, the docking collection of letters number carries out self-interference and suppresses to calculate, and obtains sampled signal；Step S1 is specifically included：
S11, the docking collection of letters number is modeled, using equation below：
In above formula, r (k) is reception signal, siK () is the spontaneous emission signal of i-th emission source, h (l) is the direct of l paths
The multipath component revealed and reflect；spK () and w (k) are respectively the signal and noise for wanting to receive, L is the number of paths of sampling；
S12, calculates the degree of association for receiving signal and spontaneous emission signal；
S13, sets up correlation matrix；
S14, according to the correlation matrix value of linear self-interference is calculated；
S15, according to the value of the linear self-interference, the receipt signal model set up by step S11 generates self-interference suppression
Sampled signal after system；
S2, according to the number and default false-alarm probability of the adjacent difference of phase place of the sampling chip of the sampled signal, calculates decision gate
Limit；The decision threshold is calculated according to below equation：
Wherein, N is the number of the adjacent difference of phase place of the sampling chip of the sampled signal, PfFor the false-alarm probability, erfc-1For remaining
Compensating error functionInverse function；
S3, the phase place for calculating the sampling chip is adjacent poor, and calculates the average of the adjacent difference of phase place of the sampling chip；The step
S3 includes：
S31, calculates the phase theta of each sampling chip of the sampled signaln；
Wherein, Re (r (n)) and Im (r (n)) are respectively the real parts and imaginary part of the sampling chip, and () mod2 π are to ensure
The phase place of calculating is in the interval of [0,2 π]；
S32：According to the phase place of each sampling chip of the sampled signal for calculating, the phase place for calculating the sampling chip is adjacent
Difference, the adjacent difference ψ of the phase placenComputing formula be：ψn=(θn+1-θn)mod2π；
S33：Calculate the average of the adjacent difference of the phase place
S4, according to the adjacent difference accumulation amount of mean value computation phase place of the adjacent difference of the phase place；Step S4 includes：
The adjacent difference accumulation amount of the phase place is calculated according to below equation：
S5, judges that primary user whether there is according to the adjacent difference accumulation amount of the phase place and the decision threshold；Step S5 is concrete
Including：
S51：Calculate the adjacent difference accumulation amount ψ of the phase placesumWith the absolute value of the difference of N π, i.e., | ψsum-Nπ|；
S52：It is relatively more described | ψsum- N π | value and the decision thresholdNumerical values recited；
S53：IfJudge that primary user's signal is present；Otherwise judge that primary user's signal is not present.
2. a kind of frequency spectrum detecting method according to claim 1, it is characterised in that the sampling chip of the sampled signal is long
Degree is required according to detection duration and sampling rate determines.
3. a kind of frequency spectrum detection device, it is characterised in that described device includes：
Self-interference suppresses unit, carries out self-interference for the docking collection of letters number and suppresses to calculate, and obtains sampled signal；The self-interference suppression
Unit processed is used to perform following steps：
S11, the docking collection of letters number is modeled, using equation below：
In above formula, r (k) is reception signal, siK () is the spontaneous emission signal of i-th emission source, h (l) is the direct of l paths
The multipath component revealed and reflect；spK () and w (k) are respectively the signal and noise for wanting to receive, L is the number of paths of sampling；
S12, calculates the degree of association for receiving signal and spontaneous emission signal；
S13, sets up correlation matrix；
S14, according to the correlation matrix value of linear self-interference is calculated；
S15, according to the value of the linear self-interference, the receipt signal model set up by step S11 generates self-interference suppression
Sampled signal after system；
Threshold sets module, according to the number and default false-alarm probability of the adjacent difference of phase place of the sampling chip of the sampled signal,
Calculate decision threshold；The decision threshold is calculated according to below equation：
Wherein, N is the number of the adjacent difference of phase place of the sampling chip of the sampled signal, PfFor the false-alarm probability, erfc-1For remaining
Compensating error functionInverse function；
The adjacent difference mean value computation module of phase place, the phase place for calculating the sampling chip is adjacent poor, and calculates the adjacent difference of the phase place
Average；The adjacent difference mean value computation module of the phase place is used to perform following steps：
S31, calculates the phase theta of each sampling chip of the sampled signaln；
Wherein, Re (r (n)) and Im (r (n)) are respectively the real parts and imaginary part of the sampling chip, and () mod2 π are to ensure
The phase place of calculating is in the interval of [0,2 π]；
S32：According to the phase place of each sampling chip of the sampled signal for calculating, the phase place for calculating the sampling chip is adjacent
Difference, the adjacent difference ψ of the phase placenComputing formula be：ψn=(θn+1-θn)mod2π；
S33：Calculate the average of the adjacent difference of the phase place
The adjacent difference accumulation amount computing module of phase place, for according to the adjacent difference accumulation amount of mean value computation phase place of the adjacent difference of the phase place；It is described
The adjacent difference accumulation amount computing module of phase place obtains the adjacent difference accumulation amount of phase place using below equation：
Determination module, for judging that primary user whether there is according to the adjacent difference accumulation amount of the phase place and the decision threshold；It is described
Determination module is used to perform following steps：
S51：Calculate the adjacent difference accumulation amount ψ of the phase placesumWith the absolute value of the difference of N π, i.e., | ψsum-Nπ|；
S52：It is relatively more described | ψsum- N π | value and the decision thresholdNumerical values recited；
S53：Judge that primary user's signal is present；Otherwise judge that primary user's signal is not present.
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