CN104052711A - Quadrature error correction using polynominal models in tone calibration - Google Patents

Abstract

One example embodiment provides a system, apparatus, and method for using polynomial models in tone calibration for quadrature error correction in I/Q receivers. In one example embodiment, method for calibrating an I/Q receiver is provided and includes receiving a first mismatch parameter indicating a mismatch between I and Q channels of the I/Q receiver; and estimating a second mismatch parameter from the first mismatch parameter using a polynomial model.

Description

Use the multinomial model in tone calibration to carry out quadrature error correction

Priority data

The application advocates the temporary patent application sequence number No.61/798 that on March 15th, 2013 submits to, 197 priority, and described temporary patent application is all incorporated to herein by reference.

Technical field

The disclosure relates generally to homophase and quadrature (I/Q) receiver signal is processed, and more specifically relates to a kind of for device, method and system at the gain of I/Q receiver alignment and unbalance in phase.

Background technology

Quadrature modulation is the technology for transmit communications signals.In quadrature modulation, reflector is simultaneously at homophase (I) passage and quadrature phase (Q) passage transmitting data.In I passage and Q passage, each carries independent data flow and phase shift 90 degree relative to each other in carrier frequency.In I/Q receiver, I and Q channel signal receive in carrier frequency, lower conversion and demodulation be with the I passage from independent and Q routing restoration data.

I/Q receiver comprises for each independent simulation process path of I passage and Q passage.Each in I and Q channel path comprises the analog signal process receiving and is converted into the processing components of digital form, such as for example, and frequency mixer, AD converter (ADC), amplifier and filter.Under these independent assemblies, change and process the channel signal data in each path.In I/Q receiver, use the so-called I/Q of independent I and Q simulation process Path generation uneven, I/Q imbalance is that phase place and the amplitude between I and Q channel signal do not mated.In I/Q receiver, the unbalanced main source of I/Q is that I and Q passage are processed in path not mating between assembly independent in each.

There is the I/Q of two types uneven: not mating of frequency-independent and not mating of frequency dependence.It is that the phase place that in the frequency mixer of each I/Q simulaed path, local oscillator (LO) produces is not mated that frequency-independent does not mate.These do not mate on frequency spectrum is similarly, and can further successfully be estimated to carry out error correction.It is that phase place and the amplitude that in I and Q tunnels analogy path, the base band component in each produces do not mated that frequency dependence does not mate.Frequency dependence does not mate that to make not mate estimation technique complicated, because do not mate disunity on frequency spectrum.

Developed the technology of the not match parameter of the simulaed path of estimating I/Q receiver.These technology comprise real-time estimation, and wherein, between the real-time operating period of receiver, receiver estimates that match parameter does not also compensate and do not mate.Described technology also comprises that off-line estimates, wherein, when the unmatched estimation of execution and correction parameter are transfused to receiver, receiver is not in use.Off-line method of estimation can be injected receiver at the input of I passage and Q passage test tone by tone injection technique, thereby carrys out not mating between calibrated channel by the method for tone calibration.In low noise environment and further, when the shake of test tone signal is less than certain level, it is the most effective that described technology has been proved to be.In high noise-level environment or when test tone signal jitter is risen over certain level, the validity reduction of these known technologies.Therefore, for estimating that I/Q passage is unmatched, will provide advantage at noisy environment and/or in the situation that the high jitter level of test tone signal has the method for improving effect.

Summary of the invention

It is a kind of at the unbalanced device of I/Q receiver alignment I/Q, method and system that the disclosure provides.According in embodiment of the present disclosure, multinomial model is applied to the result of tone calibration to generate for calibrating the not match parameter of I/Q receiver.An exemplary embodiment provides a kind of system, apparatus and method of carrying out quadrature error correction by the multinomial model in tone calibration in I/Q receiver.In an exemplary embodiment, the method that is provided for calibrating I/Q receiver, and described method comprises: unmatched first between the I passage of reception indication I/Q receiver and Q passage be match parameter not; With by multinomial model, come from first not match parameter estimate the second match parameter not.

Originally, tone calibration does not always mate estimation for what generate the I passage of I/Q receiver and Q passage.Then the result of tone calibration can be processed with the multinomial calibration steps of embodiment, and not match parameter relevant with generated frequency and frequency-independent is estimated.Then the estimated value of the frequency dependence that multinomial calibration steps generates and the not match parameter of frequency-independent can not mate with compensation in order to the signal of processing in quadrature error correction (QEC) unit.An embodiment of the present disclosure provides by using Polynomial Method to cause gain and the unmatched value of phase place of improving with more accurate calibration process.Because significantly reduced the unknown parameter of estimating for multinomial calibration compared with known technology, so described method has shown very noisy robustness.

According to another embodiment of the present disclosure, multinomial model is applied to the result of tone calibration to generate for calibrating the not match parameter of I/Q receiver.Originally, tone calibration does not mate with total phase place for estimating I passage and the overall gain between Q passage of I/Q receiver.Then the result of tone calibration is processed with multinomial calibration steps, with the relevant gain of generated frequency and phase place, does not mate with the phase place of frequency-independent and does not mate estimation.Then the estimated value of the not match parameter that multinomial calibration steps generates can not mate with compensation in order to the signal of processing in quadrature error correction (QEC) unit.

According to another embodiment of the present disclosure, multinomial model is applied to tone calibration overall gain and total phase estimation result, thereby estimating that the gain of the frequency dependence of I passage and Q passage in RF receiver and phase place are not mated with the phase place of frequency-independent does not mate.When by not mating under symmetry positive frequency and negative frequency identical estimate not mate rather than assess frequency right do not mate time, multinomial model is applied to all frequencies in frequency spectrum to upper.In an exemplary embodiment, positive frequency and negative frequency are treated to has independent not mating.The gain of frequency dependence and phase place are not mated with the unmatched estimated value of phase place of frequency-independent and then can with compensation, not mated in order to the signal in process errors correcting unit.

According to another embodiment of the present disclosure, multinomial model is applied to tone calibration to estimate not mating of the frequency dependence between I passage and Q passage and frequency-independent in RF receiver.Multinomial model uses least squares error (LSE) optimization to be applied to tone calibration overall gain and total phase place is not mated estimated result, with estimated frequency is relevant more accurately gain and phase place, does not mate with the phase place of frequency-independent and does not mate.By symmetry positive frequency and negative frequency, there is identical not mating, all frequencies in frequency spectrum on common application multinomial model, rather than each frequency is not mated assessment individually.

According to another embodiment, the disclosure provides a kind of calibration system, and described calibration system comprises multinomial calibration (PCAL) estimator, tone calibration (TCAL) estimator, tone generator and transform processor.In an exemplary embodiment, calibration system is for off-line test I/Q receiver.TCAL estimator is controlled tone generator the test tone under test frequency spectrum medium frequency value is inputted to the simulaed path of I/Q receiver.I/Q receiver comprises the mixing unit of have local oscillator (LO) and frequency mixer, and has I and the Q path of AD converter (ADC).Tone sends by receiver simulaed path.After passing through receiver path, gained time-domain signal is transformed processor and transforms from the time domain to frequency domain.

Then TCAL estimator operates frequency-region signal and does not mate g (f with the unmatched overall gain generating between I passage and Q passage _t) estimate not mate with total phase place estimate.Then the result of TCAL tone calibration estimator is processed by PCAL estimator.G (n) is not mated in the gain that PCAL estimator uses Polynomial Method and least square (LSE) method to estimate that modeling value does not mate the frequency dependence of profile.Estimate multinomial coefficient, and the multinomial coefficient of estimating is in order to calculate the value g (n) of each frequency band with multinomial.Then PAL estimator comes the irrelevant phase place of estimated frequency not mate with Polynomial Method do not mate with the phase place of frequency dependence the gain of frequency dependence and phase place not match parameter and frequency-independent phase place not match parameter then input quadrature error and proofread and correct (QEC) processor, and QEC processor can compensate and proofread and correct not mate in I/Q receiver.

Accompanying drawing explanation

Fig. 1 illustrates the exemplary simplified functional block diagram according to the test macro of example of the present disclosure;

Fig. 2 illustrates the example procedure operation according to embodiment of the present disclosure;

Fig. 3 A illustrates the example procedure operation according to embodiment of the present disclosure;

Fig. 3 B illustrates the example procedure operation according to embodiment of the present disclosure;

Fig. 4 A is illustrated in the exemplary diagram of the performance of embodiment of the present disclosure under the first noise level;

Fig. 4 B is illustrated in the exemplary diagram of the performance of embodiment of the present disclosure under the second noise level;

Fig. 4 C is illustrated in the exemplary diagram of the performance of embodiment of the present disclosure under the 3rd noise level; With

Fig. 4 D is illustrated in the exemplary diagram of the performance of embodiment of the present disclosure under the 4th noise level.

Embodiment

With reference now to Fig. 1,, illustrate according to the simplification functional block diagram of the test macro 100 of an exemplary embodiment of the present disclosure.Test macro 100 comprises testing apparatus 101 and receiver 102.Testing apparatus 101 comprises tone generator 104, transform processor 106, tone calibration (TCAL) estimator 108 and multinomial calibration (PCAL) estimator 110.At Fig. 1, receiver 102 represents the receiver that testing apparatus 101 to be used is calibrated.Receiver 102 comprises low noise amplifier (LNA) 112, frequency mixer 114, digital processing unit piece 118 and quadrature error correction (QEC) processor piece 120.Frequency mixer 114 comprises local oscillator (LO) 126 and multiplier 128a and 128b.The simulaed path of receiver 102 comprises that the independent I passage of homophase (I) for receiving and quadrature phase (Q) signal and Q passage process path.Simulaed path comprises by the I tunnels analogy path of multiplier 128a, trans-impedance amplifier (TIA) 124a and AD converter (ADC) 122a, and passes through the Q tunnels analogy path of multiplier 128b, trans-impedance amplifier (TIA) 124b and ADC122b.In an exemplary embodiment of Fig. 1, testing apparatus 101 in order to calibrate receiver 102 under off-line mode, that is, receiver 102 is considered to off-line and can not operates between alignment epoch.Testing apparatus 101 can be implemented in the various combinations of hardware and software.For example, other circuit of digital signal processor (DSP), application-specific integrated circuit (ASIC) (ASIC) or suitable software control can be in order to implement the function of embodiment.

In an exemplary embodiment of Fig. 1, PCAL estimator 110 provides the unmatched estimation between the I of receiver 102 and Q path for QEC processor 120.PCAL estimator 110 receives the overall gain between I and Q passage is not mated and total unmatched estimation of phase place from TCAL estimator 108.The optimization of multinomial model and least squares error (LSE) is applied to overall gain with PCAL estimator 110 and sum frequency is not mated, with generate to the gain of frequency dependence do not mate, the phase place of frequency dependence is not mated and the unmatched not match parameter of frequency-independent phase place is estimated.Then the not match parameter of estimating in PCAL estimator 110 can be used for QEC processor piece 120 with calibration receiver 102, thereby compensating gain and frequency are not mated.

With reference now to Fig. 2,, shown in it according to the process operation of exemplary embodiment of the present disclosure.These operate in the hardware and software of the functional block shown in the exemplary embodiment of implementing Fig. 1 and carry out.Test process starts during by tone generator 104 input mixer 114 when RF test tone at process operation 200.Each test tone is in the frequency of the frequency sets on expectation test frequency spectrum from scope.At frequency mixer 114, test tone is multiplied by cophase wave cos (2 π f at multiplier 128a and 128b respectively _ct) and quadrature wave-sin (2 π f _ct).Test tone can be modeled as signal z (t):

z(t)＝2A·cos(2πf _ct+2πf _Tt+θ)＝2A·(cos(2πf _ct)cos(2πf _Tt+θ)-sin(2πf _ct)sin(2πf _Tt+θ))，

Wherein, 2A is the amplitude (having added factor 2 for the ease of calculating in amplitude here) of tone, f _ccarrier frequency, f _tthat pitch frequency and θ are that tone is with respect to the relative phase of the LO126 in frequency mixer 114.

Result is delivered to each in the I passage of simulaed path and Q passage by low pass filter 124a and 124b respectively.Quadrature wave has value and phase deviation, is expressed as g _lOwith then, quadrature wave becomes for I passage, signal is treated to:

$\begin{array}{c}{x}_I\left(t\right)=\mathrm{LPF}(z\left(t\right)\·\cos \left(2\mathrm{\π}{f}_{c}t\right))\\ =\mathrm{LPF}(2A\·\cos (2\mathrm{\π}{f}_{c}t+2\mathrm{\π}{f}_{T}t+\mathrm{\θ})\cos \left(2\mathrm{\π}{f}_{c}t\right))\end{array}$

$\begin{array}{c}=\mathrm{LPF}(2A\·\frac{1}{2}(\cos (4\mathrm{\π}{f}_{c}t+2\mathrm{\π}{f}_{T}t+\mathrm{\θ})+\cos (2\mathrm{\π}{f}_{T}t+\mathrm{\θ})))\\ =A\·\cos (2\mathrm{\π}{f}_{T}t+\mathrm{\θ})\end{array}$

Similarly, in Q passage, signal is:

On tone, nominal Baseband Channel is to frequency f _timpact by value g _n(f _t) do not mate and phase shift do not mate composition.These do not mate and all depend on pitch frequency.Process hypothesis I signal by nominal Baseband Channel, so:

Again, processing hypothesis base band does not mate and is only applied to Q path.Channel gain in Q path and phase shift are g _n(f _t) g _m(f _t) and g wherein _m(f _t) and unmatched baseband gain and phase place.Then, Q path signal becomes:

Signal y _iand y (t) _q(t) having the value and the phase place that are defined as between following I and Q path does not mate:

Use common factor:

A(f _t)=g _n(f _t) A and

Baseband I/Q signal y of the end of simulaed path and digital block 118 inputs _iand y (t) _q(t) be given as,

y _I(t)＝A(f _T)·cos(2πf _Tt+θ(f _T))

Baseband signal then device being tested 101 processes to estimate the not match parameter of I passage and Q passage.

At process operation 202, transform processor 106 is respectively to each the application conversion in baseband I and Q signal, so that each baseband signal is transformed from the time domain to frequency domain.In an exemplary embodiment of Fig. 1, transform processor 106 may be able to be carried out any one in fast Fourier transform (FFT) or discrete Fourier transform (DFT) (DFT) as test replacement.In alternate embodiment, transform processor 106 can be used in FFT or DFT one or both or another kind of conversion.FFT or DFT can generate the transformation results that can input TCAL estimator 108.FFT and DFT method can be avoided the homophonic interference from common existence.Difference is between the two that FFT calculates the Frequency point on whole frequency spectrum, and DFT can calculate pitch frequency Chosen Point around.The latter's possibility computational complexity is much smaller, especially all the more so when signal length increases.Two kinds of methods all can be followed herein by the identical mathematical formulae shown in the exemplary embodiment for Fig. 1.

Transform processor 106 is used DFT(or FFT) with by signal is associated calculated rate point with the complicated harmonic wave in described frequency.Conversion is applied to I signal, draws:

$Y_I\left(f\right)=\∫y_I\left(t\right)\·e^{-j2\mathrm{\πft}}\mathrm{dt}$

$\begin{array}{c}=\∫A\left(f_T\right)\·\cos (2\mathrm{\π}{f}_{T}t+\mathrm{\θ}\left(f_T\right))e^{-j2\mathrm{\πft}}\mathrm{dt}\\ =\frac{A\left(f_T\right)}{2}\·\∫(e^{j2\mathrm{\π}{f}_{T}t+\mathrm{j\θ}\left(f_T\right)}+e^{-j2\mathrm{\π}{f}_{T}t-\mathrm{j\θ}\left(f_T\right)})e^{-j2\mathrm{\πft}}\mathrm{dt}\\ =\left\{\begin{array}{c}\frac{A\left(f_T\right)}{2}\·e^{\mathrm{j\θ}\left(f_T\right)},f=f_T\\ \frac{A\left(f_T\right)}{2}\·e^{-\mathrm{j\θ}\left(f_T\right)},f=-f_T\end{array}\right.\end{array}$

Similarly, conversion is applied to Q signal, draws:

Transform processor 106 is then the signal Y of conversion _q(f _t) and Y _i(f _t) output to TCL estimator 108.At process operation 204, then TCAL estimator 108 estimates not match parameter of overall gain and sum frequency with frequency domain figure signal.TCAL estimator 108 is Y _q(f _t) divided by Y _i(f _t), draw:

H wherein _d(f _t) be base band do not mate and be that LO does not mate, and overall gain is not mated and is given as:

$g\left(f_T\right)=\left|\frac{Y_Q\left(f_T\right)}{Y_I\left(f_T\right)}\right|,$

And total phase place is not mated and is given as:

The phase place that total phase place of estimating is not mated the combination that is LO126 and baseband analog path is not mated, and is given as two components are not mated from total phase place to separate to carry out quadrature error I/Q receiver 102 proofreaies and correct.Now, TCAL estimator 108 has in order to the relevant gain of calculated rate and phase place and does not mate the information with the unmatched estimation of phase place of frequency-independent.Carrying out a kind of optional method calculating will be hypothesis g (f _t) symmetrical and suppose that phase place do not mate and zero frequency odd symmetry between positive frequency and negative frequency, can use this hypothesis, because the unmatched impulse response of base band is real-valued.Then, the LO phase place that can calculate in the bandwidth of the equipment that test tone skims over is not mated.In addition, the baseband phase of frequency dependence does not mate and then can be estimated as that total phase place is not mated and poor between not mating of LO phase place yet.Yet, use this hypothesis not allow entirely accurate and estimate not mating of receiver, while especially having high jitter level in high-noise environment or in test tone.

In an exemplary embodiment, testing apparatus 101(comprises PCAL estimator 110) by all frequencies on common use in order to calculate from overall gain and the unmatched Polynomial Method that does not mate estimation of phase place with provide g (f), with the estimation of improvement.Little difference in the pole and zero of the uneven main transfer function by I passage and Q channel path of I/Q of frequency dependence causes.Therefore, frequency domain unmatch list is now the comparatively level and smooth curve on frequency spectrum.This attribute makes likely with polynomial function, to carry out not match curve of modeling.In Polynomial Method, the crucial factor in match parameter estimation is not the estimation of multinomial coefficient.

Refer again to Fig. 2, at process operation 206, PCAL estimator 110 receives overall gain and not match parameter estimation of frequency from TCAL estimator 108.PCAL estimator 110 then in the frequency of test frequency spectrum to the relevant gain of (comprising positive frequency and negative frequency) upper common estimated frequency and the phase place phase place match parameter not of match parameter and frequency-independent not.

With reference to figure 3A, the process operation that the estimator 110 of PCAL shown in it is carried out during the process of the operation 206 of Fig. 2.At process operation 302, PCAL estimator 110 receives overall gain from TCAL estimator 108 and does not mate estimation with total phase place.In an exemplary embodiment of testing apparatus 101, on test frequency spectrum, generate N tone.The always match parameter not of each in this N of PCAL estimator 110 assessment tone, thereby provide, overall gain Q (n) does not mate and the unmatched value below of total phase place W (n):

$Q\left(n\right)=\left|\frac{Y_Q\left(f_n\right)}{Y_I\left(f_n\right)}\right|,n=\mathrm{0,1},...,N-1$

With,

$W\left(n\right)=\mathrm{angle}\left(\frac{Y_Q\left(f_n\right)}{Y_I\left(f_n\right)}\right)-\frac{\mathrm{\π}}{2}$

In step 304, PCAL estimator 110 is applied to gain parameter multinomial model.In an exemplary embodiment, quadravalence multinomial can not mate profile g (n) in order to the gain of modeling frequency dependence.In alternate embodiment, the polynomial exponent number using can be any rank, three rank for example, and select based on simulation or any other suitable method of being suitable for selecting.Multinomial model for g (n) is:

S(n)＝P ₀+P ₁n+P ₂n ²+P ₃n ³+P ₄n ⁴

There is N Frequency point to provide N system of linear equations to estimate 5 known variables.For positive frequency, equation group is:

$P_0+P_{1}n+P_2{n}^2+P_3{n}^3+P_4{n}^4=Q\left(n\right),n=0,...,\frac{N}{2}-1$

For negative frequency, index is revised from conversion, for example:

$\begin{array}{c}{P}_0+P_1(n-N)+P_2{(n-N)}^2+P_3{(n-N)}^3+P_4{(n-N)}^4\\ =Q\left(n\right),n=\frac{N}{2},...,N-1\end{array}$

Under matrix format, linear system becomes:

K·P＝Q

Wherein,

$K=\left[\begin{array}{ccccc}1& 0& 0& 0& 0\\ 1& 1& 1& 1& 1\\ .& .& .& .& .\\ .& .& .& .& .\\ .& .& .& .& .\\ 1& n& n^2& n^3& n^4\\ .& .& .& .& .\\ .& .& .& .& .\\ .& .& .& .& .\\ 1& n-N& {(n-N)}^2& {(n-N)}^3& {(n-N)}^4\\ .& .& .& .& .\\ .& .& .& .& .\\ .& .& .& .& .\\ 1& -1& 1& -1& 1\end{array}\right]$

P＝[P ₀?P ₁?P ₂?P ₃?P ₄] ^T

Q＝[Q(0)?...?Q(N-1)] ^T

In step 306, then PCAL estimator 110 is applied least squares error method and is minimized matrix:

J＝(K·P-Q) ^T·(K·P-Q)

＝P ^TK ^TKP-P ^TK ^TQ-Q ^TKP+Q ^TQ

PCAL estimator 110 calculates derivative and it is equalled zero, and produces:

P＝(K ^TK) ^-1K ^TQ

At process operation 308, g (n) is not mated in PCAL estimator 110 gain that then calculated rate is relevant.PCAL estimator 110 uses the multinomial coefficient of estimating the gain of using multinomial model to calculate the frequency dependence on each frequency band not to mate the value of g (n).

With reference now to Fig. 3 B,, the unmatched process operation of phase place of the relevant and frequency-independent of the estimated frequency carried out according to the PCAL estimator 110 of embodiment of the present disclosure shown in it.Fig. 3 B illustrates the phase place that estimated frequency is relevant and does not mate do not mate with the phase place of frequency-independent operation.In the process operation 312 of Fig. 3 B, not match parameter W (n) operation of total phase place that PCAL estimator 110 receives from TCAL estimator 108 in step 302.

At process operation 312, PCAL estimator 110 uses relational expression and baseband phase be modeled as multinomial.PCAL estimator 110 also uses relational expression quadravalence multinomial can be used for the embodiment of Fig. 1.Polynomial selection can be carried out in other system of selection based on simulation or definite enough use of specific multinomial.110 of PCAL estimators be modeled as:

This is given linear equation group pattern:

PCAL estimator 110 use 5 unknown numbers and the phase place that equation group is separated coefficient and frequency-independent is not mated at process operation 314,110 application of PCAL estimator are for the least squares error method of linear regression.The equation group of using can be expressed as with matrix format:

H·C＝W

Wherein,

$H=\left[\begin{array}{ccccc}-1& 1& 1& 1& 1\\ .& .& .& .& .\\ .& .& .& .& .\\ .& .& .& .& .\\ -1& n& n^2& n^3& n^4\\ .& .& .& .& .\\ .& .& .& .& .\\ .& .& .& .& .\\ -1& N/2-1& {(N/2-1)}^2& {(N/2-1)}^3& {(N/2-1)}^4\end{array}\right]$

W＝(W(1)?...?W(N/2-1)] ^T

Least squares error method minimizes J:

J＝(H·C-W) ^T·(H·C-W)

＝C ^TH ^THC-C ^TH ^TW-W ^THC+W ^TW

Then, can differentiation and it is equalled zero, produce:

C＝(H ^ＴH) ^-1H ^TW

At process operation 315, the value of PCAL estimator evaluator coefficient, comprises value.The phase place that PCAL estimator 110 has frequency-independent is now match parameter not value.

At process operation 316, then PCAL estimator 110 comes the phase place that estimated frequency is relevant not mate with multinomial coefficient value, this value can be used availability coefficient vector C to estimate from multinomial model.The gain that PCAL estimator has frequency dependence is now the phase place match parameter not of match parameter g (n), frequency dependence not with the phase place of frequency-independent match parameter not value.

Refer again to Fig. 2, at process operation 208, PCAL estimator 110 then the gain of the frequency dependence of estimating and phase place not match parameter and frequency-independent phase place not match parameter value output to quadrature error correcting block 120.Then QEC functional block can estimate to be applied to error compensation and the correction in receiver 102 PCAL.

With reference now to Fig. 4 A-Fig. 4 B,, shown in it, shown image rejection ratio (IRR) figure of the computer simulation of the improvement that can be provided according to the exemplary embodiment of Fig. 1 by PCAL estimator.At Fig. 4 A-Fig. 4 D, the PCAL calibration of using Polynomial Method and TCAL calibration-gain and phase place match parameter are estimated the result not providing in the situation that not using Polynomial Estimation method make comparisons (that is, gained and do not mated between positive frequency and negative frequency symmetry and suppose that phase place do not mate and zero frequency odd symmetry by hypothesis).

Fig. 4 A is illustrated in the improvement in noiselessness situation, and Fig. 4 B illustrates the improvement under 51dB, and improvement and Fig. 4 D that Fig. 4 C illustrates under 41dB illustrate the improvement under 31dB.Can find out, along with noise progressively worsens, the 31dB from the noiselessness of Fig. 4 A to the 51dB of Fig. 4 B, the 41dB of Fig. 4 C and Fig. 4 D, compared with not using Polynomial Method, PCAL figure is more level and smooth on frequency spectrum.Simulation is illustrated under low-noise situation, and performance is similar.Along with noise increases, the better performance of PCAL calibration becomes remarkable.In certain embodiments, along with noise increases, use the PCAL of Polynomial Method to estimate at least 10dB than the TCAL that does not use Polynomial Method.Because unknown estimated parameter significantly reduces, so method has shown very strong noise robustness.

In the discussion of embodiment above, capacitor, buffering area, interconnection plate, clock, tone generator, processor, TCAL, PCAL, receiver, LNA, frequency mixer, digital processing unit piece, QEC, LO, distributor, inductor, resistor, amplifier, switch, digital core, transistor and/or other assembly can be replaced at an easy rate, replace or otherwise revise and adapt to specific circuit needs.In addition, it should be noted that and use complementary electronic equipment, hardware, non-of short duration software etc. to provide for implementing the same feasible selection of instruction of the present disclosure.

Although the disclosure has been described at least one illustrative embodiment, various changes, modification and improvement are possible.This type of changes, revises and improves in spirit and scope of the present disclosure.Therefore, above-mentioned disclosure is only exemplary, is not intended to restriction.Any amount of functional block of exemplary can be implemented on the circuit board of associated electronic device.Described circuit board can be the various assemblies of the internal electron system that can keep electronic equipment and the general circuit board of connector is further provided for other ancillary equipment.More specifically, described circuit board can provide other assembly of system can be in order to the electrical connection of telecommunication.Any suitable processor (comprising digital signal processor, microprocessor, support chip group etc.), memory component etc. can suitably be couple to described circuit board based on particular configuration needs, processing demands, Computer Design etc.For example exterior storage, additional sensors, for the controller of audio/visual displays and other assembly of ancillary equipment, can be connected to described circuit board as plug-in card, be connected or be integrated into described circuit board itself by cable.

In another exemplary embodiment, described function can be embodied as standalone module (for example, have and be configured to carry out the associated component of concrete application or function and the equipment of circuit) or as card module, be implemented in the specialized hardware of electronic equipment.Note, particular of the present disclosure easily a part or whole part is included in SOC (system on a chip) (SOC) encapsulation.SOC represents the IC that the assembly of computer or other electronic system is integrated into single-chip.It can comprise numeral, simulation, mixed signal and common radio-frequency enabled: all these can provide on single-chip substrate.Other embodiment can comprise multi-chip module (MCM), and wherein a plurality of independent IC are arranged in single electron encapsulation and are configured to by Electronic Packaging closely interactive each other.In various other embodiments, enlarging function can be implemented in the one or more silicon cores in application-specific integrated circuit (ASIC) (ASIC), field programmable gate array (FPGA) and other semiconductor chip.

Also it should be noted that all described functions and process are only for the object of giving an example and instruct provides.Described information can be in the situation that do not depart from the scope of spirit of the present disclosure or appended claims and differ widely.Specification is only applied to a nonrestrictive example, so they should be understood like this.In description above, exemplary embodiment has consulted par-ticular processor and function layout is described.Can carry out various modifications and variations to this type of embodiment without departing from the scope of the appended claims.Therefore, description and accompanying drawing are interpreted as descriptive sense rather than restrictive, sense.

Note, in some examples provided herein, can be described with regard to two, three, four or more electronic component alternately.Yet this just carries out with object that give an example for clear.The system of should be understood that can merge in any suitable manner.Along similar design, any assembly illustrating, module and the element of accompanying drawing can combine with various possible configurations, and all these is obviously in the broad range of this specification.In some cases, by being only easy to describe one or more in the function of given flow process set with reference to the element of limited quantity.Should be understood that accompanying drawing and its easy convergent-divergent of instruction and can hold the assembly of larger quantity and layout and the configuration of more complicated/precision.Therefore the example, providing should not limit and potentially be applicable to the scope of the present disclosure of countless other structures or suppress broad teachings of the present disclosure.

Note, in this specification, (be for example included in various features in " embodiment ", " exemplary embodiment ", " embodiment ", " another embodiment ", " some embodiments ", " various embodiment ", " other embodiment ", " alternate embodiment " etc., element, structure, module, assembly, step, operation, feature etc.) quote and be intended to mean any this category feature and be included in one or more embodiment of the present disclosure, but may or may needn't in identical embodiment, combine.

Those skilled in the art can determine many other variation, replacement, modification, change and modifications, and are intended that, and the disclosure comprises all these type of variations, replacement, modification, change and the modification falling within the scope of appended claims.In order to assist United States Patent and Trademark Office (USPTO) and to assist in addition any reader of any patent that the application issues to explain claims, what applicant wished attention is, applicant: (a) do not intend to quote when any appending claims is present in the applying date the 112nd article the 6th (6) sections of 35U.S.C., unless term " for ... means " or " for ... step " in specific claim, using clearly; (b) do not intend to limit the disclosure by any mode not embodying in claims by any statement in this specification.

Claims (20)

1. for calibrating a method for I/Q receiver, it comprises:

Between the I passage of the described I/Q receiver of reception indication and Q passage unmatched first be match parameter not; And

With multinomial model come from described first not match parameter estimate the second match parameter not.

2. the method for claim 1, wherein said estimation comprises: application three rank multinomials are estimated the described second match parameter not.

3. method as claimed in claim 2, wherein said estimation comprises: application quadravalence multinomial is estimated the described second match parameter not.

4. the method for claim 1, wherein said first not match parameter be included in the not match parameter of more than first frequency dependence under the frequency of test on frequency spectrum, and wherein said estimation comprises: the negative frequency in described test frequency spectrum and positive frequency on, estimate the not match parameter of more than second frequency dependence.

5. the method for claim 1, wherein said estimation comprises: use least squares error (LSE) to calculate and minimize matrix.

6. the method for claim 1, wherein said first not match parameter comprise that overall gain is not mated and total phase place is not mated.

7. the method for claim 1, it also comprises:

By generate N tone signal on test frequency spectrum, carry out tone calibration;

Described tone signal is inputted to described I/Q receiver;

In tone calibration estimator, carry out tone calibration and generate the described first match parameter not; And

Described first not match parameter input described multinomial calibration estimator.

8. method as claimed in claim 7, wherein said estimation second not match parameter comprises: gain match parameter and the phase place match parameter not of estimating each frequency of described tone signal.

9. method as claimed in claim 7, wherein said estimation second not match parameter comprises: the negative frequency in described test frequency spectrum and positive frequency on, estimated parameter does not mate.

10. for calibrating a device for I/Q receiver, described device comprises:

Polynomial Estimation device, it is configured to:

Receive the first match parameter not, wherein said first not match parameter estimate not mating between the I passage of the described I/Q receiver of indication and Q passage; And

With multinomial model from described first not match parameter estimate the second match parameter not.

11. devices as claimed in claim 10, wherein said Polynomial Estimation device by apply three rank multinomials from described first not match parameter estimate the described second match parameter not.

12. devices as claimed in claim 11, wherein said Polynomial Estimation device by application quadravalence multinomial from described first not match parameter estimate the described second match parameter not.

13. devices as claimed in claim 10, wherein said first not match parameter be included in the not match parameter of more than first frequency dependence under the frequency of test frequency spectrum, and wherein said Polynomial Estimation device the negative frequency of described test frequency spectrum and positive frequency on estimate the not match parameter of described more than second frequency dependence.

14. devices as claimed in claim 10, wherein said Polynomial Estimation device is estimated the described second match parameter use least squares error (LSE) to calculate not with the multinomial with matrix.

15. devices as claimed in claim 10, wherein said Polynomial Estimation device receive described first not match parameter comprise that overall gain is not mated and total phase place is not mated.

16. devices as claimed in claim 10, it also comprises:

Tone generator, it is configured to be created on the N tone signal on test frequency spectrum and described tone signal is inputted to described I/Q receiver simulaed path;

Transform block, it is couple to the end of specific simulaed path, and described transform block is for being transformed to the described signal receiving on the described end of described specific simulaed path frequency-region signal and exporting described frequency-region signal from time-domain signal; And

Tone calibration estimator, it is couple to described transform block and described Polynomial Estimation device, described tone calibration estimator be configured to from described transform block receive described frequency-region signal, to frequency domain test signal carry out tone calibration with generate described first not match parameter and described first not match parameter estimate to input described Polynomial Estimation device.

17. devices as claimed in claim 16, wherein said second not match parameter comprise overall gain match parameter and the total phase place match parameter not of each frequency of described N tone signal.

18. devices as claimed in claim 16, wherein said the first parameter is included in the not match parameter of a plurality of frequency dependences under the frequency on described test frequency spectrum, and the negative frequency of wherein said Polynomial Estimation device in described test frequency spectrum and positive frequency on estimate the not match parameter that described second frequency is relevant.

19. 1 kinds for calibrating the device of I/Q receiver, and it comprises:

Tone calibration estimator, it is configured to the test tone under the frequency in frequency spectrum test and injects described I/Q receiver, estimates to comprise not or not the first set of match parameter described in the first set of the not match parameter of match parameter and output of match parameter and total phase place of overall gain;

Multinomial calibration estimator, it is couple to described tone calibration estimator, not the first set of match parameter and estimate not the second set of match parameter from the first set of described not match parameter by multinomial model described in described multinomial calibration estimator is configured to receive from described tone calibration estimator, second of described not match parameter is gathered the gain phase place phase place match parameter not of match parameter and frequency-independent not of match parameter, frequency dependence not that comprises frequency dependence.

20. devices as claimed in claim 19, wherein said multinomial calibration estimator is that negative frequency in described test frequency spectrum and positive frequency are to not second of match parameter the set described in upper estimation.