CN103744066A - Optimizing method for digital orthogonal phase identifying and matched filtering - Google Patents
Optimizing method for digital orthogonal phase identifying and matched filtering Download PDFInfo
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- G—PHYSICS
- G01—MEASURING; TESTING
- G01S—RADIO DIRECTION-FINDING; RADIO NAVIGATION; DETERMINING DISTANCE OR VELOCITY BY USE OF RADIO WAVES; LOCATING OR PRESENCE-DETECTING BY USE OF THE REFLECTION OR RERADIATION OF RADIO WAVES; ANALOGOUS ARRANGEMENTS USING OTHER WAVES
- G01S7/00—Details of systems according to groups G01S13/00, G01S15/00, G01S17/00
- G01S7/02—Details of systems according to groups G01S13/00, G01S15/00, G01S17/00 of systems according to group G01S13/00
- G01S7/35—Details of non-pulse systems
- G01S7/352—Receivers
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- G—PHYSICS
- G01—MEASURING; TESTING
- G01S—RADIO DIRECTION-FINDING; RADIO NAVIGATION; DETERMINING DISTANCE OR VELOCITY BY USE OF RADIO WAVES; LOCATING OR PRESENCE-DETECTING BY USE OF THE REFLECTION OR RERADIATION OF RADIO WAVES; ANALOGOUS ARRANGEMENTS USING OTHER WAVES
- G01S7/00—Details of systems according to groups G01S13/00, G01S15/00, G01S17/00
- G01S7/02—Details of systems according to groups G01S13/00, G01S15/00, G01S17/00 of systems according to group G01S13/00
- G01S7/35—Details of non-pulse systems
- G01S7/352—Receivers
- G01S7/356—Receivers involving particularities of FFT processing
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Abstract
The invention discloses an optimizing method for digital orthogonal phase identifying and matched filtering and mainly solves the problems of large operand and complex processing flow when the order of a filter is higher in the prior art. The realizing process comprises the steps of (1), performing fast Fourier transformation on a radar echo to obtain the positive frequency and image frequency of a signal and remaining partial points in the image frequency as effective image frequency; (2), performing point multiplication on a domain-frequency digital orthogonal phase identifying filter coefficient with a frequency-domain matched filter coefficient to obtain a passband coefficient P and a transition band coefficient Q; (3), overlapping the point multiplication result of the signal positive frequency and the passband coefficient P and the point multiplication result of the effective image frequency and the transition band coefficient Q to obtain the frequency spectrum Z after the signal matched filtering; (4) performing inverse fast Fourier transformation on the frequency spectrum Z to calculate the target distance. The method of combining the filtering coefficients in advance is adopted, so the limitation to the order of the filter is reduced, the processing efficiency on the radar echo is improved and the optimizing method can be used for the speed measuring and ranging on a target in the radar signal processing.
Description
Technical field
The present invention relates to digital signal processing technique field, relate generally to the optimization method of digital quadrature phase demodulation and matched filtering, for the data processing that target is tested the speed, found range.
Background technology
In Radar Signal Processing, digital quadrature phase demodulation and matched filtering are basic and necessary links, and its processing procedure is: first, intermediate-freuqncy signal Direct Sampling is completed to A/D conversion; Then, by digital quadrature phase demodulation, obtain orthogonal I, Q two paths of signals; Finally, by matched filtering, obtain the distance of target.Digital quadrature phase demodulation is widely used in fields such as communication, radars.At the normally narrow band signal of signal of the communications field, signal bandwidth is much smaller than sampling rate, so the exponent number of digital quadrature phase detection filter is very low, is easy to hardware and realizes.And radar signal bandwidth is very wide, conventionally adopt Low Medium Frequency sampling, when connecing after digital quadrature phase demodulation when large that the long-pending matched filtering of wide bandwidth is processed, time domain approach requires high to hardware device amount, is unfavorable for that hardware realizes,
Digital quadrature phase demodulation and matched filtering all can realize in time domain and frequency domain, and these two kinds of methods are of equal value in performance.Time domain method is suitable for the situation that filter order is lower, adopts stream treatment mode; Frequency domain filtering is suitable for the situation that filter order is higher, now for long sequence, need to select optimal segmentation length to carry out staging treating.
The time domain disposal route of existing digital quadrature phase demodulation adopts low pass filtering method conventionally, the two-way orthogonal signal of if sampling output signal and local oscillator generation are carried out to mixing, allow the signal after mixing pass through low-pass filter, filtering high fdrequency component, obtains the orthogonal two-way signal of required base band.When filter order is higher, the orthogonal phase demodulation disposal route of time-domain digital need be carried out in a large number repeatedly multiplication and be completed convolution when filtering, and operand is large.The frequency domain technique of existing digital quadrature phase demodulation, is first signal to be changed to frequency domain by Fast Fourier Transform (FFT), carries out frequency spectrum shift, then by low-pass filter, suppresses image frequency, then carries out spectral aliasing, and remaining image frequency is added on positive frequency.
Existing matched filtering is processed and conventionally at frequency domain, is carried out, because matched filtering coefficient length is larger.Disposal route is, first signal changed to frequency domain by Fast Fourier Transform (FFT), then dot product matched filtering coefficient.
Known by above-mentioned disposal route, the orthogonal phase detecting method of frequency domain digital and frequency matching filter processing method have common factor, and completing respectively these two treatment schemees can increase operand, and disposal route is succinct not.
Summary of the invention
The object of the invention is to for above-mentioned the deficiencies in the prior art, the optimization method of a kind of digital quadrature phase demodulation and matched filtering is proposed, to reduce the operand when filter order is higher, improve the treatment effeciency to radar return data, simplify signal processing flow.
The technical scheme that realizes the object of the invention is: digital quadrature phase demodulation and matched filtering merging are carried out, and concrete steps comprise as follows:
(1) Radar IF Echo is done to Fast Fourier Transform (FFT), conversion is counted as 2L, and obtaining length is the positive frequency A of L and the image frequency E that length is L, wherein, and the power that L is 2, and 2L is more than or equal to the length of echoed signal, from image frequency E, before taking-up
individual point and after
individual as effective image frequency B, W is less than L, and is greater than 0;
(2) according to the parameter of radar emission signal, in the design of filter instrument of Matlab, low-pass filter parameter is set, generate the low-pass filter coefficients of specifying exponent number, by Fast Fourier Transform (FFT), this coefficient is changed to frequency domain, again frequency domain low-pass filter coefficients is done to frequency spectrum shift, obtaining length is the orthogonal phase detection filter coefficient of the frequency domain digital F of 2L;
(3) baseband signal of radar is done to conjugation reversion, obtain matched filter coefficient, by Fast Fourier Transform (FFT), this coefficient is changed to frequency domain, obtaining length is the frequency matching filter coefficient D of 2L;
(4) according to frequency domain digital orthogonal phase detection filter coefficient F and frequency matching filter coefficient D, obtain the filter factor merging: H=FD, filter coefficient H is divided into length and is two sections of L: one section as passband FACTOR P, another section is as stopband coefficient S, and before taking out from stopband coefficient S
individual point and after
individual as transitional zone coefficient Q;
(5), according to above-mentioned parameter, obtain the frequency spectrum after Radar IF Echo matched filtering: Z=AP+BQ;
(6) frequency spectrum Z is done to inverse fast fourier transform, obtain time domain matched filtering result, according to the peak point of this time domain matched filtering result, calculate the distance r of target, for follow-up Radar Signal Processing.
The present invention compared with prior art has the following advantages:
1) being easy to hardware realizes
The orthogonal phase demodulation of existing time-domain digital and frequency matching filtering method are when filter order is higher, the multiplication number of times that convolution algorithm need complete increases sharply, to the handling property of hardware device, require very high, be unfavorable for hardware realization, and the present invention adopts the optimization method of digital quadrature phase demodulation and matched filtering, the change of filter order is very little on operand impact, is easy to hardware and realizes;
2) simplify treatment scheme
Existing the disposal route of Radar IF Echo has been separated digital quadrature phase demodulation and matched filtering, treatment step is succinct not, and the present invention utilizes digital quadrature phase demodulation and the matched filtering general character at frequency domain filtering, merge in advance the orthogonal phase demodulation coefficient of frequency domain digital and frequency matching filter factor, thereby on hardware, be only used as filtering processing and just can complete digital quadrature phase demodulation and matched filtering, simplified signal processing flow;
3) operand is little
The processing of existing digital quadrature phase demodulation, on frequency domain, be equivalent to positive frequency filtering result and image frequency filtering result are superposeed completely, but image frequency filtering result can be ignored than positive frequency filtering result, so positive filtering result frequently and image frequency filtering result superpose can increase unnecessary operand completely, and the present invention is when guaranteeing handling property, only retain a small amount of image frequency data and transitional zone coefficient dot product in transitional zone, reduced operand, improved the treatment effeciency to radar return data.
Accompanying drawing explanation
Fig. 1 is realization flow figure of the present invention;
Fig. 2 is the sub-process figure that produces frequency domain filter coefficient in the present invention;
Fig. 3 is the segmentation schematic diagram of frequency domain filter coefficient of the present invention;
Fig. 4 singly takes advantage of handling capacity comparison diagram with existing method and the present invention when the digital quadrature phase detection filter coefficient length variations;
Fig. 5 singly takes advantage of handling capacity comparison diagram with existing method and the present invention when the matched filter coefficient length variations;
Fig. 6 is that existing method and the present invention singly take advantage of handling capacity comparison diagram under different section lengths.
Embodiment
With reference to Fig. 1, the specific implementation step of this example is as follows:
Step 1, obtains the positive frequency A of radar echo signal and effective image frequency B.
(1a) Radar IF Echo is done to Fast Fourier Transform (FFT), conversion is counted as 2L, obtains the frequency spectrum of signal, the frequency spectrum of signal can be divided into two parts: the image frequency E that the positive frequency A that length is L and length are L, wherein, the power that L is 2, and 2L is more than or equal to the length of echoed signal;
(1b) from image frequency E, before taking-up
individual point and after
individual as effective image frequency B:
The obtaining value method of W is: in Matlab software, the peak point of the time domain matched filtering while equaling the length L of image frequency E take W is as reference value, the peak point of the time domain matched filtering while obtaining respectively W from 1 to L-1 value, obtain again amplitude relative error and the phase place absolute error of these peak points than reference value, when the amplitude relative error of peak point reaches 10
-4when the order of magnitude and phase place absolute error are less than 0.02 °, the error of this peak point, in allowed band, under the prerequisite that reaches allowed band, is preferentially selected minimum W value.
With reference to Fig. 2, being implemented as follows of this step:
(2a) obtain the orthogonal phase detection filter coefficient of frequency domain digital F:
(2a1) according to the parameter of radar emission signal, in the design of filter instrument of Matlab, filter type, signal sampling rate, filter transmission band frequency, filter stop band frequency, wave filter transitional zone frequency and these parameters of filter order of low-pass filter are set, generate low-pass filter coefficients; By Fast Fourier Transform (FFT), this low-pass filter coefficients is transformed to frequency domain, obtain low-pass filter frequency spectrum;
(2a2) low-pass filter frequency spectrum is moved, the centre frequency that is about to passband in low-pass filter frequency spectrum moves on to the intermediate frequency place of positive frequency A, the centre frequency of stopband in low-pass filter frequency spectrum is moved on to the intermediate frequency place of image frequency E, obtaining length is the orthogonal phase detection filter coefficient of the frequency domain digital F of 2L.
(2b) obtain frequency matching filter coefficient D, in Matlab software, the baseband signal of radar is done to conjugation reversion, obtain the matched filter coefficient of time domain, by Fast Fourier Transform (FFT), this matched filter coefficient is transformed to frequency domain, obtaining length is the frequency matching filter coefficient D of 2L.
(2c) obtain passband FACTOR P and transitional zone coefficient Q:
(2c1) according to frequency domain digital orthogonal phase detection filter coefficient F and frequency matching filter coefficient D, obtain the filter factor merging: H=FD, the length of H is 2L;
(2c2) with reference to Fig. 3, filter coefficient H is divided into length and is two sections of L: one section as passband FACTOR P, another section is as stopband coefficient S, and before taking out from stopband coefficient S
individual point and after
individual as transitional zone coefficient Q.
The extracting method of W point is identical with step (1b).
Z=A·P+B·Q。
(4a) frequency spectrum Z is done to inverse fast fourier transform, obtain time domain matched filtering result x:x=IFFT (Z);
(4b) according to the peak point position n of time domain matched filtering result x, calculate the time delay τ of radar return with respect to radar transmitting wave:
wherein f
sfor signal sampling rate;
(4c) time delay τ and the light velocity c with respect to radar transmitting wave according to radar return, calculates the distance r of target:
Effect of the present invention further illustrates by following l-G simulation test:
1. simulated conditions
Radar emission signal is linear FM signal, and transmitted waveform duration is T=20us, and signal bandwidth is B=5MHz, and signal intermediate frequency is f
0=7.5MHz, sampling rate is f
s=10MHz, Fast Fourier Transform (FFT) is counted as 2L=8192, and digital quadrature phase detection filter exponent number is N
a=64, matched filter exponent number is N
b=200, effectively image frequency length is W=410.
2. emulation content:
1) emulation when matched filter exponent number constant, when digital quadrature phase detection filter exponent number changes, the present invention and the existing methodical handling capacity of singly taking advantage of, digital quadrature phase detection filter exponent number is conventionally in 16 to 128 scope, singly taking advantage of handling capacity is that the valid data of processing out in single multiplication are counted, and simulation result as shown in Figure 4;
2) emulation when digital quadrature phase detection filter exponent number constant, when matched filter exponent number changes, the present invention and the existing methodical handling capacity of singly taking advantage of, simulation result is as shown in Figure 5;
3) emulation is when section length changes, the present invention and the existing methodical handling capacity of singly taking advantage of, and simulation result is as shown in Figure 6.
3. analysis of simulation result
As can be seen from Figure 4, along with digital quadrature phase detection filter exponent number increases, than the present invention, the existing methodical handling capacity of singly taking advantage of declines rapidly, and it is now methodical more than 2 times that the treatment effeciency of the present invention when digital quadrature phase detection filter exponent number is larger can reach.
As can be seen from Figure 5, along with matched filter exponent number increases, the handling capacity of singly taking advantage of of the present invention is methodical more than 2 times now all the time.
As can be seen from Figure 6, singly the take advantage of handling capacity of existing method when optimal segmentation length is 0.008132, and singly the take advantage of handling capacity of the present invention when optimal segmentation length is 0.01759, of the present inventionly singly takes advantage of handling capacity to be about existing method list to take advantage of 2.16 times of handling capacity.
To sum up, the present invention has obviously reduced the operand that radar echo signal is done to digital quadrature phase demodulation and matched filtering, has improved treatment effeciency.
Claims (4)
1. an optimization method for digital quadrature phase demodulation and matched filtering, comprises the steps:
(1) Radar IF Echo is done to Fast Fourier Transform (FFT), conversion is counted as 2L, and obtaining length is the positive frequency A of L and the image frequency E that length is L, wherein, and the power that L is 2, and 2L is more than or equal to the length of echoed signal, from image frequency E, before taking-up
individual point and after
individual as effective image frequency B, W is less than L, and is greater than 0;
(2) according to the parameter of radar emission signal, in the design of filter instrument of Matlab, low-pass filter parameter is set, generate the low-pass filter coefficients of specifying exponent number, by Fast Fourier Transform (FFT), this coefficient is changed to frequency domain, again frequency domain low-pass filter coefficients is done to frequency spectrum shift, obtaining length is the orthogonal phase detection filter coefficient of the frequency domain digital F of 2L;
(3) baseband signal of radar is done to conjugation reversion, obtain matched filter coefficient, by Fast Fourier Transform (FFT), this coefficient is changed to frequency domain, obtaining length is the frequency matching filter coefficient D of 2L;
(4) according to frequency domain digital orthogonal phase detection filter coefficient F and frequency matching filter coefficient D, obtain the filter factor merging: H=FD, filter coefficient H is divided into length and is two sections of L: one section as passband FACTOR P, another section is as stopband coefficient S, and before taking out from stopband coefficient S
individual point and after
individual as transitional zone coefficient Q;
(5), according to above-mentioned parameter, obtain the frequency spectrum after Radar IF Echo matched filtering: Z=AP+BQ;
(6) frequency spectrum Z is done to inverse fast fourier transform, obtain time domain matched filtering result, according to the peak point of this time domain matched filtering result, calculate the distance r of target, for follow-up Radar Signal Processing.
2. according to the digital quadrature phase demodulation described in claims 1 and the optimization method of matched filtering, the low-pass filter parameter in wherein said step (2) comprises: filter type, signal sampling rate, filter transmission band frequency, filter stop band frequency, wave filter transitional zone frequency and the filter order of low-pass filter.
3. according to the digital quadrature phase demodulation described in claims 1 and the optimization method of matched filtering, what wherein step (2) was described does frequency spectrum shift to frequency domain low-pass filter coefficients, be the intermediate frequency place that the centre frequency of passband in low-pass filter frequency spectrum is moved on to positive frequency A, the centre frequency of stopband in low-pass filter frequency spectrum moved on to the intermediate frequency place of image frequency E.
4. according to the digital quadrature phase demodulation described in claims 1 and the optimization method of matched filtering, in wherein said step (6), according to the peak point of this time domain matched filtering result, calculate the distance r of target, by following formula, calculate:
Wherein c is the light velocity, and τ is the time delay of radar return with respect to radar transmitting wave,
n is the position of time domain matched filtering result peak point, f
sfor signal sampling rate.
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| CN104731762A (en) * | 2015-03-25 | 2015-06-24 | 西安电子科技大学 | Cubic phase signal parameter estimation method based on cyclic shift |
| CN106656106A (en) * | 2016-12-26 | 2017-05-10 | 哈尔滨工程大学 | Frequency domain adaptive matched filter method |
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| CN109541556A (en) * | 2018-12-21 | 2019-03-29 | 中国航天科工集团八五研究所 | A kind of recognition methods of pair of linear FM signal shift-frequency jamming |
| CN111277245A (en) * | 2020-03-24 | 2020-06-12 | 西安电子科技大学 | Design method for low-order sub-band filter of filtering orthogonal frequency division multiplexing system |
| CN113126033A (en) * | 2021-03-01 | 2021-07-16 | 西安电子科技大学 | Radar signal digital orthogonal down-conversion method |
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| CN104731762A (en) * | 2015-03-25 | 2015-06-24 | 西安电子科技大学 | Cubic phase signal parameter estimation method based on cyclic shift |
| CN104731762B (en) * | 2015-03-25 | 2017-11-21 | 西安电子科技大学 | Cube phase modulated parameter estimating method based on cyclic shift |
| CN106656106A (en) * | 2016-12-26 | 2017-05-10 | 哈尔滨工程大学 | Frequency domain adaptive matched filter method |
| CN106656106B (en) * | 2016-12-26 | 2019-04-23 | 哈尔滨工程大学 | A kind of frequency domain adaptive matched-filter approach |
| CN109495187A (en) * | 2018-11-23 | 2019-03-19 | 山东航天电子技术研究所 | A kind of TOA essence estimation method based on Hilbert transform |
| CN109495187B (en) * | 2018-11-23 | 2021-07-13 | 山东航天电子技术研究所 | TOA fine estimation method based on Hilbert transform |
| CN109541556A (en) * | 2018-12-21 | 2019-03-29 | 中国航天科工集团八五研究所 | A kind of recognition methods of pair of linear FM signal shift-frequency jamming |
| CN111277245A (en) * | 2020-03-24 | 2020-06-12 | 西安电子科技大学 | Design method for low-order sub-band filter of filtering orthogonal frequency division multiplexing system |
| CN111277245B (en) * | 2020-03-24 | 2023-03-10 | 西安电子科技大学 | Design method for low-order sub-band filter of filtering orthogonal frequency division multiplexing system |
| CN113126033A (en) * | 2021-03-01 | 2021-07-16 | 西安电子科技大学 | Radar signal digital orthogonal down-conversion method |
| CN113126033B (en) * | 2021-03-01 | 2023-12-22 | 西安电子科技大学 | Radar signal digital quadrature down-conversion method |
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