CN103001654B - Self-adaption radio frequency receiver capable of converting frequency into intermediate frequency - Google Patents
Self-adaption radio frequency receiver capable of converting frequency into intermediate frequency Download PDFInfo
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Abstract
The invention discloses a self-adaption radio frequency receiver capable of converting frequency into intermediate frequency. The radio frequency receiver comprises a receiving antenna, a low-noise amplifier, an analog lower frequency converter, a corner frequency controllable low-pass filter, an analog-to-digital converter, a static direct-current shifting correcting module and a channel selecting and processing module. The output end of the receiving antenna is connected with the input end of the channel selecting and processing module sequentially through the noise amplifier, the analog lower frequency converter, the corner frequency adjustable low-pass filter, the analog-to-digital converter and the static direct-current shifting correcting module. The channel selecting and processing module can select a zero intermediate frequency channel or a low intermediate frequency channel according to signals corrected primarily and can optimize direct-current shifting and adjacent channel selection simultaneously. Further more, the invention further comprises a receiving signal strength indicating module. The radio frequency receiver is simple in structure, low in cost and easy to achieve. In addition, the radio frequency receiver has good expandability and portability and can be widely applied to the technical field of wireless communication.
Description
Technical field
The present invention relates to wireless communication technology field, especially a kind of adaptive strain intermediate frequency radio-frequency transmitter.
Background technology
Explanation of nouns:
CW: single carrier;
ZIF: zero intermediate frequency;
DC offset: direct current offset;
ACS: neighboring trace is selected;
ACI: monkey chatter;
LIF: Low Medium Frequency;
LNA: low noise amplifier;
Mixer: frequency mixer;
PLL: phase-locked loop.
Existing radio-frequency transmitter framework mainly contains following three kinds:
(1) super-heterodyne architecture
Super-heterodyne architecture is the most widely used a kind of system configuration of early stage radio-frequency transmitter, its general principle is the signal high-frequency signal received from antenna being converted to after amplification and down-conversion a fixed intermediate frequency, then carries out further down-conversion to this fixed intermediate frequency signal or directly carries out demodulation.
Realizing the subject matter that superheterodyne receiver runs into is that mirror image suppresses problem, and this problem is caused by down-conversion.When down-conversion, except useful signal is converted to intermediate frequency, image signal is also converted to intermediate frequency, thus causes interference to useful signal.Suppress unique way of Image interference before down-conversion, to suppress image signal exactly, and the suppression of image signal has generally come by being positioned at the image-reject filter before low-converter.Under very poor reception environment, higher performance is still kept in order to make receiver, the necessary high compression image signal of image-reject filter, thus image-reject filter needs to have high-quality-factor and high exponent number, is difficult to be integrated on silicon chip, and the external mode of general employing realizes.This adds increased circuit scale and sheet external component number, improve system cost, thus make the application of super-heterodyne architecture greatly limited.
(2) zero-intermediate-frequency architecture
In ZIF receiver, useful signal is direct down-conversion-to base band, and like this, image signal is exactly useful signal itself, alleviates the requirement suppressed mirror image.But there is a series of problem in ZIF receiver, as I/Q branch road do not mate, DC offset and 1/f noise etc.The DC offset composition introduced by down-conversion and post-module will directly be superimposed upon on useful signal, thus causes interference to useful signal.The energy of these DC offset compositions may be much stronger than useful signal, can flood useful signal, and make the processing modules at different levels of rear class occur saturated.Therefore DC offset is the principal element hindering zero intermediate frequency reciver extensive use.
What Fig. 1 showed is when CW inputs, the situation of ZIF framework receiver double-side band output spectrum.Wherein, DC offset is positioned at 0Hz place.Generally, unregulated DC offset all specific sensitivity test time useful signal larger (for narrowband systems GSM, the sensitivity of radio-frequency transmitter General Requirements reaches-108dBm), will seriously limit received signal to noise ratio and the sensitivity of narrowband systems receiver if therefore do not calibrate.
The technology of calibrating DC offset at present can be divided into Static and dynamic to calibrate two large classes substantially:
1) static calibration (comprising the implementation of analog/digital circuit): detect the DC offset components size in a period of time useful signal and deducted.The method Problems existing is, the DC offset of receiver exists longer stabilization process (coming from the transient response that circuit is intrinsic) after entering accepting state.As shown in Figure 2, suppose that Received signal strength is sine wave signal, then its DC offset(receiving output is shown in the black thick line in figure) just can to settle out through a very long time.Because only need DC offset stablize after testing result just meaningful, therefore DC offset is detected to the time also needing one longer.And detection is carried out to DC offset just must enter accepting state in radio system, valid data complete before arriving, otherwise will affect valid data arrive after received signal to noise ratio.And for most protocol system sequential, system only has the very limited time (being usually less than 100us) can be used for DC offset detection and eliminate before entering receiving mode at every turn.Therefore, the effect of static DC offset testing calibration is usually undesirable.
2) dynamic calibration: utilize the high pass filter of a corner frequency very narrow (being usually less than 1KHz) that DC offset is given filtering.The corner frequency of this high pass filter is that DC offset suppresses, received signal quality and signal stabilization time compromise: if select corner frequency wider, DC offset is suppressed better, but will more useful signal be had to be attenuated for narrow band signal, thus have impact on the quality of Received signal strength; And if selection corner frequency is narrower, the quality of Received signal strength will increase, but limited to the suppression of DC offset, and the step response time of narrow corner frequency is longer, and receiver is also longer for stabilization time, can not meet the timing requirements of gsm system receiving mode.
3) Low Medium Frequency framework
Because superheterodyne receiver is easily subject to the interference of image signal, and ZIF receiver can be subject to the interference of DC offset, therefore there has been proposed LIF receiver architecture.Mirror image suppresses problem to transfer to lower intermediate frequency by radio frequency by LIF receiver, alleviate the pressure of realization, make such receiver ratio be easier to integrated, and the signal after LIF receiver down-conversion is not positioned at zero-frequency, avoids the DC offset problem that ZIF receiver runs into.
Still for gsm system, usually adopt the gsm system of LIF framework can select intermediate frequency about-100KHz.LIF receiver architecture is to the processing procedure of DC offset as shown in Figure 3: assuming that the frequency that CW useful signal is Flo+F0, LIF is Fif, then the frequency of local oscillation signal is Flo-Fif(and the local frequency of ZIF framework is Flo).First CW useful signal amplifies and frequency mixer Mixer mixing through low noise amplifier LNA, and then, the signal after mixing carries out analog filtering and analog-to-digital conversion through analog filter and analog to digital converter.Useful signal frequency after analog-to-digital conversion becomes (Flo+F0)-(Flo-Fif)=F0+Fif(and useful signal frequency after ZIF framework down-conversion is F0), the frequency of DC offset is at 0Hz.Can find out, LIF framework is adopted can effectively to make useful signal and DC offset frequency content every obtaining farther (in LIF framework, the frequency interval of the two is than the Fif far away in ZIF framework), therefore LIF framework can use the high pass filter with high corner frequency to carry out filtering, as shown in step (b) to DC offset when not damaging useful signal.After completing high-pass filtering, useful signal is unaffected, but DC offset usually can suppressed more than 30dB.And then, the useful signal after high-pass filtering is through the digital frequency conversion of step (c), and be restored in F0 frequency, DC offset is then shifted on-Fif.Now DC offset is enough decayed, and can not form obviously impact again to the sensitivity of useful signal, and due to its corner frequency higher, the stabilization time of receiver is shorter, and gsm system receiving mode sequential also will be easier to be satisfied.Therefore, with regard to the performance of DC offset, comparatively ZIF framework is advantageously for LIF framework.
But for the performance of ACS, LIF framework does not but have advantage.
Still for gsm system.The ACS of GSM requires: as shown in Figure 4, when useful signal (oblique line portion) is-82dBm, monkey chatter (ACI) intensity at distance carrier frequency 200KHz place is-73dBm, and the ACI intensity at distance carrier frequency 400KHz place is-41dBm, and the ACI intensity at distance carrier frequency 600KHz place is-33dBm.ACI(is particularly apart from the neighboring trace of carrier frequency 400KHz and 600KHz) disturb very by force, late-class circuit will be caused saturated if do not process, thus affect the performance of receiver.Therefore, also can add that simulation low-pass filter suppresses ACI (filter amplitude-frequency response as Fig. 4 in thick black line shown in) in the ADC prime of receive path.
When adopting ZIF framework receiver, useful signal (being in carrier frequency place before frequency conversion) is direct down-conversion-to zero-frequency place, for frequently positive and negative ACI frequently, simulation low-pass filter only needs to suppress same amplitude (the analog filter amplitude-frequency response see thick line black in Fig. 5 and Fig. 6), can ensure the performance of receiver ACS.
And when adopting LIF framework receiver, suppose that IF-FRE is Fif, then, before digital frequency conversion, the signal center received is at Fif place.For the signal of positive part frequently, in order to ensure that useful signal is injury-free, the bandwidth of the analog filter under LIF framework must wider than the pass band width under ZIF framework (minimum wide Fif); And due to simulation low-pass filter positive frequently and negative place frequently show same amplitude-frequency characteristic (see Fig. 7 and Fig. 8), under LIF framework, the ACI of negative part frequently suppresses to be deteriorated (the analog filter amplitude-frequency response see thick line black in Fig. 8).Select larger intermediate frequency Fif, the ACI of negative part frequently suppresses poorer.Therefore, LIF framework must adopt circuit more complicated, realizes difficulty and the larger band pass filter of power consumption to ensure ACS performance.
In sum, not yet there is a kind of receiver architecture at present, the performance of DC offset and ACS two indexs can be optimized simultaneously.And analyze from the characteristic of existing receiver architecture, there is not the framework simultaneously can optimizing DC offset and ACS two index performances by less cost yet.
Summary of the invention
In order to solve the problems of the technologies described above, the object of the invention is: a kind of adaptive strain intermediate frequency radio-frequency transmitter is provided, direct current offset can be optimized and neighboring trace selects this two performance index simultaneously.
The technical solution adopted for the present invention to solve the technical problems is: a kind of adaptive strain intermediate frequency radio-frequency transmitter, comprising:
Reception antenna, for receiving wireless signal;
Low noise amplifier, for amplifying the wireless signal received;
Analog down converter, for carrying out down-conversion to the signal after amplification, thus generates analog intermediate frequency signal;
Corner frequency tunable low pass filter, for carrying out neighboring trace selection and anti-aliasing filter to the analog intermediate frequency signal generated;
Analog to digital converter, for by select through neighboring trace and anti-aliasing filter after analog if signal be converted to digital medium-frequency signal;
Static DC offsets calibration module, for carrying out preliminary calibration to the direct current offset of digital medium-frequency signal;
Channel selecting and processing module, for according to the signal behavior zero intermediate frequency channel after preliminary calibration or Low Medium Frequency passage, and then process the signal after preliminary calibration according to the passage selected;
The output of described reception antenna passes through low noise amplifier, analog down converter, corner frequency tunable low pass filter, analog to digital converter, static DC offsets calibration module successively and then is connected with the input of described channel selecting and processing module.
Further, described channel selecting and processing module comprise dynamic direct current offset calibration submodule and for selecting the diverter switch of zero intermediate frequency channel or Low Medium Frequency passage, the input of described diverter switch is connected with the output of described static DC offsets calibration module, the output of described diverter switch comprises the first switching point and the second switching point, the input that described first switching point calibrates submodule with described dynamic direct current offset is connected, and the output of described dynamic direct current offset calibration submodule is connected with Digital Down Convert submodule and digital filter in turn; Described second switching point is connected with the input of described digital filter.
Further, described analog down converter comprises the frequency mixer that is connected with low noise amplifier output and for providing the phase-locked loop of orthogonal local oscillation signal for frequency mixer; Described frequency mixer is used for orthogonal local oscillation signal and the signal after amplifying to carry out mixing, thus is sent to the input of corner frequency tunable low pass filter after the signal after amplification is down-converted to intermediate-freuqncy signal.
Further, also comprise for carrying out the received signal strength indicator module controlled according to the handoff threshold selected, the input of described received signal strength indicator module is connected with the output of described digital filter, first output of described received signal strength indicator module is connected with the input of described corner frequency tunable low pass filter, second output of described received signal strength indicator module is connected with the input of described diverter switch, and the 3rd output of described received signal strength indicator module is connected with the input of described phase-locked loop.
Further, comprise a radio frequency chip, described low noise amplifier, analog down converter, corner frequency tunable low pass filter, analog to digital converter, static DC offsets calibration module, channel selecting and processing module, received signal strength indicator module are all located on described radio frequency chip.
Further, comprise a baseband chip and radio frequency chip, described received signal strength indicator module installation is on baseband chip, and described low noise amplifier, analog down converter, corner frequency tunable low pass filter, analog to digital converter, static DC offsets calibration module, channel selecting and processing module are all arranged on described radio frequency chip.
Further, the handoff threshold of described received signal strength indicator module sets according to different communication systems.
Further, the handoff threshold of described received signal strength indicator module in gsm system is-87dBm.
The invention has the beneficial effects as follows: the present invention includes for according to the channel selecting of the signal behavior zero intermediate frequency channel after preliminary calibration or Low Medium Frequency passage and processing module, direct current offset can be optimized and neighboring trace selects this two performance index simultaneously; Further, also comprise for carrying out the received signal strength indicator module controlled according to the handoff threshold selected, can select zero intermediate frequency channel or Low Medium Frequency passage according to the Self-adaptive strength of Received signal strength, structure is simple, cost is lower and be easy to realize; Further, the handoff threshold of described received signal strength indicator module sets according to different communication systems, and namely the input signal thresholding of described radio-frequency transmitter can set according to different communication systems, is with good expansibility and portability.
Accompanying drawing explanation
Fig. 1 is the output spectrum of zero-intermediate-frequency architecture receiver;
Fig. 2 is the stabilization process of direct current offset after entering accepting state;
Fig. 3 is that Low Medium Frequency framework receiver is to the processing procedure of direct current offset;
Fig. 4 is monkey chatter and the analog filter amplitude-frequency response of gsm communication system;
Fig. 5 is the suppression schematic diagram that zero-intermediate-frequency architecture filter aligns monkey chatter frequently;
Fig. 6 is the suppression schematic diagram of zero-intermediate-frequency architecture filter to negative frequency monkey chatter
Fig. 7 is the suppression schematic diagram that Low Medium Frequency framework filter aligns monkey chatter frequently;
Fig. 8 is the suppression schematic diagram of Low Medium Frequency framework filter to negative frequency monkey chatter;
Fig. 9 is the block diagram of a kind of adaptive strain intermediate frequency radio-frequency transmitter of the present invention;
Figure 10 is the present invention carries out direct current offset calibration schematic diagram when signal is larger;
Figure 11 is the present invention carries out direct current offset calibration schematic diagram when signal is less;
Figure 12 is the composition structured flowchart of channel selecting of the present invention and processing module and received signal strength indicator module;
Figure 13 is the composition structured flowchart of analog down converter of the present invention.
Reference numeral: SW. diverter switch.
Embodiment
Below in conjunction with accompanying drawing, the specific embodiment of the present invention is described further.
With reference to Fig. 9, a kind of adaptive strain intermediate frequency radio-frequency transmitter of the present invention, comprising:
Reception antenna, for receiving wireless signal;
Low noise amplifier, for amplifying the wireless signal received;
Analog down converter, for carrying out down-conversion to the signal after amplification, thus generates analog intermediate frequency signal;
Corner frequency tunable low pass filter, for carrying out neighboring trace selection and anti-aliasing filter to the analog intermediate frequency signal generated;
Analog to digital converter, for by select through neighboring trace and anti-aliasing filter after analog if signal be converted to digital medium-frequency signal;
Static DC offsets calibration module, for carrying out preliminary calibration to the direct current offset of digital medium-frequency signal;
Channel selecting and processing module, for according to the signal behavior zero intermediate frequency channel after preliminary calibration or Low Medium Frequency passage, and then process the signal after preliminary calibration according to the passage selected;
The output of described reception antenna passes through low noise amplifier, analog down converter, corner frequency tunable low pass filter, analog to digital converter, static DC offsets calibration module successively and then is connected with the input of described channel selecting and processing module.
With reference to Figure 12, be further used as preferred embodiment, described channel selecting and processing module comprise dynamic direct current offset calibration submodule and for selecting the diverter switch SW of zero intermediate frequency channel or Low Medium Frequency passage, the input of described diverter switch SW is connected with the output of described static DC offsets calibration module, the output of described diverter switch SW comprises the first switching point and the second switching point, the input that described first switching point calibrates submodule with described dynamic direct current offset is connected, the output of described dynamic direct current offset calibration submodule is connected with Digital Down Convert submodule and digital filter in turn, described second switching point is connected with the input of described digital filter.Wherein, the function of dynamic direct current offset calibration submodule is realized by high pass filter, and diverter switch SW to cut what select when the first switching point be Low Medium Frequency passage, it is zero intermediate frequency channel that diverter switch SW cuts what select when the second switching point.
With reference to Figure 13, be further used as preferred embodiment, described analog down converter comprises the frequency mixer that is connected with low noise amplifier output and for providing the phase-locked loop of orthogonal local oscillation signal for frequency mixer; Described frequency mixer is used for orthogonal local oscillation signal and the signal after amplifying to carry out mixing, thus is sent to the input of corner frequency tunable low pass filter after the signal after amplification is down-converted to intermediate-freuqncy signal.
With reference to Figure 12, be further used as preferred embodiment, also comprise for carrying out the received signal strength indicator module controlled according to the handoff threshold selected, the input of described received signal strength indicator module is connected with the output of described digital filter, first output of described received signal strength indicator module is connected with the input of described corner frequency tunable low pass filter, second output of described received signal strength indicator module is connected with the input of described diverter switch SW, 3rd output of described received signal strength indicator module is connected with the input of described phase-locked loop.Wherein, handoff threshold selects according to the input signal strength of communication system or amplitude, and the control that described received signal strength indicator module is carried out comprises: tangential, the local frequency of phase-locked loop and the corner frequency of corner frequency tunable low pass filter that control diverter switch SW.
Be further used as preferred embodiment, comprise a radio frequency chip, described low noise amplifier, analog down converter, corner frequency tunable low pass filter, analog to digital converter, static DC offsets calibration module, channel selecting and processing module, received signal strength indicator module are all located on described radio frequency chip.
Below in conjunction with Fig. 9-13 and radio frequency chip, the radio-frequency transmitter to the adaptive strain intermediate frequency of the present invention only adopts the embodiment of one piece of radio frequency chip to illustrate:
The radio-frequency transmitter framework of the adaptive strain intermediate frequency of the present invention is as shown in Fig. 9, Figure 12 and Figure 13.Aerial wireless signal receives low noise amplifier through reception antenna, and the frequency mixer place of analog down converter delivered to by low noise amplifier after signal is amplified.Frequency mixer for analog down converter is provided orthogonal local oscillation signal by phase-locked loop pll, also namely by frequency divider, amplifying signal is divided into orthogonal I road signal and Q road signal.After down-conversion, the low pass filter adjustable through corner frequency is all carried out neighboring trace selection and anti-aliasing filter by I/Q two paths of signals.The output of the low pass filter that corner frequency is adjustable, by connection mode number converter, is converted to digital signal analog signal.Signal, after analog to digital converter, first through static DC offsets calibration module, will carry out preliminary calibration when radio frequency chip just powers on to direct current offset DC offset.Radio-frequency transmitter will record the value of this preliminary calibration, and automatically deduct this value when entering accepting state at every turn.Then signal will be selected to be through zero intermediate frequency channel by diverter switch SW and also be through Low Medium Frequency passage: if through Low Medium Frequency passage, then first signal will carry out dynamic direct current offset calibration through high pass filter (i.e. dynamic direct current offset calibration submodule), then carry out Digital Down Convert through digital down converter, send after the carrier wave vanishing intermediate-freuqncy signal of input signal into digital filter; If selection zero intermediate frequency channel, signal directly will send into digital filter.Digital filter will carry out filtering to the received signal, and by the formatted output of filtered signal according to interface setting.
When radio frequency chip just powers on, gsm communication system has a very long time, allows system carry out initialization, stablize and allow radio frequency chip complete various calibration algorithm.Utilization is carried out static DC offsets calibration (this calibration is carried out under specific frequency) by static DC offsets calibration module during this period of time.Because DC offset can change with frequency change, therefore static DC offsets calibration can also ensure to suppress very well by DC offset under the characteristic frequency at initialization place, and for other frequencies, static DC offsets calibration module can only be suppressed to a relatively little value (relative to not being for static DC offset calibrates) DC offset, to ensure DC offset (when that is to say employing ZIF framework) when no longer carrying out dynamic DC offset and calibrating, for relatively large signal the input (-82dBm as during test ACS performance), still there is enough output signal-to-noise ratios.
DC offset calibration method of the present invention (comprising static DC offsets calibration and the calibration of dynamic direct current offset) as shown in Figure 10 and Figure 11.As shown in figure 11, when input signal carrier frequency is F0, input signal strength or amplitude less time, receiver system is it is of concern that the index of sensitivity.Current GSM radio frequency chip generally can be accomplished to make sensitivity between-105 to-108dBm.For small-signal, remaining DC offset will obviously affect the signal to noise ratio of reception, now the dynamic direct current offset calibration submodule of inventive receiver can be calibrated laggard Mobile state DC offset at static DC offset and calibrates, and namely inventive receiver can proceed as follows:
1) diverter switch SW is cut at Low Medium Frequency passage (i.e. the first switching point of diverter switch);
2) control phase-locked loop pll and the local oscillator of F0-Fif (Fif is IF-FRE) is provided;
3) under the corner frequency of corner frequency tunable low pass filter is arranged on Low Medium Frequency pattern (now corner frequency is wider).
Aforesaid operations can utilize the high pass filter of Low Medium Frequency framework receiver effectively to suppress DC offset, thus the received signal to noise ratio improved under small-signal and sensitivity.
As shown in Figure 10, when input signal amplitude exceedes-82dBm, the signal to noise ratio of receiver system is enough high, and now DC offset can ignore the impact of signal to noise ratio, therefore receiving system is more it is of concern that ACS performance.Now, radio-frequency transmitter of the present invention only carries out static DC offset and calibrates and no longer carry out dynamic DC offset and calibrate, and namely radio-frequency transmitter of the present invention proceeds as follows:
1) diverter switch SW is cut at zero intermediate frequency channel (i.e. the second switching point of diverter switch);
2) local oscillator that phase-locked loop pll provides input signal carrier frequency F0 is controlled;
3) under the corner frequency of corner frequency tunable low pass filter is arranged on zero intermediate frequency pattern (now corner frequency is narrower).
The feature that aforesaid operations can utilize the low pass filter corner frequency of zero-intermediate-frequency architecture receiver narrower, effectively suppresses ACI, improves the ACS performance of receiver; Meanwhile, when just powering on, static DC offsets calibration module is calibrated to a less scope DC offset, even if do not use high pass filter also can ensure in the measurement of ACS, DC offset is not obvious produces harmful effect to output signal-to-noise ratio.
According to international, domestic code requirement, for gsm communication system, the input useful signal that ACS measures is-82dBm.And there is the effect of multipath fading due to wireless transmission, the signal that base station sends-82dBm arrives radio frequency chip antenna when being received, and signal has the fluctuation of scope.Therefore, as long as adopt zero-intermediate-frequency architecture when ensureing that input signal amplitude is greater than in theory, just ACS performance can be ensured.And this handoff threshold of-87dBm, minimum than the large 18dB of signal strength signal intensity when measuring receiving sensitivity, so time DC offset be negligible for the impact of this large-signal signal to noise ratio.
The receiver radio frequency chip of this embodiment is integrated with received signal strength indicator (RSSI) module, for detecting the intensity receiving signal at digital filter output.With-87dBm for handoff threshold, received signal strength indicator module is according to detecting that the size of input signal (i.e. the output signal of digital filter) is selected:
1) diverter switch SW;
2) local frequency of phase-locked loop pll;
3) corner frequency of the corner frequency of corner frequency tunable low pass filter.
The handoff threshold of received signal strength indicator model choice is the input signal thresholding that receiver architecture (i.e. channel selecting) switches, and it can be configured by the mode writing register.Therefore different handoff thresholds can be configured to adapt to different communication systems (such as gsm communication system, handoff threshold is exactly-87dBm).
Be further used as preferred embodiment, comprise a baseband chip and radio frequency chip, described received signal strength indicator module installation is on baseband chip, and described low noise amplifier, analog down converter, corner frequency tunable low pass filter, analog to digital converter, static DC offsets calibration module, channel selecting and processing module are all arranged on described radio frequency chip.
Below in conjunction with Fig. 9-13, radio frequency chip and baseband chip, the embodiment that the radio-frequency transmitter of the adaptive strain intermediate frequency of the present invention adopts radio frequency chip and baseband chip jointly to realize is described further:
This embodiment with only adopt the structure of the embodiment of one piece of radio frequency chip roughly the same, difference is: this embodiment selects radiofrequency receiving chip to adopt any framework by the received signal strength indicator module of baseband chip or received signal quality module.Now the framework of radio-frequency transmitter selects (i.e. channel selecting) directly to control by baseband chip, and does not control by radio-frequency transmitter internal chip enable signal.Powerful due to baseband chip, can the series of complex computing such as settling signal demodulation, therefore except by received signal strength indicator module, baseband chip can also judge current adopted radio-frequency transmitter framework whether optimization by the quality of received signal quality.If received signal quality is not now optimum, generation feedback signal is selected to radiofrequency receiving chip by baseband chip:
1) diverter switch SW;
2) local frequency of phase-locked loop pll;
3) corner frequency of the corner frequency of corner frequency tunable low pass filter.
Be further used as preferred embodiment, the handoff threshold of described received signal strength indicator module sets according to different communication systems.
Be further used as preferred embodiment, the handoff threshold of described received signal strength indicator module in gsm system is-87dBm.
More than that better enforcement of the present invention is illustrated, but the invention is not limited to described embodiment, those of ordinary skill in the art also can make all equivalent variations or replacement under the prerequisite without prejudice to spirit of the present invention, and these equivalent distortion or replacement are all included in the application's claim limited range.
Claims (7)
1. an adaptive strain intermediate frequency radio-frequency transmitter, is characterized in that comprising:
Reception antenna, for receiving wireless signal;
Low noise amplifier, for amplifying the wireless signal received;
Analog down converter, for carrying out down-conversion to the signal after amplification, thus generates analog intermediate frequency signal;
Corner frequency tunable low pass filter, for carrying out neighboring trace selection and anti-aliasing filter to the analog intermediate frequency signal generated;
Analog to digital converter, for by select through neighboring trace and anti-aliasing filter after analog if signal be converted to digital medium-frequency signal;
Static DC offsets calibration module, for carrying out preliminary calibration to the direct current offset of digital medium-frequency signal;
Channel selecting and processing module, for according to the signal behavior zero intermediate frequency channel after preliminary calibration or Low Medium Frequency passage, and then process the signal after preliminary calibration according to the passage selected;
The output of described reception antenna passes through low noise amplifier, analog down converter, corner frequency tunable low pass filter, analog to digital converter, static DC offsets calibration module successively and then is connected with the input of described channel selecting and processing module;
Described channel selecting and processing module comprise dynamic direct current offset calibration submodule and for selecting the diverter switch (SW) of zero intermediate frequency channel or Low Medium Frequency passage, the input of described diverter switch (SW) is connected with the output of described static DC offsets calibration module, the output of described diverter switch (SW) comprises the first switching point and the second switching point, the input that described first switching point calibrates submodule with described dynamic direct current offset is connected, and the output of described dynamic direct current offset calibration submodule is connected with Digital Down Convert submodule and digital filter in turn; Described second switching point is connected with the input of described digital filter.
2. one according to claim 1 adaptive strain intermediate frequency radio-frequency transmitter, is characterized in that: described analog down converter comprises the frequency mixer that is connected with low noise amplifier output and for providing the phase-locked loop of orthogonal local oscillation signal for frequency mixer; Described frequency mixer is used for orthogonal local oscillation signal and the signal after amplifying to carry out mixing, thus is sent to the input of corner frequency tunable low pass filter after the signal after amplification is down-converted to intermediate-freuqncy signal.
3. one according to claim 2 adaptive strain intermediate frequency radio-frequency transmitter, it is characterized in that: also comprise for carrying out the received signal strength indicator module controlled according to the handoff threshold selected, the input of described received signal strength indicator module is connected with the output of described digital filter, first output of described received signal strength indicator module is connected with the input of described corner frequency tunable low pass filter, second output of described received signal strength indicator module is connected with the input of described diverter switch (SW), 3rd output of described received signal strength indicator module is connected with the input of described phase-locked loop.
4. the adaptive strain intermediate frequency of the one according to Claims 2 or 3 radio-frequency transmitter, it is characterized in that: comprise a radio frequency chip, described low noise amplifier, analog down converter, corner frequency tunable low pass filter, analog to digital converter, static DC offsets calibration module, channel selecting and processing module, received signal strength indicator module are all located on described radio frequency chip.
5. the adaptive strain intermediate frequency of the one according to Claims 2 or 3 radio-frequency transmitter, it is characterized in that: comprise a baseband chip and radio frequency chip, described received signal strength indicator module installation is on baseband chip, and described low noise amplifier, analog down converter, corner frequency tunable low pass filter, analog to digital converter, static DC offsets calibration module, channel selecting and processing module are all arranged on described radio frequency chip.
6. the adaptive strain intermediate frequency of the one according to Claims 2 or 3 radio-frequency transmitter, is characterized in that: the handoff threshold of described received signal strength indicator module sets according to different communication systems.
7. the adaptive strain intermediate frequency of the one according to Claims 2 or 3 radio-frequency transmitter, is characterized in that: the handoff threshold of described received signal strength indicator module in gsm system is-87dBm.
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| CN107888274B (en) * | 2016-09-30 | 2021-01-26 | 展讯通信（上海）有限公司 | Mobile signal relay amplifier |
| CN111091697B (en) * | 2019-11-29 | 2021-08-13 | 湖北航天飞行器研究所 | Telemetry data processing system |
| CN113364479B (en) * | 2020-03-05 | 2023-01-17 | 海能达通信股份有限公司 | Method for eliminating direct current bias, receiver and communication equipment |
| CN111447035B (en) * | 2020-04-23 | 2022-02-11 | 紫光展锐(重庆)科技有限公司 | Adjacent channel interference suppression method and related equipment |
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| Publication number | Priority date | Publication date | Assignee | Title |
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| CN101061640A (en) * | 2004-09-30 | 2007-10-24 | 诺基亚公司 | Direct conversation receiver radio frequency integrated circuit |
| CN101490997A (en) * | 2006-07-14 | 2009-07-22 | 高通股份有限公司 | Multi-carrier receiver for wireless communication |
| US8160529B1 (en) * | 2006-03-07 | 2012-04-17 | Marvell International Ltd. | Adaptive FM/AM radio architecture |
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| CN100426895C (en) * | 2001-12-07 | 2008-10-15 | 中兴通讯股份有限公司 | Signal receiving method and apparatus in wireless base station |
| US7773545B2 (en) * | 2008-02-27 | 2010-08-10 | Mediatek Inc. | Full division duplex system and a leakage cancellation method |
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Patent Citations (3)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN101061640A (en) * | 2004-09-30 | 2007-10-24 | 诺基亚公司 | Direct conversation receiver radio frequency integrated circuit |
| US8160529B1 (en) * | 2006-03-07 | 2012-04-17 | Marvell International Ltd. | Adaptive FM/AM radio architecture |
| CN101490997A (en) * | 2006-07-14 | 2009-07-22 | 高通股份有限公司 | Multi-carrier receiver for wireless communication |
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