CN102801340B - Control method and controller for AC-DC converter - Google Patents
Control method and controller for AC-DC converter Download PDFInfo
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- CN102801340B CN102801340B CN201210295489.0A CN201210295489A CN102801340B CN 102801340 B CN102801340 B CN 102801340B CN 201210295489 A CN201210295489 A CN 201210295489A CN 102801340 B CN102801340 B CN 102801340B
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Abstract
The invention discloses a control method for an alternating current to a direct current (AC-DC) converter. The auxiliary winding voltage signal of the AC-DC converter is collected, and a feedback quantity is automatically compensated by a high-precision primary feedback technology to obtain a precise feedback quantity, so that a pulse-width modulation (PWM) signal is formed to drive a switch tube in the AC-DC converter to finally achieve the aim of controlling and regulating the output voltage of the converter; and therefore, the precision of the feedback quantity calculated by the method ensures the precision of the output voltage of the AC-DC converter. The invention further discloses a controller for the AC-DC converter. The controller comprises a primary sampling circuit and a digital compensator, wherein the primary sampling circuit comprises a waveform real-time analyzing module, a single-input double-output digital-to-analog converter and two comparators. According to the controller, a relatively precise feedback quantity can be obtained; and the digital-to-analog converter rather than an analog-to-digital converter is adopted so as to reduce the design difficulty and save the consumed area.
Description
Technical field
The invention belongs to voltage changer control technology field, be specifically related to control method and the controller thereof of a kind of AC-DC (AC-DC) converter.
Background technology
Along with the development of battery charger, LED drive circuit etc., the designing technique chip of AC-DC converter has also obtained develop rapidly.The integrated level of AC-DC converter chip is required also improving gradually, and designer is required to use as little as possible the outer device of sheet, to reduce hardware spending and converter overall volume.
Fig. 1 is traditional based on secondary feedback AC-DC converter.This chip adopts light-coupled isolation feedback system as shown in the figure, output voltage on load resistance passes through photoelectrical coupler, be delivered to transformer primary side as feedback voltage, and remove regulation output voltage by controller, this feedback system not only needs the outer photoelectrical coupler of a sheet, increase expense, and the current transfer ratio of photoelectrical coupler is subject to the impact of temperature larger, along with the variation of temperature, current transfer ratio can be nonlinear change, cause the sampling of output voltage to occur error, affect output voltage precision, this impact is the most obvious in the larger power supply of the heavier heating of load.
The AC-DC converter based on former limit feedback is as shown in Figure 2 widely adopted.In figure, feedback voltage is that the auxiliary winding up-sampling of transformer from converter obtains, and is characterized in also realizing the isolation of former limit and secondary without photoelectrical coupler in the situation that, but due to auxiliary winding voltage V
sensenon-direct voltage, therefore, at a sampling hold circuit of chip internal design, removes at a fixing sampled point V that samples
senseobtain feedback quantity V
fBbut under actual conditions, sampling hold circuit may be very inaccurate, this fixing sampled point cannot be followed the tracks of knee voltage, and the impact of diode drop can cause the not accurate of sampling.
According to the known existing sampling feedback technology of above-mentioned situation, the feedback quantity V of its output
fBbetween corresponding feedback voltage and converter output voltage, there is certain error.This error, along with loading condition and the outer device parameters of sheet of system change and change, cannot compensate this error in sheet.The error of feedback quantity directly affects the precision of output voltage.
Summary of the invention
For the existing above-mentioned technological deficiency of prior art, the invention provides a kind of control method and controller thereof of AC-DC converter, can obtain the output voltage of relatively accurate feedback quantity with control change device.
A control method for AC-DC converter, comprises the steps:
(1) the auxiliary winding voltage signal V of collection AC-DC converter
sense, and obtain the feedback quantity V in a cycle on AC-DC converter
fB[i-1];
(2) to described feedback quantity V
fBafter [i-1] digital-to-analogue conversion, obtain feedback voltage V 1, and will after fixed voltage value of the amplitude lifting of feedback voltage V 1, obtain comparative voltage V2;
(3) by described auxiliary winding voltage signal V
sensecompare with feedback voltage V 1 and comparative voltage V2 respectively, obtain respectively two comparison signal V
s1and V
s2;
(4) calculate two comparison signal V
s1and V
s2trailing edge time difference Δ t, and by trailing edge time difference Δ t and fiducial time poor Δ t
refcompare, determine regulated quantity Δ V according to both differences
fB, and then utilize regulated quantity Δ V by feedback compensation algorithm
fBto feedback quantity V
fB[i-1] regulates compensation, in the hope of the feedback quantity V of AC-DC converter current period
fB[i];
(5) according to described feedback quantity V
fB[i] constructs pwm signal, to control the break-make of switching tube in AC-DC converter.
Described feedback compensation algorithm is based on following formula:
As Δ t > Δ t
reftime: V
fB[i]=V
fB[i-1]-Δ V
fB
As Δ t=Δ t
reftime: V
fB[i]=V
fB[i-1]
As Δ t < Δ t
reftime: V
fB[i]=V
fB[i-1]+Δ V
fBwherein: differ from Δ t fiducial time
reffor default set-point; Δ t and Δ t
refdiffer larger, Δ V
fBalso larger.
A controller for AC-DC converter, comprises former limit sample circuit and digital compensator;
Described digital compensator is used for according to the feedback quantity V of the AC-DC converter current period of former limit sample circuit output
fB[i] constructs pwm signal, to control the break-make of switching tube in AC-DC converter;
Described former limit sample circuit comprises a waveform real-time analysis module, a single-input double-output digital to analog converter and two comparators;
The feedback quantity V in a cycle on the AC-DC converter of described single-input double-output digital to analog converter reception waveform real-time analysis module output
fB[i-1], to feedback quantity V
fBafter [i-1] digital-to-analogue conversion, obtain feedback voltage V 1 output, will after fixed voltage value of the amplitude lifting of feedback voltage V 1, obtain comparative voltage V2 output;
Two comparators are respectively by the auxiliary winding voltage signal V of feedback voltage V 1 and comparative voltage V2 and AC-DC converter
sensecompare, obtain respectively two comparison signal V
s1and V
s2;
Described waveform real-time analysis module is used for calculating two comparison signal V
s1and V
s2trailing edge time difference Δ t, and by trailing edge time difference Δ t and fiducial time poor Δ t
refcompare, determine regulated quantity Δ V according to both differences
fB, and then utilize regulated quantity Δ V by feedback compensation algorithm
fBto feedback quantity V
fB[i-1] regulates compensation, in the hope of the feedback quantity V of AC-DC converter current period
fB[i].
Preferably, described single-input double-output digital to analog converter is built by two MUX and a string divider resistance, and this digital to analog converter adopts the linear dividing potential drop of resistance to form, simple in structure, realize easily, and the matching precision of resistance is very high, guarantees that dividing potential drop has the good linearity.
Preferably, described waveform real-time analysis module and digital compensator are all by the FPGA realization of programming, and FPGA programming has stronger flexibility, and convenient control and adjusting for clock accuracy, have good repeatability.
The present invention is by gathering the auxiliary winding voltage signal of AC-DC converter, and adopt high-precision former limit feedback technique, auto-compensation feedback quantity, to obtain accurate feedback quantity, and then construct pwm signal to drive the switching tube in AC-DC converter, finally realize the object of regulating and controlling converter output voltage; Therefore the inventive method calculates the precision of feedback quantity, and then guarantee the precision of AC-DC converter output voltage; Controller simultaneously of the present invention adopts digital to analog converter (but not analog to digital converter), under comparing, has reduced design difficulty, has saved the area consuming.
Accompanying drawing explanation
Fig. 1 is the structural representation of AC-DC converter and the controller based on secondary feedback thereof.
Fig. 2 is the structural representation of AC-DC converter and the controller based on former limit feedback thereof.
Fig. 3 is AC-DC converter of the present invention and control structure schematic diagram thereof.
Fig. 4 is signal I in AC-DC converter
s, V
sensework wave schematic diagram with PWM.
Fig. 5 is the structural representation of controller of the present invention.
Fig. 6 is the structural representation of single-input double-output digital to analog converter.
The waveform schematic diagram of each signal when Fig. 7 (a) is the corresponding knee voltage of feedback quantity.
Fig. 7 (b) is the waveform schematic diagram of the relative knee voltage of feedback quantity each signal when excessive.
Fig. 7 (c) is the waveform schematic diagram of the relative knee voltage of feedback quantity each signal when too small.
Fig. 8 is the schematic flow sheet of feedback compensation algorithm of the present invention.
Embodiment
In order more specifically to describe the present invention, below in conjunction with the drawings and the specific embodiments, control method of the present invention and controller thereof are elaborated.
Shown in Fig. 3 the structure of AC-DC converter of the present invention and controller thereof, AC-DC converter is made up of half-wave rectifier BR, transformer T, switching tube Q, diode D and capacitor C; Wherein, the positive-negative input end of half-wave rectifier BR meets alternating voltage AC, positive output end and the former limit of transformer T winding N
psame Name of Ends be connected, negative output terminal ground connection; The former limit of transformer T winding N
pnon-same polarity be connected with the drain electrode of switching tube Q, the source ground of switching tube Q, the grid of switching tube Q receives the pwm signal that controller provides, transformer T secondary winding N
snon-same polarity be connected with the anode of diode D, the negative electrode of diode D is connected with one end of capacitor C, the other end of capacitor C and transformer T secondary winding N
ssame Name of Ends be connected and ground connection, transformer T assists winding N
auxnon-same polarity be connected with resistance R
1, transformer T assists winding N
auxsame Name of Ends ground connection, resistance R
1by with resistance R
2ground connection after series connection; The two ends of capacitor C are the output port of AC-DC converter, and the output port of AC-DC converter meets load R, and the voltage at load R two ends is the output voltage V o of AC-DC converter.
Controller comprises former limit sample circuit and digital compensator; Former limit sample circuit gathers the auxiliary winding voltage signal V of AC-DC converter
sense, and according to the feedback quantity V of this signal output AC-DC converter current period
fB[i]; Digital compensator is according to the feedback quantity V of former limit sample circuit output
fB[i] constructs pwm signal, to control the break-make of switching tube Q in AC-DC converter.
Shown in Fig. 4 the basic waveform of AC-DC converter each signal of when work, wherein I
sfor output winding current; In the time that PWM is 1, switching tube Q is open-minded, former limit winding current I
prise gradually, transformer T is at former limit winding N
pupper stored energy, auxiliary winding voltage
for negative value (N
auxand N
pbe respectively the coil turn of auxiliary winding and former limit winding), output winding (is secondary winding N
s) both end voltage V
salso be negative voltage, now diode D turn-offs, the electric current I on output winding
sbe 0, load R is powered by output capacitance C.
In the time that PWM is 0, switching tube Q turn-offs, and diode D conducting, is stored in former limit winding N
pon energy be transferred to output winding, output winding current I
srise to rapidly peak I
sPrear beginning declines gradually, and descending slope is with output winding both end voltage V
srelevant.Work as I
sdo not drop to before zero,
Wherein: V
dthe pressure drop of diode D, R
pit is the dead resistance of wire and diode D.Work as electric current I
sthe null moment, V
d=0,
this moment point voltage is designated as knee voltage (knee voltage).Work as I
selectric current drops to after 0, due to not conducting of switching tube Q, and former limit winding N
pand can there is series resonance between the parasitic capacitance of switching tube Q, harmonic period is by former limit winding N
pthe parasitic capacitance size of inductance and switching tube Q determines, at this one-phase
Wherein: L
mit is former limit winding inductance.
By
known, work as output winding current I at flex point place
sdrop to for 0 moment, V
sensewith output voltage V
orelation in direct ratio, therefore according to the V at this some place
sensethe feedback quantity calculating is the most accurate.
When Q turn-offs, output winding current I
sdrop to after 0, i.e. V
senseafter flex point, can enter resonance condition, the moment T occurring in flex point
kneefront and back, V
senseslope variation be very large, for this feature, the present invention proposes a kind of control method of AC-DC converter output voltage, comprise the steps:
(1) the auxiliary winding voltage signal V of collection AC-DC converter
sense, and obtain the feedback quantity V in a cycle on AC-DC converter
fB[i-1]; Present embodiment is passed through resistance R
1and R
2to the auxiliary winding N of transformer T
auxthe voltage at two ends carries out dividing potential drop, therefore the auxiliary winding voltage signal V collecting
sensefor auxiliary winding N
auxthe voltage of both end voltage after step-down;
(2) to feedback quantity V
fBafter [i-1] digital-to-analogue conversion, obtain feedback voltage V 1, and will after fixed voltage value of the amplitude lifting of feedback voltage V 1, obtain comparative voltage V2; In present embodiment, this fixed voltage value is 100mV;
(3) will assist winding voltage signal V
sensecompare with feedback voltage V 1 and comparative voltage V2 respectively, obtain respectively two comparison signal V
s1and V
s2;
(4) calculate two comparison signal V
s1and V
s2trailing edge time difference Δ t, and by trailing edge time difference Δ t and fiducial time poor Δ t
refcompare, determine regulated quantity Δ V according to both differences
fB;
In present embodiment, differ from Δ t fiducial time
reffor 4clk, clk is a clock cycle; Δ t and Δ t
refdiffer larger, Δ V
fBalso larger; In present embodiment, | Δ t-Δ t
ref| with Δ V
fBconcrete determine that relation is as shown in table 1;
Table 1
| |Δt-Δt ref| | ΔV FB |
| 0clk | 0 |
| |
1 |
| |
2 |
| 3clk | 3 |
| 4clk | 4 |
Wherein, if continuous several control cycle | Δ t-Δ t
ref| all larger, can suitably strengthen its corresponding regulated quantity.
Utilize regulated quantity Δ V by following feedback compensation algorithm
fBto feedback quantity V
fB[i-1] regulates compensation, in the hope of the feedback quantity V of AC-DC converter current period
fB[i];
As Δ t > Δ t
reftime: V
fB[i]=V
fB[i-1]-Δ V
fB
As Δ t=Δ t
reftime: V
fB[i]=V
fB[i-1]
As Δ t < Δ t
reftime: V
fB[i]=V
fB[i-1]+Δ V
fB
By select to set poor Δ t of suitable fixed voltage value and fiducial time in conjunction with actual parameter
ref, make to equal Δ t as Δ t
reftime, feedback quantity has just reacted needed knee voltage, to realize the automatic tracing to knee voltage and to realize accurate former limit sampling.
(5) according to feedback quantity V
fB[i] constructs pwm signal, to control the break-make of switching tube Q in AC-DC converter.
As shown in Figure 3, the controller of present embodiment AC-DC converter comprises former limit sample circuit and digital compensator; As shown in Figure 5, former limit sample circuit comprises a waveform real-time analysis module, a single-input double-output digital to analog converter and two comparators;
The input of single-input double-output digital to analog converter is connected with the output of waveform real-time analysis module, and two outputs are connected with the inverting input of two comparators respectively; The feedback quantity V in a cycle on the AC-DC converter of its reception waveform real-time analysis module output
fB[i-1], to feedback quantity V
fBafter [i-1] digital-to-analogue conversion, obtain feedback voltage V 1 output, will after fixed voltage value of the amplitude lifting of feedback voltage V 1, obtain comparative voltage V2 output;
As shown in Figure 6, the single-input double-output digital to analog converter in present embodiment is by two MUX Mux1 and Mux2, and a string divider resistance R
1～R
511composition, R
1～R
511it is all substitutional resistance.Reference voltage V
refinput by the voltage after divider resistance dividing potential drop as MUX.There is an initial side-play amount in MUX Mux1 and Mux2 coding, by this digital to analog converter of this side-play amount by same input variable V
fBconvert two analog voltage V with fixed voltage difference to
1and V
2.In present embodiment, the figure place of digital-to-analogue conversion is 9, reference voltage V
reffor 1.2V; V
2and V
1with V
fBpass be:
Visible V
1voltage is the feedback voltage of simulation.
The normal phase input end of two comparator C OMP1～COMP2 all receives the auxiliary winding voltage signal V of AC-DC converter
sense; It is respectively by feedback voltage V 1 and comparative voltage V2 and auxiliary winding voltage signal V
sensecompare, obtain respectively two comparison signal V
s1and V
s2.
Two inputs of waveform real-time analysis module are connected with the output of comparator C OMP1～COMP2 respectively; It is for calculating two comparison signal V
s1and V
s2trailing edge time difference Δ t, and by trailing edge time difference Δ t and fiducial time poor Δ t
refcompare, determine regulated quantity Δ V according to both differences
fB, and then utilize regulated quantity Δ V by feedback compensation algorithm
fBto feedback quantity V
fB[i-1] regulates compensation, in the hope of the feedback quantity V of AC-DC converter current period
fB[i].
As shown in Figure 7, after PWM is zero level, V
sensebecome high voltage from negative voltage, V
s1and V
s2be turned to high level, afterwards along with V
sensedecline gradually, due to V2 voltage ratio, V1 is high, V
s2can be at t
1moment is first turned to low level, through V after the Δ t time
s1at t
2moment is turned to low level.The moment T that knee voltage occurs
kneefront and back, V
sensevariation slope differ greatly, therefore V
1and V
2be in V
senseon the Δ t difference that produces of diverse location very large.As shown in Fig. 7 (b), if V
fBbigger than normal, represent that the feedback voltage sampling is higher than knee voltage, V
2and V
1also can phase strain large, due to T
kneev before moment
sensedescending slope less, the Δ t now detecting is bigger than normal.As shown in Fig. 7 (c), if V
fBless than normal, the Δ t now detecting is very little.As shown in Fig. 7 (a), choose suitable Δ t
refwith Δ V, make to equal Δ t as Δ t
reftime, V
fBjust to have reacted needed knee voltage.
As shown in Figure 8, first waveform real-time analysis module detects and stores the Δ t time, then by itself and Δ t
refcompare, to the feedback quantity V in next cycle
fBadjust, wherein the V that obtains of i cycle
fBvalue is designated as V
fB[i].In order to accelerate V
fBfoundation, on the basic principle basis shown in Fig. 8 to V
fBadjusted value improve, V between the cycle of front and back
fBpass be V
fB[i+1]=V
fB[i] ± Δ V
eB, Δ t and default Δ t
refdiffer larger, regulated quantity Δ V
fBalso larger, concrete corresponding relation is because of different parameter setting differences.
The input of digital compensator is connected with the output of waveform real-time analysis module; It is for according to the feedback quantity V of the AC-DC converter current period of waveform real-time analysis module output
fB[i] regulates duty ratio d, and provide zero limit to realize the stability of system loop, comparing analog compensation does not need extra resistance capacitance to compensate, reduce the expense of the outer device of sheet, construct pwm signal according to duty ratio D simultaneously, to control the break-make of switching tube Q in AC-DC converter, realize the modulation to AC-DC converter output voltage.
In present embodiment, waveform real-time analysis module and digital compensator are all by the FPGA realization of programming.
Present embodiment, by gathering the auxiliary winding voltage signal of AC-DC converter, adopts the former limit of high accuracy Sampling techniques, and automatic tracing knee voltage, to obtain accurate feedback quantity; Calculate duty ratio according to feedback quantity, and output pwm signal corresponding to duty ratio is with the break-make of switching tube in control change device, finally realizes the modulation to converter output voltage, realizes voltage stabilizing output.
Present embodiment realizes at diode forward pressure drop V by the former limit of high accuracy Sampling techniques
dthe moment of being almost equal to zero is to V
sensesample.Get under fixed condition in peripheral parameter, calculating desirable feedback voltage is 883mV, the feedback voltage V obtaining by this implementation method
1for 890mV, feedback error is 7mV, and adopts general traditional sampling control method cannot eliminate diode current flow pressure drop V
dimpact, the feedback voltage 1V nearly that obtains of sampling, feedback error is 117mv nearly.Therefore by comparing with traditional sampling control technology, present embodiment feedback error has reduced 94%.
Claims (4)
1. a control method for AC-DC converter, comprises the steps:
(1) the auxiliary winding voltage signal V of collection AC-DC converter
sense, and obtain the feedback quantity V in a cycle on AC-DC converter
fB[i-1];
(2) to described feedback quantity V
fBafter [i-1] digital-to-analogue conversion, obtain feedback voltage V 1, and will after fixed voltage value of the amplitude lifting of feedback voltage V 1, obtain comparative voltage V2;
(3) by described auxiliary winding voltage signal V
sensecompare with feedback voltage V 1 and comparative voltage V2 respectively, obtain respectively two comparison signal V
s1and V
s2;
(4) calculate two comparison signal V
s1and V
s2trailing edge time difference Δ t, and by trailing edge time difference Δ t and fiducial time poor Δ t
refcompare, determine regulated quantity Δ V according to both differences
fB, and then utilize regulated quantity Δ V by feedback compensation algorithm
fBto feedback quantity V
fB[i-1] regulates compensation, in the hope of the feedback quantity V of AC-DC converter current period
fB[i];
Described feedback compensation algorithm is based on following formula:
As Δ t > Δ t
reftime: V
fB[i]=V
fB[i-1]-Δ V
fB;
As Δ t=Δ t
reftime: V
fB[i]=V
fB[i-1];
As Δ t < Δ t
reftime: V
fB[i]=V
fB[i-1]+Δ V
fB;
(5) according to described feedback quantity V
fB[i] constructs pwm signal, to control the break-make of switching tube in AC-DC converter.
2. a controller for AC-DC converter, comprises former limit sample circuit and digital compensator; Described digital compensator is used for according to the feedback quantity V of the AC-DC converter current period of former limit sample circuit output
fB[i] constructs pwm signal, to control the break-make of switching tube in AC-DC converter; It is characterized in that:
Described former limit sample circuit comprises a waveform real-time analysis module, a single-input double-output digital to analog converter and two comparators;
The feedback quantity V in a cycle on the AC-DC converter of described single-input double-output digital to analog converter reception waveform real-time analysis module output
fB[i-1], to feedback quantity V
fBafter [i-1] digital-to-analogue conversion, obtain feedback voltage V 1 output, will after fixed voltage value of the amplitude lifting of feedback voltage V 1, obtain comparative voltage V2 output;
Two comparators are respectively by the auxiliary winding voltage signal V of feedback voltage V 1 and comparative voltage V2 and AC-DC converter
sensecompare, obtain respectively two comparison signal V
s1and V
s2;
Described waveform real-time analysis module is used for calculating two comparison signal V
s1and V
s2trailing edge time difference Δ t, and by trailing edge time difference Δ t and fiducial time poor Δ t
refcompare, determine regulated quantity Δ V according to both differences
fB, and then utilize regulated quantity Δ V by feedback compensation algorithm
fBto feedback quantity V
fB[i-1] regulates compensation, in the hope of the feedback quantity V of AC-DC converter current period
fB[i];
Described feedback compensation algorithm is based on following formula:
As Δ t > Δ t
reftime: V
fB[i]=V
fB[i-1]-Δ V
fB;
As Δ t=Δ t
reftime: V
fB[i]=V
fB[i-1];
As Δ t < Δ t
reftime: V
fB[i]=V
fB[i-1]+Δ V
fB.
3. the controller of AC-DC converter according to claim 2, is characterized in that: described single-input double-output digital to analog converter is built by two MUX and a string divider resistance.
4. the controller of AC-DC converter according to claim 2, is characterized in that: described waveform real-time analysis module and digital compensator are all by the FPGA realization of programming.
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| CN103401442B (en) * | 2013-07-30 | 2015-09-02 | 浙江大学 | A kind of digitial controller of the AC-DC isolated converter based on output constant current |
| CN104092384A (en) * | 2014-07-29 | 2014-10-08 | 东南大学 | Output voltage sampling method and system for flyback converter based on primary feedback |
| CN105449807B (en) * | 2014-09-28 | 2018-04-20 | 比亚迪股份有限公司 | Charging system and its secondary control device based on secondary control |
| CN104578850B (en) * | 2015-01-15 | 2017-10-31 | 东南大学 | A kind of constant pressure control method and its circuit of AC DC converter output voltages |
| JP6670852B2 (en) | 2016-02-05 | 2020-03-25 | オッポ広東移動通信有限公司Ｇｕａｎｇｄｏｎｇ Ｏｐｐｏ Ｍｏｂｉｌｅ Ｔｅｌｅｃｏｍｍｕｎｉｃａｔｉｏｎｓ Ｃｏｒｐ．， Ｌｔｄ． | Adapter and charge control method |
| KR102593457B1 (en) * | 2016-10-25 | 2023-10-25 | 엘지디스플레이 주식회사 | Display Device and Method for Driving the same |
| CN111864886B (en) * | 2020-07-14 | 2024-05-24 | 北京诺信泰伺服科技有限公司 | Power supply and floodgate machine equipment |
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| CN102427300A (en) * | 2011-10-10 | 2012-04-25 | 浙江大学 | Control method and controller for output voltage of AC-DC (alternating current-direct current) converter |
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| US8179699B2 (en) * | 2008-12-31 | 2012-05-15 | Stmicroelectronics S.R.L. | Method for controlling a switching regulator and related switching regulator |
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| CN101795077A (en) * | 2010-04-12 | 2010-08-04 | Bcd半导体制造有限公司 | A kind of device of control change device output current voltage response |
| CN102427300A (en) * | 2011-10-10 | 2012-04-25 | 浙江大学 | Control method and controller for output voltage of AC-DC (alternating current-direct current) converter |
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