CN102445699A - System structure for double-channel navigating radio-frequency receiver sharing radio-frequency front end - Google Patents
System structure for double-channel navigating radio-frequency receiver sharing radio-frequency front end Download PDFInfo
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Abstract
The invention relates to a system structure for a double-channel navigating radio-frequency receiver sharing a radio-frequency front end. Two GNSS (Global Navigation Satellite System) radio-frequency signals can be simultaneously received by double channels, thereby enhancing the positioning precision. After being subjected to the down-conversion for the first time, the first channel is processed by an intermediate-frequency filter, thereby obtaining an intermediate-frequency signal corresponding to one of the radio-frequency signals. After being subjected to the down-conversion for the first time, the second channel is subjected to the down-conversion treatment for the second time performed by a Weaver structural mirror image restraining low/intermediate-frequency system structure, thereby obtaining an intermediate-frequency signal corresponding to the other radio-frequency signal. A radio-frequency front end module till the down-conversion treatment for the first time is shared by the two signal channels, a same frequency synthesizer phase-locked ring is used for correspondingly supplying a local vibration signal to the down-conversion treatments for the first time and second time respectively, and a same sampling clock module is used for correspondingly supplying same or different sampling clock frequencies to the double channels, thereby simplifying the system design, effectively reducing the power consumption and saving the cost.
Description
Technical field
The present invention relates to a kind of radio frequency chip of field of wireless communication, particularly a kind of binary channels of shared radio-frequency front-end navigation radio-frequency transmitter system architecture.
Background technology
The worldwide navigation Positioning System (GPS) has been widely used in vehicle mounted guidance, vehicle tracking, time synchronized, measurement mapping, ship or vehicle monitoring, geodata collection, space industry or the like.Up to the present, navigation positioning system maximum and maximum users are vehicle-mounted and hand-held navigation.At hand-held navigating instrument (PND; Portable Navigation Device) or similarly in using, because whole navigating instrument is through powered battery, so to this application; The chip power-consumption of navigational system has special meaning: power consumption is low more, and the time of use is just long more.On market, as the SiRF company of the U.S., all there has been very ripe navigation radio frequency chip in the MAXIM company of the Canadian SiGe company and the U.S. at present, and its product is most to be designed and make with SiGe technology, to reach low-power consumption, high performance purpose.
As shown in Figure 1; These products all are to adopt in the system architecture of traditional Low Medium Frequency navigation radio-frequency transmitter; 1575.42MHz navigation GPS rf modulated signal; Be received through the antenna (not shown) in the signalling channel of radio frequency, the low noise amplifier 10 (LNA) through front end amplifies.In order to filter out contiguous mobile phone or other communication undesired signal, need output to outside the chip through the radio frequency rf signal that amplifies, carry out Filtering Processing by the outer acoustic filter 20 (SAW FILTER) of sheet; After taking back further amplification of radio frequency prime amplifier 30 (RFA) work in the sheet again, (MixerI MixerQ) carries out the frequency down-converts of radio frequency to medium-frequency IF to output to quadrature down converter 40 and 50.For the ease of explanation, we are with cell frequency f
0=1.023MHz calculates radio frequency (1540f
0) and IF-FRE.In the navigation radio frequency chip, the IF-FRE of main flow is 4f
0Intermediate-frequency filter 60 (IF Filter) carries out channel to intermediate-freuqncy signal to be selected, and filtering out need be by the intermediate-freuqncy signal of demodulation in bandwidth, and outer any signal or the noise of bandwidth can be filtered fully.The bandwidth of navigation GPS is 2f
0, the bandwidth ratio 2f of general intermediate-frequency filter
0High slightly.This intermediate-freuqncy signal is after variable gain amplifier 70 (VGA) amplifies; The signal intensity that appropriateness is provided is to analog to digital converter 80 (ADC); Thereby convert analog intermediate frequency signal to comprise polarity S IGN and amplitude MAG two digits signal, these digital signals are exported to the digital baseband (not shown) and are done follow-up signal Processing at last.In Low Medium Frequency navigation radio-frequency transmitter system architecture; Because radio frequency chip needs independently to become a single-chip; So the amplitude MAG signal of analog to digital converter 80 outputs also feeds back to variable gain amplifier 70 through variable gain amplifier control circuit 90 (VGA Controller); As the detection of its signal intensity, so that this variable gain amplifier 70 can provide constant signal output for analog to digital converter 80.
Wherein, carry out the quadrature down converter 40 and 50 of radio frequency to medium-frequency IF down coversion, its local oscillator is provided by frequency synthesizer.No matter be integral frequency divisioil frequency synthesizer (Integer-N RFPLL) or fractional frequency division frequency synthesizer (Fractional-N RFPLL), frequency synthesizer phaselocked loop (RFPLL) generally comprises the backfeed loop that is connected to form by phase frequency detector 120 (PFD), charge pump 130 (CP), loop filter 140 (LPF), voltage controlled oscillator 150 (VCO), a set of division module.Wherein, phase frequency detector 120, (the navigation radio frequency chip is generally used 16f with feedback signal and canonical reference clock
0) compare; By the control of this comparative result, 130 pairs of loop filters of said charge pump 140 carry out charge or discharge, make the DC voltage after loop filter 140 output filterings, and the frequency of voltage controlled oscillator 150 is controlled.The local oscillation signal that voltage controlled oscillator 150 produces, after the frequency division processing via two-divider 160 (DIV2), pre-divider 170 (Prescaler), feedback divider 180 (Feedback Divider), feedback outputs to phase frequency detector 120; When the standard frequency of frequency of feeding back and reference equates; Phase frequency detector 120 these frequency synthesizer pll locks of control, the local frequency that this moment, voltage controlled oscillator 150 was exported are exactly N times (multiple N cooperates decision by said some frequency division modules 160,170,180) of reference clock.Because the system architecture of navigation radio frequency chip main flow is all selected the pressuring controlling oscillator frequency of two frequencys multiplication, i.e. 2 * 1536f
0, so the output of voltage controlled oscillator 150 exports said quadrature down converter 40 and 50 respectively to via two-divider 160 frequency divisions acquisition orthogonal local oscillation LOI and LOQ.
In general; In order to satisfy the high-precision requirement of navigation radio frequency chip to frequency; Crystal oscillator (TCXO by the outer temperature compensation of sheet; Do not draw) clock signal (TCXO_IN) that provides, after the shaping through clock isolation amplifier 100 (CLK BUF), be input into frequency synthesizer phaselocked loop (RFPLL) as the canonical reference clock.Meanwhile, this clock of clock isolation amplifier 100 outputs also offers analog to digital converter 80 as its sampling clock.This sampling clock finally also passes through the shaping of another one clock isolation amplifier 110 (CLK BUF), outputs to the outer navigation baseband chip of sheet and does the synchronous of data sampling.
Four Global Navigation System Global Navigation Satellite System (GNSS) are arranged at present in the world: the firstth, the GPS of USA navigational system; Its rf frequency is 1575.42MHz; Bandwidth is 2.046MHz, is containing the C/A sign indicating number of time and positional information in the bandwidth.The secondth, the GLONASS navigational system of Russia, its rf frequency is 1598.0625MHz to 1605.375MHz, bandwidth is 8MHz, is divided into 14 channels; Channel and channel be 0.5625MHz at interval, the bandwidth of each channel is 0.5625MHz; The 3rd is the Chinese Big Dipper COMPASS navigational system in two generations, and its rf frequency is 1561.098MHz, and bandwidth is 4.092MHz.The 4th is Galileo (Galileo) navigational system of European Union, and its rf frequency is 1575.42MHz, and bandwidth is 4.092MHz.
Use at present the most extensively, the navigational system of main flow is exactly the GPS of USA navigational system.By in February, 2011, there have been 22 GLONASS of the Russia Navsats that can run the sky.The COMPASS navigational system in two generations of the Big Dipper of China is more and more ripe, and there have been 9 Navsats the sky at present.The Big Dipper two generations expectation can cover the Asian-Pacific area and get into substantive operation in 2012.The Galileo of European Union (Galileo) navigational system speed of development is the most slowly.
Yet, no matter be government of Russia now, Chinese Government or European Union, it is unpractical that requirement and encourage consumer only use the navigational system of oneself.The first, number of satellite is insufficient, and the Glonass Navsat that just is Russia also is less than 24; The second, the ripe operation of Global Navigation System separately (GNSS) also needs more time.Referring to table 1; Therefore, if a twin-channel navigation radio-frequency transmitter is arranged, can receive the Glonass Navsat of GPS of America Navsat and Russia simultaneously on market; Or the while can receive the Big Dipper Compass Navsat of GPS of America Navsat and China; Or can receive simultaneously Galileo (Galileo) Navsat of GPS of America Navsat and European Union, it is comprehensively located will be more accurate, will have very high using value.
Table 1 is twin-channel maybe practical combination
But the often just simple correlation technique with single passage of present binary channels GNSS radio-frequency transmitter technology copies to two passages fully, is difficult to satisfy the requirement of radio-frequency transmitter low cost, low-power consumption.
Summary of the invention
The binary channels navigation radio-frequency transmitter system architecture that the purpose of this invention is to provide a kind of shared radio-frequency front-end; Can receive two-way GNSS radio frequency navigation signal simultaneously precisely locatees; For example be GPS of America and Chinese Big Dipper Compass navigation satellite signal, perhaps GPS of America and the Glonass of Russia navigation satellite signal.Simultaneously, through sharing the correlation module of radio-frequency front-end, obtain the low power consumption and low cost effect the same with the single channel scheme.
Technical scheme of the present invention provides a kind of binary channels navigation radio-frequency transmitter system architecture of shared radio-frequency front-end, and it is provided with first, second passage and comes the corresponding two-way radiofrequency signal that receives;
Said first, second passage is shared RF front-end circuit, said RF front-end circuit comprises: the low noise amplifier that connects successively, the outer acoustic filter of sheet, radio frequency prime amplifier, and quadrature down converter; The said two-way radiofrequency signal that said RF front-end circuit receives simultaneously, carry out the down-converted first time by said quadrature down converter after, the subsequent conditioning circuit of output intermediate-freuqncy signal to first, second passage;
In the said first passage; Also be included in the intermediate-frequency filter that is provided with after the said quadrature down converter; It is handled down coversion first time intermediate-freuqncy signal afterwards, obtains corresponding first intermediate-freuqncy signal of radiofrequency signal and the first intermediate frequency switching signal that receive with this passage;
In the said second channel, the mirror image that also is provided with the Weaver structure suppresses the Low Medium Frequency framework, promptly is included in after the said quadrature down converter intermediate-frequency filter that sets gradually, low-converter and totalizer for the second time; By this intermediate-frequency filter down coversion first time intermediate-freuqncy signal is afterwards handled; Obtain corresponding second intermediate-freuqncy signal of radiofrequency signal with this passage reception; Again by said second time low-converter and totalizer carry out the down-converted second time, obtain the corresponding second intermediate frequency switching signal.
Local frequency when said quadrature down converter carries out down coversion for the first time; And the local frequency when for the second time low-converter carries out down coversion for the second time in the said second channel, by same frequency synthesizer phaselocked loop corresponding providing behind the divide ratio is set respectively.
In the said frequency synthesizer phaselocked loop; Further comprise: the backfeed loop that phase frequency detector, charge pump, loop filter, voltage controlled oscillator, two-divider, pre-divider, feedback divider constitute, this backfeed loop is that said first, second passage is shared.
The required local frequency of down-converted is to be undertaken obtaining behind the two divided-frequency by the output result of the two-divider in the said backfeed loop to said voltage controlled oscillator for the first time;
In the said frequency synthesizer phaselocked loop, corresponding with second channel, also be provided with parameter frequency divider and another two-divider, come the output result of two-divider in the said backfeed loop is carried out the frequency division processing, obtain the required local frequency of down-converted for the second time.
In said first, second passage, also be provided with separately:
Variable gain amplifier corresponds to first, second intermediate frequency switching signal and carries out processing and amplifying;
Analog to digital converter, first, second intermediate frequency switching signal after correspondence will be amplified converts the two digits signal that comprises polarity and amplitude to by analog quantity, and the baseband processing chip outside sheet sends;
The variable gain amplifier control circuit, the range signal after will changing respectively feeds back to corresponding variable gain amplifier.
Said first, second passage is also shared to have a clock isolation amplifier, after its reference clock to the outside input carries out shaping, is sent to said frequency synthesizer phaselocked loop;
Sampling clock module that said first, second passage is also shared, it sends the analog to digital converter that corresponding sampling clock frequency is given first, second passage;
Go back each self-contained another clock isolation amplifier in said first, second passage, said sampling clock frequency outputs to the outer navigation baseband chip of sheet and does the synchronous of data sampling through after this clock isolation amplifier shaping.
Said sampling clock module is exported alap sampling clock frequency, but said sampling clock frequency must be greater than 2 times of intermediate-freuqncy signal frequency maximum separately in two passages.
Said sampling clock module is sent identical sampling clock frequency to the analog to digital converter of said first, second passage; The reference clock of said sampling clock module after with shaping directly export or carry out frequency division handle after output, as said sampling clock frequency.
Said sampling clock module is sent different sampling clock frequencies to the analog to digital converter of said first, second passage;
The reference clock of said clock isolation amplifier after with shaping directly export or carry out frequency division handle after output, as one of them sampling clock frequency;
Said sampling clock module to the output of said frequency synthesizer phaselocked loop the first time down coversion local frequency, carry out frequency division and handle back output, as another sampling clock frequency.
Compared with prior art; The binary channels navigation radio-frequency transmitter system architecture of shared radio-frequency front-end according to the invention; Its advantage is: parameters such as the bandwidth that reference clock, local frequency, sampling clock, the channel of the present invention through controlling first passage and second channel respectively selected, intermediate-freuqncy signal, and make first passage carry out down coversion first time, second channel carries out for the first time, after the second time down-converted; Can correspondingly receive two-way GNSS radio frequency navigation signal; For example be the Big Dipper Compass navigation satellite signal that receives GPS of America and China, the perhaps Glonass navigation satellite signal of GPS of America and Russia, thereby the accuracy of raising navigator fix.Simultaneously, owing to shared RF front-end module and frequency synthesizer phaselocked loop etc., this binary channels navigation radio-frequency transmitter system architecture can be saved power consumption, reduces cost, and has good application value.
Description of drawings
Fig. 1 is the system architecture synoptic diagram of existing single pass navigation radio-frequency transmitter;
Fig. 2 is the synoptic diagram of binary channels navigation radio-frequency transmitter system architecture in embodiment 1 of shared radio-frequency front-end according to the invention;
Fig. 3 is the synoptic diagram of binary channels navigation radio-frequency transmitter system architecture in embodiment 2 of shared radio-frequency front-end according to the invention.
Embodiment
Below in conjunction with description of drawings a plurality of embodiments of the present invention.
As shown in Figure 2, in the binary channels navigation radio-frequency transmitter system architecture of shared radio-frequency front-end according to the invention, be provided with first, second passage and come the corresponding two-way GNSS radiofrequency signal that receives.
Said first, second passage is shared RF front-end circuit (zone among Fig. 2 shown in the frame of broken lines); Comprise: the low noise amplifier 1 (LNA) that connects successively, the outer acoustic filter 2 (SAW FILTER) of sheet, radio frequency prime amplifier 3 (RFA) and quadrature down converter 4 and 5 (MixerI; MixerQ), basically identical in the circuit framework of those devices and signal processing and the existing single channel radio-frequency transmitter.
The framework of said first passage and single channel framework basically identical; Promptly; After said quadrature down converter 4 and 5; Set gradually intermediate-frequency filter 61, variable gain amplifier 71 (VGA), analog to digital converter 81 (ADC), and feedback is connected to the variable gain amplifier control circuit 91 (VGA Controller) of variable gain amplifier 71.
And in the said second channel, after described quadrature down converter 4 and 5, be provided with intermediate-frequency filter 62, for the second time low-converter 72,82 and totalizer 92, suppress the Low Medium Frequency framework with the mirror image that forms the Weaver structure; Be provided with variable gain amplifier 102, analog to digital converter 112 again, and feedback is connected to the variable gain amplifier control circuit 122 of variable gain amplifier 102.
Said quadrature down converter 4 and 5 carries out for the first time local frequency LOI, the LOQ of down coversion, and the low-converter 72,82 second time in the said second channel, carries out the local frequency LOI of down coversion for the second time
2, LOQ
2, by same frequency synthesizer phaselocked loop (RFPLL) divide ratio is set respectively and obtains.
More specifically set forth; The backfeed loop that the phase frequency detector 12 (PFD) of said frequency synthesizer phaselocked loop, charge pump 13 (CP), loop filter 14 (LPF), voltage controlled oscillator 15 (VCO), two-divider 16 (DIV2), pre-divider 17 (Prescaler), feedback divider 18 (Feedback Divider) constitute is that said first, second passage is shared, basically identical in the circuit framework of those modules and signal processing and the existing single channel radio-frequency transmitter.
Said local frequency LOI, LOQ are via behind 16 pairs of voltage controlled oscillator 15 two divided-frequencies of two-divider, export said quadrature down converter 4 and 5 to.For second channel,, carry out exporting local frequency LOI behind time frequency division of N2 * 2 through parameter frequency divider 19 (establishing its divide ratio is N2) and another two-divider 22 that sets gradually again according to the output result of two-divider 16 in the above-mentioned backfeed loop
2, LOQ
2Give described second time low-converter 72,82.
In addition, the analog to digital converter 81 of first, second passage and 112 sampling clock are provided by same sampling clock module 11 (ADC CLK GEN).After the shaping of reference clock (TCXO_IN) through clock isolation amplifier 10, be input to said sampling clock module 11.Sampling clock module 11 is through after carrying out the several times frequency division to reference clock frequency or its, provides best sampling clock frequency to analog to digital converter 81 and 112.After this sampling clock frequency is also passed through clock isolation amplifier 131 or 132 shapings in addition, output to the outer navigation baseband chip of sheet and do the synchronous of data sampling.
Embodiment 1
Based on the binary channels navigation radio-frequency transmitter system architecture of shared radio-frequency front-end shown in Figure 2, the said two-way GNSS radiofrequency signal that receives in the present embodiment is respectively the Big Dipper Compass navigation satellite signal of GPS of America and China.Wherein first passage is the GPS passage, and the first radiofrequency signal RF1 of its reception is the signal of GPS of America; Second channel is a Big Dipper passage, and the second radiofrequency signal RF2 of its reception is the signal of Chinese Big Dipper COMPASS.
At first, through the antenna (not shown), (LNA_IN) is received in the signalling channel through same rf input port simultaneously for the first radiofrequency signal RF1 and the second radiofrequency signal RF2.From rf input port (LNA_IN) until quadrature down converter 4 and 5, the basically identical of its circuit framework and signal Processing and existing single channel radio-frequency transmitter.Described quadrature down converter 4 and 5 local frequency LOI and the value of LOQ are 1571.328MHz, and it carries out the same intermediate-freuqncy signal exported after the down-converted for the first time, is sent to first and second passages simultaneously; Comprised frequency in this intermediate-freuqncy signal and be the first intermediate-freuqncy signal IF1 and the second intermediate-freuqncy signal IF2 of the Chinese Big Dipper that frequency is 10.23MHz of the GPS of America of 4.092MHz.
For first passage (GPS passage); Export intermediate-freuqncy signal after the down-converted for the first time; Carrying out channel through intermediate-frequency filter 61 selects; Filtering out in bandwidth BW 1 (bandwidth BW 1 of navigation GPS is 2MHz) frequency is the first intermediate-freuqncy signal IF1 of 4.092MHz, and bandwidth outer any signal or noise can be filtered fully.This intermediate-freuqncy signal does not need for the second time down-converted promptly as need be by the GPS intermediate-freuqncy signal CH1_IF=4.092MHz of demodulation, and is as shown in table 2.
Processing after the said intermediate-freuqncy signal CH1_IF; With basically identical in the single channel; Successively after variable gain amplifier 71 amplifies; Provide the appropriateness signal intensity to analog to digital converter 81, thereby convert analog intermediate frequency signal to digital signal, these digital signals are just done signal Processing at digital baseband at last.The range signal MAG1 output of analog to digital converter 81 as the detection of variable gain amplifier 71 signal intensities, and through variable gain amplifier control circuit 91, feeds back to variable gain amplifier 71 and controls the constant VGA output to analog to digital converter 81.
For second channel (Big Dipper passage); Export intermediate-freuqncy signal after the down-converted for the first time; Carrying out channel through intermediate-frequency filter 62 selects; Filter out that (bandwidth BW 2 of the Big Dipper is 4MHz) frequency is the second intermediate-freuqncy signal IF2 of 10.23MHz in bandwidth BW 2, bandwidth outer any signal (intermediate-freuqncy signal that comprises the 4.092MHz of GPS) or noise are all filtered fully.
The intermediate-freuqncy signal of the frequency 10.23MHz that obtains after the filtering is carried out the down-converted second time through the mirror image inhibition Low Medium Frequency system architecture of Weaver structure again.Input for the second time low-converter 72,82 the second time down coversion local frequency LOI
2, LOQ
2, also by described same frequency synthesizer RFPLL through producing behind 110 frequency divisions and providing.That is to say,, behind parameter frequency divider 19 (setting its divide ratio N2 is 55) and another two-divider 22, produce the local frequency LOI of down coversion for the second time local oscillation signal LOI and the LOQ of 1571.328MHz
2, LOQ
2Be 14.2848MHz.Carry out mirror image through totalizer 92 again and suppress, needing to obtain the Big Dipper intermediate-freuqncy signal CH2_IF=4.05MHz of demodulation and export variable gain amplifier 102 to, its intermediate frequency and bandwidth are as shown in table 2.Similar in signal Processing after this Big Dipper intermediate-freuqncy signal CH2_IF and the first passage repeated no more here.
Described sampling clock module 11 (ADC CLK GEN) is handled the reference clock after the shaping (TCXO_IN), obtains the analog to digital converter 81 and 112 that sampling clock is also exported to first passage, second channel simultaneously.Need to prove that the design of said sampling clock module 11 must consider to make the clock signal frequency of navigation base band low more good more, but the sampling clock frequency must be greater than each passage 2 times of maximum intermediate frequency separately.In table 2, listed according to different reference clock schemes, when the reception GPS that provides and the double-channel signal of big-dipper satellite, its intermediate frequency, bandwidth, ADC timing parameter separately.Wherein 16.368MHz is a reference clock commonly used at present, and 26MHz is used for the reference clock of mobile phone or WiFi more.
The twin-channel reference clock of table 2 GPS and the Big Dipper, intermediate frequency, bandwidth and ADC clock
Embodiment 2
As shown in Figure 3, the framework that uses among binary channels navigation radio-frequency transmitter and the embodiment 1 in the present embodiment is similar, and correspondence adds double quotation marks and distinguishes among Fig. 3 on each frequency label of Fig. 2.The said two-way GNSS radiofrequency signal that receives in the present embodiment is respectively the Glonass navigation satellite signal of GPS of America and Russia.Wherein first passage is the GPS passage, the first radiofrequency signal RF1 of its reception " be the signal of GPS of America; Second channel is the Glonass passage, the second radiofrequency signal RF2 of its reception " be the navigation signal of the Glonass of Russia.
First passage in this binary channels navigation radio-frequency transmitter, second channel are shared RF front-end circuit module and frequency synthesizer phaselocked loop (RFPLL); Wherein, quadrature down converter 4 and 5 carries out the down-converted second time through the mirror image inhibition Low Medium Frequency system architecture of Weaver structure also for first passage and second channel carry out the down coversion first time in the second channel again.
Different is, in the present embodiment by this frequency synthesizer phaselocked loop (RFPLL), quadrature down converter 4 that provides and 5 local frequency LOI " and LOQ " be 1579.5MHz.Thereby, in the first passage (GPS passage), for the first time carry out channel by intermediate-frequency filter 61 after the down coversion and select, filter out bandwidth BW 1 at 2MHz " in, directly obtaining need be by the GPS intermediate-freuqncy signal CH1_IF of demodulation " be 4.08MHz.
And in the second channel (Glonass passage); Carrying out channel by intermediate-frequency filter 62 after the down coversion for the first time selects; Filter out bandwidth BW 2 at 8.4MHz " in; frequency is the second intermediate-freuqncy signal IF2 of 22.395MHz ", bandwidth outer any signal (intermediate-freuqncy signal that comprises the 4.08MHz of GPS) or noise are all filtered fully.
The intermediate-freuqncy signal that obtains frequency 22.395MHz after the filtering is carried out the down-converted second time through the mirror image inhibition Low Medium Frequency system architecture of Weaver structure again.In the present embodiment, input for the second time low-converter 72,82 the second time down coversion local frequency LOI
2", LOQ
2", by said frequency synthesizer RFPLL through producing behind 100 frequency divisions and providing.That is to say, with the local oscillation signal LOI of 1579.5MHz " and LOQ ", behind parameter frequency divider 19 (set its divide ratio N2 " be 50) and another two-divider 22, produce the local frequency LOI of down coversion for the second time
2", LOQ
2" be 15.795MHz.Carry out mirror image through totalizer 92 again and suppress, needing to obtain the Glonass intermediate-freuqncy signal CH2_IF of modulation " be 6.6MHz, and export this signal to variable gain amplifier 102.
Said GPS intermediate-freuqncy signal CH1_IF ", and said Glonass intermediate-freuqncy signal CH2_IF ", to handle to the follow-up signal that exports digital baseband to from the variable gain amplifier of passage separately, similar with among the embodiment 1 repeated no more here.
In addition, first passage, the shared sampling clock module 11 (ADC CLK GEN) of second channel in the present embodiment are to export the analog to digital converter 81 and 112 that different sampling clocks is given first passage, second channel respectively.The design of said sampling clock module 11 also must consider to make the clock signal frequency of navigation base band low more good more, but the sampling clock frequency must be greater than each passage 2 times of maximum intermediate frequency separately.
Consider that mobile phone and WiFi radio-frequency transmitter all are to use the reference clock of 26MHz, after its shaping, be input to the phase frequency detector 12 (PFD) of said sampling clock module 11 and said frequency synthesizer through clock isolation amplifier 10.The sampling clock of in the present embodiment analog to digital converter 81 of GPS passage being exported is 19.5MHz; This sampling clock is the local frequency 1579.5MHz with 16 outputs of the two-divider of said frequency synthesizer phaselocked loop, outputs to that said sampling clock module 11 carries out obtaining after the frequency division 81 times.And to the analog to digital converter 112 of Glonass passage, the sampling clock of output promptly is the reference clock of 26MHz.In table 3, listed when receiving the double-channel signal of GPS and Glonass satellite its intermediate frequency, bandwidth, ADC timing parameter separately.
The twin-channel reference clock of table 3 GPS and Glonass, intermediate frequency, bandwidth and ADC clock
In sum; The binary channels navigation radio-frequency transmitter system architecture of shared radio-frequency front-end according to the invention; Parameters such as the bandwidth that the reference clock through controlling first passage and second channel respectively, local frequency, sampling clock, channel are selected, intermediate-freuqncy signal make first passage carry out down coversion first time, and second channel carries out for the first time, after the second time down-converted; Can correspondingly receive two-way GNSS radio frequency navigation signal; For example be the Big Dipper Compass navigation satellite signal that receives GPS of America and China, the perhaps Glonass navigation satellite signal of GPS of America and Russia, thereby the accuracy of raising navigator fix.Simultaneously, owing to shared RF front-end module and frequency synthesizer phaselocked loop etc., this binary channels navigation radio-frequency transmitter system architecture can be saved power consumption, reduces cost, and has good application value.
Embodiments of the invention can also extend to twin-channel any possible practicality combination in the table 1 according to the basic design of embodiment 1 and embodiment 2.
Although content of the present invention has been done detailed introduction through above-mentioned preferred embodiment, will be appreciated that above-mentioned description should not be considered to limitation of the present invention.After those skilled in the art have read foregoing, for multiple modification of the present invention with to substitute all will be conspicuous.Therefore, protection scope of the present invention should be limited appended claim.
Claims (8)
1. the binary channels of shared radio-frequency front-end navigation radio-frequency transmitter system architecture is characterized in that, is provided with first, second passage and comes the corresponding two-way radiofrequency signal (RF1, RF2) that receives;
Said first, second passage is shared RF front-end circuit, said RF front-end circuit comprises: the low noise amplifier (1) that connects successively, the outer acoustic filter (2) of sheet, radio frequency prime amplifier (3), and quadrature down converter (4,5); The said two-way radiofrequency signal (RF1, RF2) that said RF front-end circuit receives simultaneously, carry out the down-converted first time by said quadrature down converter (4,5) after, export the subsequent conditioning circuit of the intermediate-freuqncy signal on same road to first, second passage;
In the said first passage; Also be included in the intermediate-frequency filter (61) that said quadrature down converter (4,5) is provided with afterwards; It is handled down coversion first time intermediate-freuqncy signal afterwards, obtains corresponding first intermediate-freuqncy signal of radiofrequency signal (RF1) (IF1) and the first intermediate frequency switching signal (CH1_IF) that receive with this passage;
In the said second channel, the mirror image that also is provided with the Weaver structure suppresses the Low Medium Frequency framework, promptly is included in said quadrature down converter (4,5) afterwards, the intermediate-frequency filter that sets gradually (62), low-converter (72,82) and totalizer (92) for the second time; By this intermediate-frequency filter (62) down coversion first time intermediate-freuqncy signal is afterwards handled; Obtain corresponding second intermediate-freuqncy signal of radiofrequency signal (RF2) (IF2) with this passage reception; Carry out the down-converted second time by the said low-converter second time (72,82) and totalizer (92) again, obtain the corresponding second intermediate frequency switching signal (CH2_IF).
2. the binary channels of shared radio-frequency front-end as claimed in claim 1 navigation radio-frequency transmitter system architecture is characterized in that,
Local frequency (LOI, LOQ) when said quadrature down converter (4,5) carries out down coversion for the first time, and the local frequency (LOI when low-converter (72,82) carries out down coversion for the second time for the second time in the said second channel
2, LOQ
2), by same frequency synthesizer phaselocked loop corresponding providing behind the divide ratio is set respectively; In the said frequency synthesizer phaselocked loop; Further comprise: the backfeed loop that phase frequency detector (12), charge pump (13), loop filter (14), voltage controlled oscillator (15), two-divider (16), pre-divider (17), feedback divider (18) constitute, this backfeed loop is that said first, second passage is shared.
3. the binary channels of shared radio-frequency front-end as claimed in claim 2 navigation radio-frequency transmitter system architecture is characterized in that,
The required local frequency (LOI, LOQ) of down-converted is to be undertaken obtaining behind the two divided-frequency by the output result of the two-divider in the said backfeed loop (16) to said voltage controlled oscillator (15) for the first time;
In the said frequency synthesizer phaselocked loop; Corresponding with second channel; Also be provided with parameter frequency divider (19) and another two-divider (21), come the output result of two-divider (16) in the said backfeed loop is carried out the frequency division processing, obtain the required local frequency (LOI of down-converted for the second time
2, LOQ
2).
4. the binary channels of shared radio-frequency front-end as claimed in claim 3 navigation radio-frequency transmitter system architecture is characterized in that,
In said first, second passage, also be provided with separately:
Variable gain amplifier (71,102) corresponds to first, second intermediate frequency switching signal (CH1_IF, CH2_IF) and carries out processing and amplifying;
Analog to digital converter (81,112), first, second intermediate frequency switching signal (CH1_IF, CH2_IF) after correspondence will be amplified converts the two digits signal that comprises polarity and amplitude to by analog quantity, and the baseband processing chip outside sheet sends;
Variable gain amplifier control circuit (91,122), the range signal (MAG1, MAG2) after will changing respectively feeds back to corresponding variable gain amplifier (71,102).
5. the binary channels of shared radio-frequency front-end as claimed in claim 4 navigation radio-frequency transmitter system architecture is characterized in that,
Said first, second passage is also shared to have a clock isolation amplifier (10), after its reference clock to the outside input carries out shaping, is sent to said frequency synthesizer phaselocked loop;
A sampling clock module (110) that said first, second passage is also shared, it sends the analog to digital converter (81,112) that corresponding sampling clock frequency is given first, second passage;
Go back each self-contained another clock isolation amplifier (131,132) in said first, second passage; After the shaping of said sampling clock frequency process said clock isolation amplifier (131,132), output to the outer navigation baseband chip of sheet and do the synchronous of data sampling.
6. the binary channels of shared radio-frequency front-end as claimed in claim 5 navigation radio-frequency transmitter system architecture is characterized in that,
The alap sampling clock frequency of said sampling clock module (110) output, but said sampling clock frequency must be greater than 2 times of intermediate-freuqncy signal frequency maximum separately in two passages.
7. the binary channels of shared radio-frequency front-end as claimed in claim 6 navigation radio-frequency transmitter system architecture is characterized in that,
Said sampling clock module (110) is sent identical sampling clock frequency to the analog to digital converter (81,112) of said first, second passage; Said sampling clock module (110) is directly exported the reference clock after the shaping or is carried out frequency division and handle output afterwards, as said sampling clock frequency.
8. the binary channels of shared radio-frequency front-end as claimed in claim 6 navigation radio-frequency transmitter system architecture is characterized in that,
Said sampling clock module (110) is sent different sampling clock frequencies to the analog to digital converter (81,112) of said first, second passage;
Said clock isolation amplifier (10) is directly exported the reference clock after the shaping or is carried out frequency division and handle output afterwards, as one of them sampling clock frequency;
Said sampling clock module (110) to the output of said frequency synthesizer phaselocked loop the first time down coversion local frequency (LOI, LOQ), carry out frequency division and handle back output, as another sampling clock frequency.
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Cited By (12)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN102928856A (en) * | 2012-10-19 | 2013-02-13 | 西安欣创电子技术有限公司 | Global positioning system (GPS) and Beidou double-module navigation radio frequency receiving system |
| CN103048666A (en) * | 2012-12-07 | 2013-04-17 | 广州润芯信息技术有限公司 | Beidou satellite and GPS (global positioning system) double-passage radio frequency receiving machine |
| CN103308932A (en) * | 2013-05-28 | 2013-09-18 | 中国电子科技集团公司第三十八研究所 | Monolithic multimode navigation chip based on broadband radio frequency direct technology |
| CN103762996A (en) * | 2014-01-04 | 2014-04-30 | 南昌大学 | VHF-UHF software radio receiving system |
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Citations (7)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN1285980A (en) * | 1998-11-11 | 2001-02-28 | 三星电子株式会社 | Receiver for pseudo-noise signals from satellite radio-navigation systems |
| CN1714509A (en) * | 2002-11-22 | 2005-12-28 | 日本电气株式会社 | PLL circuit |
| CN101123436A (en) * | 2006-07-14 | 2008-02-13 | 美国凹凸微系有限公司 | Analog to digital converter with interference rejection capability |
| CN101241179A (en) * | 2007-01-19 | 2008-08-13 | 恩益禧电子股份有限公司 | Multi-band RF receiver |
| CN101281245A (en) * | 2008-05-27 | 2008-10-08 | 北京大学 | Method and apparatus for receiving army and civil dual-purpose global satellite navigation system multi-module radio frequency |
| CN101907698A (en) * | 2009-06-03 | 2010-12-08 | 晨星软件研发(深圳)有限公司 | Signal process device of multiple satellite positioning system and method thereof |
| CN202305808U (en) * | 2011-10-18 | 2012-07-04 | 上海迦美信芯通讯技术有限公司 | Dual-channel navigation RF (radio-frequency) receiver system architecture on front end of shared RF |
-
2011
- 2011-10-18 CN CN2011103156662A patent/CN102445699A/en active Pending
Patent Citations (7)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN1285980A (en) * | 1998-11-11 | 2001-02-28 | 三星电子株式会社 | Receiver for pseudo-noise signals from satellite radio-navigation systems |
| CN1714509A (en) * | 2002-11-22 | 2005-12-28 | 日本电气株式会社 | PLL circuit |
| CN101123436A (en) * | 2006-07-14 | 2008-02-13 | 美国凹凸微系有限公司 | Analog to digital converter with interference rejection capability |
| CN101241179A (en) * | 2007-01-19 | 2008-08-13 | 恩益禧电子股份有限公司 | Multi-band RF receiver |
| CN101281245A (en) * | 2008-05-27 | 2008-10-08 | 北京大学 | Method and apparatus for receiving army and civil dual-purpose global satellite navigation system multi-module radio frequency |
| CN101907698A (en) * | 2009-06-03 | 2010-12-08 | 晨星软件研发(深圳)有限公司 | Signal process device of multiple satellite positioning system and method thereof |
| CN202305808U (en) * | 2011-10-18 | 2012-07-04 | 上海迦美信芯通讯技术有限公司 | Dual-channel navigation RF (radio-frequency) receiver system architecture on front end of shared RF |
Cited By (15)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN102928856A (en) * | 2012-10-19 | 2013-02-13 | 西安欣创电子技术有限公司 | Global positioning system (GPS) and Beidou double-module navigation radio frequency receiving system |
| CN103048666A (en) * | 2012-12-07 | 2013-04-17 | 广州润芯信息技术有限公司 | Beidou satellite and GPS (global positioning system) double-passage radio frequency receiving machine |
| CN103901449A (en) * | 2012-12-24 | 2014-07-02 | 瑞士优北罗股份有限公司 | Methods of processing a radio frequency signal, signal processing devices for carrying out the methods, radio frequency front-ends, radio receivers and gnss receivers |
| CN103308932A (en) * | 2013-05-28 | 2013-09-18 | 中国电子科技集团公司第三十八研究所 | Monolithic multimode navigation chip based on broadband radio frequency direct technology |
| CN103762996A (en) * | 2014-01-04 | 2014-04-30 | 南昌大学 | VHF-UHF software radio receiving system |
| CN107181477A (en) * | 2017-05-11 | 2017-09-19 | 清华大学深圳研究生院 | A kind of new frequency generator |
| CN107479054A (en) * | 2017-06-20 | 2017-12-15 | 华东理工大学 | Synthetic aperture radiometer based on injection frequency receiving array |
| CN107678021A (en) * | 2017-09-26 | 2018-02-09 | 南京索尔维电子科技有限公司 | A kind of synchronous radio beat frequency phase range unit and method |
| CN108897019A (en) * | 2018-04-27 | 2018-11-27 | 武汉大学 | A kind of GPS/ Beidou II navigation radio-frequency receiving system in Dual-mode two-way road |
| CN112105960A (en) * | 2018-05-04 | 2020-12-18 | 高通股份有限公司 | Concurrent support for multiple frequency bands for satellite navigation signals |
| CN112105960B (en) * | 2018-05-04 | 2021-09-24 | 高通股份有限公司 | Concurrent support for multiple frequency bands for satellite navigation signals |
| CN108594279A (en) * | 2018-06-20 | 2018-09-28 | 北京遥测技术研究所 | A kind of device received suitable for multisystem navigation signal monitoring |
| CN108594279B (en) * | 2018-06-20 | 2021-04-13 | 北京遥测技术研究所 | Device suitable for monitoring and receiving multi-system navigation signals |
| CN113364472A (en) * | 2020-03-04 | 2021-09-07 | 鹤壁天海电子信息系统有限公司 | Transmitter, receiver and communication equipment |
| CN113364472B (en) * | 2020-03-04 | 2023-08-22 | 鹤壁天海电子信息系统有限公司 | Transmitter, receiver and communication equipment |
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