CN101989862B - Receiver and method for receiving wireless signal - Google Patents
Receiver and method for receiving wireless signal Download PDFInfo
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- CN101989862B CN101989862B CN200910164996.9A CN200910164996A CN101989862B CN 101989862 B CN101989862 B CN 101989862B CN 200910164996 A CN200910164996 A CN 200910164996A CN 101989862 B CN101989862 B CN 101989862B
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Abstract
The invention provides a receiver and a receiving method. The receiver can receive a radio-frequency signal and generate a fundamental-frequency signal. A radio-frequency module in the receiver can receive the radio-frequency signal and reduce the frequency based on the first oscillation frequency to generate an intermediate-frequency signal. An intermediate-frequency module reduces the intermediate-frequency signal based on the second oscillation frequency to generate the fundamental-frequency signal. In a calibration mode, a test generator transmits a test signal to the radio-frequency module to simulate the radio-frequency signal; and blending and accumulation operation are performed on the solved intermediate-frequency signal based on the third oscillation frequency by a calibration module to detect in-phase/quadrature (I/Q) unbalance, wherein the third oscillation frequency is 16 times the second oscillation frequency.
Description
Technical field
The invention relates to wireless communication technique, in particular to the unbalance collimation technique of I/Q in receiver.
Background technology
Fig. 1 is known receiver 100.This receiver 100 is to design based on Weaver framework, wherein mainly comprises radio-frequency module 110 and ifd module 120.This radio-frequency module 110 received RF signal RF be intermediate-freuqncy signal IF by it frequency reducing, and this ifd module 120 by this intermediate-freuqncy signal IF again frequency reducing be fundamental frequency signal LF.Wherein the path of signal is divided into again homophase (I-path) and orthogonal (Q-path) two-way.For instance, in radio-frequency module 110, the first phase-locked loop PLL1 provides oscillator signal LO1I and the LO1Q with the first frequency of oscillation LO1.And the first mixer 102a and the second mixer 102b multiply each other this oscillator signal LO1I and LO1Q and radiofrequency signal RF respectively.The composite signal obtaining, after the first low pass filter 104a and the second low pass filter 104b, just produces intermediate-freuqncy signal IF, comprises homophase intermediate-freuqncy signal I
1with orthogonal intermediate-freuqncy signal Q
1.In ifd module 120, the second phase-locked loop PLL2 provides oscillator signal LO2I and LO2Q to the three mixer 106a and the 4th mixer 106b with the second frequency of oscillation LO2.And homophase and orthogonal intermediate-freuqncy signal I
1and Q
1respectively by after the 3rd mixer 106a and the 4th mixer 106b smear, the homophase of gained and quadrature baseband signal I
2and Q
2in adder 108, be added, obtain Output rusults intermediate-freuqncy signal IF.
The framework main purpose of receiver 100 is in order to get rid of image frequency (ImageRejection) in frequency reducing process.In the time of the circuit perfect matching of in-phase path and quadrature path, can produce splendid image frequency and get rid of effect ideally.General so-called efficiency index Image Rejection Ratio (IRR) is higher, just represents that image frequency is got rid of effect better.On actual circuit is manufactured, due to all faulty factor impacts, between in-phase path and quadrature path, conventionally have amplitude error, gain error and phase error, be referred to as I/Q unbalance.The effect that effect that these I/Q are unbalance can make image frequency get rid of is had a greatly reduced quality.The gain error of general circuit approximately between+-10% between, phase error approximately between+-5% between.In order to improve unbalance the caused loss of efficacy of I/Q, known way is to use extra I/Q calibration circuit, detects the error amount between in-phase path and quadrature path, and gives corresponding offset.For instance, more common error detection and compensation mode adopts adaptive architecture (adaptive) mostly, advantage be can get rid of all I/Q of impact unbalance enclose element, also possess larger circuit design elasticity.But adaptive architecture need to be longer training time just can show the effect of compensation.In addition,, in order to detect error, often need extra circuit to produce test signal #CAL.And the requirement of the signal to noise ratio (SNR) of test signal #CAL itself is generally all very high, so can need extra one-tenth originally to promote its quality.
Summary of the invention
The following example specific description as how preferably mode realize the present invention.The mode that embodiment only generally applies for explanation, but not in order to limit scope of the present invention.Actual range is as the criterion so that claim is listed.
Embodiments of the invention comprise a kind of receiver, in order to received RF signal and produce fundamental frequency signal.Wherein comprise radio-frequency module, can received RF signal and carry out frequency reducing to produce intermediate-freuqncy signal with the first frequency of oscillation, and ifd module, receive this intermediate-freuqncy signal and with the second frequency of oscillation frequency reducing, to produce this fundamental frequency signal.In addition, still there is calibration module, with the 3rd frequency of oscillation, this intermediate-freuqncy signal is carried out to smear and accumulating operation unbalance to detect I/Q, and produce and adjust signal according to this, unbalance in order to adjust this I/Q.Wherein the 3rd frequency of oscillation is this second frequency of oscillation at least two times, for example 16 times.In this receiver, can further comprise test pattern generator.In the time of calibration mode, this test pattern generator transmission test signal is to this radio-frequency module with this radiofrequency signal of emulation, and this test signal has frequency and amplitude.
This radio-frequency module comprises the first phase-locked loop, in order to produce the first in-phase oscillator signal and first quadrature oscillator signal with this first frequency of oscillation.The first mixer is with this first in-phase oscillator signal by this test signal smear, and the first low pass filter filters to export homophase intermediate-freuqncy signal by the smear result of this first mixer.The second mixer is with this first quadrature oscillator signal by this test signal smear, and the second low pass filter filters the smear result of this second mixer, with output orthogonal intermediate-freuqncy signal.
In this ifd module, the second phase-locked loop produces the second in-phase oscillator signal and second quadrature oscillator signal with this second frequency of oscillation.The 3rd mixer with this second in-phase oscillator signal by this homophase intermediate-freuqncy signal smear, to produce homophase fundamental frequency signal.The 4th mixer with this second quadrature oscillator signal by this orthogonal intermediate-freuqncy signal smear, to produce quadrature baseband signal.Compensator receives this homophase fundamental frequency signal and this quadrature baseband signal, and unbalance according to this I/Q of this adjustment signal correction, and exports by this this fundamental frequency signal.
In this calibration module, the first and second digital quantizers are converted to homophase and quadrature digital signal by this homophase and orthogonal intermediate-freuqncy signal respectively.Then again mixer carries out smear to obtain the poor and relative phase difference of relative gain with the 3rd frequency of oscillation to this in-phase digital signal and this quadrature digital signal.Finally by statistical module, poor and this relative phase difference of this relative gain is carried out to accumulating operation to obtain the poor and absolute phase difference of absolute gain.
This compensator receives this homophase fundamental frequency signal, this quadrature baseband signal, and poor and this absolute phase difference of this absolute gain, obtain same-phase compensation result and quadrature compensation result according to following formula:
I’
2＝I
2/(1+ε)
Q’
2＝-I
2.tanΘ/(1+ε)+Q
2/cosΘ
It is poor that wherein ε is this absolute gain, I
2for this homophase fundamental frequency signal, I '
2for this same-phase compensation result, and Q '
2be this quadrature compensation result.In this compensator, still comprise adder, this same-phase compensation result can be produced to this fundamental frequency signal with this quadrature compensation results added.
This multiple mixer comprises the first multiplier, with the 3rd in-phase oscillator signal with the 3rd frequency of oscillation by this in-phase digital signal smear, and the second multiplier, with the 3rd quadrature oscillator signal with the 3rd frequency of oscillation by this quadrature digital signal smear.First adder is by the smear results added of this first multiplier and this second multiplier, and the 3rd multiplier is by the addition result of this first adder and this in-phase digital signal multiplication, poor to produce this relative gain.
In this statistical module, all relative gains that the first accumulator produced within the cumulative time cycle are poor, and wherein this time cycle is relevant with the frequency of this test signal.The first regular device carries out normalization according to the amplitude of this test signal by the accumulation result of this first accumulator.The first graduator is adjusted the regular result of this first regular device according to the multiplying power of the 3rd frequency of oscillation and this second frequency of oscillation, poor to produce this absolute gain.
Similarly, in order to process phase difference, this calibration module further comprises the 4th multiplier, with the 3rd in-phase oscillator signal by this orthogonal intermediate-freuqncy signal smear, the 5th multiplier, by the 3rd quadrature oscillator signal by this homophase intermediate-freuqncy signal smear, second adder, by the smear results added of the 4th multiplier and the 5th multiplier, and the 6th multiplier, by the addition result of this second adder and this in-phase digital signal multiplication, to produce relative phase difference.And accordingly, this statistical module comprises the second accumulator, all relative phase differences that produce within the cumulative time cycle, wherein this time cycle is relevant with the frequency of this test signal.The second regular device carries out normalization according to the amplitude of this test signal by the accumulation result of this second accumulator.The second graduator, adjusts the regular result of this second regular device, to produce this absolute phase difference according to the multiplying power of the 3rd frequency of oscillation and this second frequency of oscillation.
The present invention also provides a kind of radio signal receiving method, produces fundamental frequency signal in order to received RF signal and by I/Q channel, comprises: at calibration mode: the input of test signal to this I/Q channel is provided, and this test signal has frequency and amplitude; With first this test signal of frequency of oscillation frequency reducing, produce intermediate-freuqncy signal at the output of this I/Q channel; And it is unbalance to detect I/Q with the 3rd frequency of oscillation, this intermediate-freuqncy signal to be carried out to smear and accumulating operation; At normal mode: receive this radiofrequency signal and with this this radiofrequency signal of the first frequency of oscillation frequency reducing, produce this intermediate-freuqncy signal at the output of this I/Q channel; And with second this intermediate-freuqncy signal of frequency of oscillation frequency reducing, and it is unbalance to produce this fundamental frequency signal to proofread and correct this I/Q.
The another embodiment that proposes of the present invention illustrates the radio signal receiving method based on above-mentioned receiver implementation.Although the present invention illustrates as above with preferred embodiment, is understandable that the not necessarily so restriction of scope of the present invention.Relative, any based on same spirit or be that apparent improvement is all in covering scope of the present invention to those skilled in the art.Therefore patent claimed range must be understood in the mode of broad sense.
Brief description of the drawings
Fig. 1 is known receiver 100;
Fig. 2 is the receiver 200 of one of embodiment of the present invention;
Fig. 3 is the embodiment of Fig. 2 alignment module 220;
Fig. 4 is the embodiment of compensator 230 in Fig. 2; And
Fig. 5 is the flow chart of radio signal receiving method of the present invention.
[main element label declaration]
100,200～receiver; 102a, 102b, 106a, 106b～mixer;
104a, 104b～low pass filter; 108～adder;
110～radio-frequency module; 120～ifd module;
210～test pattern generator; 220～calibration module;
230～compensator; PLL1, PLL2, PLL3～phase-locked loop;
310～multiple mixer; 320～statistical module;
302a, 302b, 302c, 302d, 306a, 306b～multiplier;
304a, 304b～first adder, second adder;
308a, 308b～digital quantizer;
322a, 322b～accumulator;
324a, the regular device of 324b～the first, the second regular device;
326a, 326b～the first graduator, the second graduator;
The 402,404～the first arithmetic element, the second arithmetic element;
The 406～three arithmetic element;
408～adder.
Embodiment
Fig. 2 is the receiver 200 of one of embodiment of the present invention.In receiver 200, except known radio-frequency module 110 and ifd module 120, separately add test pattern generator 210, calibration module 220 and compensator 230.Wherein compensator 230 is the adder 108 of improvement in Fig. 1 and obtaining.The running of receiver 200 is divided into two patterns, and one is calibration mode, and one is normal mode.Test pattern generator 210 and calibration module 220 are to operate on calibration mode, and compensator 230 operates on normal mode jointly with radio-frequency module 110 and ifd module 120.In calibration mode, test pattern generator 210 sends test signal #CAL, in order to this radiofrequency signal of emulation RF, makes radio-frequency module 110 carry out down conversion process to it.This test signal #CAL is essentially known value, has given frequency and known amplitude.And radio-frequency module 110 produces intermediate-freuqncy signal IF after receiving this test signal #CAL, be expressed as homophase intermediate-freuqncy signal I
1with orthogonal intermediate-freuqncy signal Q
1.In the present embodiment, this calibration module 220 couples this radio-frequency module 110, and the intermediate-freuqncy signal IF that the 3rd frequency of oscillation LO3 providing according to the 3rd phase-locked loop PLL3 exports radio-frequency module 110 carries out smear and accumulating operation is unbalance with the I/Q between detection in-phase path and quadrature path.Detect I/Q unbalance after, calibration module 220 produces adjusts signal #ADJ, sends compensator 230 to, and compensator 230 is operated under normal mode, unbalance according to the I/Q between this adjustment signal #ADJ adjustment in-phase path and quadrature path, the fundamental frequency signal LF after last output calibration.In Fig. 2, calibration module 220 can be coupled in the output of radio-frequency module 110, can be also other node on in-phase path and quadrature path.The 3rd frequency of oscillation LO3 that calibration module 220 has adopted the 3rd phase-locked loop PLL3 to provide.And the 3rd frequency of oscillation LO3 is at least more than twice of the second frequency of oscillation LO2.For an example preferably, the 3rd frequency of oscillation LO3 can be 16 times of the second frequency of oscillation LO2.The frequency relation of radiofrequency signal RF and intermediate-freuqncy signal IF is not limited by embodiment, and general communication applications is all applicable.The second frequency of oscillation LO2 and the 3rd frequency of oscillation LO3 not necessarily will by two independently phase-locked loop produce, also can pick up from same phase-locked loop, produce different frequency in the mode of raising frequency.About the existing many known details of sharing of different phase-locked loops.Detailed implementation mode as for calibration module 220 and compensator 230 will be detailed in back segment.
Fig. 3 is the embodiment of Fig. 2 alignment module 220.In in-phase path, the first digital quantizer 308a couples the first low pass filter 104a in Fig. 2, by this homophase intermediate-freuqncy signal I
1be converted to in-phase digital signal DI.On quadrature path, the second digital quantizer 308b couples the second low pass filter 104b in Fig. 2, by orthogonal intermediate-freuqncy signal Q
1be converted to quadrature digital signal DQ.Then, in-phase digital signal DI and quadrature digital signal DQ that multiple mixer 310 reception this first digital quantizer 308a and this second digital quantizer 308b export, the 3rd frequency of oscillation LO3 being provided with the 3rd phase-locked loop PLL3 carries out smear to obtain the poor Δ ε of relative gain and relative phase difference Δ Θ to this in-phase digital signal DI and this quadrature digital signal DQ.The 3rd frequency of oscillation LO3 more particularly, has comprised the 3rd in-phase oscillator signal LO3I and the 3rd quadrature oscillator signal LO3Q, and phase phasic difference 90 is spent, respectively in order to supply corresponding element.Belong to known technology as for homophase and orthogonal producing method of shaking shake signal, therefore not explanation in this enforcement.After obtaining the poor Δ ε of relative gain and relative phase difference Δ Θ, multiple mixer 310 exports statistical module 320 to.320 of this statistical modules are further unbalance to obtain definite I/Q to the poor Δ ε of this relative gain and the individual accumulating operation that do not carry out of this relative phase difference Δ Θ.In the present embodiment, I/Q is unbalance taking the poor ε of absolute gain and absolute phase difference Θ as leading indicator.
Specifically, what multiple mixer 310 carried out is a kind of complex operation, can be from homophase intermediate-freuqncy signal I
1and Q
1middle extraction relative phase difference Δ Θ and the poor Δ ε of relative gain.In multiple mixer 310, four multiplier 302a, 302b, 302c and 302d are comprised.Multiplier 302a is to have the 3rd in-phase oscillator signal LO3I of the 3rd frequency of oscillation LO3, this in-phase digital signal DI smear is produced to smear signal II, multiplier 302b, to have the 3rd quadrature oscillator signal LO3Q of the 3rd frequency of oscillation LO3, is multiplied by this quadrature digital signal DQ and produces smear signal QQ afterwards.The computing of multiplier 302c and multiplier 302d is just contrary, multiplier 302c with the 3rd in-phase oscillator signal LO3I by quadrature digital signal DQ smear, produce smear signal QI, and multiplier 302d by the 3rd quadrature oscillator signal LO3Q by this in-phase digital signal DI smear, produce smear signal IQ.The smear signal II that first adder 304a calculates multiplier 302a and 302b and QQ export multiplier 306a to after being added, and this multiplier 306a multiplies each other the output valve of this first adder 304a and this in-phase digital signal DI, the result of generation is just the poor Δ ε of relative gain.Similarly, second adder 304b is added smear signal QI and IQ, and exports multiplier 306b to and in-phase digital signal DI multiplies each other, and just obtains relative phase difference Δ Θ.In the present embodiment, in the poor Δ ε of relative gain and relative phase difference Δ Θ, comprised homophase intermediate-freuqncy signal I
1and Q
1compound composition after smear, as LO3+ (LO1-LO2) and LO3-(LO1-LO2).The object of doing these computings is by the 3rd frequency of oscillation LO3 raising frequency, makes homophase and orthogonal intermediate-freuqncy signal I
1and Q
1unbalance situation deliver to without reservation statistical module 320 with the form of energy and carry out accumulating operation.
In statistical module 320, computing is mainly divided into three steps, cumulative, amplitude normalization and time normalization.The poor Δ ε of relative gain of multiplier 306a output is sent to the first accumulator 322a.The poor Δ ε of all relative gains that this 322a produced within the cumulative time cycle, wherein this time cycle is relevant with the frequency of this test signal #CAL.Then the first regular device 324a carries out normalization according to the amplitude of this test signal #CAL by the accumulation result of this first accumulator 322a.And the first graduator 326a couples this first regular device 324a, adjust the regular result of this first regular device 324a according to the multiplying power of the 3rd frequency of oscillation LO3 and this second frequency of oscillation LO2, make the poor ε of absolute gain of output represent the absolute value of unit interval.Similarly, in the time of the poor ε of computing absolute gain, all relative phase difference Δ Θ that the second accumulator 322b produced within the cumulative time cycle, wherein this time cycle is relevant with the frequency of this test signal #CAL.The second regular device 324b carries out normalization according to the amplitude of this test signal #CAL by the accumulation result of this second accumulator 322b, and the second graduator 326b adjusts the regular result of this second regular device 324b according to the multiplying power of the 3rd frequency of oscillation LO3 and this second frequency of oscillation LO2, to produce the absolute phase difference Θ of unit interval.
Fig. 4 is the embodiment of compensator 230 in Fig. 2.In the present embodiment, the adjustment signal #ADJ that this compensator 230 receives, is exactly in fact the poor ε of absolute gain and the absolute phase difference Θ that in Fig. 3, statistical module 320 is obtained.In ifd module 120 in Fig. 2, the 3rd mixer 106a and the 4th mixer 106b first according to the second oscillator signal LO2I and LO2Q by homophase and orthogonal intermediate-freuqncy signal I
1and Q
1frequency reducing is homophase and quadrature baseband signal I
2and Q
2.Suppose in the ideal situation, the ideal value of homophase and quadrature baseband signal can be expressed as:
I
ideal＝Acos(wt+δ) (1)
Q
ideal＝Asin(wt+δ) (2)
And homophase and the quadrature baseband signal actual value with phase error and gain error are expressed as:
I
mismacth＝A(1+ε)cos(wt+δ) (3)
Q
mismacth＝Asin(wt+δ+Θ) (4)
Can be (4) formula abbreviation to (3) formula according to (1):
Q
mismatch＝Q
idealcosΘ+I
idealsinΘ (5)
So as long as just can be from (3) and the I of (4) formula according to the poor ε of absolute gain and Θ
mismatchand Q
mismatchestimate (1) and the ideal value of (2) formula.
I
ideal＝I
mismatch/(1+ε) (6)
Q
ideal＝tanΘ.I
mismatch/(1+ε)I+Q
mismatch/cosΘ (7)
According to (6) and (7) formula, compensator 230 can be to this homophase and quadrature baseband signal I
2and Q
2carry out following compensating movement, in the hope of same-phase compensation result I '
2with quadrature compensation result Q '
2:
I’
2＝I
2/(1+ε) (8)
Q’
2＝(-I’
2.sinΘ+Q
2)/cosΘ (9)
Last by the adder 108 in this compensator 230, by this same-phase compensation result I '
2with this quadrature compensation result Q '
2be added and generation fundamental frequency signal LF.Because (8) formula and (9) formula are simple arithmetic, only need substitution homophase fundamental frequency signal I
2, quadrature baseband signal Q
2, the poor ε of absolute gain and absolute phase difference Θ, so actual circuit implementation is not defined as any form.For instance, in Fig. 4, can comprise the first arithmetic element 402, in order to according to homophase fundamental frequency signal I
2calculate same-phase compensation result I ' with the poor ε of absolute gain
2.As for quadrature compensation result Q '
2calculating, also can be completed by the second arithmetic element 404 and the 3rd arithmetic element 406.Wherein the second arithmetic element 404 receives homophase fundamental frequency signal I
2, the poor ε of absolute gain and absolute phase difference Θ, calculate-I
2.tan the value of Θ/(1+ ε), and the 3rd arithmetic element 406 receives quadrature baseband signal Q
2with absolute phase difference Θ, calculate quadrature baseband signal Q
2the value of/cos Θ, then by 1, the output of the second arithmetic element 404 and the 3rd arithmetic element 406 is added, quadrature compensation result Q ' obtained
2.Substantially, the fundamental frequency signal LF that adder 108 is exported, is the optimum after correction.
Fig. 5 is the flow chart of radio signal receiving method of the present invention.After receiver 200 starts, in step 502, enter calibration mode, provide test signal #CAL to carry out frequency reducing to radio-frequency module 110 by test pattern generator 210, produce homophase and orthogonal intermediate-freuqncy signal I
1and Q
1.This test signal #CAL has given frequency and known amplitude, and in radio-frequency module 110, the unbalance situation of in-phase path and quadrature path can be reacted at homophase and orthogonal intermediate-freuqncy signal I
1and Q
1in.In step 504, by the multiple mixer 310 in calibration module 220 with the 3rd frequency of oscillation LO3 to homophase and orthogonal intermediate-freuqncy signal I
1and Q
1carry out compound smear computing, to calculate the poor Δ ε of relative phase difference Δ Θ and relative gain.Then in step 506, by statistical module 320 to relative phase difference Δ Θ and the poor Δ ε of relative gain carry out a period of time cumulative, amplitude is regular and regular computing of time, tries to achieve the poor ε of absolute gain and absolute phase difference Θ.Then in step 508, enter normal mode, radio-frequency module 110 received RF signal RF with first this radiofrequency signal of frequency of oscillation LO1 frequency reducing RF, produce this intermediate-freuqncy signal IF at the output of this I/Q passage.Then in step 510, with the second frequency of oscillation LO2, the IF frequency reducing of this intermediate-freuqncy signal is produced to homophase fundamental frequency signal I by ifd module 120
2with quadrature baseband signal Q
2.In step 512, the poor ε of absolute gain and the absolute phase difference Θ that are obtained according to calibration mode by compensator 230, the homophase fundamental frequency signal I that compensation ifd module 120 produces
2with quadrature baseband signal Q
2, finally produce the fundamental frequency signal LF of I/Q balance.In the present embodiment, the 3rd frequency of oscillation LO3 specified value is 16 times of the second frequency of oscillation LO2, but substantially can operate as long as being greater than two times.It is to adopt Weaver framework that receiver 200 does not limit, and measures the also unnecessary output that is coupled in radio-frequency module 110 of the unbalance calibration module 220 of I/Q, is determined by the structure of receiver 200.The adjustment signal #ADJ that calibration module 220 produces is digital pattern in the present embodiment, but also can pass through known analog converter (DAC), converts the pattern of simulation to adjust the part of analog circuit in receiver 200.In other words not limit be the digital circuit of design among ifd module 120 to compensator 230, can be also the analog circuit of design among RF module 110.Receiver 200 can be applicable to field of wireless communication widely, even comprise wireless network, mobile phone is bluetooth communication agreement.
Although the present invention discloses as above with preferred embodiment; so it is not in order to limit the present invention; any those skilled in the art; without departing from the spirit and scope of the present invention; when doing a little change and retouching, therefore protection scope of the present invention is when being as the criterion depending on the appended claim scope person of defining.
Claims (13)
1. a receiver, received RF signal also produces fundamental frequency signal, comprises:
Radio-frequency module, received RF signal also carries out frequency reducing with the first frequency of oscillation, and to produce intermediate-freuqncy signal, described intermediate-freuqncy signal comprises a homophase fundamental frequency signal and a quadrature baseband signal;
Ifd module, couples this radio-frequency module, receives this intermediate-freuqncy signal and with the second frequency of oscillation frequency reducing, to produce this fundamental frequency signal;
Calibration module, couple this radio-frequency module, with the 3rd frequency of oscillation, this intermediate-freuqncy signal is carried out to computing unbalance to detect I/Q, and signal is adjusted in generation according to this, unbalance in order to adjust this I/Q, this calibration module comprises: the first digital quantizer, couple this radio-frequency module, and this homophase intermediate-freuqncy signal is converted to in-phase digital signal; The second digital quantizer, couples this radio-frequency module, and this orthogonal intermediate-freuqncy signal is converted to quadrature digital signal; Multiple mixer, couples this first digital quantizer and this second digital quantizer, with the 3rd frequency of oscillation, this in-phase digital signal and this quadrature digital signal is carried out to smear to obtain the poor and relative phase difference of relative gain; And statistical module, couple this multiple mixer, poor and this relative phase difference of this relative gain is carried out to accumulating operation unbalance to obtain this I/Q, comprise the poor and absolute phase difference of absolute gain;
This multiple mixer comprises: the first multiplier, with the 3rd in-phase oscillator signal with the 3rd frequency of oscillation by this in-phase digital signal smear; The second multiplier, with the 3rd quadrature oscillator signal with the 3rd frequency of oscillation by this quadrature digital signal smear; First adder, by the smear results added of this first multiplier and this second multiplier; And the 3rd multiplier, by the addition result of this first adder and this in-phase digital signal multiplication, poor to produce this relative gain;
This statistical module comprises: the first accumulator, couple the 3rd multiplier, and all relative gains that produce within the cumulative time cycle are poor, and wherein this time cycle is relevant with the frequency of this test signal; The first regular device, couples this first accumulator, according to the amplitude of this test signal, the accumulation result of this first accumulator is carried out to normalization; And first graduator, couple this first regular device, adjust the regular result of this first regular device according to the multiplying power of the 3rd frequency of oscillation and this second frequency of oscillation, poor to produce this absolute gain;
This calibration module further comprises: the 4th multiplier, with the 3rd in-phase oscillator signal by this orthogonal intermediate-freuqncy signal smear; The 5th multiplier, by the 3rd quadrature oscillator signal by this homophase intermediate-freuqncy signal smear; Second adder, by the smear results added of the 4th multiplier and the 5th multiplier; And the 6th multiplier, by the addition result of this second adder and this in-phase digital signal multiplication, to produce relative phase difference;
This statistical module comprises: the second accumulator, couple the 6th multiplier, and all relative phase differences that produce within the cumulative time cycle, wherein this time cycle is relevant with the frequency of this test signal; The second regular device, couples this second accumulator, according to the amplitude of this test signal, the accumulation result of this second accumulator is carried out to normalization; And second graduator, couple this second regular device, adjust the regular result of this second regular device according to the multiplying power of the 3rd frequency of oscillation and this second frequency of oscillation, to produce this absolute phase difference.
2. receiver according to claim 1, wherein: the 3rd frequency of oscillation is the integral multiple of this second frequency of oscillation, and this integer is greater than two.
3. receiver according to claim 2, wherein: this integer is 16.
4. receiver according to claim 1, also comprises test pattern generator, couples the input of this radio-frequency module; Wherein, in the time of calibration mode, this test pattern generator transmission test signal is to this radio-frequency module with this radiofrequency signal of emulation, and this test signal has frequency and amplitude.
5. receiver according to claim 4, wherein this radio-frequency module comprises:
The first phase-locked loop, in order to produce the first in-phase oscillator signal and first quadrature oscillator signal with this first frequency of oscillation;
The first mixer, couples this first phase-locked loop, with this first in-phase oscillator signal by this test signal smear;
The first low pass filter, couples this first mixer, the smear result of this first mixer is filtered, to export the in-phase component of this intermediate-freuqncy signal, homophase intermediate-freuqncy signal;
The second mixer, couples this first phase-locked loop, with this first quadrature oscillator signal by this test signal smear; And
The second low pass filter, couples this second mixer, the smear result of this second mixer is filtered, to export the orthogonal intermediate-freuqncy signal of this intermediate-freuqncy signal.
6. receiver according to claim 5, wherein this ifd module comprises:
The second phase-locked loop, in order to produce the second in-phase oscillator signal and second quadrature oscillator signal with this second frequency of oscillation;
The 3rd mixer, couples this second phase-locked loop, with this second in-phase oscillator signal by this homophase intermediate-freuqncy signal smear, to produce this homophase fundamental frequency signal;
The 4th mixer, couples this second phase-locked loop, with this second quadrature oscillator signal by this orthogonal intermediate-freuqncy signal smear, to produce this quadrature baseband signal;
Compensator, couples the 3rd mixer and the 4th mixer, receives this homophase fundamental frequency signal and this quadrature baseband signal, and unbalance according to this I/Q of this adjustment signal correction, and exports by this this fundamental frequency signal.
7. receiver according to claim 6, wherein this compensator receives this homophase fundamental frequency signal, this quadrature baseband signal, poor and this absolute phase difference of this absolute gain, obtain same-phase compensation result and quadrature compensation result according to following formula:
I'
2=I
2/(1+ε)
Q'
2=-I
2.tanΘ/(1+ε)+Q
2/cosΘ
It is poor that wherein ε is this absolute gain, and Θ is this absolute phase difference, I
2for this homophase fundamental frequency signal, I '
2for this same-phase compensation result, and Q
2for this quadrature baseband signal, Q '
2be this quadrature compensation result; And
In this compensator, comprise adder, this same-phase compensation result is produced to this fundamental frequency signal with this quadrature compensation results added.
8. a radio signal receiving method, produces fundamental frequency signal in order to received RF signal and by I/Q channel, comprises:
At calibration mode:
The input of test signal to this I/Q channel is provided, and this test signal has frequency and amplitude;
With first this test signal of frequency of oscillation frequency reducing, produce intermediate-freuqncy signal at the output of this I/Q channel; And
With the 3rd frequency of oscillation, this intermediate-freuqncy signal is carried out to smear and accumulating operation unbalance to detect I/Q, this step comprises:
This homophase intermediate-freuqncy signal is sampled, to produce in-phase digital signal;
This orthogonal intermediate-freuqncy signal is sampled, to produce quadrature digital signal;
With the 3rd frequency of oscillation, this in-phase digital signal and this quadrature digital signal are carried out to plural smear to obtain the poor and relative phase difference of relative gain, this step comprises by having the 3rd in-phase oscillator signal and the in-phase digital signal multiplication of the 3rd frequency of oscillation, to produce the first multiplied result; The 3rd quadrature oscillator signal and this quadrature digital signal with the 3rd frequency of oscillation are multiplied each other, to produce the second multiplied result; This first and second multiplied result is added, to produce addition result; And this addition result and this homophase intermediate-freuqncy signal are multiplied each other, poor to produce this relative gain; The 3rd in-phase oscillator signal and this orthogonal intermediate-freuqncy signal are multiplied each other, take advantage of result to produce third phase; The 3rd quadrature oscillator signal and this homophase intermediate-freuqncy signal are multiplied each other, to produce the 4th multiplied result; This third and fourth multiplied result is added, to produce the second addition result; This second addition result and this homophase intermediate-freuqncy signal are multiplied each other, with obtain this relative phase difference and
Poor and this relative phase difference of this relative gain is carried out to accumulating operation unbalance to obtain this I/Q, comprise the poor and absolute phase difference of absolute gain, this step comprises: all relative gains that produce within the cumulative time cycle are poor, to produce the first accumulation result; Wherein this time cycle is relevant with the frequency of this test signal; According to the amplitude of this test signal, this first accumulation result is carried out to normalization, to produce the first regular result; And adjust this first regular result according to the multiplying power of the 3rd frequency of oscillation and this second frequency of oscillation, to produce all relative phase differences that produce within the poor cumulative time cycle of this absolute gain of this I/Q in unbalance, to produce the second accumulation result; Wherein this time cycle is relevant with the frequency of this test signal; According to the amplitude of this test signal, this second accumulation result is carried out to normalization, to produce the second regular result; And adjust this second regular result according to the multiplying power of the 3rd frequency of oscillation and this second frequency of oscillation, to produce this I/Q this absolute phase difference in unbalance;
At normal mode:
Receive this radiofrequency signal and with this this radiofrequency signal of the first frequency of oscillation frequency reducing, produce this intermediate-freuqncy signal at the output of this I/Q channel; And
With second this intermediate-freuqncy signal of frequency of oscillation frequency reducing, and it is unbalance to produce this fundamental frequency signal to proofread and correct this I/Q.
9. radio signal receiving method according to claim 8, wherein the 3rd frequency of oscillation is the integral multiple of this second frequency of oscillation, this integer is greater than two.
10. radio signal receiving method according to claim 9, wherein this integer is 16.
11. radio signal receiving methods according to claim 8, wherein comprise with the step of first this test signal of frequency of oscillation frequency reducing:
The first in-phase oscillator signal and first quadrature oscillator signal with this first frequency of oscillation are provided;
After being multiplied each other, this first in-phase oscillator signal and this test signal carry out low-pass filter, to export the homophase intermediate-freuqncy signal of this intermediate-freuqncy signal; And
After being multiplied each other, this first quadrature oscillator signal and this test signal carry out low-pass filter, to export the orthogonal intermediate-freuqncy signal of this intermediate-freuqncy signal.
12. radio signal receiving methods according to claim 11, wherein comprise with the step of second this intermediate-freuqncy signal of frequency of oscillation frequency reducing:
The second in-phase oscillator signal and second quadrature oscillator signal with this second frequency of oscillation are provided;
This second in-phase oscillator signal and this homophase intermediate-freuqncy signal are multiplied each other, to produce homophase fundamental frequency signal;
This second quadrature oscillator signal and this orthogonal intermediate-freuqncy signal are multiplied each other, to produce quadrature baseband signal;
By unbalance this I/Q, this homophase fundamental frequency signal and this quadrature baseband signal substitution calibration computing, to export this fundamental frequency signal.
13. radio signal receiving methods according to claim 8, wherein the step of this calibration computing comprises:
Receive this homophase fundamental frequency signal, this quadrature baseband signal, poor and this absolute phase difference of this absolute gain, obtain same-phase compensation result and quadrature compensation result according to following formula:
I’
2=I
2/(1+ε)
Q’
2=-I
2.tanΘ/(1+ε)+Q
2/cosΘ
It is poor that wherein ε is this absolute gain, and Θ is this absolute phase difference, I
2for this homophase fundamental frequency signal, I '
2for this same-phase compensation result, and Q
2for this quadrature baseband signal, Q '
2be this quadrature compensation result; And
This same-phase compensation result is produced to this fundamental frequency signal with this quadrature compensation results added.
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| CN1643777A (en) * | 2002-01-24 | 2005-07-20 | 高通股份有限公司 | System and method for i-q mismatch compensation in a low if or zero if receiver |
| CN1655465A (en) * | 2004-02-11 | 2005-08-17 | 络达科技股份有限公司 | Receiver gain balance compensation circuit and method therefor |
| CN1937417A (en) * | 2005-06-08 | 2007-03-28 | 英特尔公司 | Method of reducing imbalance in a quadrature frequency converter, method of measuring imbalance in such a converter, and apparatus for performing such method |
| WO2007096800A2 (en) * | 2006-02-22 | 2007-08-30 | Nxp B.V. | In phase and quadrature path imbalance compensation |
| CN101309100A (en) * | 2007-05-18 | 2008-11-19 | 富士通株式会社 | I/Q phase and gain compensating apparatus and method of orthogonal receiver |
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|---|---|---|---|---|
| CN1643777A (en) * | 2002-01-24 | 2005-07-20 | 高通股份有限公司 | System and method for i-q mismatch compensation in a low if or zero if receiver |
| CN1655465A (en) * | 2004-02-11 | 2005-08-17 | 络达科技股份有限公司 | Receiver gain balance compensation circuit and method therefor |
| CN1937417A (en) * | 2005-06-08 | 2007-03-28 | 英特尔公司 | Method of reducing imbalance in a quadrature frequency converter, method of measuring imbalance in such a converter, and apparatus for performing such method |
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