CN100405865C - TD-SCDMA terminal and its same-frequency cell time delay and power detecting method - Google Patents

Abstract

The present invention discloses a TD-SCDMA terminal and a testing method for the time delay and the power of a common-frequency cell. The TD-SCDMA terminal comprises a distributing module, a function module, a calculating module for the characteristic vector of an initial channel, a calculating module for a mutual interference vector, an interference counteracting module for the characteristic vector of the initial channel, and a calculating module for time delay and power. The method comprises the steps: the product of the reverse matrix of a cycle matrix composed of downlink pilot frequency codes corresponding to each cell and signals received by the terminal is calculated to obtain the characteristic vector of the initial channel; the cycle matrixes of the downlink pilot frequency codes of every two cells are divided to obtain the mutual interference vector of the two cells; the mutual interference vector is used for interfering in and counteracting the characteristic vector of the initial channel to obtain the characteristic vector of the channel; the power and the time delay of each cell are calculated out according to the characteristic vector of the channel.

Description

TD-SCDMA terminal and same-frequency cell time delay thereof and power detecting method

Technical field

The present invention relates to a kind of portable terminal and control method thereof, relate in particular to a kind of TD-SCDMA (Time Division-Synchronous Code Division Multiple Access, TD SDMA) terminal and same-frequency cell time delay and power detecting method.

Background technology

Along with communicate by letter with 3G (3G (Third Generation) Moblie) in the world rise of development of wireless communication devices, Radio Resource is as a kind of Limited resources, change more and more nervous.For the TD-SCDMA system of one of 3G mainstream standard, its Radio Resource that is assigned with also is very limited.In order to improve the availability of frequency spectrum of TD-SCDMA system, identical networking becomes a kind of the most effectively solution.

In the TD-SCDMA system under the identical networking condition, each cell downlink pilot code time delay and power detection have been used the computational methods under the inter-frequency networking condition.

Under the inter-frequency networking condition, the computational methods of downlink frequency pilot code time delay and power detection comprise following two steps:

(1) downlink frequency pilot code is carried out related operation or matched filtering, obtain the channel characteristics vector;

(2), calculate the time delay and the power of downlink frequency pilot code according to above-mentioned channel characteristics vector.

Under the inter-frequency networking condition, because the distance between co-frequency cell is far away, so co-channel interference is very little, can reach the degree of ignoring.

And under the condition of identical networking, because co-frequency cell is adjacent, interfering with each other bigger, therefore, the downlink frequency pilot code time delay under the application inter-frequency networking condition and the computational methods of power detection will produce bigger error.In the method as the downlink frequency pilot code time delay of above-mentioned calculating identical networking and power detection, comprised in the channel characteristics vector that in step (1), obtains and adjacent cell downlink pilot code between the mutual interference composition, will produce bigger error when therefore, the channel characteristics vector of step (2) in utilizing step (1) carries out the time delay of common frequency community downlink pilot code and power calculation.

Summary of the invention

The present invention overcomes the shortcoming of prior art, a kind of TD-SCDMA terminal and same-frequency cell time delay and power detecting method are provided, by eliminating in the channel characteristics vector and the mutual interference composition between adjacent cell downlink pilot code, thereby improve the accuracy of same-frequency cell time delay and power detection.

TD-SCDMA terminal of the present invention comprises scheduler module and functional module, also comprises:

Initial channel characteristic vector computing module is used for the inverse matrix of the circular matrix that constitutes according to the downlink frequency pilot code of each co-frequency cell correspondence and the product of the signal that terminal receives and calculates the initial channel characteristic vector;

Mutual interference vector calculation module, being used for being divided by according to per two co-frequency cells downlink frequency pilot code circular matrix separately obtains the mutual interference vector of these two sub-districts;

Initial channel characteristic vector Interference Cancellation module is used for according to above-mentioned mutual interference vector the initial channel characteristic vector being carried out Interference Cancellation, obtains the channel characteristics vector;

Time delay and power computation module are used for power and time delay according to above-mentioned each co-frequency cell of channel characteristics vector calculation.

The present invention also provides a kind of TD-SCDMA terminal to carry out the method for same-frequency cell time delay and power detection, and its step comprises:

Step 1 is calculated the inverse matrix of the circular matrix that the downlink frequency pilot code of each sub-district correspondence constitutes and the product of the signal that terminal receives, and obtains initial channel characteristic vector separately;

Step 2, being divided by according to per two sub-districts downlink frequency pilot code circular matrix separately obtains the mutual interference vector of these two sub-districts;

Step 3 utilizes above-mentioned mutual interference vector that the initial channel characteristic vector is carried out Interference Cancellation, obtains the channel characteristics vector;

Step 4 goes out the power and the time delay of each sub-district according to above-mentioned channel characteristics vector calculation.

The present invention offsets the interference in the initial channel characteristic vector on the basis of existing technology, and utilizes the time delay and the power of the channel characteristics vector calculation sub-district that obtains after the counteracting.With respect to prior art, the present invention can effectively eliminate the error when utilizing the channel characteristics vector to carry out the time delay of common frequency community downlink pilot code and power calculation, has improved the time delay of common frequency community downlink pilot code and the precision of power calculation.

Description of drawings

Fig. 1 is a TD-SCDMA terminal structure schematic diagram of the present invention;

Fig. 2 carries out the method flow diagram of same-frequency cell time delay and power detection for TD-SCDMA terminal of the present invention.

Embodiment

The present invention will be further described below in conjunction with accompanying drawing.

As shown in Figure 1, TD-SCDMA terminal of the present invention comprises scheduler module and functional module, and described scheduler module is used for when certain each functional module of ordered pair and carries out scheduled for executing; Described functional module is used to realize the specific function of TD-SCDMA terminal, and this functional module can comprise cell search module, channel coding/decoding module and baseband modulation and demodulation module etc.; In the TD-SCDMA terminal, also increase and be provided with initial channel characteristic vector computing module, mutual interference vector calculation module, initial channel characteristic vector Interference Cancellation module and time delay and power computation module.

Wherein, initial channel characteristic vector computing module is used for the inverse matrix of the circular matrix that constitutes according to the downlink frequency pilot code of each sub-district correspondence and the product of the signal that terminal receives calculates the initial channel characteristic vector.

The signal R that the TD-SCDMA terminal is received _{Dl_sync}Expression, the initial channel characteristic vector of each sub-district is used corresponding

...

Expression, the corresponding H of channel characteristics vector of each sub-district ₁, H ₂... H _nExpression.The signal R that receives of TD-SCDMA terminal then _{Dl_sync}Can be formulated as:

R _{dl_sync}＝S ₁H ₁+S ₂H ₂+...+S _iH _i+...+S _nH _n+n

Wherein, S ₁, S ₂... S _i... S _nThe circular matrix that the downlink frequency pilot code of using for each sub-district constitutes, n is a white Gaussian noise.The circular matrix S that constitutes by the downlink frequency pilot code of calculating each sub-district correspondence _iInverse matrix and the signal R that receives _{Dl_sync}Product, can draw the initial channel characteristic vector.The initial channel characteristic vector of each sub-district correspondence

Can be expressed as with formula:

${\hat{H}}_i={S_i}^{-1}{R}_{\mathrm{dl}\_\mathrm{sync}}$

Wherein, S _i ^-1Be circular matrix S _iInverse matrix.

Mutual interference vector calculation module is used for being divided by according to per two sub-districts downlink frequency pilot code circular matrix separately and obtains the mutual interference vector of these two sub-districts.

Initial channel characteristic vector Interference Cancellation module is used for according to above-mentioned mutual interference vector the initial channel characteristic vector being carried out Interference Cancellation, obtains the channel characteristics vector.

Time delay and power computation module are used for power and the time delay according to each sub-district of above-mentioned channel characteristics vector calculation.

The present invention is by increasing above-mentioned module in the TD-SCDMA terminal, can effectively offset the interference in the initial channel characteristic vector, thereby utilize the power and the time delay of each sub-district of channel characteristics vector calculation behind the Interference Cancellation, improved the precision of calculating each cell power and time delay.

The present invention also provides a kind of TD-SCDMA terminal to carry out the method for same-frequency cell time delay and power detection, as shown in Figure 2, comprises the steps:

Step 101, the TD-SCDMA terminal is calculated the initial channel characteristic vector.

In this step, the inverse matrix of the circular matrix that the initial channel characteristic vector of each sub-district correspondence constitutes for separately downlink frequency pilot code and the product of the signal that terminal receives.

The signal R that the TD-SCDMA terminal is received _{Dl_sync}Expression, the initial channel characteristic vector of each sub-district is used corresponding

... Expression, the corresponding H of channel characteristics vector of each sub-district ₁, H ₂... H _nExpression.The signal R that receives of TD-SCDMA terminal then _{Dl_sync}Can be formulated as:

R _{dl_sync}＝S ₁H ₁+S ₂H ₂+...+S _iH _i+...+S _nH _n+n

Wherein, S ₁, S ₂... S _i... S _nThe circular matrix that the downlink frequency pilot code of using for each sub-district constitutes, n is a white Gaussian noise.The circular matrix S that constitutes by the downlink frequency pilot code of calculating each sub-district correspondence _iInverse matrix and the signal R that receives _{Dl_sync}Product, can draw the initial channel characteristic vector.The initial channel characteristic vector of each sub-district correspondence

Can be expressed as with formula:

${\hat{H}}_i={S_i}^{-1}{R}_{\mathrm{dl}\_\mathrm{sync}}$

Wherein, S _i ^-1Be circular matrix S _iInverse matrix.

Be example with two sub-districts below, the process of calculating the initial channel characteristic vector is described.

According to above-mentioned formula, the signal that the TD-SCDMA terminal receives is:

R _{dl_sync}＝S ₁H ₁+S ₂H ₂+n。

The downlink frequency pilot code of two sub-districts uses of structure earlier constitutes the circular matrix S of N * N ₁, S ₂, N is the signal R that terminal receives here _{Dl_sync}Length, the length of the descending pilot frequency code value of each sub-district is 64, circular matrix building method and two sub-districts under many cell conditions are similar.

Two sub-district circular matrix S _iThe constitution step of (i=1,2) comprising:

A. construct column vector S _i(:, 1)=(s _{I, 1}, s _{I, 2}... s _{I, 64}, 0,0 ... 0) ^TBe matrix S _iFirst row; In the formula, column vector S _iThe number of elements that (:, 1) comprises is N.

B. with column vector S _i(:, 1) cyclic shift once obtains vectorial S _i(:, 2)=(0, s _{I, 1}, s _{I, 2}... s _{I, 64}, 0,0 ... 0) ^TBe matrix S _iSecondary series;

C. cyclic shift obtains S successively _i(:, 3), S _i(:, 4) ... S _i(:, 64), constitute the downlink frequency pilot code matrix S at last _i(i=1,2).

In the process of above-mentioned structural matrix, because the length of the descending pilot frequency code value of each sub-district of using is 64, so s _{I, 1}, s _{I, 2}... s _{I, 64}The length of having represented the individual sub-district of i (i=1,2) is 64 descending pilot frequency code value.

Circular matrix S in two sub-districts of above-mentioned structure _iIn (i=1,2), as the signal R that receives _{Dl_sync}Length be 128 o'clock, can obtain following matrix:

Through above-mentioned structure circular matrix S _iAfter (i=1,2), the corresponding initial channel characteristic vector in each sub-district is the circular matrix S that downlink frequency pilot code separately constitutes _iThe inverse matrix S of (i=1,2) _i ^-1(i=1,2) and the signal R that receives _{Dl_sync}Product.

The initial channel characteristic vector of two sub-districts

Can be expressed as with formula:

${\hat{H}}_1={S_1}^{-1}{R}_{\mathrm{dl}\_\mathrm{sync}}=\mathrm{IDFT}\left(\mathrm{DFT}\left({S_1}^{-1}{R}_{\mathrm{dl}\_\mathrm{sync}}\right)\right)=\mathrm{IDFT}\left[\frac{\mathrm{DFT}\left(R_{\mathrm{dl}\_\mathrm{sync}}\right)}{\mathrm{DFT}\left(S_1{I}_{N,0}\right)}\right]$

${\hat{H}}_2={S_2}^{-1}{R}_{\mathrm{dl}\_\mathrm{sync}}=\mathrm{IDFT}\left(\mathrm{DFT}\left({S_2}^{-1}{R}_{\mathrm{dl}\_\mathrm{sync}}\right)\right)=\mathrm{IDFT}\left[\frac{\mathrm{DFT}\left(R_{\mathrm{dl}\_\mathrm{sync}}\right)}{\mathrm{DFT}\left(S_2{I}_{N,0}\right)}\right]$

Aforementioned calculation initial channel characteristic vector

Formula in, I _{N, 0}Be a column vector that length is N, first is 1, and its remainder is 0.

Similar with above-mentioned two sub-districts, under the situation of many sub-districts, the formula that adopts the DFT transform method to calculate the initial channel characteristic vector of each co-frequency cell is:

${\hat{H}}_i={S_i}^{-1}{R}_{\mathrm{dl}\_\mathrm{sync}}=\mathrm{IDFT}\left(\mathrm{DFT}\left({S_i}^{-1}{R}_{\mathrm{dl}\_\mathrm{sync}}\right)\right)=\mathrm{IDFT}\left[\frac{\mathrm{DFT}\left(R_{\mathrm{dl}\_\mathrm{sync}}\right)}{\mathrm{DFT}\left(S_i{I}_{N,0}\right)}\right]$

Wherein, Be the initial channel characteristic vector of i sub-district, S _iBe the circular matrix of downlink frequency pilot code of structure, S _i ^-1Be S _iCorresponding inverse matrix, R _{Dl_sync}Be the signal that terminal receives, I _{N, 0}Be a column vector that length is N, its first be 1, and its remainder is 0.

In this step, also can pass through sliding correlation method, try to achieve the initial channel characteristic vector of each sub-district correspondence.

Suppose the signal R that terminal receives _{Dl_sync}Length be N, the length of descending pilot frequency code value is X, then the initial channel characteristic vector of each sub-district correspondence can be expressed as with formula:

${\hat{h}}_{i,k}=\underset{t=1}{\overset{X}{\mathrm{\Σ}}}{s_{i,t}}^{*}\×R_{\mathrm{dl}\_\mathrm{sync},(t+k-1)};$ k＝1，2，…N-X-1

${\hat{h}}_{i,k}=0;$ k＝N-X-2，N-X-3，…，N

Wherein,

Sequence constitutes the initial channel characteristic vector of i sub-district

Promptly ${\hat{H}}_i={({\hat{h}}_{i1},{\hat{h}}_{i2},...{\hat{h}}_{\mathrm{iN}})}^T$ , s _{I, t} ^*It is the conjugate of t downlink frequency pilot code of i sub-district.R _{Dl_sync, (t+k-1)}It is (t+k-1) individual value of the signal that receives of terminal.

In the TD-SCDMA system, the length of descending pilot frequency code value is 64, at this moment, adopts the formula of sliding correlation method calculating initial channel characteristic vector as follows:

${\hat{h}}_{i,k}=\underset{t=1}{\overset{64}{\mathrm{\Σ}}}{s_{i,t}}^{*}\×R_{\mathrm{dl}\_\mathrm{sync},(t+k-1)};$ k＝1，2，…N-63

${\hat{h}}_{i,k}=0;$ k＝N-62，N-61，…，N

By above formula as can be seen, work as K=N-62, N-61 ... during N, calculate

Be 0.

Step 102, TD-SCDMA terminal are calculated the mutual interference vector of per two minizones.

In this step, the TD-SCDMA terminal is divided by according to per two sub-districts downlink frequency pilot code circular matrix separately and is obtained the mutual interference vector of these two sub-districts.The mutual interference vector V of per two minizones _IjCan be expressed as with formula:

V _ij＝S _j ^-1S _iI _N，0(i≠j)，

Wherein, I _{N, 0}For length is the column vector of N, first is 1, and its remainder is 0; S _j ^-1It is the inverse matrix of the downlink frequency pilot code circular matrix of j sub-district; S _iIt is the downlink frequency pilot code circular matrix of i sub-district.

Because S _iMatrix is actually the circular convolution matrix, therefore, and above-mentioned mutual interference vector calculation formula

V _ij＝S _j ^-1S _iI _N，0，

Be equivalent to S _jI _{N, 0}Convolution V _IjObtain S _iI _{N, 0}According to the character of DFT conversion, the time domain convolution equals the frequency domain product, and therefore, the time solution convolution just equals frequency domain and is divided by.So in this step, the TD-SCDMA terminal is calculated the mutual interference vector also can calculate mutual interference vector V by following formula _Ij, can be expressed as with formula:

$V_{\mathrm{ij}}=\mathrm{IDFT}\left[\mathrm{DFT}\left(S_j^{-1}{S}_i{I}_{N,0}\right)\right]=\mathrm{IDFT}\left[\frac{\mathrm{DFT}\left(S_i{I}_{N,0}\right)}{\mathrm{DFT}\left(S_j{I}_{N,0}\right)}\right]$

Wherein, I _{N, 0}For length is the column vector of N, first is 1, and its remainder is 0; S _jIt is the downlink frequency pilot code circular matrix of j sub-district; S _iIt is the downlink frequency pilot code circular matrix of i sub-district.

Step 103 utilizes above-mentioned mutual interference vector that the initial channel characteristic vector is carried out Interference Cancellation, obtains the channel characteristics vector.

Exist the mutual interference component of other channel characteristics vectors in the initial channel characteristic vector that in above-mentioned steps 101, calculates to it, therefore, need to eliminate the interference components of these channel characteristics vectors, just can obtain the channel characteristics vector that needs current initial channel characteristic vector.For example, initial channel characteristic vector

In have H ₂... H _nTo its mutual interference component, therefore, need to eliminate H ₂... H _nThe mutual interference component, obtain channel characteristics vector H ₁In like manner, can obtain channel characteristics vector H ₂... H _n

Utilize the mutual interference vector that the initial channel characteristic vector is carried out the method for Interference Cancellation, its step comprises:

Step 201, the sytem matrix equation with mutual interference vector substitution initial channel vector constitutes obtains system equation;

Step 202 is carried out abbreviation to the said system equation, obtains the channel characteristics vector.

Still to be example with frequency two sub-districts, the concrete introduction carried out Interference Cancellation to the initial channel characteristic vector, obtains the process of channel characteristics vector.

According to the formula that calculates the initial channel characteristic vector in the step 101, ignoring under the situation of white Gaussian noise, following formula is arranged:

$\left\{\begin{array}{c}{\hat{H}}_1={S_1}^{-1}{R}_{\mathrm{dl}\_\mathrm{sync}}={S_1}^{-1}(S_1{H}_1+S_2{H}_2)=H_1+{S_1}^{-1}{S}_2{H}_2\\ {\hat{H}}_2={S_2}^{-1}{R}_{\mathrm{dl}\_\mathrm{sync}}={S_2}^{-1}(S_1{H}_1+S_2{H}_2)={S_2}^{-1}{S}_1{H}_1+H_2\end{array}\right.$

If T _Ij=S _j ^-1S _i, T _IjMatrix is by mutual interference vector V _IjThe direct cyclic shift square formation of Sheng Chenging, T _IjThe matrix construction method is as follows:

A). with V _Ij=(v _{Ij, 1}, v _{Ij, 2}... v _{Ij, N}) as T _IjFirst row of matrix.

B). with V _IjCyclic shift once obtains (v _{Ij, N}, v _{Ij, 1}, v _{Ij, 2}... v _{Ij, (N-1)}), constitute T _IjThe secondary series of matrix.

C). cyclic shift successively constitutes T _IjThe 3rd row of matrix, the 4th row ... the N row.

At last, generate the T of N * N _IjMatrix.

Below the formula of aforementioned calculation initial channel characteristic vector is used the T of structure _IjMatrix notation, i.e. formula

$\left\{\begin{array}{c}{\hat{H}}_1=H_1+{S_1}^{-1}{S}_2{H}_2\\ {\hat{H}}_2={S_2}^{-1}{S}_1{H}_1+H_2\end{array}\right.$

Use T _IjMatrix notation is:

$\left\{\begin{array}{c}{\hat{H}}_1=H_1+T_{21}{H}_2\\ {\hat{H}}_2=T_{12}{H}_1+H_2\end{array}\right.$

Calculate for convenience, make P=T ₂₁, Q=T ₁₂Then following formula becomes:

$\left\{\begin{array}{c}{\hat{H}}_1=H_1+P{H}_2\\ {\hat{H}}_2=Q{H}_1+H_2\end{array}\right.$

Being write as corresponding matrix form is:

$\left\{\begin{array}{c}\left(\begin{array}{c}{\hat{h}}_{11}\\ {\hat{h}}_{12}\\ .\\ .\\ .\\ {\hat{h}}_{1N}\end{array}\right)=\left(\begin{array}{c}{h}_{11}\\ h_{12}\\ .\\ .\\ .\\ h_{1N}\end{array}\right)+\left(\begin{array}{cccc}{p}_{11}& p_{12}& ...& p_{1N}\\ p_{21}& p_{22}& ...& p_{2N}\\ ...& & & \\ p_{N1}& p_{N2}& ...& p_{\mathrm{NN}}\end{array}\right)\×\left(\begin{array}{c}{h}_{21}\\ h_{22}\\ .\\ .\\ .\\ h_{2N}\end{array}\right)\\ \left(\begin{array}{c}{\hat{h}}_{21}\\ {\hat{h}}_{22}\\ .\\ .\\ .\\ {\hat{h}}_{2N}\end{array}\right)=\left(\begin{array}{cccc}{q}_{11}& q_{12}& ...& q_{1N}\\ q_{21}& q_{22}& ...& q_{2N}\\ ...& & & \\ q_{N1}& q_{N2}& ...& q_{\mathrm{NN}}\end{array}\right)\×\left(\begin{array}{c}{h}_{11}\\ h_{12}\\ .\\ .\\ .\\ h_{1N}\end{array}\right)+\left(\begin{array}{c}{h}_{21}\\ h_{22}\\ .\\ .\\ .\\ h_{2N}\end{array}\right)\end{array}\right.$

Converting this matrix form to equational form is:

$\left\{\begin{array}{c}{\hat{h}}_{11}=h_{11}+p_{11}{h}_{21}+p_{12}{h}_{22}+...+p_{1N}{h}_{2N}\\ {\hat{h}}_{12}=h_{12}+p_{21}{h}_{21}+p_{22}{h}_{22}+...+p_{2N}{h}_{2N}\\ ...\\ {\hat{h}}_{1N}{=h}_{1N}+p_{N1}{h}_{21}+p_{N2}{h}_{22}+...+p_{\mathrm{NN}}{h}_{2N}\\ {\hat{h}}_{21}=h_{21}+q_{11}{h}_{11}+q_{12}{h}_{12}+...+q_{1N}{h}_{1N}\\ {\hat{h}}_{22}=h_{22}+q_{21}{h}_{11}+q_{22}{h}_{12}+...+q_{2N}{h}_{1N}\\ ...\\ {\hat{h}}_{2N}{=h}_{2N}+q_{N1}{h}_{11}+q_{N2}{h}_{12}+...+q_{\mathrm{NN}}{h}_{1N}\end{array}\right.$

Below above-mentioned equation is carried out abbreviation, finds the solution, to obtain the channel characteristics vector behind the Interference Cancellation.Can utilize the maximum power window as constraints abbreviation system equation herein.

In wireless telecommunication system, the power of channel characteristics vector is generally concentrated on several the footpaths, and these several footpaths form a maximum power window.Around this principle, above-mentioned equation group can be carried out abbreviation by following step:

Step 301 is determined the maximum power window position of each initial channel characteristic vector correspondence.

Seek the initial channel characteristic vector respectively

Continuous W corresponding element, this W that require to seek continuously element power and greater than other any W continuously elements power and, the position of satisfying this W element correspondence of above-mentioned condition is the position of maximum power window, element value in the maximum power window is kept, and maximum power element value outside window gets 0.Determine in the process of initial channel characteristic vector that in reality the general value of number of elements W is 16, certainly, also can get other value according to the channel situation of reality.

Step 302 is according to above-mentioned definite maximum power window position abbreviation equation.

Because the mutual interference power between each cell downlink pilot code is much smaller than the power of each sub-district, so H ₁With

H ₂With

Maximum power window position unanimity, so, can determine H ₁And H ₂W element the unknown arranged respectively, and all the other elements are 0.

According to above-mentioned definite maximum power window position, can delete in the equation group ${\hat{h}}_{\mathrm{ij}}=0$ Equation, just realized abbreviation, thereby constituted the 2W unit equation group of forming by 2W equation above-mentioned equation group.

The original position of supposing the 1st sub-district maximum power window is α, and the original position of the 2nd sub-district maximum power window is β, and the window length of maximum power window is 16, then deletion ${\hat{h}}_{\mathrm{ij}}=0$ Equation group afterwards is:

$\left\{\begin{array}{c}{\hat{h}}_{1\mathrm{\α}}=h_{1\mathrm{\α}}+p_{\mathrm{\α\β}}{h}_{2\mathrm{\β}}+p_{\mathrm{\α}(\mathrm{\β}+1)}{h}_{2(\mathrm{\β}+1)}+...+p_{\mathrm{\α}(\mathrm{\β}+15)}{h}_{2(\mathrm{\β}+15)}\\ {\hat{h}}_{1(\mathrm{\α}+1)}=h_{1(\mathrm{\α}+1)}+p_{(\mathrm{\α}+1)\mathrm{\β}}{h}_{2\mathrm{\β}}+p_{(\mathrm{\α}+1)(\mathrm{\β}+1)}{h}_{2(\mathrm{\β}+1)}+...+p_{(\mathrm{\α}+1)(\mathrm{\β}+15)}{h}_{2(\mathrm{\β}+15)}\\ ...\\ {\hat{h}}_{1(\mathrm{\α}+15)}=h_{1(\mathrm{\α}+15)}+p_{(\mathrm{\α}+15)\mathrm{\β}}{h}_{2\mathrm{\β}}+p_{(\mathrm{\α}+15)(\mathrm{\β}+1)}{h}_{2(\mathrm{\β}+1)}+...+p_{(\mathrm{\α}+15)(\mathrm{\β}+15)}{h}_{2(\mathrm{\β}+15)}\\ {\hat{h}}_{2\mathrm{\β}}=h_{2\mathrm{\β}}+q_{\mathrm{\β\α}}{h}_{1\mathrm{\α}}+q_{\mathrm{\β}(\mathrm{\α}+1)}{h}_{1(\mathrm{\α}+1)}+...+q_{\mathrm{\β}(\mathrm{\α}+15)}{h}_{1(\mathrm{\α}+15)}\\ {\hat{h}}_{2(\mathrm{\β}+1)}=h_{2(\mathrm{\β}+1)}+q_{(\mathrm{\β}+1)\mathrm{\α}}{h}_{1\mathrm{\α}}+q_{(\mathrm{\β}+1)(\mathrm{\α}+1)}{h}_{1(\mathrm{\α}+1)}+...+q_{(\mathrm{\β}+1)(\mathrm{\α}+15)}{h}_{1(\mathrm{\α}+15)}\\ ...\\ {\hat{h}}_{2(\mathrm{\β}+15)}=h_{2(\mathrm{\β}+15)}+q_{(\mathrm{\β}+15)\mathrm{\α}}{h}_{1\mathrm{\α}}+q_{(\mathrm{\β}+15)(\mathrm{\α}+1)}{h}_{1(\mathrm{\α}+1)}+...+q_{(\mathrm{\β}+15)(\mathrm{\α}+15)}{h}_{1(\mathrm{\α}+15)}\end{array}\right.$

By the equation group behind the above-mentioned abbreviation is found the solution, just can obtain the channel characteristics vector H behind the Interference Cancellation ₁, H ₂In like manner, for many sub-districts, by the above-mentioned H that can obtain behind the Interference Cancellation ₁, H ₂... H _n

Step 104 is according to the power and the time delay of each sub-district of above-mentioned channel characteristics vector calculation.

The time delay of each sub-district is by determining that the first active path position obtains, and the power of each sub-district obtains by the power of this sub-district active path that superposes.

Channel characteristics vector after the elimination that obtains according to step 103 is disturbed is determined first active path and cell power, and its step is as follows:

Step 401 is determined the power of corresponding element in each channel characteristics vector.

The power powin of corresponding element can use following formulate:

(pow _i1，pow _i2，…，pow _iN)＝(h _i1×h _i1 ^*，h _i2×h _i2 ^*，…，h _iN×h _iN ^*)

Promptly

pow _in＝h _in×h _in ^*，

Wherein, h _InBe the channel characteristics vector H of i sub-district _iIn n element, h _In ^*Be h _InConjugate complex number.

Step 402 is determined the corresponding noise gate of each channel characteristics vector.

Calculate the average of each element power in each the channel characteristics vector that obtains in the above-mentioned steps 401, six times of noise gates that are the respective channels characteristic vector of gained average.

Step 403, with the power of element in each channel characteristics vector and corresponding noise gate relatively, choosing element power is active path greater than the respective path of noise gate.

In this step, in each channel characteristics vector that aforementioned calculation is obtained the power of element and corresponding noise gate relatively, as the power of the element noise gate greater than correspondence, then the path of this element correspondence is an active path; As the power of the element noise gate less than correspondence, then the path of this element correspondence is an Invalid path.For Invalid path, performance number that can its element correspondence is set to 0, has so just removed noise path.

Step 404 is determined the power of first active path and corresponding district time delay and sub-district.

In the active path that above-mentioned steps 403 obtains, be designated as minimum under selecting in each element power and be the pairing element of first nonzero value, the subscript of this element power correspondence is subtracted the position that 1 gained is exactly first active path, be the time delay of sub-district.The power of the active path corresponding element that for example, obtains in the step 403 is pow _I1, pow _I2... pow _IN, then from each element power, select to be designated as down minimum and be that the pairing element power of first nonzero value is pow _I1, this pow _I1It is 0 that corresponding subscript subtracts 1, i.e. the position of first active path, and also promptly the time delay of this sub-district is 0.

Definite method of cell power is: with the element power addition of all active path correspondences, the gained sum is the power of this sub-district.

The present invention offsets the interference in the initial channel characteristic vector on the basis of existing technology, and utilizes the time delay and the power of the channel characteristics vector calculation sub-district that obtains after the counteracting.With respect to prior art, the present invention can effectively eliminate the error when utilizing the channel characteristics vector to carry out the time delay of common frequency community downlink pilot code and power calculation, has improved the time delay of common frequency community downlink pilot code and the precision of power calculation.

Although embodiment of the present invention are open as above, but it is not restricted to listed utilization in specification and the execution mode, it can be applied to various suitable the field of the invention fully, for those skilled in the art, can easily realize other modification, therefore under the universal that does not deviate from claim and equivalency range and limited, the legend that the present invention is not limited to specific details and illustrates here and describe.

Claims (13)

1. a TD-SCDMA terminal comprises scheduler module and functional module, it is characterized in that, also comprises:

Initial channel characteristic vector computing module is used for the inverse matrix of the circular matrix that constitutes according to the downlink frequency pilot code of each co-frequency cell correspondence and the product of the signal that terminal receives and calculates the initial channel characteristic vector;

Mutual interference vector calculation module, being used for being divided by according to per two co-frequency cells downlink frequency pilot code circular matrix separately obtains the mutual interference vector of these two sub-districts;

Initial channel characteristic vector Interference Cancellation module is used for according to above-mentioned mutual interference vector the initial channel characteristic vector being carried out Interference Cancellation, obtains the channel characteristics vector;

Time delay and power computation module are used for power and time delay according to above-mentioned each co-frequency cell of channel characteristics vector calculation.

2. a TD-SCDMA terminal is carried out same-frequency cell time delay and power detecting method, it is characterized in that step comprises:

Step 1 is calculated the inverse matrix of the circular matrix that the downlink frequency pilot code of each sub-district correspondence constitutes and the product of the signal that terminal receives, and obtains initial channel characteristic vector separately;

Step 2, being divided by according to per two sub-districts downlink frequency pilot code circular matrix separately obtains the mutual interference vector of these two sub-districts;

Step 3 utilizes above-mentioned mutual interference vector that the initial channel characteristic vector is carried out Interference Cancellation, obtains the channel characteristics vector;

Step 4 goes out the power and the time delay of each sub-district according to above-mentioned channel characteristics vector calculation.

3. same-frequency cell time delay as claimed in claim 2 and power detecting method is characterized in that, in the described step 1, the building method of downlink frequency pilot code circular matrix comprises the steps:

Steps A, the first row column vector of structure downlink frequency pilot code circular matrix;

Step B obtains next column column vector corresponding in the downlink frequency pilot code circular matrix with the above-mentioned first row column vector cyclic shift;

Step C with the above-mentioned column vector that obtains cyclic shift successively, obtains corresponding next column column vector, until the column vector of the length correspondence that obtains the descending pilot frequency code value.

4. same-frequency cell time delay as claimed in claim 2 and power detecting method is characterized in that, in the described step 1, the initial channel characteristic vector of each sub-district correspondence is:

${\hat{H}}_i={S_i}^{-1}{R}_{\mathrm{dl}\_\mathrm{sync}}=\mathrm{IDFT}\left(\mathrm{DFT}\left({S_i}^{-1}{R}_{\mathrm{dl}\_\mathrm{sync}}\right)\right)=\mathrm{IDFT}\left[\frac{\mathrm{DFT}\left(R_{\mathrm{dl}\_\mathrm{sync}}\right)}{\mathrm{DFT}\left(S_i{I}_{N,0}\right)}\right]$

Wherein,

Be the initial channel characteristic vector of i sub-district, S _iBe the circular matrix of downlink frequency pilot code of structure, S _i ^-1Be S _iCorresponding inverse matrix, R _{Dl_sync}Be the signal that terminal receives, I _{N, 0}Be a column vector that length is N, its first be 1, and its remainder is 0, and N is R _{Dl_sync}Length.

5. same-frequency cell time delay as claimed in claim 2 and power detecting method is characterized in that, in the described step 1, the initial channel characteristic vector that adopts sliding correlation method to calculate each sub-district correspondence is:

${\hat{h}}_{i,k}=\underset{t=1}{\overset{X}{\mathrm{\Σ}}}{s_{i,t}}^{*}\×R_{\mathrm{dl}\_\mathrm{sync},(t+k-1)};k=\mathrm{1,2},...N-X-1$

${\hat{h}}_{i,k}=0;k=N-X-2,N-X-3,...,N$

Wherein, N is the signal R that terminal receives _{Dl_sync}Length, X is the length of descending pilot frequency code value,

Sequence constitutes the initial channel characteristic vector of i sub-district

s _{I, t} ^*Be the conjugate of t downlink frequency pilot code of i sub-district, R _{Dl_sync, (t+k-1)}It is (t+k-1) individual value of the signal that receives.

6. same-frequency cell time delay as claimed in claim 2 and power detecting method is characterized in that, in the described step 3, the initial channel characteristic vector are carried out the method for Interference Cancellation, and its step comprises:

Step 201, the sytem matrix equation with mutual interference vector substitution initial channel characteristic vector constitutes obtains system equation;

Step 202 is carried out abbreviation to the said system equation, obtains the channel characteristics vector.

7. same-frequency cell time delay as claimed in claim 6 and power detecting method is characterized in that, in the described step 202, utilize the maximum power window as constraints abbreviation system equation.

8. same-frequency cell time delay as claimed in claim 7 and power detecting method is characterized in that, in the described step 202, utilize the maximum power window as the method for constraints abbreviation system equation to be:

Step 301 is determined the maximum power window position of each initial channel characteristic vector correspondence;

Step 302 is according to above-mentioned definite maximum power window position abbreviation system equation.

9. same-frequency cell time delay as claimed in claim 2 and power detecting method is characterized in that, in the described step 4, determine cell time delay according to the position of first active path; Element power according to the channel characteristics vector of active path correspondence is determined cell power.

10. same-frequency cell time delay as claimed in claim 9 and power detecting method is characterized in that, determine that the method for the described first active path position is:

Step 401 is determined the power of corresponding element in each channel characteristics vector;

Step 402 is determined the corresponding noise gate of each channel characteristics vector;

Step 403, with the power of element in each channel characteristics vector and corresponding noise gate relatively, choosing element power is active path greater than the respective path of noise gate;

Step 404 is designated as minimum and is the pairing element of first nonzero value under selecting in the element power of each active path correspondence, and the subscript of this element power correspondence is subtracted the position that 1 gained is first active path.

11. same-frequency cell time delay as claimed in claim 10 and power detecting method is characterized in that, with the element power addition of all active path correspondences, the gained sum is the power of this sub-district.

12. same-frequency cell time delay as claimed in claim 10 and power detecting method is characterized in that, in the described step 401, and the power pow of each element correspondence _InFor:

pow _in＝h _in×h _in ^*，

Wherein, h _InBe the channel characteristics vector H of i sub-district _iIn n element, h _In ^*Be h _InConjugate complex number.

13. same-frequency cell time delay as claimed in claim 10 and power detecting method is characterized in that, in the described step 402, and six times of noise gates that are the respective channels characteristic vector of the average of each element power in each channel characteristics vector.

Images