CN100358261C - An array antenna MC-CDMA system up-link receiving method - Google Patents

Abstract

The present invention relates to an uplink receiving method of an array antenna MC-CDMA system, which comprises the steps that signals received by each array element of the array antenna are carried out with the separation of sub-carrier signals; the sub-carrier signals of each separated array element are treated by dispreading and matched filtering so as to realize the dispreading of subscriber signals and obtain the matched filtering output of subscriber sub-carrier signals; the signals belonging to the same subscriber and the same sub-carrier in the signals outputted by a matched filter on different array elements are carried out with spatial domain combination so as to obtain a spatial domain diversity gain; each obtained sub-carrier signals which are carried out with the spatial domain combination and belong to the same subscriber and the same sub-carrier are carried out with frequency domain combination so as to obtain a frequency domain diversity gain; a final decision variable of the subscriber signals after the spatial domain combination and the frequency domain combination is decided to obtain the decision result of the subscriber signals. The present invention has the advantages that processing is simple, the method is easy to realize, and the system has good receptivity because the combination of the spatial domain diversity gain and the frequency domain diversity gain is obtained.

Description

A kind of array antenna MC-CDMA system up-link receiving method

Technical field

The invention belongs to MC-CDMA cell mobile communication systems array antenna technical field.

Background technology

CDMA is a kind of topmost technology in the third generation (3G) mobile communication, and multi-carrier modulation will be the key technology of following wideband wireless transmission system.Merge CDMA technology with multi-transceiver technology, constituting multi-carrier CDMA system is one of important directions of future mobile communications development.The scheme that multi-transceiver technology combines with CDMA technology mainly contains CDMA multiple carrier (MC-CDMA), multi-carrier direct sequence spectrum CDMA (multicarrier DS-CDMA) and three kinds of principal modes of multitone modulation CDMA (MT-CDMA).Wherein, the MC-CDMA scheme also is one of the most competitive scheme of future mobile communication system owing to can adopt frequency diversity and good performance to be considered in three kinds of schemes the scheme of tool prospect.

The same with cdma system, use array antenna can improve capacity, spectrum efficiency, communication quality and the coverage of system significantly at the MC-CDMA system base-station.Existing array antenna MC-CDMA system is handled in the advanced line frequency of receiving terminal territory, and then carries out the spatial domain and handle, and frequency domain and spatial domain are handled and organically do not associated, and handles complicated.

Summary of the invention

The present invention has proposed a kind of array antenna MC-CDMA system up-link spatial domain and frequency domain merging method of reseptance for solving the problems of the technologies described above, compare with array antenna MC-CDMA system up-link receiving method in the past, the advanced line space of method of the present invention territory merges, and then carry out frequency domain and merge, the weight vector of spatial domain merging and the weight vector of frequency domain merging are organically associated, method of reseptance is handled simple, be easy to realize, and owing to obtained spatial domain, the frequency diversity gain of associating, system has good receptivity.

The technical solution adopted in the present invention is that the signal that at first each array element of array antenna is received carries out the separation of sub-carrier signal; Secondly, the sub-carrier signal of isolated each array element of institute is carried out despreading and matched filter processing, realize the despreading of subscriber signal, and the matched filtering that obtains user's sub-carrier signal is exported; Then, carry out the spatial domain merging, obtain the spatial domain diversity gain belonging to the same subcarrier signals of same user in the matched filter output signal on the different array elements; Afterwards, each sub-carrier signal that belongs to same user in the signal after more resultant spatial domain being merged carries out frequency domain and merges, and obtains the frequency diversity gain; At last, the conclusive judgement variable of resultant subscriber signal after spatial domain, frequency domain merge is adjudicated, obtain the court verdict of subscriber signal.

Below method of the present invention is discussed.

1. the separation of sub-carrier signal

Investigate array antenna MC-CDMA system up-link, array antenna is adopted in the base station, and travelling carriage adopts single antenna.Travelling carriage uplink scheme adopts traditional single antenna MC-CDMA transmission plan and QPSK modulation system.

K mobile subscriber arranged in certain cellular cell in the supposing the system.Each subcarrier of MC-CDMA transmission plan is carried identical user profile, and k the signal that the user launched can be expressed as:

$s_k\left(t\right)=\underset{l=1}{\overset{L}{\mathrm{\Σ}}}\sqrt{P_{k,l}}(b_k^I\left(t\right)c_{k,l}^I\left(t\right)\cos \left({\mathrm{\ω}}_{l}t\right)+b_k^Q\left(t\right)c_{k,l}^Q\left(t\right)\sin \left({\mathrm{\ω}}_{l}t\right))$ [formula 1]

In the formula, P _{K, l}Represent k user l (signal power of individual subcarrier of 1≤l≤L), ω _lBe the angular frequency of l subcarrier, bit period is T _s, c _k ^IAnd c _k ^QBe respectively the frequency expansion sequence of I road and Q road correspondence, its expression formula is respectively $c_k^I=[c_{k,1}^I{c}_{k,2}^l...c_{k,L}^I]$ With $c_k^Q=[c_{k,1}^Q{c}_{k,2}^Q...c_{k,L}^Q],$ Chip period T _c=T _sHomophase and quadrature signal component b _k ^IAnd b _k ^QBe expressed as respectively:

$b_k^I\left(t\right)=\underset{l=-\∞}{\overset{\∞}{\mathrm{\Σ}}}{d}_k^I{\mathrm{rect}}_T(t-{\mathrm{iT}}_s)$

[formula 2]

$b_k^Q\left(t\right)=\underset{l=-\∞}{\overset{\∞}{\mathrm{\Σ}}}{d}_k^Q{\mathrm{rect}}_T(t-{\mathrm{iT}}_s)$

In the formula, d _k ^IAnd d _k ^QBe corresponding digital signal, value is ± 1, rect _T(t) being is T in the cycle _sSquare wave.

To the MC-CDMA transmission plan, wireless channel is a frequency non-selective fading channel.The multiple low-pass impulse response of l sub-carrier channels of k user can be expressed as:

h _{K, l}(t)=ρ _{K, l}e ^{-j φ k, l}δ (t-τ _{K, l}) [formula 3]

Wherein, suppose complex channel coefficient ρ _{K, l}e ^{-j φ k, l}Be the multiple Gaussian random variable of zero-mean, ρ _{K, l}And φ _{K, l}Be respectively corresponding amplitude and phase gain, variance is σ _{K, l} ²τ _{K, l}Be the time delay of l subcarrier of user k,, suppose τ the different user different sub carrier _{K, l}Be independent identically distributed stochastic variable, [0, T _s) between evenly distribute.

Suppose that the base station adopts equidistantly linear battle array, like this base station array antenna n (=1 ..., N) signal that receives on the individual array element is:

$r_n\left(t\right)=\underset{k=1}{\overset{K}{\mathrm{\Σ}}}\underset{l=1}{\overset{L}{\mathrm{\Σ}}}\sqrt{P_{k,l}}{\mathrm{\ρ}}_{k,l}[b_k^I(t-{\mathrm{\τ}}_{k,l})c_{k,l}^I(t-{\mathrm{\τ}}_{k,l})\cos ({\mathrm{\ω}}_l(t-{\mathrm{\τ}}_{k,l})+{\mathrm{\φ}}_{k,l})$

[formula 4]

$+b_k^Q(t-{\mathrm{\τ}}_{k,l})c_{k,l}^Q(t-{\mathrm{\τ}}_{k,l})\sin ({\mathrm{\ω}}_l(t-{\mathrm{\τ}}_{k,l})+{\mathrm{\φ}}_{k,l})]a_{k,l,n}+n_n\left(t\right)$

Wherein, $a_{k,l,n}=\exp [-j\frac{2\mathrm{\πd}}{{\mathrm{\λ}}_{k,l}}(n-1)\sin \left({\mathrm{\θ}}_{k,l}\right)]$ Be the array response of l subcarrier of user k n array element, λ _{K, l}Be corresponding carrier wavelength, d is the distance between the adjacent array element, θ _{K, l}It is the angle of arrival of l subcarrier of user k.n _n(t) be additive white Gaussian noise, bilateral power spectral density is N ₀/ 2.

Like this array antenna received to resultant signal can be expressed as:

$r\left(t\right)={[r_1\left(t\right),r_2\left(t\right),\·\·\·{,r}_N\left(t\right)]}^T$

$=\underset{k=1}{\overset{K}{\mathrm{\Σ}}}\underset{l=1}{\overset{L}{\mathrm{\Σ}}}\sqrt{P_{k,l}}{\mathrm{\ρ}}_{k,l}[b_k^I(t-{\mathrm{\τ}}_{k,l})c_{k,l}^I(t-{\mathrm{\τ}}_{k,l})\cos ({\mathrm{\ω}}_l(t-{\mathrm{\τ}}_{k,l})+{\mathrm{\φ}}_{k,l})$ [formula 5]

$+b_k^Q(t-{\mathrm{\τ}}_{k,l})c_{k,l}^Q(t-{\mathrm{\τ}}_{k,l})\sin ({\mathrm{\ω}}_l(t-{\mathrm{\τ}}_{k,l})+{\mathrm{\φ}}_{k,l})]a_{k,l}+n\left(t\right)$

Wherein, () ^TBe the transposition computing, n (t)=[n ₁..., n _N] ^TBe corresponding noise vector, a _{K, l}Be the array vector of l subcarrier of k user,

a _{K, l}=[a _{K, l, 1}, a _{K, l, 2}..., a _{K, l, N}] ^T[formula 6]

Be without loss of generality, the signal of supposing the 1st user is a desired signal.The signal times that each array element is received is with the subcarrier cos (ω corresponding with the transmitting terminal modulation system _l, t), sin (ω _l, combination t), and corresponding time delay taken into account, just can realize the separation of each sub-carrier signal.To isolated the 1st the user l ' of QPSK modulation system base station array antenna (1≤l '≤L) individual subcarrier signals is:

x _1，l′(t)＝[x _1，l′，1(t)，x _1，l′，2(t)，…，x _1，l′，N(t)] ^T＝r(t)(cos(ω _l′(t-τ _1，l′))+sin(ω _l′(t-τ _1，l′)))

＝[r ₁(t)(cos(ω _l′(t-τ _1，l′))+sin(ω _l′(t-τ _1，l′)))，r ₂(t)(cos(ω _l′(t-τ _1，l′))+sin(ωo _l′(t-τ _1，l′)))，

…，r _N(t)(cos(ω _l′(t-τ _1，l′))+sin(ω _l′(t-τ _1，l′)))] ^T

[formula 7]

2. despreading and matched filter processing

Isolated sub-carrier signal is carried out despreading and matched filter processing, realize the despreading of subscriber signal and obtain the matched filtering output of user's sub-carrier signal.Base station array antenna is output as the matched filtering of i bit of the 1st the individual carrier signal of user l ':

$y_{1,l^{\′}}\left(i\right)={[y_{1,l^{\′},1},\·\·\·,y_{1,l^{\′},N}]}^T$

$=\frac{1}{T_s}{\∫}_{{\mathrm{iT}}_s+{\mathrm{\τ}}_{1,l^{\′}}}^{(i+1)T_s+{\mathrm{\τ}}_{1,l^{\′}}}{x}_{1,l^{\′}}\left(t\right)c_{1,l^{\′}}^I\left(t\right)\mathrm{dt}+j\frac{1}{T_s}{\∫}_{{\mathrm{iT}}_s+{\mathrm{\τ}}_{1,l^{\′}}}^{(i+1)T_s+{\mathrm{\τ}}_{1,l^{\′}}}{x}_{1,l^{\′}}{c}_{1,l^{\′}}^Q\left(t\right)\mathrm{dt}$ [formula 8]

$=\sqrt{P_{1,l^{\′}}}{\mathrm{\ρ}}_{1,l^{\′}}(b_1^I\left(i\right)+{\mathrm{jb}}_1^Q\left(i\right))a_{1,l^{\′}}\left(i\right)+m_{1,l^{\′}}\left(i\right)+n_{1,l^{\′}}\left(i\right)$

Wherein, m _{1, l '}(i), n _{1, l '}(i) represent total interference and noise signal respectively.

The noise of system and interference characteristic have significant effects to the empty performance that merges method of reseptance frequently that is proposed.Below the kind of system noise and interference is analyzed earlier.

1) noise

Noise item can provide as follows:

$n_{1,l^{\′}}\left(i\right)=n_{1,l^{\′}}^I\left(i\right)+{\mathrm{jn}}_{1,l^{\′}}^Q\left(i\right)$ [formula 9]

Homophase has identical variance with quadrature component

${\mathrm{\σ}}_N^{I2}={\mathrm{\σ}}_N^{Q2}={\mathrm{\σ}}_N^2/2=\frac{N_0}{{4T}_s}$ [formula 10]

2) disturb

To the MC-CDMA transmission plan, wireless channel is a frequency non-selective fading channel, still keeps orthogonality between the subcarrier, and therefore, total interference is the interference of other user's same carrier wave, comprises homophase and quadrature component, can be expressed as:

$m_{1,l^{\′}}\left(i\right)=m_{1,l^{\′}}^I\left(i\right)+{\mathrm{jm}}_{1,l^{\′}}^Q\left(i\right)$ [formula 11]

m _{1, l '} ^IAnd m _{1, l '} ^QBe respectively:

$m_{1,l^{\′}}^I\left(i\right)=\underset{k=2}{\overset{K}{\mathrm{\Σ}}}{a}_{k,l^{\′}}\sqrt{P_{k,l^{\′}}}{\mathrm{\ρ}}_{k,l^{\′}}\cos ({\mathrm{\ω}}_{l^{\′}}({\mathrm{\τ}}_{k,l^{\′}}-{\mathrm{\τ}}_{1,l^{\′}})+({\mathrm{\φ}}_{k,l^{\′}}-{\mathrm{\φ}}_{1,l^{\′}}))$

[formula 12]

$c_{1,l^{\′}}^I[(b_k^I(i-1)c_{k,l^{\′}}^I+{\mathrm{jb}}_k^Q(i-1)c_{k,l^{\′}}^Q)R_g\left({\mathrm{\τ}}_{k,l^{\′}}^{\′}\right)+(b_k^I\left(i\right)c_{k,l^{\′}}^I+{\mathrm{jb}}_k^Q\left(i\right)c_{k,l^{\′}}^Q)R_g(T_c-{\mathrm{\τ}}_{k,l^{\′}}^{\′})]$

$m_{1,l^{\′}}^Q\left(i\right)=\underset{k=2}{\overset{K}{\mathrm{\Σ}}}{a}_{k,l^{\′}}\sqrt{P_{k,l^{\′}}}{\mathrm{\ρ}}_{k,l^{\′}}\cos ({\mathrm{\ω}}_{l^{\′}}({\mathrm{\τ}}_{k,l^{\′}}-{\mathrm{\τ}}_{1,l^{\′}})+({\mathrm{\φ}}_{k,l^{\′}}-{\mathrm{\φ}}_{1,l^{\′}}))$

[formula 13]

$c_{1,l^{\′}}^Q[(b_k^I(i-1)c_{k,l^{\′}}^I+{\mathrm{jb}}_k^Q(i-1)c_{k,l^{\′}}^Q)R_g\left({\mathrm{\τ}}_{k,l^{\′}}^{\′}\right)+(b_k^I\left(i\right)c_{k,l^{\′}}^I+{\mathrm{jb}}_k^Q\left(i\right)c_{k,l^{\′}}^I)R_g(T_c-{\mathrm{\τ}}_{k,l^{\′}}^{\′})]$

In the formula, R _gBe the partial auto correlation of chip waveform (τ), be defined as follows:

$R_g\left(\mathrm{\τ}\right)=\frac{1}{T_c}{\∫}_0^{\mathrm{\τ}}g(t+T_c-\mathrm{\τ})g\left(t\right)\mathrm{dt},0\≤\mathrm{\τ}\≤T_c$ [formula 14]

Wherein, τ _{K, l '}' be the relative time delay of l subcarrier of k user with respect to the 1st the individual subcarrier of user l '.

3. the spatial domain of signal merges

Below the correlation properties of disturbing are further analyzed, draw optimum and suboptimum merging weight that the received signal spatial domain merges.Disturb correlation properties to comprise auto-correlation and their cross correlation.

1) auto-correlation

Disturb vectorial m _{1, l '} ^I(i) and m _{1, l '} ^Q(i) element m _{1, l ', n} ^I(i) and m _{1, l ', n} ^Q(i) can be regarded as a series of independent Gaussian stochastic variables.Therefore, their auto-correlation function can approximate evaluation be:

$E\left\{m_{1,l^{\′},n}^I\left(i\right)m_{1,l^{\′}m}^{I*}(i+h)\right\}=E\left\{m_{1,l^{\′},n}^Q\left(i\right)m_{1,l^{\′},n}^{Q*}(i+h)\right\}\≅{\mathrm{\σ}}_{m,1,l^{\′}}^2\mathrm{\δ}\left(h\right),1\≤n\≤N$ [formula 15]

Wherein, () ^*Be conjugate operation, δ (h) is the delta function.

The variance that can get homophase and quadrature component is:

${\mathrm{\σ}}_{m,1,l^{\′}}^2=\underset{k=2}{\overset{K}{\mathrm{\Σ}}}{P}_{k,l^{\′}}{\mathrm{\σ}}_{k,l^{\′}}^{2}G(R_g^2\left({\mathrm{\τ}}_{k,l^{\′}}^{\′}\right)+R_g^2(T_s-{\mathrm{\τ}}_{k,l^{\′}}^{\′}))$ [formula 16]

Can suppose τ _{K, l '}' be independent identically distributed stochastic variable, and [0, T _c] go up and obey evenly distribution, g (t) is to be T in the cycle _cSquare wave, can get:

${\mathrm{\σ}}_{m,1,l^{\′}}^2=\underset{k=2}{\overset{K}{\mathrm{\Σ}}}\frac{2}{3}{\mathrm{\σ}}_{k,l^{\′}}^2{P}_{k,l^{\′}}$ [formula 17]

Therefore, in-phase component adds the population variance of quadrature component and is:

${\mathrm{\σ}}_I^2={2\mathrm{\σ}}_{m,1,l^{\′}}^2$ [formula 18]

2) cross-correlation

m _{1, l ' n} ^I(i) and m _{1, l ', n '} ^I(i) cross-correlation between is (perhaps at m _{1, l ', n} ^Q(i) and m _{1, l ', n '} ^Q(i) be that the spatial domain of received signal on different array element n and n ' is relevant the cross-correlation between).It can be derived out by the cross-correlation function of linear array, and the cross-correlation function of linear array is expressed as follows:

$E\left\{a_{k,l^{\′}}\left(t\right)a_{k,l^{\′}}^H(t+\mathrm{\τ})\right\}=J_0\left(2\mathrm{\π}{f}_d\mathrm{\τ}\right)\·R_{k,l^{\′}}$ [formula 19]

Wherein, () ^HThe expression conjugate transpose, f _dIt is maximum Doppler frequency-shift.R _{K, l '}Be k the individual subcarrier array vector of user l ' a of expression _{K, l '}The N of correlation * N Hemitian Toeplitz matrix, its real part and imaginary part can be expressed as respectively:

$\mathrm{Re}\left\{R_{k,l^{\′}}(n^{\′},n)\right\}=J_0\left(r_{k,l^{\′}}(n^{\′},n)\right)+2\underset{q=1}{\overset{\∞}{\mathrm{\Σ}}}{J}_{2q}\left(r_{k,l^{\′}}(n^{\′},n)\right)\·\cos \left(2q{\mathrm{\θ}}_{k,l^{\′}}\right)$ [formula 20]

$\mathrm{Im}\left\{R_{k,l^{\′}}(n^{\′},n)\right\}=2\underset{q=1}{\overset{\∞}{\mathrm{\Σ}}}{J}_{2q+1}\left(r_{k,l^{\′}}(n^{\′},n)\right)\·\sin \left((2q+1){\mathrm{\θ}}_{k,l^{\′}}\right)$ [formula 21]

In the formula, J _qBe first kind q rank Bessel functions,

r _{K, l '}(n ', n)=2 π d|n '-n|/λ _{K, l '}[formula 22]

3) total interference plus noise correlation matrix

Definition interference correlation matrix M (h) is:

$M\left(h\right)=E\{m_{1,l^{\′}}^I\left(i\right)m_{1,l^{\′}}^{\mathrm{IH}}(i+h)+m_{1,l^{\′}}^Q\left(k\right)m_{1,l^{\′}}^{\mathrm{QH}}(i+h)\}=\mathrm{M\δ}\left(h\right)$ [formula 23]

Matrix M can be derived by formula 17 and 18:

$M=2\underset{k=2}{\overset{K}{\mathrm{\Σ}}}\frac{2}{3}{\mathrm{\σ}}_{k,l^{\′}}^2{P}_{k,l^{\′}}{a}_{k,l^{\′}}{a}_{k,l^{\′}}^H$ [formula 24]

The distribution function f (θ) that supposes the angle of arrival is equally distributed within [0,2 π], and formula 24 can further be expressed as:

$M=2{\mathrm{\σ}}_{m,1,l^{\′}}^2{\∫}_{\mathrm{\θ}}a\left(\mathrm{\θ}\right)a^H\left(\mathrm{\θ}\right)\·f\left(\mathrm{\θ}\right)\mathrm{d\θ}={\mathrm{\σ}}_I^2{\∫}_{\mathrm{\θ}}R\left(\mathrm{\θ}\right)f\left(\mathrm{\θ}\right)\mathrm{d\θ}$ [formula 25]

R (θ) is the matrix in formula 20 and the formula 21, so the element of the row of the n ' row n in the matrix M is:

$m_{n^{\′},n}={\mathrm{\σ}}_I^2{J}_0\left(r(n^{\′},n)\right)$ [formula 26]

Therefore, total interference plus noise correlation matrix is:

$R_T=E\left\{(m_{1,l^{\′}}+n_{1,l^{\′}}){(m_{1,l^{\′}}+n_{1,l^{\′}})}^H\right\}=M+{\mathrm{\σ}}_N^{2}I$ [formula 27]

In the formula, I is a unit matrix.

R _TDetermining the optimum weight vector that merges in spatial domain of following formula, promptly the optimum weight vector that merges in the spatial domain of the 1st the individual carrier wave of user l ' is:

$w_{1,l^{\′},\mathrm{opt}}^s=\mathrm{\α}{R}_T^{-1}{a}_{1,l^{\′}}^H$ [formula 28]

Wherein, a _{1, l '} ^HBe the Hermite conversion of the individual subcarrier array response of desired user l ', α is a constant, can be taken as 1.

Work as R _TWhen approaching unit matrix, interference plus noise and can be considered to empty white noise frequently, promptly have

$R_T=M+{\mathrm{\σ}}_N^{2}I=({\mathrm{\σ}}_I^2+{\mathrm{\σ}}_N^2)I={\mathrm{\σ}}^{2}I$ [formula 29]

Wherein, σ _I ²Be defined in formula 18, σ _N ²It is the noise variance that is shown in formula 10.Like this, can obtain suboptimum spatial domain merging weight vector is:

$w_{1,l^{\′}}^s\left(i\right)=[w_{1,l^{\′},1}^s\left(i\right),w_{1,l^{\′},2}^s\left(i\right),...,w_{1,l^{\′},N}^s\left(i\right)]=\mathrm{\α}{a}_{1,l^{\′}}^H\left(i\right)$ [formula 30]

The present invention only uses the suboptimum spatial domain of having simplified to merge weight, compare with the optimum merging, systematic function descends little, but because the suboptimum spatial domain merges the knowledge that weight only need be known user's subcarrier array vector, do not merge the contrary of the necessary interference plus noise correlation matrix of weight and do not need to calculate optimum spatial domain, greatly reduce the complexity of weight calculation.The signal of the 1st the individual carrier wave of user l ' merges i the bit in back through the spatial domain and is output as:

$z_{1,l^{\′}}\left(i\right)=w_{1,l^{\′}}^s\left(i\right)y_{1,l^{\′}}\left(i\right)=\sqrt{P_{1,l^{\′}}}{\mathrm{\ρ}}_{1,l^{\′}}(b_1^I\left(i\right)+{\mathrm{jb}}_1^Q\left(i\right))\left|a_{1,l^{\′}}\left(i\right)\right|+{\mathrm{\η}}_{1,l^{\′}}\left(i\right)$ [formula 31]

Wherein, $\left|a_{1,l^{\′}}\right|=\frac{a_{1,l^{\′}}^H\·a_{1,l^{\′}}}{\sqrt{a_{1,l^{\′}}^H\·a_{1,l^{\′}}}},{\mathrm{\η}}_{1,l^{\′}}\left(i\right)$ For the spatial domain merge that the back is disturbed and noise item with.

Corresponding homophase and quadrature judgment variables are:

$z_{1,l^{\′}}^I\left(i\right)=\mathrm{Re}\left\{z_{1,l^{\′}}\left(i\right)\right\}=\sqrt{P_{1,l^{\′}}}{\mathrm{\ρ}}_{1.l^{\′}}{b}_1^I\left(i\right)\left|a_{1,l^{\′}}\right|+{\mathrm{\η}}_{1,l^{\′}}^I\left(i\right)$

[formula 32]

$z_{1,l^{\′}}^Q\left(i\right)=\mathrm{Im}\left\{z_{1,l^{\′}}\left(i\right)\right\}=\sqrt{P_{1,l^{\′}}}{\mathrm{\ρ}}_{1.l^{\′}}{b}_1^Q\left(i\right)\left|a_{1,l^{\′}}\right|+{\mathrm{\η}}_{1,l^{\′}}^Q\left(i\right)$

4. signal frequency domain combination

Each subcarrier to the same user of MC-CDMA scheme carries identical user profile.The output signal that the present invention merges each subcarrier spatial domain is carried out frequency domain again and is merged, and adopts high specific to merge (MRC), and the high specific on the individual subcarrier of l ' merges weight and is:

$w_{1,l^{\′}}^f=\left|a_{1,l^{\′}}\right|$ [formula 33]

| a _{1, l '}| will be estimated when merging, so the weight that frequency domain merges does not need to reappraise in the signal spatial domain.

Like this, through the conclusive judgement variable after the empty merging frequently be:

$Z_1\left(i\right)=\underset{l^{\′}=1}{\overset{L}{\mathrm{\Σ}}}{w}_{1,l^{\′}}^f{z}_{1,l^{\′}}\left(i\right)$ [formula 34]

Corresponding homophase and quadrature judgment variables are:

$Z_1^I\left(i\right)=\mathrm{Re}\left\{Z_1\left(i\right)\right\}$

[formula 35]

$Z_1^Q\left(i\right)=\mathrm{Im}\left\{Z_1\left(i\right)\right\}$

5. the judgement of signal

The present invention utilizes simple polarity decision method to adjudicate to resulting conclusive judgement variable, obtains the court verdict of user's sub-carrier signal.To the QPSK modulation system, be:

$b_1^I\left(i\right)=\left\{\begin{array}{c}1,Z_1^I\left(i\right)>0\\ -1,Z_1^I\left(i\right)<0\end{array}\right.$ [formula 36]

$b_1^Q\left(i\right)=\left\{\begin{array}{c}1,Z_1^Q\left(i\right)>0\\ -1,Z_1^Q\left(i\right)<0\end{array}\right.$ [formula 37]

Beneficial effect of the present invention:

At first, because isolated sub-carrier signal is carried out despreading and matched filter processing earlier, suppressed the multiple access interference to a great extent, to make the signal processing of receiver based on disturbing repressed signal to carry out, stability and performance that this can improve receiver greatly make the method for reseptance that is proposed have practical outstanding advantage.

Secondly, the spatial domain of signal merges has adopted suboptimum to merge weight, does not need to calculate optimum spatial domain and merges the contrary of the necessary interference plus noise correlation matrix of weight, greatly reduce the complexity of weight calculation, and systematic function descends very little; The frequency domain that carries out afterwards merges the high specific merging method that adopted, and merging weight does not need to reappraise, and it is simple that method of reseptance is handled, and is easy to realize.

At last, the empty method of reseptance that frequently merges that is proposed has obtained spatial domain, frequency diversity gain by spatial domain, frequency domain merging, makes system have good receptivity.

Description of drawings

Fig. 1 is that array antenna MC-CDMA system up-link (arbitrary user k) receives structured flowchart;

Fig. 2 is the simulation result of error rate of system (BER) when adopting optimum and suboptimum merging weight vector;

Fig. 3 is the not error performance of simultaneity factor of array number.

Embodiment

Below in conjunction with accompanying drawing method of the present invention is described in detail.

Method of the present invention is applicable to the array antennas mobile communication system of any employing MC-CDMA transmission plan.

Receive structured flowchart with reference to the array antenna MC-CDMA system up-link of Fig. 1, a kind of concrete steps of array antenna MC-CDMA system up-link receiving method comprise, to arbitrary user (k):

Step 1, the signal r that array antenna the 1st array element is received ₁(t) send into L carrier signal separation module (1-1-1) respectively, (1-2-1) ..., (1-L-1) in, obtain output signal x _{K, 1,1}(t)=r ₁(t) (cos (ω ₁(t-τ _{K, l}))+sin (ω ₁(t-τ _{K, l}))), x _{K, 2,1}(t)=r ₁(t) (cos (ω ₂(t-τ _{K, 2}))+sin (ω ₂(t-τ _{K, 2}))) ..., x _{K, L, 1}(t)=r ₁(t) (cos (ω _L(t-τ _{K, L}))+sin (ω _L(t-τ _{K, L}))); The signal r that the 2nd array element is received simultaneously ₂(t) send into L carrier signal separation module (1-1-2) respectively, (1-2-2) ..., (1-L-2) in, obtain output signal x _{K, 1,2}(t)=r ₂(t) (cos (ω ₁(t-τ _{K, l}))+sin (ω ₁(t-τ _{K, l}))), x _{K, 2,2}(t)=r ₂(t) (cos (ω ₂(t-τ _{K, 2}))+sin (ω ₂(t-τ _{K, 2}))) ..., x _{K, L, 2}(t)=r ₂(t) (cos (ω _L(t-τ _{K, L}))+sin (ω _L(t-τ _{K, L}))); ...; Simultaneously with N the signal r that array element received _N(t) send into L carrier signal separation module (1-1-N) respectively, (1-2-N) ..., (1-L-N) in, obtain output signal x _{K, 1, N}(t)=r _N(t) (cos (ω ₁(t-τ _{K, 1}))+sin (ω ₁(t-τ _{K, 1}))), x _{K, 2, N}(t)=r _N(t) (cos (ω ₂(t-τ _{K, 2}))+sin (ω ₂(t-τ _{K, 2}))) ..., x _{K, L, N}(t)=r _N(t) (cos (ω _L(t-τ _{K, L}))+sin (ω _L(t-τ _{K, L})));

Step 2 is with signal x _{K, 1,1}(t), x _{K, 2,1}(t) ..., x _{K, L, 1}(t) send into L despreading and matched filtering module (2-1-1) respectively, (2-2-1) ..., (2-L-1), carry out despreading and matched filter processing, obtain the i bit signal:

$y_{k,\mathrm{1,1}}\left(i\right)=\frac{1}{T_s}{\&Integral;}_{{\mathrm{iT}}_s+{\mathrm{\&tau;}}_{k,1}}^{(i+1)T_s+{\mathrm{\&tau;}}_{k,1}}{x}_{k,\mathrm{1,1}}\left(t\right)c_{k,1}^I\left(t\right)\mathrm{dt}+j\frac{1}{T_s}{\&Integral;}_{{\mathrm{iT}}_s+{\mathrm{\&tau;}}_{k,1}}^{(i+1)T_s+{\mathrm{\&tau;}}_{k,1}}{x}_{k,1,1}{c}_{k,1}^Q\left(t\right)\mathrm{dt},$

$y_{k,\mathrm{2,1}}\left(i\right)=\frac{1}{T_s}{\&Integral;}_{{\mathrm{iT}}_s+{\mathrm{\&tau;}}_{k,2}}^{(i+1)T_s+{\mathrm{\&tau;}}_{k,2}}{x}_{k,\mathrm{2,1}}\left(t\right)c_{k,2}^I\left(t\right)\mathrm{dt}+j\frac{1}{T_s}{\&Integral;}_{{\mathrm{iT}}_s+{\mathrm{\&tau;}}_{k,2}}^{(i+1)T_s+{\mathrm{\&tau;}}_{k,2}}{x}_{k,2,1}{c}_{k,2}^Q\left(t\right)\mathrm{dt},...,$

$y_{k,L,1}\left(i\right)=\frac{1}{T_s}{\&Integral;}_{{\mathrm{iT}}_s+{\mathrm{\&tau;}}_{k,L}}^{(i+1)T_s+{\mathrm{\&tau;}}_{k,L}}{x}_{k,L,1}\left(t\right)c_{k,1}^I\left(t\right)\mathrm{dt}+j\frac{1}{T_s}{\&Integral;}_{{\mathrm{iT}}_s+{\mathrm{\&tau;}}_{k,L}}^{(i+1)T_s+{\mathrm{\&tau;}}_{k,L}}{x}_{k,L,1}{c}_{k,1}^Q\left(t\right)\mathrm{dt};$

With signal x _{K, 1,2}(t), x _{K, 2,2}(t) ..., x _{K, L, 2}(t) send into L despreading and matched filtering module (2-1-2) respectively, (2-2-2) ..., (2-L-2) in, obtain output signal:

$y_{k,\mathrm{1,2}}\left(i\right)=\frac{1}{T_s}{\&Integral;}_{{\mathrm{iT}}_s+{\mathrm{\&tau;}}_{k,1}}^{(i+1)T_s+{\mathrm{\&tau;}}_{k,1}}{x}_{k,1,2}\left(t\right)c_{k,1}^I\left(t\right)\mathrm{dt}+j\frac{1}{T_s}{\&Integral;}_{{\mathrm{iT}}_s+{\mathrm{\&tau;}}_{k,1}}^{(i+1)T_s+{\mathrm{\&tau;}}_{k,1}}{x}_{k,1,2}{c}_{k,1}^Q\left(t\right)\mathrm{dt},$

$y_{k,\mathrm{2,2}}\left(i\right)=\frac{1}{T_s}{\&Integral;}_{{\mathrm{iT}}_s+{\mathrm{\&tau;}}_{k,2}}^{(i+1)T_s+{\mathrm{\&tau;}}_{k,2}}{x}_{k,\mathrm{2,2}}\left(t\right)c_{k,2}^I\left(t\right)\mathrm{dt}+j\frac{1}{T_s}{\&Integral;}_{{\mathrm{iT}}_s+{\mathrm{\&tau;}}_{k,2}}^{(i+1)T_s+{\mathrm{\&tau;}}_{k,2}}{x}_{k,2,2}{c}_{k,2}^Q\left(t\right)\mathrm{dt},...,$

$y_{k,L,2}\left(i\right)=\frac{1}{T_s}{\&Integral;}_{{\mathrm{iT}}_s+{\mathrm{\&tau;}}_{k,L}}^{(i+1)T_s+{\mathrm{\&tau;}}_{k,L}}{x}_{k,L,2}\left(t\right)c_{k,1}^I\left(t\right)\mathrm{dt}+j\frac{1}{T_s}{\&Integral;}_{{\mathrm{iT}}_s+{\mathrm{\&tau;}}_{k,L}}^{(i+1)T_s+{\mathrm{\&tau;}}_{k,L}}{x}_{k,L,2}{c}_{k,1}^Q\left(t\right)\mathrm{dt};$

With signal x _{K, 1, N}(t), x _{K, 2, N}(t) ..., x _{K, L, N}(t) send into despreading and matched filtering module (2-1-N) respectively, (2-2-N) ..., (2-L-N) in, obtain output signal:

$y_{k,1,N}\left(i\right)=\frac{1}{T_s}{\&Integral;}_{{\mathrm{iT}}_s+{\mathrm{\&tau;}}_{k,1}}^{(i+1)T_s+{\mathrm{\&tau;}}_{k,1}}{x}_{k,1,N}\left(t\right)c_{k,1}^I\left(t\right)\mathrm{dt}+j\frac{1}{T_s}{\&Integral;}_{{\mathrm{iT}}_s+{\mathrm{\&tau;}}_{k,1}}^{(i+1)T_s+{\mathrm{\&tau;}}_{k,1}}{x}_{k,1,N}{c}_{k,1}^Q\left(t\right)\mathrm{dt},$

$y_{k,2,N}\left(i\right)=\frac{1}{T_s}{\&Integral;}_{{\mathrm{iT}}_s+{\mathrm{\&tau;}}_{k,2}}^{(i+1)T_s+{\mathrm{\&tau;}}_{k,2}}{x}_{k,2,N}\left(t\right)c_{k,2}^I\left(t\right)\mathrm{dt}+j\frac{1}{T_s}{\&Integral;}_{{\mathrm{iT}}_s+{\mathrm{\&tau;}}_{k,2}}^{(i+1)T_s+{\mathrm{\&tau;}}_{k,2}}{x}_{k,2,N}{c}_{k,2}^Q\left(t\right)\mathrm{dt},...,$

$y_{k,L,N}\left(i\right)=\frac{1}{T_s}{\&Integral;}_{{\mathrm{iT}}_s+{\mathrm{\&tau;}}_{k,L}}^{(i+1)T_s+{\mathrm{\&tau;}}_{k,L}}{x}_{k,L,N}\left(t\right)c_{k,1}^I\left(t\right)\mathrm{dt}+j\frac{1}{T_s}{\&Integral;}_{{\mathrm{iT}}_s+{\mathrm{\&tau;}}_{k,L}}^{(i+1)T_s+{\mathrm{\&tau;}}_{k,L}}{x}_{k,L,N}{c}_{k,1}^Q\left(t\right)\mathrm{dt};$

Step 3 is with N matched filtering output signal y _{K, 1,1}(i), y _{K, 1,2}(i) ..., y _{K, 1, N}(i) send into the spatial domain and merge module (3-1), obtain vector y _{K, 1}(i)=[y _{K, 1,1}(i), y _{K, 1,2}(i) ..., y _{K, 1, N}(i)] ^T, merge weight vector by the spatial domain $w_{k,1}^s\left(i\right)=[w_{k,1,1}^s\left(i\right),w_{k,1,2}^s\left(i\right),...,w_{k,1,N}^s\left(i\right)],$ The spatial domain of finishing the 1st sub-carrier signal of user k merges, and obtains the signal after the spatial domain merges $z_{k,1}\left(i\right)=w_{k,1}^s\left(i\right)\&CenterDot;y_{k,1}\left(i\right);$ Simultaneously with N matched filtering output signal y _{K, 2,1}(i), y _{K, 2,2}(i) ..., y _{K, 2, N}(i) send into the spatial domain and merge module (3-2), obtain vector y _{K, 2}(i)=[y _{K, 2,1}(i), y _{K, 2,2}(i) ..., y _{K, 2, N}(i)] ^T, merge weight vector by the spatial domain $w_{k,2}^s\left(i\right)=[w_{k,\mathrm{2,1}}^s\left(i\right),w_{k,\mathrm{2,2}}^s\left(i\right),...,w_{k,2,N}^s\left(i\right)],$ The spatial domain of finishing the 2nd sub-carrier signal of user k merges, and obtains the signal after the spatial domain merges $z_{k,2}\left(i\right)=w_{k,2}^s\left(i\right)\&CenterDot;y_{k,2}\left(i\right),...,$ Simultaneously with N matched filtering output signal y _{K, L, 1}(i), y _{K, L, 2}(i) ..., y _{K, L, N}(i) send into the spatial domain and merge module (3-L), obtain vector y _{K, L}(i)=[y _{K, L, 1}(i), y _{K, L, 2}(i) ..., y _{K, L, N}(i)] ^T, merge weight vector by the spatial domain $w_{k,L}^s\left(i\right)=[w_{k,L,1}^s\left(i\right),w_{k,L,2}^s\left(i\right),...,w_{k,L,N}^s\left(i\right)],$ The spatial domain of finishing L sub-carrier signal of user k merges, and obtains the signal after the spatial domain merges $z_{k,L}\left(i\right)=w_{k,L}^s\left(i\right)\&CenterDot;y_{k,L}\left(i\right);$

Step 4 is with L sub-carrier signal z after the merging of spatial domain _{K, 1}(i), z _{K, 2}(i) ..., z _{K, L}(i) send into carrier wave and merge module (4), obtain vector z _k(i)=[z _{K, 1}(i), z _{K, 2}(i) ..., z _{K, L}(i)] ^T, merge weight vector by frequency domain $w_k^f\left(i\right)=[w_{k,1}^f\left(i\right),w_{k,2}^f\left(i\right),\&CenterDot;\&CenterDot;\&CenterDot;,w_{k,L}^f\left(i\right)]$ Finish the merging of multi-carrier signal, obtain the final judgment variables of user k $Z_k\left(i\right)=w_k^f\left(i\right)\&CenterDot;z_k\left(i\right);$

Step 5 is with final judgment variables Z _k(i) send into signal decision module (5) and carry out polarity decision, obtain the court verdict of arbitrary user (k) signal.

A kind of array antenna MC-CDMA system up-link receiving method, the spatial domain that it is characterized in that step 3 merge and to be based on suboptimum and to merge that weight vector carries out, and the weight vector of l carrier signal spatial domain merging of k user is $w_{k,l}^s\left(i\right)=\mathrm{\&alpha;}{a}_{k,l}^H\left(i\right).$

A kind of array antenna MC-CDMA system up-link receiving method is characterized in that the carrier wave merging in the step 4 is undertaken by the high specific merging criterion, and k user's multi-carrier signal merges weight vector and is $w_k^f\left(i\right)=\left[\right|a_{k,1}\left(i\right)|,|a_{k,2}\left(i\right)|,...,|a_{k,L}\left(i\right)\left|\right].$

Fig. 2 and Fig. 3 have provided the performance simulation result of a kind of array antenna MC-CDMA system up-link receiving method that adopts the present invention's proposition.Supposing the system has reached synchronously in emulation is crossed, and the array element distance of the even linear battle array of employing is λ/2, if there is not channel fading, all transmit a signal to and have identical power when reaching the base station so, and Normalized Signal/Noise Ratio is E _b/ N ₀=10dB, the spread processing gain is 128 with sub-carrier number, and channel is the Rayleigh slow fading channel, and the user is distributed in the sub-district randomly, and its ripple reaches the angle and evenly distributes between [0,2 π].

Fig. 2 has provided the simulation result when number of users BER performance when the inventive method does not adopt optimum and suboptimum merging weight vector respectively simultaneously.As can be seen from Figure 2 adopt suboptimum to merge weight vector and compare with adopting the optimum weight vector that merges, the BER decreased performance of system is very little, but can reduce to calculate the amount of calculation of weight greatly, and it is suitable therefore adopting suboptimum merging method.

Fig. 3 has provided the BER performance that adopts the inventive method system when the array number of array antenna is respectively 1,3 and 5.As can be seen from Figure 3, along with the increase of array number,, improved the performance of system significantly owing to obtained bigger space-frequency diversity gain.

Claims (3)

1. the big line MC-CDMA of an array system up-link method of reseptance is characterized in that comprising following receiving step, to arbitrary user k:

Step 1, the signal r that array antenna the 1st array element is received ₁(t) send into the pairing L of the 1st array element carrier signal separation module (1-1-1) respectively, (1-2-1) ..., (1-L-1) in, obtain output signal

x _k，1，1(t)＝r ₁(t)(cos(ω ₁(t-τ _k，1))+sin(ω ₁(t-τ _k，1)))，

x _k，2，1(t)＝r ₁(t)(cos(ω ₂(t-τ _k，2))+sin(ω ₂(t-τ _k，2)))，...，

x _{K, L, 1}(t)=r ₁(t) (cos (ω _L(t-τ _{K, L}))+sin (ω _L(t-τ _{K, L}))); The signal r that the 2nd array element is received simultaneously ₂(t) send into the pairing L of the 2nd array element carrier signal separation module (1-1-2) respectively, (1-2-2) ..., (1-L-2) in, obtain output signal x _{K, 1,2}(t)=r ₂(t) (cos (ω ₁(t-τ _{K, 1}))+sin (ω ₁(t-τ _{K, 1}))), x _{K, 2,2}(t)=r ₂(t) (cos (ω ₂(t-τ _{K, 2}))+sin (ω ₂(t-τ _{K, 2}))) ..., x _{K, L, 2}(t)=r ₂(t) (cos (ω _L(t-τ _{K, L}))+sin (ω _L(t-τ _{K, L}))); ...; Simultaneously with N the signal r that array element received _N(t) send into the pairing L of N array element carrier signal separation module (1-1-N) respectively, (1-2-N) ..., (1-L-N) in, obtain output signal x _{K, 1, N}(t)=r _N(t) (cos (ω ₁(t-τ _{K, 1}))+sin (ω ₁(t-τ _{K, 1}))),

x _k，2，N(t)＝r _N(t)(cos(ω ₂(t-τ _k，2))+sin(ω ₂(t-τ _k，2)))，...，

x _k，L，N(t)＝r _N(t)(cos(ω _L(t-τ _k，L))+sin(ω _L(t-τ _k，L)))；

Step 2 is with signal x _{K, 1,1}(t), x _{K, 2,1}(t) ..., x _{K, L, 1}(t) send into the pairing L of the 1st an array element despreading and matched filtering module (2-1-1) respectively, (2-2-1) ..., (2-L-1), carry out despreading and matched filter processing, obtain the i bit signal:

$y_{k,\mathrm{1,1}}\left(i\right)=\frac{1}{T_s}{\&Integral;}_{{\mathrm{iT}}_s+{\mathrm{\&tau;}}_{k,1}}^{(i+1)T_s+{\mathrm{\&tau;}}_{k,1}}{x}_{k,\mathrm{1,1}}\left(t\right)c_{k,1}^I\left(t\right)\mathrm{dt}+j\frac{1}{T_s}{\&Integral;}_{i{T}_s+{\mathrm{\&tau;}}_{k,1}}^{(i+1)T_s+{\mathrm{\&tau;}}_{k,1}}{x}_{k,\mathrm{1,1}}\left(t\right)c_{k,1}^Q\left(t\right)\mathrm{dt},$

$y_{k,\mathrm{2,1}}\left(i\right)=\frac{1}{T_s}{\&Integral;}_{{\mathrm{iT}}_s+{\mathrm{\&tau;}}_{k,2}}^{(i+1)T_s+{\mathrm{\&tau;}}_{k,2}}{x}_{k,\mathrm{2,1}}\left(t\right)c_{k,2}^I\left(t\right)\mathrm{dt}+j\frac{1}{T_s}{\&Integral;}_{i{T}_s+{\mathrm{\&tau;}}_{k,2}}^{(i+1)T_s+{\mathrm{\&tau;}}_{k,2}}{x}_{k,,21}\left(t\right)c_{k,2}^Q\left(t\right)\mathrm{dt},...,$

$y_{k,L,l}\left(i\right)=\frac{1}{T_s}{\&Integral;}_{i{T}_s+{\mathrm{\&tau;}}_{k,L}}^{(i+1)T_s+{\mathrm{\&tau;}}_{k,1}}{x}_{k,L,l}\left(t\right)c_{k,1}^l\left(t\right)\mathrm{dt}+j\frac{1}{T_s}{\&Integral;}_{{\mathrm{iT}}_s+{\mathrm{\&tau;}}_{k,1}}^{(i+1)T_s+{\mathrm{\&tau;}}_{k,1}}{x}_{k,L,1}\left(t\right)c_{k,1}^Q\left(t\right)\mathrm{dt};$

With signal x _{K, 1,2}(t), x _{K, 2,2}(t) ..., x _{K, L, 2}(t) send into the pairing L of the 2nd an array element despreading and matched filtering module (2-1-2) respectively, (2-2-2) ..., (2-L-2) in, obtain output signal:

$y_{k,1,2}\left(i\right)=\frac{1}{T_s}{\&Integral;}_{{\mathrm{iT}}_s+{\mathrm{\&tau;}}_{k,1}}^{(i+1)T_s+{\mathrm{\&tau;}}_{k,1}}{x}_{k,1,2}\left(t\right)c_{k,1}^I\left(t\right)\mathrm{dt}+j\frac{1}{T_s}{\&Integral;}_{i{T}_s+{\mathrm{\&tau;}}_{k,1}}^{(i+1)T_s+{\mathrm{\&tau;}}_{k,1}}{x}_{k,1,2}\left(t\right)c_{k,1}^Q\left(t\right)\mathrm{dt},$

$y_{k,2,2}\left(i\right)=\frac{1}{T_s}{\&Integral;}_{{\mathrm{iT}}_s+{\mathrm{\&tau;}}_{k,2}}^{(i+1)T_s+{\mathrm{\&tau;}}_{k,2}}{x}_{k,2,2}\left(t\right)c_{k,2}^I\left(t\right)\mathrm{dt}+j\frac{1}{T_s}{\&Integral;}_{i{T}_s+{\mathrm{\&tau;}}_{k,2}}^{(i+1)T_s+{\mathrm{\&tau;}}_{k,2}}{x}_{k,2,2}\left(t\right)c_{k,2}^Q\left(t\right)\mathrm{dt},...,$

$y_{k,L,2}\left(i\right)=\frac{1}{T_s}{\&Integral;}_{{\mathrm{iT}}_s+{\mathrm{\&tau;}}_{k,L}}^{(i+1)T_s+{\mathrm{\&tau;}}_{k,L}}{x}_{k,L,2}\left(t\right)c_{k,L}^I\left(t\right)\mathrm{dt}+j\frac{1}{T_s}{\&Integral;}_{i{T}_s+{\mathrm{\&tau;}}_{k,L}}^{(i+1)T_s+{\mathrm{\&tau;}}_{k,L}}{x}_{k,L,2}\left(t\right)c_{k,L}^Q\left(t\right)\mathrm{dt},$

With signal x _{K, 1, N}(t), x _{K, 2, N}(t) ..., x _{K, L, N}(t) send into the pairing L of a N array element despreading and matched filtering module (2-1-N) respectively, (2-2-N) ..., (2-L-N) in, obtain output signal:

$y_{k,1,N}\left(i\right)=\frac{1}{T_s}{\&Integral;}_{{\mathrm{iT}}_s+{\mathrm{\&tau;}}_{k,1}}^{(i+1)T_s+{\mathrm{\&tau;}}_{k,1}}{x}_{k,1,N}\left(t\right)c_{k,1}^I\left(t\right)\mathrm{dt}+j\frac{1}{T_s}{\&Integral;}_{i{T}_s+{\mathrm{\&tau;}}_{k,1}}^{(i+1)T_s+{\mathrm{\&tau;}}_{k,1}}{x}_{k,1,N}\left(t\right)c_{k,1}^Q\left(t\right)\mathrm{dt},$

$y_{k,2,N}\left(i\right)=\frac{1}{T_s}{\&Integral;}_{{\mathrm{iT}}_s+{\mathrm{\&tau;}}_{k,2}}^{(i+1)T_s+{\mathrm{\&tau;}}_{k,2}}{x}_{k,2,N}\left(t\right)c_{k,2}^I\left(t\right)\mathrm{dt}+j\frac{1}{T_s}{\&Integral;}_{i{T}_s+{\mathrm{\&tau;}}_{k,2}}^{(i+1)T_s+{\mathrm{\&tau;}}_{k,2}}{x}_{k,2,N}\left(t\right)c_{k,2}^Q\left(t\right)\mathrm{dt},...,$

$y_{k,L,N}\left(i\right)=\frac{1}{T_s}{\&Integral;}_{{\mathrm{iT}}_s+{\mathrm{\&tau;}}_{k,L}}^{(i+1)T_s+{\mathrm{\&tau;}}_{k,L}}{x}_{k,L,N}\left(t\right)c_{k,L}^I\left(t\right)\mathrm{dt}+j\frac{1}{T_s}{\&Integral;}_{i{T}_s+{\mathrm{\&tau;}}_{k,L}}^{(i+1)T_s+{\mathrm{\&tau;}}_{k,L}}{x}_{k,L,N}\left(t\right)c_{k,L}^Q\left(t\right)\mathrm{dt},$

Step 3 is with N matched filtering output signal y _{K, 1,1}(i), y _{K, 1,2}(i) ..., y _{K, 1, N}(i) send into the 1st the pairing spatial domain of subcarrier and merge module (3-1), obtain vector y _{K, 1}(i)=[y _{K, 1,1}(i), y _{K, 1,2}(i) ..., y _{K, 1, N}(i)] ^T, merge weight vector by the spatial domain $w_{k,1}^s\left(i\right)=[w_{k,l,1}^s\left(i\right),w_{k,l,2}^s\left(i\right),...,w_{k,l,N}^s\left(i\right)],$ The spatial domain of finishing the 1st sub-carrier signal of user k merges, and obtains the signal after the spatial domain merges $z_{k,l}\left(i\right)=w_{k,l}^s\left(i\right)\&CenterDot;y_{k,l}\left(i\right);$ Simultaneously with N matched filtering output signal y _{K, 2,1}(i), y _{K, 2,2}(i) ..., y _{K, 2, N}(i) send into the 2nd the pairing spatial domain of subcarrier and merge module (3-2), obtain vector y _{K, 2}(i)=[y _{K, 2,1}(i), y _{K, 2,2}(i) ..., y _{K, 2, N}(i)] ^T, merge weight vector by the spatial domain $w_{k,2}^s\left(i\right)=[w_{k,\mathrm{2,1}}^s\left(i\right),w_{k,\mathrm{2,2}}^s\left(i\right),...,w_{k,2,N}^s\left(i\right)],$ The spatial domain of finishing the 2nd sub-carrier signal of user k merges, and obtains the signal after the spatial domain merges $z_{k,2}\left(i\right)=w_{k,2}^s\left(i\right)\&CenterDot;y_{k,2}\left(i\right),...,$ Simultaneously with N matched filtering output signal y _{K, L, 1}(i), y _{K, L, 2}(i) ..., y _{K, L, N}(i) send into L the pairing spatial domain of subcarrier and merge module (3-L), obtain vector y _{K, L}(i)=[y _{K, L, 1}(i), y _{K, L, 2}(i) ..., y _{K, L, N}, (i)] ^T, merge weight vector by the spatial domain $w_{k,L}^s\left(i\right)=[w_{k,L,1}^s\left(i\right),w_{k,L,2}^s\left(i\right),...,w_{k,L,N}^s\left(i\right)],$ The spatial domain of finishing L sub-carrier signal of user k merges, and obtains the signal after the spatial domain merges $z_{k,L}\left(i\right)=w_{k,L}^s\left(i\right)\&CenterDot;y_{k,L}\left(i\right);$

Step 4 is with L sub-carrier signal z after the merging of spatial domain _{K, 1}(i), z _{K, 2}(i) ..., z _{K, L}(i) send into carrier wave and merge module (4), obtain vector z _k(i)=[z _{K, 1}(i), z _{K, 2}(i) ..., z _{K, L}(i)] ^T, merge weight vector by frequency domain $w_k^f\left(i\right)=[w_{k,1}^f\left(i\right),w_{k,2}^f\left(i\right),...,w_{k,L}^f\left(i\right)]$ Finish the merging of multi-carrier signal, obtain the final judgment variables of user k $z_k\left(i\right)=w_k^f\left(i\right)\&CenterDot;z_k\left(i\right);$

Step 5 is with final judgment variables Z _k(i) send into signal decision module (5) and carry out polarity decision, obtain the court verdict of arbitrary user k signal;

ω in the step in the above _lBe angular frequency (1≤l≤L), the τ of l subcarrier of user _{K, l}Be the time delay of l subcarrier of user k, T _sBe bit period, [c _{K, 1} ^Ic _{K, 2} ^I... c _{K, L} ^I] and [c _{K, 1} ^Qc _{K, 2} ^Q... c _{K, L} ^Q] be respectively the I road of user k and the frequency expansion sequence of Q road correspondence, c wherein _{K, l} ^I, c _{K, l} ^QSpreading code for user k l subcarrier I road and Q road.

2. according to the described a kind of array antenna MC-CDMA system up-link receiving method of claim 1, it is characterized in that spatial domain in the step 3 merges to be based on suboptimum and to merge that weight vector carries out that the weight vector of l carrier signal spatial domain merging of user k is $w_{k,l}^s\left(i\right)=\mathrm{\&alpha;}{a}_{k,l}^H\left(i\right);$

Wherein, α _{K, l} ^HBe the Hermite conversion of l subcarrier array response vector of user k, α is a constant, is taken as 1.

3. according to the described a kind of array antenna MC-CDMA system up-link receiving method of claim 1, it is characterized in that the carrier wave merging in the step 4 is undertaken by the high specific merging criterion, k user's multi-carrier signal merges weight vector and is $w_k^f\left(i\right)=\left[\right|a_{k,l}\left(i\right)|,|a_{k,2}\left(i\right)|,...,|a_{k,L}\left(i\right)\left|\right];$

Wherein, α _{K, 1}(i), α _{K, 2}(i) ..., α _{K, L}(i) be user k the 1st, 2 respectively ..., the array response vector of L subcarrier.

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