WO2025260232A1 - 电源切换系统 - Google Patents

电源切换系统

Info

Publication number
WO2025260232A1
WO2025260232A1 PCT/CN2024/099783 CN2024099783W WO2025260232A1 WO 2025260232 A1 WO2025260232 A1 WO 2025260232A1 CN 2024099783 W CN2024099783 W CN 2024099783W WO 2025260232 A1 WO2025260232 A1 WO 2025260232A1
Authority
WO
WIPO (PCT)
Prior art keywords
switch
power
winding
power supply
voltage
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Pending
Application number
PCT/CN2024/099783
Other languages
English (en)
French (fr)
Inventor
陈信智
蔡孟江
高肇利
谢奕平
林鸿杰
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Delta Electronics Inc
Original Assignee
Delta Electronics Inc
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Delta Electronics Inc filed Critical Delta Electronics Inc
Priority to PCT/CN2024/099783 priority Critical patent/WO2025260232A1/zh
Publication of WO2025260232A1 publication Critical patent/WO2025260232A1/zh
Pending legal-status Critical Current
Anticipated expiration legal-status Critical

Links

Classifications

    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02J—ELECTRIC POWER NETWORKS; CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
    • H02J9/00—Circuit arrangements for emergency or stand-by power supply, e.g. for emergency lighting
    • H02J9/04—Circuit arrangements for emergency or stand-by power supply, e.g. for emergency lighting in which the distribution system is disconnected from the normal source and connected to a standby source
    • H02J9/06—Circuit arrangements for emergency or stand-by power supply, e.g. for emergency lighting in which the distribution system is disconnected from the normal source and connected to a standby source with automatic change-over, e.g. UPS systems

Definitions

  • This invention relates to a power switching system, and more particularly to a power switching system that can provide a forced commutation procedure.
  • Static transfer switches are essential components in data center power system configurations, providing uninterrupted power to loads such as critical equipment. They typically contain multiple silicon controlled rectifiers (SCRs). STSs are usually powered by two or more independent power supplies, with one set of STSs corresponding to one independent power supply. If the primary power supply exceeds acceptable limits, the system automatically switches to a backup power supply to provide continuous uninterrupted power to critical equipment, preventing forced shutdowns due to power outages.
  • SCRs silicon controlled rectifiers
  • transformers are inductive devices, they can experience magnetic flux saturation when the accumulated magnetic flux is too high. Therefore, if the primary power supply exceeds acceptable limits and improper switching occurs between the two power supplies—for example, causing voltage discontinuity in the transformer and resulting in magnetic flux shift—high inrush currents can occur in the downstream transformer. Excessive inrush currents can overload upstream circuits or trip circuit breakers, leading to a system power outage or damage to the static transfer switches.
  • the current power switching method involves waiting for the current flowing through the silicon controlled rectifier (SCR) of the primary power supply to drop to zero before switching on the backup power supply's SCR after a suitable time has elapsed, thus avoiding excessive inrush currents.
  • SCR silicon controlled rectifier
  • this switching method requires waiting for the current to drop to zero and an additional waiting time before switching, which can lead to excessively low output voltages and still pose a risk of forcing critical equipment to shut down.
  • One object of the present invention is to provide a power switching system having a first power source and a second power source with three-phase AC power.
  • the power switching system includes a first power switch group, a second power switch group, and a three-phase transformer.
  • the first power switch group includes a first switch, a second switch, and a third switch, which are sequentially electrically connected to the first, second, and third phases of the first power source.
  • the second power switch group includes a fourth switch, a fifth switch, and a sixth switch, which are sequentially electrically connected to the first, second, and third phases of the second power source.
  • the three-phase transformer includes a first winding, a second winding, and a third winding, wherein the first, second, and third windings of the three-phase transformer form three common connection points in a delta connection.
  • the first common connection point connects the first switch and the fourth switch; the second common connection point connects the second switch and the fifth switch; and the third common connection point connects the third switch and the sixth switch.
  • the power switching system provides a forced commutation procedure, including: detecting the magnetic flux of the first, second, and third windings, and selecting the winding with the fastest magnetic flux switching as the fastest magnetic flux switching winding; after energizing two of the first, second, and third switches of the fastest magnetic flux switching winding, energizing two of the fourth, fifth, and sixth switches of the fastest magnetic flux switching winding; and after energizing the remaining unenergized switches of the first, second, and third switches, energizing the remaining unenergized switches of the fourth, fifth, and sixth switches.
  • the power switching system includes a first power switch group, a second power switch group, and a three-phase transformer.
  • the first power switch group includes a first switch, a second switch, and a third switch, which are sequentially electrically connected to the first phase sequence, second phase sequence, and third phase sequence of the first power source.
  • the second power switch group includes a fourth switch, a fifth switch, and a sixth switch, which are sequentially electrically connected to the first phase sequence, second phase sequence, and third phase sequence of the second power source.
  • the three-phase transformer includes a first winding, a second winding, and a third winding, wherein the first winding, second winding, and third winding of the three-phase transformer are connected in a star configuration to form a common contact point and three contacts, with the common contact point grounded.
  • the first contact point connects to the first switch and the fourth switch
  • the second contact point connects to the second switch and the fifth switch
  • the third contact point connects to the third switch and the sixth switch.
  • the power switching system provides a forced commutation procedure, including: detecting the magnetic flux of the first, second, and third windings, and selecting the winding with the fastest magnetic flux switching as the fastest magnetic flux switching winding; after energizing one of the first, second, and third switches of the fastest magnetic flux switching winding, energizing one of the fourth, fifth, and sixth switches of the fastest magnetic flux switching winding; after energizing the remaining two non-energized switches of the first, second, and third switches, energizing the remaining two non-energized switches of the fourth, fifth, and sixth switches.
  • Figure 1 is a circuit block diagram of the power switching system of the present invention
  • Figure 2 is a waveform diagram of the main power supply, backup power supply and output power supply of the present invention
  • Figure 3 is a schematic diagram of the forced commutation of the power switching system of the present invention.
  • Figure 4 is a flowchart of the forced commutation method of the power switching system of the present invention.
  • Figure 5 is a schematic diagram of the voltage and magnetic flux waveforms of the forced commutation of the power switching system of the present invention.
  • Figure 6 is a circuit block diagram of the three-phase three-wire power switching system of the present invention.
  • Figure 7 is a circuit block diagram of the three-phase four-wire power switching system of the present invention.
  • Figure 8 is a flowchart of the forced commutation method of the three-phase three-wire power switching system of the present invention.
  • Figure 9 is a flowchart of the forced commutation method of the three-phase four-wire power switching system of the present invention.
  • Power switching system 110 First power supply 111: Second power supply 130: First static transfer switch 131: Second static changeover switch 130a: First thyrax fluid 130b: Second thyratron 131a: Third thyrax fluid 131b: Fourth thyratron 122: First voltage sensor 123: Second voltage sensor 124: Third voltage sensor 132: First current sensor; 133: Second current sensor 134: Controller 120: Inductive device 120A: Primary winding 120B: Secondary winding 121: Load V1: First voltage signal V2: Second voltage signal Vo: Third voltage signal I1: First current signal I2: Second current signal Sc1: First control signal Sc2: Second control signal Sc3: Third control signal Sc4: Fourth control signal f1: First magnetic flux f2: Second magnetic flux fo: Third magnetic flux S-pri: Main power supply, primary power supply S-alt: Backup power, secondary power supply ipri,ialt: Current Vpri, Valt: Voltage Vload: Load
  • the power switching system 100 mainly supplies power to the load 121 (e.g., critical equipment), and the power switching system 100 includes a static switching...
  • the system includes switching devices 130 and 131, an inductive device 120, and a controller 134.
  • the static switching devices 130 and 131 include a first static switching switch 130 and a second static switching switch 131.
  • the load 121 is preferably, but not limited to, a critical load requiring uninterrupted and continuous operation, such as a server or communication system, but this is not intended to limit the invention.
  • the input side of the first static transfer switch 130 is coupled to the first power supply 110, and the input side of the second static transfer switch 131 is coupled to the second power supply 111.
  • the output sides of the first static transfer switch 130 and the second static transfer switch 131 are connected to a common connection node.
  • the inductive device 120 can be, for example but not limited to, a transformer, which includes a primary winding 120A and a secondary winding 120B.
  • the primary winding 120A is coupled to the first static transfer switch 130 and the second static transfer switch 131 at a common connection node, and the secondary winding 120B is coupled to the load 121.
  • the controller 134 is used to detect the power supply of the first power supply 110 and the second power supply 111 to collect power information of the first power supply 110 and the second power supply 111 in real time. Furthermore, the controller 134 detects the output power received by the inductive device 120 from the first static transfer switch 130 or the second static transfer switch 131, and adjusts and controls the first static transfer switch 130 and the second static transfer switch 131 accordingly. Specifically, the controller 134 selects the first power supply 110 or the second power supply 111 to supply power to the load 121 coupled to the inductive device 120 by controlling the first static transfer switch 130 and the second static transfer switch 131. In one embodiment, the controller 134 can be a digital signal processor (DSP), but is not limited thereto; any physical circuit that can use signals for circuit control, a control device containing control software, etc., should be included in the scope of this embodiment.
  • DSP digital signal processor
  • the power switching system 100 further includes voltage sensors 122, 123, 124 and current sensors 132, 133.
  • Voltage sensors 122, 123, 124 include a first voltage sensor 122, a second voltage sensor 123, and a third voltage sensor 124.
  • the first voltage sensor 122 and the second voltage sensor 123 are respectively coupled to a first power supply 110 and a second power supply 111, and are used to detect a first voltage signal V1 and a second voltage signal V2 corresponding to the first power supply 110 and the second power supply 111, respectively.
  • Current sensors 132 and 133 include a first current sensor 132 and a second current sensor 133, both of which are respectively coupled to the first power supply 110 and the second power supply 111, and are used to detect a first current signal I1 and a second current signal I2 corresponding to the first power supply 110 and the second power supply 111, respectively, to obtain the power supplied by the first power supply 110 and the second power supply 111.
  • a third voltage sensor 124 is coupled to the primary winding 120A (as shown in FIG. 1) or the secondary winding 120B (not shown, but should be included in the scope of this embodiment) of the inductive device 120 to detect a third voltage signal Vo corresponding to the primary winding 120A or the secondary winding 120B. Therefore, the voltage sensor...
  • the voltage and current signals detected by sensors 122, 123, 124 and current sensors 132, 133 are transmitted to controller 134 for control purposes.
  • FIG 2 is a waveform diagram of the main power supply, backup power supply, and output power supply of this invention.
  • the controller 134 obtains the first voltage signal V1, the second voltage signal V2, and the third voltage signal Vo, and integrates the first voltage signal V1, the second voltage signal V2, and the third voltage signal Vo to obtain the magnetic flux f1, f2 corresponding to the first power supply 110 and the second power supply 111, and the magnetic flux fo on the inductive device 120, which is the expected magnetic flux.
  • the first magnetic flux f1 is the integral of the first voltage signal V1
  • the second magnetic flux f2 is the integral of the second voltage signal V2
  • the third magnetic flux fo is the integral of the third voltage signal Vo.
  • the first static changeover switch 130 is turned on, the first power supply 110 connects the inductive device 120 and the first power supply 110, so the first magnetic flux f1 and the third magnetic flux fo are the same. Since the integral of voltage is the magnetic flux, and the integral of a sine wave is still a sine wave, the first and second magnetic fluxes f1, f2 and the third magnetic flux (expected magnetic flux) fo are still sinusoidal waveforms.
  • the first static transfer switch 130 and the second static transfer switch 131 each include multiple silicon controlled rectifiers (SCRs).
  • the first static transfer switch 130 includes a first thyristor 130a and a second thyristor 130b, which are the operating thyristors for the positive and negative half-cycles, respectively, and are connected in parallel against each other.
  • the anode of the first thyristor 130a is connected to the cathode of the second thyristor 130b
  • the cathode of the first thyristor 130a is connected to the anode of the second thyristor 130b.
  • the second static transfer switch 131 includes a third thyristor 131a and a fourth thyristor 131b, which are the operating thyristors for the positive and negative half-cycles, respectively, and are connected in parallel against each other.
  • the anode of the third thyristor 131a is connected to the cathode of the fourth thyristor 131b
  • the cathode of the third thyristor 131a is connected to the anode of the fourth thyristor 131b.
  • the thyristors 130a to 131b can be silicon controlled rectifiers, but this is not a limitation.
  • the controller 134 generates multiple independent control signals Sc1 to Sc4, which respectively control the first thyristor 130a to the fourth thyristor 131b.
  • the first control signal Sc1 controls the gate of the first thyristor 130a
  • the second control signal Sc2 controls the gate of the second thyristor 130b
  • the third control signal Sc3 controls the gate of the third thyristor 131a
  • the fourth control signal Sc4 controls the gate of the fourth thyristor 131b.
  • the anodes/cathodes of the first thyristor 130a and the third thyristor 131a are arranged in the same direction
  • the anodes/cathodes of the second thyristor 130b and the fourth thyristor 131b are arranged in the same direction. Therefore, the first thyristor fluid 130a and the fourth thyristor fluid 131b have the same forward deflection direction, and the second thyristor fluid 130b and the third thyristor fluid 131a have the same forward deflection direction.
  • the controller 134 cannot turn off the thyristors 130a to 131b by controlling the gate when current flows through them, the thyristors 130a to 131b can only be turned off after the current in the thyristors 130a to 131b naturally flows to zero or the anode current is canceled by using forced commutation technology.
  • the controller 134 of the present invention selectively controls the first thyristor 130a, the second thyristor 130b, the third thyristor 131a, and the fourth thyristor 131b based on whether the power source is the first power source 110 or the second power source 111.
  • the controller 134 can continuously and instantaneously calculate the first magnetic flux f1, the second magnetic flux f2, and the third magnetic flux fo in the first power source 110, the second power source 111, and the inductive device 120 (e.g., but not limited to, an inductive element such as a transformer).
  • the controller 134 If a power failure event occurs (e.g., but not limited to, an abnormality in the first power source 110), the controller 134 provides a first control signal Sc1 and a second control signal Sc2 to shut off the first thyristor 130a and the second thyristor 130b on the operating path of the first power source 110.
  • a power failure event e.g., but not limited to, an abnormality in the first power source 110
  • the controller 134 calculates the magnetic flux based on the currently detected first voltage signal V1, second voltage signal V2, and third voltage signal Vo, and according to the specific operating mode designed in this invention, provides the third control signal Sc3 and the fourth control signal Sc4 to conduct the third thyristor 131a and the fourth thyristor 131b on the backup path (i.e., the second power supply 111), respectively.
  • This is to avoid improper switching between the two power supplies, which could cause high surge current in the downstream inductive device 120, and to avoid the output power dropping too low due to waiting for the silicon controlled rectifier freewheeling current to reach zero, thus failing to maintain the stable operation of the load 121.
  • the third control signal Sc3 and the fourth control signal Sc4 can be provided in segments to conduct the third thyristor 131a and the fourth thyristor 131b, respectively. That is, during a specific period of commutation, only one of the third thyristor 131a and the fourth thyristor 131b is conducted.
  • the controller 134 can detect the first current flowing through the first static transfer switch 130 (i.e., the corresponding first current signal I1) via the first current sensor 132 to determine whether the first static transfer switch 130 is on or off. That is, the controller 134 can confirm whether the first static transfer switch 130 is correctly turned on or off using the first current (i.e., the corresponding first current signal I1) to confirm whether the entire power switching system 100 is operating normally. On the other hand, the controller 134 can easily determine whether the first thyristor 130a and the second thyristor 130b are correctly turned on or off by detecting the voltage across the terminals of the first thyristor 130a and the second thyristor 130b (via the first voltage signal V1 and the third voltage signal Vo).
  • the controller 134 can detect the second current flowing through the second static transfer switch 131 (i.e., the corresponding second current signal I2) via the second current sensor 133 to determine whether the second static transfer switch 131 is on or off. That is, the controller 134 can confirm whether the second static transfer switch 131 is correctly on or off using the second current (i.e., the corresponding second current signal I2) to confirm whether the entire power switching system 100 is operating normally.
  • the controller 134 can detect the second current flowing through the second static transfer switch 131 (i.e., the corresponding second current signal I2) via the second current sensor 133 to determine whether the second static transfer switch 131 is on or off. That is, the controller 134 can confirm whether the second static transfer switch 131 is correctly on or off using the second current (i.e., the corresponding second current signal I2) to confirm whether the entire power switching system 100 is operating normally.
  • the controller 134 can easily determine whether the third thyristor 131a and the fourth thyristor 131b are correctly on or off by detecting the voltage across the terminals of the third thyristor 131a and the fourth thyristor 131b (via the second voltage signal V2 and the third voltage signal Vo).
  • FIG 3 is a schematic diagram of the forced commutation of the power switching system of the present invention.
  • the controller 134 provides a forced commutation mechanism.
  • the present invention provides a control method with forced commutation.
  • Figure 4 is a flowchart of the forced commutation method of the power switching system of the present invention.
  • the permission of the forced commutation mechanism that is, the opportunity to force commutation, can be likened to obtaining an admission ticket.
  • the controller 134 When an abnormal event occurs in the main power supply S-pri, the controller 134 first turns off all thyristors connected to the main power supply S-pri, that is, thyristors T1P and T1N, through the control gate (step S101). As explained above, due to the characteristics of thyristors, thyristors T1P and T1N that are turned off by gate control may not be completely turned off.
  • controller 134 determines whether the current ipri of the detected main power supply S-pri is greater than zero (step S102). If the current ipri is greater than zero, it indicates that there is a thyristor T1P that has not been completely turned off. At this time, the thyristor T1P is in a conducting state. Next, controller 134 determines whether the voltage Valt of the backup power supply S-alt is greater than the load voltage Vload (step S103).
  • controller 134 turns on the thyristor T2P, so that the voltage Valt reverse-magnetizes the thyristor T1P, turning off the still conducting thyristor T1P (positive switch) with a reverse voltage. This is to allow forced switching of the conducting positive switch, that is, to obtain the ticket (FC ticket-Pos) for forced switching of the conducting positive switch (step S104).
  • step S102 if the current ipri of the main power supply S-pri is less than zero, it indicates that there is a thyristor T1N that has not been completely turned off. At this time, the thyristor T1N is in a conducting state.
  • the controller 134 determines whether the voltage Valt of the backup power supply S-alt is less than the load voltage Vload (step S105). If the voltage Valt is less than the load voltage Vload, the thyristor T2N can be turned on, causing a current change (alteration) effect, which can force the still conducting thyristor T1N (negative switch) to be turned off. This is to allow the forced switching of the conducting negative switch, that is, to obtain the ticket (FC ticket-Neg) for the forced switching of the conducting negative switch (step S106).
  • forced switching is not necessarily required immediately. This is because the effect of forced switching at that moment may not be ideal, as the introduction of forced switching may cause excessive magnetic flux offset.
  • the timing of forced switching can be determined based on considerations such as magnetic flux switching speed and magnetic flux magnitude, which will be explained later.
  • a voltage difference ⁇ Vpri exists between voltage Valt and load voltage Vload.
  • the controller 134 determines whether this voltage difference ⁇ Vpri is greater than a voltage threshold Vthz (step S107). If the voltage difference ⁇ Vpri is greater than the voltage threshold Vthz, it indicates that the thyristors connected to the main power supply S-pri, i.e., thyristors T1P and T1N, have been turned off.
  • FC ticket-NoCare FC ticket-NoCare
  • a ticket FC ticket-NoCare is obtained to turn on either the positive or negative switch (step S108).
  • a short circuit will not occur between the main power supply S-pri and the backup power supply S-alt.
  • FIG. 5 is a schematic diagram of the voltage and magnetic flux waveforms for forced commutation in the power switching system of this invention. Since the load voltage is in the form of a sine wave (as shown in the upper waveform of Figure 5), the magnetic flux is also in the form of a sine wave:
  • the amount of excitation generated by the magnetic flux within the sine wave period can be predicted, that is, it can be obtained by integrating the voltage (as shown in the middle waveform of Figure 5).
  • the timing of forced commutation can be determined based on the current load voltage and the inversely deduced magnitude of the magnetic flux excitation. In other words, forced commutation of the thyristor can be initiated when the accumulated excitation after the switch is turned on does not exceed the saturation flux.
  • the forced commutation of the thyristor fluid can be temporarily suspended until the magnitude of the accumulated excitation does not exceed the saturation flux before the forced commutation of the thyristor fluid is initiated.
  • the polarity of the magnetic flux deflection and the voltage polarity should be further considered.
  • the polarity of the magnetic flux deflection is the same as the voltage polarity—for example, during the positive half-cycle of the voltage and when the magnetic flux is positive—forced commutation of the thyristor can be initiated at an opportune time.
  • the accumulated excitation is too large, it can be delayed; conversely, if the accumulated excitation is not yet too large, forced commutation of the thyristor can be initiated to prevent magnetic flux saturation.
  • Another scenario is when the polarity of the magnetic flux offset is different from the voltage polarity, for example, when a power failure occurs during the negative half-cycle. This results in excitation during the negative half-cycle and demagnetization during the positive half-cycle, reducing the likelihood of magnetic flux saturation. With demagnetization, early forced commutation of the thyristor is preferable. Therefore, as long as the controller 134 determines that the polarity of the magnetic flux offset is different from the voltage polarity and does not lead to magnetic flux saturation, forced commutation of the thyristor can be initiated immediately.
  • the above can be achieved through the following relationship.
  • Equation 2 calculates the accumulated magnetic flux offset of the load; Equation 3 calculates the future available magnetic flux and obtains the maximum and minimum future magnetic flux (as shown in the lower waveform of Figure 5) to determine whether the saturation flux has been exceeded; Equation 4 determines the polarity of the future magnetic flux and the current magnetic flux. As mentioned above, if they are of the same polarity, a suitable timing point is needed to initiate forced commutation of the thyristor fluid; conversely, if they are of different polarities, more lenient conditions can be used to initiate forced commutation of the thyristor fluid.
  • Figure 6 is a circuit block diagram of the three-phase three-wire power switching system of the present invention.
  • the two power supplies including the main power supply S-pri and the backup power supply S-alt, are respectively connected to the downstream three-phase transformer 33 via their respective three-phase static transfer switches 31 and 32.
  • the three-phase power switching system includes a first power source S-pri and a second power source S-alt, both providing three-phase AC power.
  • the power switching system includes a first power switch group 31 and a second power switch group 32.
  • the first power switch group 31 includes a first switch 311, a second switch 312, and a third switch 313, which are sequentially...
  • the first power supply S-pri is electrically connected to the first phase sequence (R phase), the second phase sequence (S phase), and the third phase sequence (T phase).
  • the second power supply switch group 32 includes a fourth switch 321, a fifth switch 322, and a sixth switch 323, which are electrically connected to the first phase sequence (R phase), the second phase sequence (S phase), and the third phase sequence (T phase) of the second power supply S-alt in sequence.
  • the three-phase transformer 33 includes a first winding W12, a second winding W23, and a third winding W31.
  • the first winding W12, the second winding W23, and the third winding W31 of the three-phase transformer 33 are connected in a delta configuration ( ⁇ connection) to form three common connection points N1, N2, and N3.
  • the first common connection point N1 connects the first switch 311 and the fourth switch 321, the second common connection point N2 connects the second switch 312 and the fifth switch 322, and the third common connection point N3 connects the third switch 313 and the sixth switch 323.
  • a certain winding may be powered by both the main power supply S-pri and the backup power supply S-alt simultaneously.
  • the winding may be subjected to twice the rated voltage, which will cause insulation failure of the three-phase transformer 33 or saturation of the three-phase transformer 33, resulting in surge current.
  • this invention designs a technical solution that can effectively achieve successful switching between two power supplies.
  • the control gate When an abnormal event occurs in the main power supply S-pri, the control gate first shuts down all thyristor signals connected to the main power supply S-pri. Then, a forced commutation permit (ticket) is issued, selecting to simultaneously conduct two phases of thyristors to avoid ineffective excitation. After waiting for half a cycle, for example, if it is currently the positive half cycle, the remaining thyristors of the two phases are conducted in the negative half cycle of the next half cycle to complete the conduction of the four thyristors across two phases.
  • ticket forced commutation permit
  • the timing of its conduction is determined based on whether magnetic flux saturation will occur after the calculated future magnetic flux is added. If magnetic flux saturation will occur, the conduction time is waited for. If magnetic flux saturation will not occur, the conduction of the remaining two phases of the thyristor is completed sequentially.
  • a preferred forced commutation procedure is provided, as shown in Figure 8, and in conjunction with Figure 6.
  • This procedure includes: firstly, detecting the first winding of the three-phase transformer 33...
  • the magnetic flux velocities of winding W12, second winding W23, and third winding W31 are determined, and the winding with the fastest magnetic flux switching is selected as the fastest magnetic flux switching winding (step S201).
  • the first winding W12 is the fastest magnetic flux switching winding.
  • step S202 energizing two of the first, second, and third switches of the fastest flux switching winding. If the first winding W12 is the fastest flux switching winding, then the first switch 311 and the second switch 312 of the first power switch group 31, and the fourth switch 321 and the fifth switch 322 of the second power switch group 32 are energized. Incidentally, if the second winding W23 is the fastest flux switching winding, then the second switch 312 and the third switch 313 of the first power switch group 31, and the fifth switch 322 and the sixth switch 323 of the second power switch group 32 are energized.
  • step S203 After turning on the remaining unconverted switches of the first switch 311, the second switch 312, and the third switch 313, turn on the remaining unconverted switches of the fourth switch 321, the fifth switch 322, and the sixth switch 323 (step S203). If the first winding W12 is the fastest flux switching winding, after turning on the remaining unconverted third switch 313, turn on the remaining unconverted sixth switch 313. Incidentally, if the second winding W23 is the fastest flux switching winding, after turning on the remaining unconverted first switch 311, turn on the remaining unconverted fourth switch 321.
  • the optimal timing for the forced commutation of the thyristor fluid can be achieved, effectively realizing the goal of successfully switching between the two power sources.
  • Figure 7 is a circuit block diagram of the three-phase four-wire power switching system of the present invention.
  • the two power sources including the main power source S-pri and the backup power source S-alt, are respectively connected to the downstream three-phase transformer 43 via their respective three-phase static transfer switch devices 41 and 42.
  • the three-phase power switching system includes a first power source S-pri and a second power source S-alt, both providing three-phase AC power.
  • the power switching system includes a first power switch group 41 and a second power switch group 42.
  • the first power switch group 41 includes a first switch 411, a second switch 412, and a third switch 413, which are sequentially electrically connected to the first phase sequence (R phase), the second phase sequence (S phase), and the third phase sequence (T phase) of the first power source S-pri.
  • the second power switch group 42 includes a fourth switch 421, a fifth switch 422 and a sixth switch 423, which are sequentially electrically connected to the first phase sequence (R phase), the second phase sequence (S phase) and the third phase sequence (T phase) of the second power supply S-alt.
  • the three-phase transformer 43 includes a first winding W11, a second winding W22, and a third winding W33.
  • the first winding W11, the second winding W22, and the third winding W33 of the three-phase transformer 43 are connected in a star configuration (Y connection) to form a common contact Nc and three contacts N1, N2, and N3.
  • This common contact Nc is grounded to GND.
  • the first contact N1 connects to the first switch 411 and the fourth switch 421; the second contact N2 connects to the second switch 412 and the fifth switch 422; and the third contact N3 connects to the third switch 413 and the sixth switch 423.
  • this invention designs a technical solution that can effectively achieve successful switching between two power supplies.
  • an abnormal event occurs in the main power supply S-pri
  • all thyristors connected to the main power supply S-pri are first shut down via the control gate.
  • a forced commutation permit (ticket) is issued, selecting one phase of thyristor to be turned on to avoid passive excitation.
  • the thyristors are turned on again in the negative half cycle of the next half cycle to complete the conduction of two thyristors in one phase.
  • the timing of their conduction is determined based on whether magnetic flux saturation will occur after the calculated future magnetic flux is added. If magnetic flux saturation will occur, the conduction time is waited for. If magnetic flux saturation will not occur, the conduction of the remaining two phases (4 thyratrons) is completed sequentially.
  • a preferred forced commutation procedure is provided, as shown in Figure 9, and in conjunction with Figure 7.
  • This procedure includes: firstly, detecting the flux velocity of the first winding W11, the second winding W22, and the third winding W33 of the three-phase transformer 43, and selecting the winding with the fastest flux switching as the fastest flux switching winding (step S301).
  • the first winding W11 is the fastest flux switching winding.
  • step S302 After energizing one of the first, second, and third switches of the fastest flux switching winding, energizing one of the fourth, fifth, and sixth switches of the tangent flux switching winding (step S302). If the first winding W11 is the fastest flux switching winding, then the first switch 411 of the first power switch group 41 and the fourth switch of the second power switch group 42 are energized. 421. Incidentally, if the second winding W22 is the fastest flux switching winding, then the second switch 412 of the first power switch group 41 and the fifth switch 422 of the second power switch group 42 are turned on.
  • step S303 After turning on the first switch 411, the second switch 412, and the two remaining unconverted switches of the third switch 413, turn on the fourth switch 421, the fifth switch 422, and the two remaining unconverted switches of the sixth switch 423 (step S303). If the first winding W11 is the fastest flux switching winding, after turning on the remaining unconverted second switch 412 and the third switch 413, turn on the remaining unconverted fifth switch 422 and the sixth switch 423. Incidentally, if the second winding W22 is the fastest flux switching winding, after turning on the remaining unconverted first switch 411 and the third switch 413, turn on the remaining unconverted fourth switch 421 and the sixth switch 423.
  • the optimal timing for the forced commutation of the thyristor fluid can be achieved, effectively realizing the goal of successfully switching between the two power sources.

Landscapes

  • Business, Economics & Management (AREA)
  • Emergency Management (AREA)
  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Ac-Ac Conversion (AREA)

Abstract

一种电源切换系统，包括具有三相交流电力的第一电源与第二电源。电源切换系统包括第一电源开关组、第二电源开关组以及三相变压器。三相变压器包括第一绕组、第二绕组以及第三绕组，其中第一绕组、第二绕组以及第三绕组以三角形接法形成三个共接点。第一共接点连接第一开关与第四开关，第二共接点连接第二开关与第五开关，第三共接点连接第三开关与第六开关。

Description

电源切换系统 技术领域
本发明涉及一种电源切换系统，尤其涉及一种可提供强制换向程序的一种电源切换系统。
背景技术
静态转换开关装置(static transfer switch,STS)是数据中心电源系统配置中必不可少的组件，可为关键设备(critical equipment)等负载提供不间断电源，其内部通常包括多个硅控整流器。静态转换开关装置通常由两个或多个独立的电源供电，其中一组静态转换开关装置对应一个独立的电源。一旦首选主要电源超出可接受范围，就会自动从首选主要电源切换到备用电源，以提供不间断电源对关键设备持续供电，以避免关键设备的供电中断而导致关键设备被迫停机。
通常地，多组的静态转换开关装置的输出共接后，通过变压器连接到关键设备。由于变压器为电感性装置，当其所累积的磁通量过高时，会有磁通饱和的问题。因此，若首选主要电源超出可接受范围，且发生两个电源之间的不当切换时，例如造成变压器的电压不连续，所产生磁通偏移，会在下游变压器中引起高浪涌电流。当浪涌电流过高时，会使上游的电路过载或使断路器跳闸，导致整个系统断电，或者静态转换开关装置遭受损坏。因此，现行的电源切换方式为：在主要电源流过硅控整流器的电流降为零后，等待合适的时间再开启备用电源的硅控整流器，以避免过高的浪涌电流。然而，此种切换方式需要等待电流降至零，且额外等待适当时间切换，导致等待的时间过久而致使输出的电压过低，仍然有可能导致关键设备被迫停机的风险。
为此，如何设计出一种电源切换系统，及其所提供的强制换向程序，解决现有技术所存在的问题与技术瓶颈，乃为本案发明人所研究的重要课题。
发明内容
本发明的一目的在于提供一种电源切换系统，其具有三相交流电力的第一电源与第二电源。电源切换系统包括第一电源开关组、第二电源开关组以及三相变压器。第一电源开关组包括第一开关、第二开关以及第三开关，依序地电性连接第一电源的第一相序、第二相序以及第三相序。第二电源开关组包括第四开关、第五开关以及第六开关，依序地电性连接第二电源的第一相序、第二相序以及第三相序。三相变压器包括第一绕组、第二绕组以及第三绕组，其中三相变压器的第一绕组、第二绕组以及第三绕组以三角形接法形成三个共接点。其中第一共接点连接第一开关与第四开关，第二共接点连接第二开关与第五开关，第三共接点连接第三开关与第六开关。其中电源切换系统提供强制换向程序，包括：检测第一绕组、第二绕组以及第三绕组的磁通量，并选择具有最快磁通切换的该绕组为最快磁通切换绕组；导通电连接最快磁通切换绕组的第一开关、第二开关以及第三开关其中两开关之后，导通电连接最快磁通切换绕组的第四开关、第五开关以及第六开关其中两开关；导通第一开关、第二开关以及第三开关剩余未导通的开关之后，导通第四开关、第五开关以及第六开关剩余未导通的开关。
本发明的另一目的在于提供一种电源切换系统，其具有三相交流电力的第一电源与第二电源。电源切换系统包括第一电源开关组、第二电源开关组以及三相变压器。第一电源开关组包括第一开关、第二开关以及第三开关，依序地电性连接第一电源的第一相序、第二相序以及第三相序。第二电源开关组包括第四开关、第五开关以及第六开关，依序地电性连接第二电源的第一相序、第二相序以及第三相序。三相变压器包括第一绕组、第二绕组以及第三绕组，其中三相变压器的第一绕组、第二绕组以及第三绕组以星型接法形成一个共接点与三个接点，共接点接地。其中第一接点连接第一开关与第四开关，第二接点连接第二开关与第五开关，第三接点连接第三开关与第六开关。电源切换系统提供强制换向程序，包括：检测第一绕组、第二绕组以及第三绕组的磁通量，并选择具有最快磁通切换的该绕组为最快磁通切换绕组；导通电连接最快磁通切换绕组的第一开关、第二开关以及第三开关其中一开关之后，导通电连接最快磁通切换绕组的第四开关、第五开关以及第六开关其中一开关；导通第一开关、第二开关以及第三开关剩余未导通的两开关之后，导通第四开关、第五开关以及第六开关剩余未导通的两开关。
为了能更进一步了解本发明为达成预定目的所采取的技术、手段及功效，请参阅以下有关本发明的详细说明与附图，相信本发明的目的、特征与特点，当可由此得一深入且具体的了解，然而所附附图仅提供参考与说明用，并非用来对本发明加以限制者。
附图说明
图1为本发明电源切换系统的电路方块图；
图2为本发明主要电源、备用电源以及输出电源的波形示意图；
图3为本发明电源切换系统的强制换向的示意图；
图4为本发明电源切换系统的强制换向的方法流程图；
图5为本发明电源切换系统的强制换向的电压、磁通量的波形示意图；
图6为本发明三相三线电源切换系统的电路方块图；
图7为本发明三相四线电源切换系统的电路方块图；
图8为本发明三相三线电源切换系统的强制换向的方法流程图；
图9为本发明三相四线电源切换系统的强制换向的方法流程图。
附图标记说明
100:电源切换系统
110:第一电源
111:第二电源
130:第一静态转换开关
131:第二静态转换开关
130a:第一闸流体
130b:第二闸流体
131a:第三闸流体
131b:第四闸流体
122:第一电压传感器
123:第二电压传感器
124:第三电压传感器
132:第一电流传感器133:第二电流传感器
134:控制器
120:电感性装置
120A:初级侧绕组
120B:次级侧绕组
121:负载
V1:第一电压信号
V2:第二电压信号
Vo:第三电压信号
I1:第一电流信号
I2:第二电流信号
Sc1:第一控制信号
Sc2:第二控制信号
Sc3:第三控制信号
Sc4:第四控制信号
f1:第一磁通量
f2:第二磁通量
fo:第三磁通量
S-pri:主要电源、第一电源
S-alt:备用电源、第二电源
ipri,ialt:电流
Vpri,Valt:电压
Vload:负载电压
T1P,T1N,T2P,T2N:闸流体
ΔVpri:电压差
Vthz:电压阈值
31:第一电源开关组
32:第二电源开关组
311:第一开关
312:第二开关
313:第三开关
321:第四开关
322:第五开关
323:第六开关
33:三相变压器
W12:第一绕组
W23:第二绕组
W31:第三绕组
N1:第一共接点
N2:第二共接点
N3:第三共接点
41:第一电源开关组
42:第二电源开关组
411:第一开关
412:第二开关
413:第三开关
421:第四开关
422:第五开关
423:第六开关
43:三相变压器
W11:第一绕组
W22:第二绕组
W33:第三绕组
GND:接地
S101～S108:步骤
S201～S203:步骤
S301～S303:步骤
具体实施方式
兹有关本发明的技术内容及详细说明，配合附图说明如下。
请参见图1，其为本发明电源切换系统的电路方块图。电源切换系统100主要是对负载(load)121(例如关键设备)供电，且电源切换系统100包括静态转 换开关装置130,131、电感性装置120以及控制器(controller)134。静态转换开关装置130,131包括第一静态转换开关130与第二静态转换开关131。负载121较佳可为例如但不限于，可以为伺服器、通讯系统等需要不间断且持续运作的关键性负载，但不以此为限制本发明。
第一静态转换开关130的输入侧耦接第一电源110，第二静态转换开关131的输入侧耦接第二电源111，且第一静态转换开关130的输出侧与第二静态转换开关131的输出侧共接于共接节点。电感性装置120，是可为，例如但不限制，一变压器，其包括初级侧绕组120A与次级侧绕组120B。初级侧绕组120A耦接第一静态转换开关130与第二静态转换开关131于共接节点，且次级侧绕组120B耦接负载121。
控制器134用以检测第一电源110与第二电源111的电源电力，以即时地收集第一电源110与第二电源111的电源信息。并且，控制器134检测电感性装置120所接收到从第一静态转换开关130或第二静态转换开关131提供的输出电力，据以对第一静态转换开关130与第二静态转换开关131进行调节与控制。其中，控制器134通过控制第一静态转换开关130与第二静态转换开关131，选择第一电源110或第二电源111对耦接电感性装置120的负载121供电。在一实施例中，控制器134可以为数字信号处理器(digital signal processor,DSP)，但不以此为限，举凡可利用信号来进行电路控制的实体电路、内含控制软件的控制装置等，皆应包括在本实施例的范畴当中。
具体地，电源切换系统100还包括电压传感器122,123,124与电流传感器132,133。电压传感器122,123,124包括第一电压传感器122、第二电压传感器123以及第三电压传感器124。第一电压传感器122与第二电压传感器123分别耦接第一电源110与第二电源111，用以分别检测相应于第一电源110与第二电源111的第一电压信号V1与第二电压信号V2。电流传感器132,133包括第一电流传感器132与第二电流传感器133，两者分别耦接第一电源110与第二电源111，用以分别检测相应于第一电源110与第二电源111的第一电流信号I1与第二电流信号I2，以获得第一电源110与第二电源111的电源电力。此外，第三电压传感器124耦接电感性装置120的初级侧绕组120A(如图1所示)或次级侧绕组120B(未附图，但应包括在本实施例的范畴当中)，用以检测相应于初级侧绕组120A或次级侧绕组120B上的第三电压信号Vo。因此，电压传感器 122,123,124与电流传感器132,133所检测到的电压信号与电流信号是传送至控制器134，以供控制器134进行控制的依据。
请参见图2所示，其为本发明主要电源、备用电源及输出电源的波形示意图。第一电源110与第二电源111的电压波形虽然具有相位差，但仅为示意，二者并无相互关联，意即，本发明的切换控制方式主要针对磁通量来控制，无关相位差的大小。控制器134取得第一电压信号V1、第二电压信号V2以及第三电压信号Vo，且对第一电压信号V1、第二电压信号V2以及第三电压信号Vo进行积分，以取得相应于第一电源110、第二电源111的磁通量f1,f2，以及电感性装置120上的磁通量fo，其为预计磁通量。其中，第一磁通量f1为第一电压信号V1的积分、第二磁通量f2为第二电压信号V2的积分。第三磁通量fo为第三电压信号Vo的积分。值得一提，因为第一静态转换开关130导通，使第一电源110接通电感性装置120与第一电源110，因此第一磁通量f1与第三磁通量fo一致。其中，由于电压的积分即为磁通量，且正弦波的积分仍然为正弦波，因此第一、第二磁通量f1,f2与第三磁通量(预计磁通量)fo仍为正弦波形。
复见图1，第一静态转换开关130与第二静态转换开关131分别包括多个硅控整流器(silicon controlled rectifier,SCR)，其中第一静态转换开关130包括第一闸流体130a与第二闸流体130b，两者分别为正、负半周期操作时的动作闸流体，且两者彼此反向并联，例如第一闸流体130a的阳极连接第二闸流体130b的阴极，第一闸流体130a的阴极连接第二闸流体130b的阳极。第二静态转换开关131包括第三闸流体131a与第四闸流体131b，两者分别为正、负半周期操作时的动作闸流体，且两者彼此反向并联，例如第三闸流体131a的阳极连接第四闸流体131b的阴极，第三闸流体131a的阴极连接第四闸流体131b的阳极。其中，上述的闸流体130a～131b较佳可以为硅控整流器，但不以此为限。
再者，控制器134产生多个各自独立的控制信号Sc1～Sc4，分别控制第一闸流体130a～第四闸流体131b。具体地，第一控制信号Sc1控制第一闸流体130a的栅极、第二控制信号Sc2控制第二闸流体130b的栅极、第三控制信号Sc3控制第三闸流体131a的栅极以及第四控制信号Sc4控制第四闸流体131b的栅极。此外，第一闸流体130a与第三闸流体131a的阳极/阴极所配置的方向为同方向，且第二闸流体130b与第四闸流体131b的阳极/阴极所配置的方向为同方向。因 此，第一闸流体130a与第四闸流体131b路径的顺偏方向相同，且第二闸流体130b与第三闸流体131a路径的顺偏方向相同。
由于闸流体130a～131b在有电流流过时，控制器134无法通过控制栅极关断闸流体130a～131b的特性，因此仅有在闸流体130a～131b的电流自然续流到零或使用强制换向(forced commutation)技术取消阳极电流后，闸流体130a～131b才有办法被关断。
具体而言，本发明的控制器134根据供电来源为第一电源110或第二电源111，选择地控制第一闸流体130a、第二闸流体130b、第三闸流体131a以及第四闸流体131b。其中，控制器134可用于连续且即时计算分别获得第一电源110、第二电源111以及电感性装置120(例如但不限于，变压器等电感性元件)中的第一磁通量f1、第二磁通量f2以及第三磁通量fo。如果发生电源故障事件(例如但不限于，第一电源110发生异常)，控制器134分别提供第一控制信号Sc1与第二控制信号Sc2关断第一电源110工作路径上的第一闸流体130a、第二闸流体130b。
然后控制器134根据当前检测的第一电压信号V1、第二电压信号V2以及第三电压信号Vo所计算的磁通量，且依照本发明设计的特定操作方式，分别提供第三控制信号Sc3与第四控制信号Sc4导通连接备用路径(即第二电源111)上的第三闸流体131a、第四闸流体131b，以避免两个电源之间的不当切换而在下游电感性装置120中引起高浪涌电流，且同时避免因等待硅控整流器续流到零而造成输出电源降至过低，不足以维持负载121稳定运作的状况。其中，依照本发明设计的特定操作方式，可以分段提供第三控制信号Sc3与第四控制信号Sc4分别导通第三闸流体131a与第四闸流体131b，意即，在换向的某个特定时段仅导通第三闸流体131a与第四闸流体131b的其中一者。
另外一方面，控制器134可以通过第一电流传感器132检测流过第一静态转换开关130的第一电流(即相应第一电流信号I1)，以决定第一静态转换开关130为导通或关断。意即，控制器134可以通过第一电流(即相应第一电流信号I1)确认第一静态转换开关130是否正确的导通、关断，以确认整个电源切换系统100是否运作正常。另外一方面，控制器134可以通过检测第一闸流体130a、第二闸流体130b二端的跨压(通过第一电压信号V1、第三电压信号Vo)来简易地判断第一闸流体130a、第二闸流体130b是否正确的导通、关断。同样地， 控制器134可以通过第二电流传感器133检测流过第二静态转换开关131的第二电流(即相应第二电流信号I2)，以决定第二静态转换开关131为导通或关断。意即，控制器134可以通过第二电流(即相应第二电流信号I2)确认第二静态转换开关131是否正确的导通、关断，以确认整个电源切换系统100是否运作正常。另外一方面，控制器134可以通过检测第三闸流体131a、第四闸流体131b二端的跨压(通过第二电压信号V2、第三电压信号Vo)来简易地判断第三闸流体131a、第四闸流体131b是否正确的导通、关断。
请参见图3所示，其为本发明电源切换系统的强制换向的示意图。为避免两电源S-pri,S-alt发生同时供电或者两者之间短路，因此控制器134提供强制换向机制。有别于现有自然换向(natural commutation)手段，本发明提供一种具强制换向的控制方式。另请参见图4所示，其为本发明电源切换系统的强制换向的方法流程图。强制换向机制的许可，即具有可强制换向的机会，可以获得入场券、门票(ticket)所比喻。当主要电源S-pri发生异常事件时，控制器134首先通过控制栅极将所有与主要电源S-pri连接的闸流体，亦即将闸流体T1P,T1N关断(步骤S101)。承前说明，由于闸流体的特性，因此不见得通过栅极控制关断的闸流体T1P,T1N都可以完全关断。
然后，控制器134判断所检测主要电源S-pri的电流ipri是否大于零(步骤S102)。若电流ipri大于零，则表示存在有尚未完全关断的闸流体T1P。此时，闸流体T1P为导通的状态。接着，控制器134判断备用电源S-alt的电压Valt是否大于负载电压Vload(步骤S103)。若电压Valt大于负载电压Vload，则控制器134导通闸流体T2P，使得电压Valt对闸流体T1P逆向激磁，将尚导通的闸流体T1P(正开关)以逆向电压关断，此为许可对导通正开关的强制换向，亦即获得对导通正开关进行强制换向的门票(FC ticket-Pos)(步骤S104)。
反之，在步骤S102的判断中，若主要电源S-pri的电流ipri小于零，则表示存在有尚未完全关断的闸流体T1N。此时，闸流体T1N为导通的状态。接着，控制器134判断备用电源S-alt的电压Valt是否小于负载电压Vload(步骤S105)。若电压Valt小于负载电压Vload，则可通过导通闸流体T2N，使得电流变化(改变)效应，可强迫将尚导通的闸流体T1N(负开关)关断，此为许可对导通负开关的强制换向，亦即获得对导通负开关进行强制换向的门票(FC ticket-Neg)(步骤S106)。
附带一提，取得对导通正开关强制换向的门票(可以是一次或者多次取得)，即许可对导通正开关的强制换向时，或者，取得对导通负开关强制换向的门票(可以是一次或者多次取得)，即许可对导通负开关的强制换向时，不见得必须立即进行强制换向，因为当下的强制换向效果不见得理想，其原因为有可能因为强制换向的导入造成磁通偏移过大。较佳地，可根据磁通切换速度、磁通大小等等的考量，决定强制换向导入的时间点，容后说明。
此外，若因为考量磁通切换速度、磁通大小等等，而没有导入强制换向时(即便已具有对导通正开关强制换向的条件和/或具有对导通负开关强制换向的条件)，此时，由于原本尚导通的闸流体因为其电流自然续流到零，所以为自然换向而关断。因此，存在电压Valt与负载电压Vload之间的电压差ΔVpri。因此控制器134判断该电压差ΔVpri是否大于一电压阈值Vthz(步骤S107)。若电压差ΔVpri大于电压阈值Vthz，则表示与主要电源S-pri连接的闸流体，亦即将闸流体T1P,T1N皆已关断。因此，获得对关断正开关或关断负开关进行导通的门票(FC ticket-NoCare)(步骤S108)。在此情况下，无论那一个闸流体导通，都不会造成主要电源S-pri与备用电源S-alt之间发生短路的异常。
以下，将说明强制换向导入的时间点的决定，亦即决定使用进行强制换向门票的时机。请参见图5所示，其为本发明电源切换系统的强制换向的电压、磁通量的波形示意图。由于负载电压Load voltage为弦波形式(如图5的上部波形所示意)，因此磁通亦为弦波形式：
由于磁通为固定弦波，因此在弦波周期内该磁通所产生的激磁量是可以预估的，亦即电压的积分即可获得(如图5的中部波形所示意)。
即然磁通所产生的激磁量是可以预估的，因此只要计算在闸流体还没导通的期间时，电压的激磁大小，即可反推得到，当闸流体导通后，可获得多少的磁通激磁量。因此，利用这样的做法，可根据当下负载电压的大小，再根据可反推得到的磁通激磁量的大小，决定强制换向导入的时间点。换言之，当开关导通后，所获得累加的激磁量的大小不会超过饱和磁通时，则可导入闸流体的强制换向。
反之，当开关导通后，所获得累加的激磁量的大小可能会超过饱和磁通时，则可等待暂先不导入闸流体的强制换向，直到所获得累加的激磁量的大小不会超过饱和磁通为止，才导入闸流体的强制换向。
具体地，进一步考虑磁通偏移的极性与电压的极性的状况。一种情况是，当磁通偏移的极性与电压的极性相同，例如在电压为正半周，且磁通为正值，因此可选择时机导入闸流体的强制换向。换言之，当累加的激磁量太大时，则可等待；反之，当累加的激磁量尚未太大时，则可导入闸流体的强制换向，使得不会发生磁通饱和的状况。
另一种情况是，当磁通偏移的极性与电压的极性不相同，例如当负半周发生电源故障时，因此产生负半周的激磁，并且在正半周时能够提供去磁，较不会发生磁通饱和的状况。在具有去磁的情况下，能够即早导入闸流体的强制换向，即为较佳方式。故此，只要控制器134判断磁通偏移的极性与电压的极性不相同且不导致磁通饱和时，即可立即导入闸流体的强制换向。上述的内容可通过下列关系式所实现。
φLoad_past+＝vLoad·Tcalc…(式2)
φfuture＝φmax-φaltLoad_pastor-φmax-φaltLoad+past…(式3)
kflux＝sgn(φLoadReal·φfuture)…(式4)
其中，根据式2可计算负载所累积的磁通偏移量；根据式3可计算未来可获得的磁通量，并且获得未来最大的磁通量与最小磁通量(如图5的下部波形所示意)，以判断是否超过饱和磁通；根据式4可判断未来磁通与当下磁通的极性。承前所述，若为同极性时，则需等待合适的时机点导入闸流体的强制换向；反之若为不同极性时，则可用较宽松条件导入闸流体的强制换向。
关于前揭磁通量、电压以及闸流体的强制换向如何在三相电源系统中应用，更具体的闸流体控制，将在后文说明。请参见图6所示，其为本发明三相三线电源切换系统的电路方块图。在图6中，两个电源，包括主要电源S-pri与备用电源S-alt分别提过各自的三相静态转换开关装置31,32，再连接至下游三相变压器33。
如图6所示，该三相电源切换系统包括具有三相交流电力的第一电源S-pri与第二电源S-alt。电源切换系统包括第一电源开关组31与第二电源开关组32。第一电源开关组31包括第一开关311、第二开关312以及第三开关313，依序地 电性连接第一电源S-pri的第一相序(R相)、第二相序(S相)以及第三相序(T相)。第二电源开关组32包括第四开关321、第五开关322以及第六开关323，依序地电性连接第二电源S-alt的第一相序(R相)、第二相序(S相)以及第三相序(T相)。
三相变压器33包括第一绕组W12、第二绕组W23以及第三绕组W31。其中三相变压器33的第一绕组W12、第二绕组W23以及第三绕组W31以三角形接法(Δ接法)形成三个共接点N1,N2,N3，其中第一共接点N1连接第一开关311与第四开关321，第二共接点N2连接第二开关312与第五开关322，第三共接点N3连接第三开关313与第六开关323。
附带一提，对三相三线系统而言，其存在常见的问题：一、过激磁问题，二、无效激磁问题。
就过激磁问题而言，由于三相变压器33一部分的绕组由主要电源S-pri供电，而另一部分的绕组由备用电源S-alt供电，因此对某一绕组而言，其可能同时由主要电源S-pri与备用电源S-alt供电。此时，如果主要电源S-pri与备用电源S-alt的相位差是浮动时，最坏的状况，该绕组可能会承受两倍的额定电压，因此将造成三相变压器33的绝缘破坏或者三相变压器33饱和而产生涌浪电流。
就无效激磁问题而言，当经前揭磁通计算、强制换向时机决定，而导入强制换向时，若仅导通一个闸流体，则将无法有电流路径可以流回，因此这样的闸流体导通是无效的，而对三相变压器33的激磁与去磁是没有任何影响。
因此，为避免上揭过激磁与无效激磁问题，本发明设计可以有效达成两电源成功切换的技术方案。当主要电源S-pri发生异常事件时，首先通过控制栅极将所有与主要电源S-pri连接的闸流体信号关闭。然后，强制换向的许可(门票ticket)，选择同时导通两相闸流体，以避免无效激磁发生。然后等待半周的时间，例如当时为正半周时，则在下一个半周的负半周导通两相的剩余闸流体，以完成两相4个闸流体的导通。
最后一相的闸流体，则根据计算后所获得未来的磁通量加入后是否会发生磁通饱和，来决定其导通的时机。若会发生磁通饱和，则等待导通的时机。若不会发生磁通饱和，则依序完成剩余一相2个闸流体的导通。
对三相三线电源切换系统而言，其提供一较佳的强制换向程序，请参见图8所示，且配合参见图6。该程序包括：首先，检测三相变压器33的第一绕 组W12、第二绕组W23以及第三绕组W31的磁通速度，并选择具有最快磁通切换的绕组为一最快磁通切换绕组(步骤S201)。举例来说，然不以此限制本发明，第一绕组W12为该最快磁通切换绕组。
然后，导通电连接最快磁通切换绕组的第一开关、第二开关以及第三开关其中两开关之后，导通电连接最快磁通切换绕组的第四开关、第五开关以及第六开关其中两开关(步骤S202)。若第一绕组W12为该最快磁通切换绕组，则导通第一电源开关组31的第一开关311与第二开关312以及第二电源开关组32的第四开关321与第五开关322。附带一提，若第二绕组W23为该最快磁通切换绕组，则导通第一电源开关组31的第二开关312与第三开关313以及第二电源开关组32的第五开关322与第六开关323。
最后，导通第一开关311、第二开关312以及第三开关313剩余未导通的开关之后，导通第四开关321、第五开关322以及第六开关323剩余未导通的开关(步骤S203)。若第一绕组W12为该最快磁通切换绕组，导通剩余未导通的第三开关313之后，导通剩余未导通的第六开关313。附带一提，若第二绕组W23为该最快磁通切换绕组，导通剩余未导通的第一开关311之后，导通剩余未导通的第四开关321。
据此，根据前揭强制换向的许可、磁通偏移的极性与电压的极性的状况进行评估、考量，则可实现最佳导入闸流体的强制换向的时机，有效达成两电源成功切换的目的。
附带一提，前揭是以“最快磁通切换”为例据以实施。然本发明的另一实施例，亦可以“最大磁通量”为例据以实施，应包括于本发明的范畴中，且任何本领域技术人员在本发明的领域内，可轻易思及的变化或修饰皆可涵盖在本案的权利要求。
请参见图7所示，其为本发明三相四线电源切换系统的电路方块图。在图7中，两个电源，包括主要电源S-pri与备用电源S-alt分别提过各自的三相静态转换开关装置41,42，再连接至下游三相变压器43。
如图7所示，该三相电源切换系统包括具有三相交流电力的第一电源S-pri与第二电源S-alt。电源切换系统包括第一电源开关组41与第二电源开关组42。第一电源开关组41包括第一开关411、第二开关412以及第三开关413，依序地电性连接第一电源S-pri的第一相序(R相)、第二相序(S相)以及第三相序(T相)。 第二电源开关组42包括第四开关421、第五开关422以及第六开关423，依序地电性连接第二电源S-alt的第一相序(R相)、第二相序(S相)以及第三相序(T相)。
三相变压器43包括第一绕组W11、第二绕组W22以及第三绕组W33。其中三相变压器43的第一绕组W11、第二绕组W22以及第三绕组W33以星型接法(Y接法)形成一个共接点Nc与三个接点N1,N2,N3，该共接点Nc接地GND。其中第一接点N1连接第一开关411与第四开关421，第二接点N2连接第二开关412与第五开关422，第三接点N3连接第三开关413与第六开关423。
附带一提，对三相四线系统而言，其存在常见的问题：一、过激磁问题，二、被动激磁问题。
就过激磁问题而言，不再赘述，可参见前揭相应的说明。就被动激磁问题而言，对三相四线系统，导入强制换向时，不能仅导通两个闸流体，因为一旦导通两个闸流体，第三个闸流体即便不导通，也会受到磁通的影响。
因此，为避免上揭过激磁与被动激磁问题，本发明设计可以有效达成两电源成功切换的技术方案。当主要电源S-pri发生异常事件时，首先通过控制栅极将所有与主要电源S-pri连接的闸流体关闭。然后，强制换向的许可(门票ticket)，选择导通一相闸流体，以避免被动激磁发生。然后等待半周的时间，例如当时为正半周时，则在下一个半周的负半周再导通闸流体，以完成一相2个闸流体的导通。
最后两相的闸流体，则根据计算后所获得未来的磁通量加入后是否会发生磁通饱和，来决定其导通的时机。若会发生磁通饱和，则等待导通的时机。若不会发生磁通饱和，则依序完成剩余两相4个闸流体的导通。
对三相四线电源切换系统而言，其提供一较佳的强制换向程序，请参见图9所示，且配合参见图7。该程序包括：首先，检测三相变压器43的第一绕组W11、第二绕组W22以及第三绕组W33的磁通速度，并选择具有最快磁通切换的绕组为一最快磁通切换绕组(步骤S301)。举例来说，然不以此限制本发明，第一绕组W11为该最磁通切换绕组。
然后，导通电连接最快磁通切换绕组的第一开关、第二开关以及第三开关其中一开关之后，导通电连接最切磁通切换绕组的第四开关、第五开关以及第六开关其中一开关(步骤S302)。若第一绕组W11为该最快磁通切换绕组，则导通第一电源开关组41的第一开关411以及第二电源开关组42的第四开关 421。附带一提，若第二绕组W22为该最快磁通切换绕组，则导通第一电源开关组41的第二开关412以及第二电源开关组42的第五开关422。
最后，导通第一开关411、第二开关412以及第三开关413剩余未导通的两开关之后，导通第四开关421、第五开关422以及第六开关423剩余未导通的两开关(步骤S303)。若第一绕组W11为该最快磁通切换绕组，导通剩余未导通的第二开关412与第三开关413之后，导通剩余未导通的第五开关422与第六开关423。附带一提，若第二绕组W22为该最快磁通切换绕组，导通剩余未导通的第一开关411与第三开关413之后，导通剩余未导通的第四开关421与第六开关423。
据此，根据前揭强制换向的许可、磁通偏移的极性与电压的极性的状况进行评估、考量，则可实现最佳导入闸流体的强制换向的时机，有效达成两电源成功切换的目的。
以上所述，仅为本发明较佳具体实施例的详细说明与附图，惟本发明的特征并不局限于此，并非用以限制本发明，本发明的所有范围应以下述的权利要求为准，凡合于本发明权利要求的精神与其类似变化的实施例，皆应包括于本发明的范畴中，任何本领域技术人员在本发明的领域内，可轻易思及的变化或修饰皆可涵盖在以下本案的权利要求。

Claims (18)

  1. 一种电源切换系统，包括具有三相交流电力的第一电源与第二电源，所述电源切换系统包括：
    第一电源开关组，包括第一开关、第二开关以及第三开关，依序地电性连接所述第一电源的第一相序、第二相序以及第三相序；
    第二电源开关组，包括第四开关、第五开关以及第六开关，依序地电性连接所述第二电源的第一相序、第二相序以及第三相序；以及
    三相变压器，包括第一绕组、第二绕组以及第三绕组，其中所述三相变压器的所述第一绕组、所述第二绕组以及所述第三绕组以三角形接法形成三个共接点，其中第一共接点连接所述第一开关与所述第四开关，第二共接点连接所述第二开关与所述第五开关，第三共接点连接所述第三开关与所述第六开关；
    其中所述电源切换系统提供强制换向程序，包括：
    检测所述第一绕组、所述第二绕组以及所述第三绕组的磁通量，并选择具有最快磁通切换的所述绕组为最快磁通切换绕组；
    导通电连接所述最快磁通切换绕组的所述第一开关、所述第二开关以及所述第三开关其中两开关之后，导通电连接所述最快磁通切换绕组的所述第四开关、所述第五开关以及所述第六开关其中两开关；以及
    导通所述第一开关、所述第二开关以及所述第三开关剩余未导通的开关之后，导通所述第四开关、所述第五开关以及所述第六开关剩余未导通的开关。
  2. 根据权利要求1所述的电源切换系统，其中任一所述第一开关、所述第二开关以及所述第三开关包括反向并联的两闸流体；其中任一所述第四开关、所述第五开关以及所述第六开关包括反向并联的两闸流体。
  3. 根据权利要求2所述的电源切换系统，其中基于所述第一电源欲切换为所述第二电源，在所述强制换向程序中，当判断流出所述第一电源的电流大于零时，进一步判断所述第二电源的电压是否大于负载电压。
  4. 根据权利要求3所述的电源切换系统，其中若所述电压大于所述负载电压时，所述电压导通与所述第二电源连接且顺向的所述闸流体，以关断与所述第一电源连接且尚导通的所述闸流体。
  5. 根据权利要求2所述的电源切换系统，其中基于所述第一电源欲切换为所述第二电源，在所述强制换向程序中，当判断流出所述第一电源的电流小于零时，进一步判断所述第二电源的电压是否小于负载电压。
  6. 根据权利要求5所述的电源切换系统，其中若所述电压小于所述负载电压时，所述负载电压导通与所述第二电源连接且逆向的所述闸流体，以关断与所述第一电源连接且尚导通的所述闸流体。
  7. 根据权利要求2所述的电源切换系统，其中基于所述第一电源欲切换为所述第二电源，在所述强制换向程序中，当判断所述第二电源的电压与负载电压之间的电压差大于电压阈值时，与所述第一电源连接的所述闸流体已关断。
  8. 根据权利要求2所述的电源切换系统，其中当磁通偏移的极性与电压的极性相同时，可选择在不会发生磁通饱和的情况下，导入闸流体的强制换向。
  9. 根据权利要求2所述的电源切换系统，其中当磁通偏移的极性与电压的极性不相同时，可立即导入闸流体的强制换向。
  10. 一种电源切换系统，包括具有三相交流电力的第一电源与第二电源，所述电源切换系统包括：
    第一电源开关组，包括第一开关、第二开关以及第三开关，依序地电性连接所述第一电源的第一相序、第二相序以及第三相序；
    第二电源开关组，包括第四开关、第五开关以及第六开关，依序地电性连接所述第二电源的第一相序、第二相序以及第三相序；以及
    三相变压器，包括第一绕组、第二绕组以及第三绕组，其中所述三相变压器的所述第一绕组、所述第二绕组以及所述第三绕组以星型接法形成一个共接点与三个接点，所述共接点接地，其中第一接点连接所述第一开关与所述第四开关，第二接点连接所述第二开关与所述第五开关，第三接点连接所述第三开关与所述第六开关；
    其中所述电源切换系统提供强制换向程序，包括：
    检测所述第一绕组、所述第二绕组以及所述第三绕组的磁通量，并选择具有最快磁通切换的所述绕组为最快磁通切换绕组；
    导通电连接所述最快磁通切换绕组的所述第一开关、所述第二开关以及 所述第三开关其中一开关之后，导通电连接所述最快磁通切换绕组的所述第四开关、所述第五开关以及所述第六开关其中一开关；以及
    导通所述第一开关、所述第二开关以及所述第三开关剩余未导通的两开关之后，导通所述第四开关、所述第五开关以及所述第六开关剩余未导通的两开关。
  11. 根据权利要求10所述的电源切换系统，其中任一所述第一开关、所述第二开关以及所述第三开关包括反向并联的两闸流体；其中任一所述第四开关、所述第五开关以及所述第六开关包括反向并联的两闸流体。
  12. 根据权利要求11所述的电源切换系统，其中基于所述第一电源欲切换为所述第二电源，在所述强制换向程序中，当判断流出所述第一电源的电流大于零时，进一步判断所述第二电源的电压是否大于负载电压。
  13. 根据权利要求12所述的电源切换系统，其中若所述电压大于所述负载电压时，所述电压导通与所述第二电源连接且顺向的所述闸流体，以关断与所述第一电源连接且尚导通的所述闸流体。
  14. 根据权利要求11所述的电源切换系统，其中基于所述第一电源欲切换为所述第二电源，在所述强制换向程序中，当判断流出所述第一电源的电流小于零时，进一步判断所述第二电源的电压是否小于负载电压。
  15. 根据权利要求14所述的电源切换系统，其中若所述电压小于所述负载电压时，所述负载电压导通与所述第二电源连接且逆向的所述闸流体，以关断与所述第一电源连接且尚导通的所述闸流体。
  16. 根据权利要求11所述的电源切换系统，其中基于所述第一电源欲切换为所述第二电源，在所述强制换向程序中，当判断所述第二电源的电压与负载电压之间的电压差大于电压阈值时，与所述第一电源连接的所述闸流体已关断。
  17. 根据权利要求11所述的电源切换系统，其中当磁通偏移的极性与电压的极性相同时，可选择在不会发生磁通饱和的情况下，导入闸流体的强制换向。
  18. 根据权利要求11所述的电源切换系统，其中当磁通偏移的极性与电压的极性不相同时，可立即导入闸流体的强制换向。
PCT/CN2024/099783 2024-06-18 2024-06-18 电源切换系统 Pending WO2025260232A1 (zh)

Priority Applications (1)

Application Number Priority Date Filing Date Title
PCT/CN2024/099783 WO2025260232A1 (zh) 2024-06-18 2024-06-18 电源切换系统

Applications Claiming Priority (1)

Application Number Priority Date Filing Date Title
PCT/CN2024/099783 WO2025260232A1 (zh) 2024-06-18 2024-06-18 电源切换系统

Publications (1)

Publication Number Publication Date
WO2025260232A1 true WO2025260232A1 (zh) 2025-12-26

Family

ID=98212268

Family Applications (1)

Application Number Title Priority Date Filing Date
PCT/CN2024/099783 Pending WO2025260232A1 (zh) 2024-06-18 2024-06-18 电源切换系统

Country Status (1)

Country Link
WO (1) WO2025260232A1 (zh)

Citations (5)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US6560128B1 (en) * 1999-02-12 2003-05-06 Satcon Power Systems Canada Ltd. Ferroresonance-suppressing static transfer switch
CN1918769A (zh) * 2004-02-10 2007-02-21 利伯特公司 基于可控硅整流器的静态转换开头装置和方法
CN109787347A (zh) * 2019-01-02 2019-05-21 中国船舶重工集团公司第七一九研究所 一种抑制变压器励磁涌流的双电源切换装置及其切换方法
CN112653229A (zh) * 2020-12-14 2021-04-13 武汉第二船舶设计研究所(中国船舶重工集团公司第七一九研究所) 一种抑制负载变压器励磁涌流的双电源切换装置控制方法
CN117595479A (zh) * 2022-08-17 2024-02-23 台达电子工业股份有限公司 双电源切换系统及其控制方法

Patent Citations (5)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US6560128B1 (en) * 1999-02-12 2003-05-06 Satcon Power Systems Canada Ltd. Ferroresonance-suppressing static transfer switch
CN1918769A (zh) * 2004-02-10 2007-02-21 利伯特公司 基于可控硅整流器的静态转换开头装置和方法
CN109787347A (zh) * 2019-01-02 2019-05-21 中国船舶重工集团公司第七一九研究所 一种抑制变压器励磁涌流的双电源切换装置及其切换方法
CN112653229A (zh) * 2020-12-14 2021-04-13 武汉第二船舶设计研究所(中国船舶重工集团公司第七一九研究所) 一种抑制负载变压器励磁涌流的双电源切换装置控制方法
CN117595479A (zh) * 2022-08-17 2024-02-23 台达电子工业股份有限公司 双电源切换系统及其控制方法

Similar Documents

Publication Publication Date Title
US9876390B2 (en) Techniques for improving operation of static transfer switches during voltage disturbances
CN113472058B (zh) 具有自动切换开关的电源供电系统
JP2007522783A (ja) Ｓｃｒベースのスタティック切換えスイッチ装置および方法
JP7708910B2 (ja) 無瞬断電源供給制御装置及びその電源供給制御装置が適用されたｕｐｓモジュール
CN113644647B (zh) 具有零电流切换的备援电路及其备援方法
JP2024028158A (ja) 二重化電源切替システム及びその制御方法
JP4476980B2 (ja) 無瞬断切替装置
CN101512887B (zh) 用于减少三相异步电动机的负载电流中的直流分量的影响的方法和设备
TW200841550A (en) Controlling device and method of power conversion system with function of solving momentary decrease of voltage and power failure
TWI884004B (zh) 電源切換系統
US10014714B2 (en) System and method for uninterruptible power supply intelligent transfer
CN117595479A (zh) 双电源切换系统及其控制方法
TWI885743B (zh) 雙電源切換系統及其操作方法
WO2025175406A1 (zh) 双电源切换系统及其操作方法
JP7734287B1 (ja) デュアル電源切替システム及びその動作方法
WO2024002228A1 (zh) 快速自动转换开关装置及其操作方法
TWI737275B (zh) 具有零電流切換之備援電路及其備援方法
JP7513315B1 (ja) 処理システム、処理方法、およびプログラム
CN117375196A (zh) 固态自动转换开关及其操作方法
JP2003304641A (ja) 電力品質改善方法および電力品質改善装置
JPH03203534A (ja) 負荷分離しゃ断方式
JPS6260474A (ja) ゲ−ト制御方式
JPH0491633A (ja) 冗長型電源装置
JP2000253568A (ja) 位相調整変圧器

Legal Events

Date Code Title Description
121 Ep: the epo has been informed by wipo that ep was designated in this application

Ref document number: 24944988

Country of ref document: EP

Kind code of ref document: A1