WO2023169596A1 - 一种上下行非对称信道模型参数生成方法 - Google Patents

一种上下行非对称信道模型参数生成方法 Download PDF

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WO2023169596A1
WO2023169596A1 PCT/CN2023/087703 CN2023087703W WO2023169596A1 WO 2023169596 A1 WO2023169596 A1 WO 2023169596A1 CN 2023087703 W CN2023087703 W CN 2023087703W WO 2023169596 A1 WO2023169596 A1 WO 2023169596A1
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uplink
downlink
array
sub
angle
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王承祥
王俊
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Southeast University
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Southeast University
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    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B17/00—Monitoring; Testing
    • H04B17/30—Monitoring; Testing of propagation channels
    • H04B17/391—Modelling the propagation channel
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B7/00—Radio transmission systems, i.e. using radiation field
    • H04B7/02—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas
    • H04B7/04—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas
    • H04B7/0408—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas using two or more beams, i.e. beam diversity
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B7/00—Radio transmission systems, i.e. using radiation field
    • H04B7/02—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas
    • H04B7/04—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas
    • H04B7/0413—MIMO systems
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02D—CLIMATE CHANGE MITIGATION TECHNOLOGIES IN INFORMATION AND COMMUNICATION TECHNOLOGIES [ICT], I.E. INFORMATION AND COMMUNICATION TECHNOLOGIES AIMING AT THE REDUCTION OF THEIR OWN ENERGY USE
    • Y02D30/00—Reducing energy consumption in communication networks
    • Y02D30/70—Reducing energy consumption in communication networks in wireless communication networks

Definitions

  • the invention belongs to the technical field of channel modeling, and in particular relates to a method for generating uplink and downlink asymmetric channel model parameters.
  • the main millimeter-wave massive MIMO systems mainly include hybrid multi-beam arrays and fully digital multi-beam arrays.
  • This system has a symmetrical design of multi-beam transmitting and receiving arrays, that is, the number of transmitting channels and receiving channels is the same.
  • the base station side adopts a millimeter-wave hybrid/all-digital multi-beam receiving and transmitting architecture based on symmetrical design to generate transmitting and receiving multi-beams with the same gain.
  • the terminal side design is similar to the base station side, except that the array size is smaller.
  • the basic principle of the asymmetric millimeter wave massive MIMO system is to design the fully digital multi-beam transmitting and receiving arrays asymmetrically, that is, the transmitting array and the receiving array are of different sizes.
  • the base station side adopts a larger-scale all-digital multi-beam transmitting array and a smaller-scale all-digital multi-beam receiving array; thus producing a narrower transmitting multi-beam and a wider receiving multi-beam; the terminal side can still maintain the traditional symmetrical form , can also adopt asymmetric form.
  • the purpose of the present invention is to provide a method for generating uplink and downlink asymmetric channel model parameters to solve the technical problem that existing channel models are mainly generated for a single link and cannot accurately describe the relevant channel characteristics between uplink and downlinks.
  • a method for generating uplink and downlink asymmetric channel model parameters which includes the following steps:
  • Step S1 Determine the antenna configuration of the uplink and downlink transmitter, including the number of elements of the antenna array, the array form, and the arrangement of the sub-arrays, and then use the formula to calculate the three-dimensional pattern of the transceiver antenna sub-array antenna and the uplink and downlink transmission power;
  • Step S2 Generate the scatterer distribution between the downlink antennas, including the number of scatterer clusters, and the path power, delay, and transceiver angle parameters of each cluster and sub-path;
  • Step S3 Calculate the parameters of the uplink based on the channel parameters of the downlink.
  • the process is coordinate transformation to calculate the transmitting and receiving angles of each path of the uplink;
  • Step S4 Generate effective scatterers and effective paths for the uplink and downlink connections based on the three-dimensional pattern of the uplink and downlink transceiver antenna sub-array antennas in step S1, the downlink in step S2, and the path parameters of the uplink in step S3. ;
  • Step S5 Calculate the final channel impulse response of the uplink and downlink.
  • step 1 specifically includes the following steps:
  • R ( ⁇ , ⁇ ) is the direction pattern of the antenna unit
  • a ( ⁇ , ⁇ ) is the array factor
  • ⁇ and ⁇ are the pitch angle and azimuth angle.
  • the array factor calculation formula is:
  • K and L are the number of elements of the antenna array in the x and y directions respectively;
  • d x represents the unit spacing in the x direction
  • d y represents the unit spacing in the y direction
  • a x represents the x of the sub-array in the entire array.
  • the reference position in the direction, a y represents the reference position of the sub-array in the y direction in the entire array;
  • j represents the imaginary unit;
  • step S2 specifically includes the following steps:
  • Step S201 Considering the downlink, calculate the channel parameters between the p-th transmit sub-array and the q-th receive sub-array at the initial time, their straight-line distance D pq , and the initial Rice factor K R0 ;
  • the pitch angle of departure angle is written as The pitch angle of arrival angle is recorded as The azimuth angle of departure angle is written as The azimuth angle of arrival angle is written as
  • Step S202 For non-direct paths, first generate the number N of clusters, the total number of paths M n in the n-th cluster, generate the arrival angles and departure angles of N clusters according to the von Mises distribution, and for the n-th cluster, the pitch of the departure angle The angle is recorded as The pitch angle of arrival angle is recorded as The azimuth angle of departure angle is written as The azimuth angle of arrival angle is written as
  • the delay of the m-th path in the n-th cluster between the p-th transmitting sub-array and the q-th receiving sub-array is expressed as Among them, the superscript D represents the downlink, represents the distance between the p-th transmitting sub-array and the q-th receiving sub-array, Represents the time delay between the first scatterer and the last scatterer, and the calculation formula is: Among them, c is the speed of light, is the first scatterer The straight-line distance between the last scatterer and ⁇ C,link is a random variable obeying an exponential distribution;
  • z n represents the shadow fading of the nth cluster
  • DS represents the root mean square delay spread
  • r ⁇ represents the delay distribution scaling factor, which is determined by the ratio of the standard deviation of the delay to the root mean square delay spread
  • ⁇ n (p, q) represents the lognormal process in two-dimensional space
  • step S3 specifically includes the following steps:
  • the uplink receiving pitch angle emission Pitch angle receiving azimuth Launch azimuth It is calculated specifically by the following formula:
  • step S4 specifically includes the following steps:
  • Step S401 Considering the antenna pattern of the uplink and downlink transceiver ends, calculate the total power of the mth path in the nth cluster of the downlink The calculation formula is
  • Clusters that are greater than the average noise power are valid clusters, and clusters that are less than the average noise power are ignored, and the final set of all valid clusters is obtained.
  • step S5 the final downlink channel impulse response calculated in step S5 is as follows:
  • the invention can establish a geometric random channel model of asymmetric communication, and generates an accurate channel model by simultaneously establishing downlink related channel parameters, and is suitable for analyzing and describing the uplink and downlink situations of asymmetric communication.
  • Figure 1 is a schematic flow chart of a method for generating uplink and downlink asymmetric channel model parameters in Embodiment 1 of the present invention
  • Figure 2 is a schematic diagram of an uplink in the channel model in Embodiment 1 of the present invention.
  • Figure 3 is a schematic diagram of the downlink in the channel model in Embodiment 1 of the present invention.
  • this example provides a method for generating uplink and downlink asymmetric channel model parameters.
  • the schematic diagrams of the model are shown in Figures 2 and 3, which specifically include the following steps:
  • Step S1 First determine the antenna configuration of the uplink and downlink transmitters, including the number of elements of the antenna array, the array form, and the arrangement of the sub-arrays. Then use the formula to calculate the three-dimensional pattern of the sub-array antenna to obtain the uplink and downlink emissions. power.
  • R ( ⁇ , ⁇ ) is the direction pattern of the antenna unit
  • a ( ⁇ , ⁇ ) is the array factor
  • ⁇ and ⁇ are the pitch angle and azimuth angle.
  • the array factor calculation formula is:
  • K and L are the number of elements of the antenna array in the x and y directions respectively.
  • d x represents the unit spacing in the x direction
  • d y represents the unit spacing in the y direction.
  • a x and a y respectively represent the reference positions of the sub-array in the x-direction and y-direction in the entire array.
  • Superscript U is added to all parameters of the uplink channel
  • superscript D is added to all parameters of the uplink channel.
  • Add superscript T to all parameters at the transmitter, and add superscript R to all parameters at the receiver.
  • the receiver antenna pattern of the downlink is F D, R ( ⁇ , ⁇ )
  • the transmitter antenna pattern of the downlink is F D,T ( ⁇ , ⁇ )
  • the uplink receiving end antenna pattern is F U,R ( ⁇ , ⁇ )
  • the uplink transmitting end antenna pattern is F U,T ( ⁇ , ⁇ ).
  • Step S2 Generate scatterer distribution between downlink antennas, including the number of scatterer clusters, and path power, delay, and transmit and receive angle parameters of each cluster and sub-path.
  • Step S201 Considering the downlink, calculate the channel parameters between the p-th transmit sub-array and the q-th receive sub-array at the initial moment, the straight-line distance D pq , the initial Rice factor K R0 , and for the direct path, the departure angle
  • the pitch angle is recorded as
  • the pitch angle of arrival angle is recorded as
  • the azimuth angle of departure angle is written as
  • the azimuth angle of arrival angle is written as
  • Step S202 For non-direct paths, first generate the number N of clusters, the total number of paths M n in the n-th cluster, and generate the arrival angles and departure angles of N clusters according to the von Mises distribution.
  • the departure angle is The elevation angle is recorded as The pitch angle of arrival angle is recorded as The azimuth angle of departure angle is written as The azimuth angle of arrival angle is written as
  • the delay of the m-th path in the n-th cluster between the p-th transmitting sub-array and the q-th receiving sub-array in Represents the time delay between the first scatterer and the last scatterer, and the calculation formula is: Among them, c is the speed of light, is the straight-line distance between the first scatterer and the last scatterer, ⁇ C,link is a random variable obeying exponential distribution.
  • z n represents the shadow fading of the nth cluster
  • DS represents the root mean square delay spread
  • r ⁇ represents the delay distribution scaling factor, which is determined by the ratio of the standard deviation of the delay to the root mean square delay spread
  • ⁇ n (p, q) represents the lognormal process in two-dimensional space
  • Step S3 Calculate the uplink parameters based on the downlink channel parameters, and calculate the sending and receiving angles of each path:
  • the uplink receiving pitch angle Launch pitch angle receiving azimuth Launch azimuth It is calculated specifically by the following formula:
  • Step S4 Generate effective scatterers and effective paths based on the uplink and downlink transceiver antenna patterns, the scatterers in step S2, and the path parameters in step S3;
  • Step S401 Considering the antenna pattern of the uplink and downlink transceiver ends, calculate the total power of the mth path in the nth cluster of the downlink The calculation formula is
  • Clusters that are greater than the average noise power are valid clusters, and clusters that are less than the average noise power are ignored, and the final set of all valid clusters is obtained.
  • Step S5 Calculate the final downlink channel impulse response As follows:

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Abstract

本发明公开了一种上下行非对称信道模型参数生方法。该建模方法在上下行链路使用非对称收发天线配置时可以同时产生上下行链路信道传输矩阵。该方法首先根据环境参数使用几何随机建模方法生成天线间传播信道的参数，随后引入天线方向图，计算得到上下行链路的有效散射体以及对应的有效路径，最后得到上下行链路的信道冲激响应。该方法可以应用于实际的非对称通信系统的仿真优化中。

Description

一种上下行非对称信道模型参数生成方法 技术领域
本发明属于信道建模技术领域，尤其涉及一种上下行非对称信道模型参数生成方法。
背景技术
目前主要的毫米波大规模MIMO系统主要包括混合多波束阵列和全数字多波束阵列，该系统将多波束发射和接收阵列进行对称设计，即发射通道和接收通道数量相同。基站侧采用基于对称设计的毫米波混合/全数字多波束接收和发射架构，产生增益相同的发射和接收多波束。同样，终端侧设计与基站侧较为类似，区别是阵列规模较小。
非对称毫米波大规模MIMO系统基本原理是将全数字多波束发射和接收阵列进行非对称设计,即发射阵列和接收阵列规模不同。基站侧采用较大规模的全数字多波束发射阵列和较小规模的全数字多波束接收阵列；进而产生较窄的发射多波束和较宽的接收多波束；终端侧仍然可以保持传统的对称形式，也可采用非对称形式。
在非对称通信系统中，建立精确的非对称上下链路信道建模至关重要。目前的信道模型主要针对单个链路生成，无法准确描述上下行链路之间的相关的信道特性。因此准确建立非对称上下行链路信道模型是必要的。
发明内容
本发明目的在于提供一种上下行非对称信道模型参数生成方法,以解决现有的信道模型主要针对单个链路生成，无法准确描述上下行链路之间的相关的信道特性的技术问题。
为解决上述技术问题，本发明的具体技术方案如下：
一种上下行非对称信道模型参数生方法，其包括以下步骤：
步骤S1：确定上下行链路首发端的天线配置，包括天线阵列的单元数、组阵形式、子阵的排列，然后利用公式去计算收发天线子阵天线的三维方向图，上下行链路的发射功率；
步骤S2：生成下行链路天线之间的散射体分布，包括散射体簇的数量、以及各个簇和子径的路径功率、时延、收发角度参数；
步骤S3：根据下行链路的信道参数计算上行链路的参数，过程为坐标变换，计算上行链路各条路径的收发角度；
步骤S4：根据步骤S1中上下行链路的收发天线子阵天线的三维方向图、步骤S2中的下行链路和步骤S3中上行链路的路径参数生成上下行联系的有效散射体和有效路径；
步骤S5：计算得到最终上下行链路的信道冲击响应。
进一步的，所述步骤1具体包括以下步骤：
获取上下行链路首发端的总天线数；所有天线由子阵排列构成，发端子阵总数为P，收端子阵总数为Q，子阵天线的三维方向计算公式为
F(φ,θ)＝R(φ,θ)A(φ,θ)
其中，R(φ,θ)为天线单元的方向图，A(φ,θ)为阵因子，φ和θ为俯仰角和方位角，对平面阵列，阵因子计算公式为
其中，K和L分别为天线阵列在x和y方向上的单元数量；其中，dx表示为x方向上的单元间距，dy表示y方向上的单元间距；ax表示子阵的在整个阵列中的x 方向上的参考位置，ay表示子阵的在整个阵列中y方向上的参考位置；j表示虚数单位；
上行链路信道所有参数添加上标U，上行链路信道所有参数添加上标D；发射端所有参数添加上标T，接收端所有参数添加上标R，得到下行链路的接收端天线方向图为FD,R(φ,θ)，下行链路的发射端天线方向图为FD,T(φ,θ)，上行链路的接收端天线方向图为FU,R(φ,θ)，上行链路的发射端天线方向图为FU,T(φ,θ)。
进一步的，所述步骤S2具体包括以下步骤：
步骤S201：考虑下行链路，计算初始时刻第p个发射子阵和第q个接收子阵之间的信道参数，其直线距离Dpq，初始莱斯因子KR0；
对于直射径，离开角的俯仰角记为到达角的俯仰角记为离开角的方位角记为到达角的方位角记为
步骤S202：对非直射径，首先生成簇的数量N，第n簇内总径数Mn，根据冯米瑟斯分布生成N个簇的到达角和离开角，对第n个簇，离开角的俯仰角记为到达角的俯仰角记为离开角的方位角记为到达角的方位角记为
然后在每个簇内随机生成子径，子径的角度服从高斯分布；第p个发射子阵和第q个接收子阵之间的第n个簇内第m条径的时延表示为 其中，上标D表示下行链路，表示第p个发射子阵和第q个接收子阵之间距离，表示第一个散射体和最后一个散射体之间的时延，计算公式为其中，c为光速，为第一个散射体 和最后一个散射体之间的直线距离，τC,link为服从指数分布的随机变量；
每条径功率计算公式如下
其中，zn表示第n个簇的阴影衰落，DS表示均方根时延扩展，rτ表示时延分布比例因子，由时延的标准差与均方根时延扩展的比值决定；ζn(p,q)表示二维空间对数正态过程；
若簇内的径无法分辨，将上式中的时延替换为并用下式计算
进一步的，所述步骤S3具体包括以下步骤：
根据可逆原理，在不考虑非对称天线配置时，上下行的路径对称，收发端互换，因此，下行链路中生成的簇的数量、子径数量不变，功率不变，角度需要进行相应变换，对直射径，包括上行链路接收俯仰角发射俯仰角接收方位角发射方位角具体由下公式计算得到
直射径：



其中，
对非直射径的第n个簇内第m条径，上行链路接收俯仰角发射 俯仰角接收方位角发射方位角具体由下公式计算得到：



进一步的，所述步骤S4具体包括以下步骤：
步骤S401：考虑上下行链路收发端的天线方向图，计算下行链路第n个簇内第m条径的总功率计算公式为
上行链路第n个簇内第m条径的总功率计算公式为
求得下行链路每个簇的总功率计算公式为
上行链路每个簇的总功率计算公式为
将计算后得到的簇功率和平均噪声功率做对比，大于平均噪声功率的簇则为有效簇，小于平均噪声功率的簇忽略不计，得到最后所有的有效簇的合集。
进一步的，所述步骤S5中计算得到最终下行链路的信道冲击响应如下所示：
上行链路的信道冲击响应如下所示
本发明的一种上下行非对称信道模型参数生成方法，具有以下优点：
本发明能建立一个非对称通信的几何随机信道模型，通过同时建立下行链路相关的信道参数，从而生成准确的信道模型，适用于分析描述非对称通信的上下行链路的情况。
附图说明
图1为本发明的实施例1中一种上下行非对称信道模型参数生成方法的流程示意图；
图2为本发明的实施例1中信道模型中上行链路的示意图；
图3为本发明的实施例1中信道模型中下行链路的示意图。
具体实施方式
为了更好地了解本发明的目的、结构及功能，下面结合附图，对本发明一种上下行非对称信道模型参数生成方法做进一步详细的描述。
实施例1
如图1所示，本实例提供了一种上下行非对称信道模型参数生成方法，模型的示意图如图2和图3所示，具体包括以下步骤：
步骤S1：首先确定上下行链路首发端的天线配置，包括天线阵列的单元数、组阵形式、子阵的排列，然后利用公式去计算子阵天线的三维方向图，获取上下行链路的发射功率。
获取上下行链路首发端的总天线数；所有天线由子阵排列构成，发端和 收端子阵总数分别为P和Q，天线方向图计算公式为
F(φ,θ)＝R(φ,θ)A(φ,θ)
其中，R(φ,θ)为天线单元的方向图，A(φ,θ)为阵因子，φ和θ为俯仰角和方位角，对平面阵列，阵因子计算公式为
其中，K和L分别为天线阵列在x和y方向上的单元数量。其中，dx表示为x方向上的单元间距，dy表示y方向上的单元间距。ax和ay分别表示子阵的在整个阵列中的x方向和y方向上的参考位置。
上行链路信道所有参数添加上标U，上行链路信道所有参数添加上标D。发射端所有参数添加上标T，接收端所有参数添加上标R，得到下行链路的接收端天线方向图为FD,R(φ,θ)，下行链路的发射端天线方向图为FD,T(φ,θ)，上行链路的接收端天线方向图为FU,R(φ,θ)，上行链路的发射端天线方向图为FU,T(φ,θ)。
步骤S2：生成下行链路天线之间的散射体分布，包括散射体簇的数量、以及各个簇和子径的路径功率、时延、收发角度参数。
步骤S201：考虑下行链路，计算初始时刻第p个发射子阵和第q个接收子阵之间的信道参数，其直线距离Dpq，初始莱斯因子KR0，对于直射径，离开角的俯仰角记为到达角的俯仰角记为离开角的方位角记为到达角的方位角记为
步骤S202：对非直射径，首先生成簇的数量N，第n簇内总径数Mn，根据冯米瑟斯分布生成N个簇的到达角和离开角，对第n个簇，离开角的俯 仰角记为到达角的俯仰角记为离开角的方位角记为到达角的方位角记为
然后在每个簇内随机生成子径，子径的角度服从高斯分布；第p个发射子阵和第q个接收子阵之间的第n个簇内第m条径的时延其中，表示第一个散射体和最后一个散射体之间的时延，计算公式为其中，c为光速，为第一个散射体和最后一个散射体之间的直线距离，τC,link为服从指数分布的随机变量。
每条径功率计算公式如下
其中，zn表示第n个簇的阴影衰落，DS表示均方根时延扩展，rτ表示时延分布比例因子，由时延的标准差与均方根时延扩展的比值决定；ζn(p,q)表示二维空间对数正态过程；
若簇内的径无法分辨，将上式中的时延替换为并用下式计算
步骤S3：根据下行链路的信道参数计算上行链路的参数，计算各条路径的收发角度：
根据可逆原理，在不考虑非对称天线配置时，上下行的路径对称，收发端互换，因此，下行链路中生成的簇的数量、子径数量不变，功率不变，角度需要进行相应变换，对直射径，包括上行链路接收俯仰角发射俯仰角接收方位角发射方位角具体由下公式计算得到
直射径：



对非直射径的第n个簇内第m条径，上行链路接收俯仰角发射俯仰角接收方位角发射方位角具体由下公式计算得到：



步骤S4：根据上下行链路的收发天线方向图、步骤S2中的散射体和步骤S3中的路径参数生成有效散射体和有效路径；
步骤S401：考虑上下行链路收发端的天线方向图，计算下行链路第n个簇内第m条径的总功率计算公式为
上行链路第n个簇内第m条径的总功率计算公式为
求得下行链路每个簇的总功率计算公式为
上行链路每个簇的总功率计算公式为
将计算后得到的簇功率和平均噪声功率做对比，大于平均噪声功率的簇则为有效簇，小于平均噪声功率的簇忽略不计，得到最后所有的有效簇的合集。
步骤S5：计算得到最终下行链路的信道冲击响应如下所示：
上行链路的信道冲击响应如下所示
可以理解，本发明是通过一些实施例进行描述的，本领域技术人员知悉的，在不脱离本发明的精神和范围的情况下，可以对这些特征和实施例进行各种改变或等效替换。另外，在本发明的教导下，可以对这些特征和实施例进行修改以适应具体的情况及材料而不会脱离本发明的精神和范围。因此，本发明不受此处所公开的具体实施例的限制，所有落入本申请的权利要求范围内的实施例都属于本发明所保护的范围内。

Claims (6)

  1. 一种上下行非对称信道模型参数生方法，其特征在于，包括以下步骤：
    步骤S1：确定上下行链路首发端的天线配置，包括天线阵列的单元数、组阵形式、子阵的排列，然后利用公式去计算收发天线子阵天线的三维方向图，上下行链路的发射功率；
    步骤S2：生成下行链路天线之间的散射体分布，包括散射体簇的数量、以及各个簇和子径的路径功率、时延、收发角度参数；
    步骤S3：根据下行链路的信道参数计算上行链路的参数，过程为坐标变换，计算上行链路各条路径的收发角度；
    步骤S4：根据步骤S1中上下行链路的收发天线子阵天线的三维方向图、步骤S2中的下行链路和步骤S3中上行链路的路径参数生成上下行联系的有效散射体和有效路径；
    步骤S5：计算得到最终上下行链路的信道冲击响应。
  2. 根据权利要求1所述的上下行非对称信道模型参数生方法，其特征在于，所述步骤1具体包括以下步骤：
    获取上下行链路首发端的总天线数；所有天线由子阵排列构成，发端子阵总数为P，收端子阵总数为Q，子阵天线的三维方向计算公式为
    F(φ,θ)＝R(φ,θ)A(φ,θ)
    其中，R(φ,θ)为天线单元的方向图，A(φ,θ)为阵因子，φ和θ为俯仰角和方位角，对平面阵列，阵因子计算公式为
    其中，K和L分别为天线阵列在x和y方向上的单元数量；其中，dx表示为x方向 上的单元间距，dy表示y方向上的单元间距；ax表示子阵的在整个阵列中的x方向上的参考位置，ay表示子阵的在整个阵列中y方向上的参考位置；j表示虚数单位；
    上行链路信道所有参数添加上标U，上行链路信道所有参数添加上标D；发射端所有参数添加上标T，接收端所有参数添加上标R，得到下行链路的接收端天线方向图为FD,R(φ,θ)，下行链路的发射端天线方向图为FD,T(φ,θ)，上行链路的接收端天线方向图为FU,R(φ,θ)，上行链路的发射端天线方向图为FU,T(φ,θ)。
  3. 根据权利要求2所述的上下行非对称信道模型参数生方法，其特征在于，所述步骤S2具体包括以下步骤：
    步骤S201：考虑下行链路，计算初始时刻第p个发射子阵和第q个接收子阵之间的信道参数，其直线距离Dpq，初始莱斯因子KR0；
    对于直射径，离开角的俯仰角记为到达角的俯仰角记为离开角的方位角记为到达角的方位角记为
    步骤S202：对非直射径，首先生成簇的数量N，第n簇内总径数Mn，根据冯米瑟斯分布生成N个簇的到达角和离开角，对第n个簇，离开角的俯仰角记为到达角的俯仰角记为离开角的方位角记为到达角的方位角记为
    然后在每个簇内随机生成子径，子径的角度服从高斯分布；第p个发射子阵和第q个接收子阵之间的第n个簇内第m条径的时延表示为 其中，上标D表示下行链路，表示第p个发射子阵和第q个接收子阵之间距离，表示第一个散射体和最后一个散射体之间的时延，计算公式为其中，c为光速，为第一个散射体 和最后一个散射体之间的直线距离，τC,link为服从指数分布的随机变量；
    每条径功率计算公式如下
    其中，zn表示第n个簇的阴影衰落，DS表示均方根时延扩展，rτ表示时延分布比例因子，由时延的标准差与均方根时延扩展的比值决定；ζn(p,q)表示二维空间对数正态过程；
    若簇内的径无法分辨，将上式中的时延替换为并用下式计算
  4. 根据权利要求3所述的上下行非对称信道模型参数生方法，其特征在于，所述步骤S3具体包括以下步骤：
    根据可逆原理，在不考虑非对称天线配置时，上下行的路径对称，收发端互换，因此，下行链路中生成的簇的数量、子径数量不变，功率不变，角度需要进行相应变换，对直射径，包括上行链路接收俯仰角发射俯仰角接收方位角发射方位角具体由下公式计算得到
    直射径：



    其中，
    对非直射径的第n个簇内第m条径，上行链路接收俯仰角发射 俯仰角接收方位角发射方位角具体由下公式计算得到：



  5. 根据权利要求4所述的上下行非对称信道模型参数生方法，其特征在于，所述步骤S4具体包括以下步骤：
    步骤S401：考虑上下行链路收发端的天线方向图，计算下行链路第n个簇内第m条径的总功率计算公式为
    上行链路第n个簇内第m条径的总功率计算公式为
    求得下行链路每个簇的总功率计算公式为
    上行链路每个簇的总功率计算公式为
    将计算后得到的簇功率和平均噪声功率做对比，大于平均噪声功率的簇则为有效簇，小于平均噪声功率的簇忽略不计，得到最后所有的有效簇的合集。
  6. 根据权利要求5所述的上下行非对称信道模型参数生方法，其特征在于，所述步骤S5中计算得到最终下行链路的信道冲击响应如下所示：
    上行链路的信道冲击响应如下所示
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