WO2015161593A1 - Method and device for measuring wireless channel response of td-lte system - Google Patents

Method and device for measuring wireless channel response of td-lte system Download PDF

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WO2015161593A1
WO2015161593A1 PCT/CN2014/084864 CN2014084864W WO2015161593A1 WO 2015161593 A1 WO2015161593 A1 WO 2015161593A1 CN 2014084864 W CN2014084864 W CN 2014084864W WO 2015161593 A1 WO2015161593 A1 WO 2015161593A1
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frequency
signal
measurement
lte
delay
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PCT/CN2014/084864
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French (fr)
Chinese (zh)
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谈振辉
张金宝
章嘉懿
董宇辉
赵亚军
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中兴通讯股份有限公司
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    • HELECTRICITY
    • H04ELECTRIC COMMUNICATION TECHNIQUE
    • H04LTRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00Modulated-carrier systems
    • H04L27/26Systems using multi-frequency codes

Abstract

Embodiments of the present invention provide a method and device for measuring a wireless channel response of a TD-LTE system and apply to measuring the wireless channel response of a high speed rail TD-LTE system. In the measurement, a frequency point of a measurement sub-carrier and measurement sampling time are determined according to a symbol bandwidth and a symbol period of an orthogonal frequency division multiplexing signal in the TD-LTE system; a linear frequency modulation pulse measurement signal which can achieve an optimal resolution in a time domain and a frequency domain is generated in the determined frequency point of the measurement sub-carrier according to the determined measurement sampling time; after modulation, the linear frequency modulation pulse measurement signal is input to the wireless channel of the TD-LTE system; the linear frequency modulation pulse measurement signal output by the TD-LTE system is received in the corresponding frequency point of the sub-carrier and an autocorrelation value of the received linear frequency modulation pulse measurement signal is obtained; and a frequency offset and a time delay of the carrier center frequency point of the orthogonal frequency division multiplexing signal are obtained according to the autocorrelation value, then a strength value of the wireless channel impulse response is obtained by combining the wireless channel responses according to the obtained frequency offset and time delay. Comparatively accurate results can be simultaneously obtained in the frequency domain and the time domain.

Description

TD-LTE系统无线信道响应测量方法及装置 技术领域  TD-LTE system wireless channel response measurement method and device
本发明涉及通信领域, 具体涉及一种时分长期演进 ( Time Division Long Term Evolution, TD-LTE ) 系统无线信道响应测量方法及装置。  The present invention relates to the field of communications, and in particular, to a method and apparatus for measuring a wireless channel response of a Time Division Long Term Evolution (TD-LTE) system.
背景技术 随着世界范围内高速铁路的飞速发展, 高铁系统本身以及高铁乘客对高 铁宽带无线通信提出的更高的需求。 针对这一趋势, 建立高铁 TD-LTE系统 无线信道模型, 特别是其快衰落模型, 在高铁宽带无线通信系统的研究、 分 析、 设计与优化中具有非常重要的意义与价值。 而且, 所使用信道模型的准 确与否直接影响高铁宽带无线通信的性能。 为了保证高铁宽带无线信道模型 的准确和有效, 需要对高铁 TD-LTE系统无线通信信号实际经历的无线信道 特征与参数进行准确的测量。 BACKGROUND OF THE INVENTION With the rapid development of high-speed railways around the world, the high-speed rail system itself and high-speed rail passengers have placed higher demands on high-speed rail broadband wireless communications. In response to this trend, the establishment of the high-speed rail TD-LTE system wireless channel model, especially its fast fading model, has very important significance and value in the research, analysis, design and optimization of high-speed rail broadband wireless communication systems. Moreover, the accuracy of the channel model used directly affects the performance of high-speed rail broadband wireless communications. In order to ensure the accuracy and efficiency of the high-speed rail broadband channel model, it is necessary to accurately measure the wireless channel characteristics and parameters actually experienced by the high-speed rail TD-LTE system wireless communication signals.
高铁 TD-LTE 系统使用正交频分复用 (OFDM )信号作为信息的载体, 对频率偏移很敏感; 同时, OFDM信号传输需要经历复杂的多径环境, 对时 间延迟也比较敏感; 因此, 信道测量需要兼顾时域和频域的分辨率。 然而, 在无线信道测量领域, 主要存在和使用的是时域和频域两种测量方法。 其中, 时域测量方法利用接收信号与激励脉冲信号模板之间的相关性, 提取无线信 道的多径延迟特征, 主要存在的问题是: 为了获取准确的多径信号时间延迟 量, 必须使用很窄的激励脉冲信号, 一方面给接收信号的测量带来困难, 另 一方面使得测量结果在频域的分辨率不足, 使根据该测量结果最终得到的无 线信道冲击响应强度值在频域上参考价值有限。 而频域测量方法利用接收信 号频谱的反变换导出多径延迟特征, 降低了接收信号测量过程中的难度, 其 主要存在的问题是: 对接收信号进行频谱测量时需要扫描频率, 在扫频过程 中, 信道的快衰落特征有可能发生比较大的变化, 使得测量结果在时域上的 分辨率不足, 使根据该测量结果最终得到的无线信道冲击响应强度值在时域 上参考价值有限。 目前, 还没有针对高铁 TD-LTE系统同时保证其时域和频 域分辨率, 从而无法在时域和频域获取到准确测量结果的问题。 发明内容 The high-speed rail TD-LTE system uses Orthogonal Frequency Division Multiplexing (OFDM) signals as the carrier of information, which is sensitive to frequency offset. At the same time, OFDM signal transmission needs to go through a complex multipath environment and is sensitive to time delay; therefore, Channel measurement requires both time and frequency domain resolution. However, in the field of wireless channel measurement, there are mainly two methods of measurement in time domain and frequency domain. The time domain measurement method utilizes the correlation between the received signal and the excitation pulse signal template to extract the multipath delay characteristic of the wireless channel. The main problems are: To obtain accurate multipath signal time delay, it must be used very narrowly. The excitation pulse signal, on the one hand, brings difficulties to the measurement of the received signal, on the other hand, the resolution of the measurement result in the frequency domain is insufficient, so that the wireless channel impulse response intensity value finally obtained according to the measurement result is reference value in the frequency domain. limited. The frequency domain measurement method uses the inverse transform of the received signal spectrum to derive the multipath delay feature, which reduces the difficulty in the measurement process of the received signal. The main problems are: the scanning frequency is required for the spectrum measurement of the received signal, during the frequency sweeping process. In the middle, the fast fading characteristics of the channel may undergo relatively large changes, so that the measurement results are in the time domain. The resolution is insufficient, so that the wireless channel impulse response intensity value finally obtained according to the measurement result has a limited reference value in the time domain. At present, there is no problem for the high-speed rail TD-LTE system to ensure its time domain and frequency domain resolution at the same time, so that accurate measurement results cannot be obtained in the time domain and the frequency domain. Summary of the invention
本发明实施例提供一种 TD-LTE系统无线信道响应测量方法及装置,解决 现有对高铁 TD-LTE 系统无线信道响应进行测量不能同时在时域和频域获取 到准确结果的问题。  The embodiment of the invention provides a method and a device for measuring a wireless channel response of a TD-LTE system, which solves the problem that the current wireless channel TD-LTE system wireless channel response measurement cannot obtain accurate results in both the time domain and the frequency domain.
本发明要解决的主要技术问题是,提供一种 TD-LTE系统无线信道响应测 量方法及装置,解决现有对高铁 TD-LTE系统无线信道响应进行测量不能同时 在时域和频域获取到准确结果的问题。  The main technical problem to be solved by the present invention is to provide a method and a device for measuring a wireless channel response of a TD-LTE system, and to solve the existing measurement of the wireless channel response of the high-speed rail TD-LTE system, which cannot be accurately acquired in the time domain and the frequency domain at the same time. The problem with the result.
为解决上述问题, 本发明提供一种 TD-LTE系统无线信道响应测量方法, 所述 TD-LTE系统具有多径无线信道,相对地面的速度大于等于 300千米每小 时; 所述无线信道响应测量方法包括:  To solve the above problem, the present invention provides a radio channel response measurement method for a TD-LTE system, where the TD-LTE system has a multipath radio channel, and a speed relative to the ground is greater than or equal to 300 km/h; the radio channel response measurement Methods include:
才艮据所述 TD-LTE系统的正交频分复用信号的符号带宽和符号周期确定 测量子载波频点和测量釆样时刻;  Determining, according to the symbol bandwidth and symbol period of the orthogonal frequency division multiplexed signal of the TD-LTE system, measuring the subcarrier frequency point and measuring the sampling time;
在所述测量子载波频点上根据所述测量釆样时刻生成线性调频脉冲测量 信号;  Generating a chirped pulse measurement signal according to the measurement sample time at the measurement subcarrier frequency point;
将所述线性调频脉冲测量信号调制处理后输入所述 TD-LTE系统的无线 信道;  And modulating the chirped pulse measurement signal into a wireless channel of the TD-LTE system;
在相应的子载波频点上接收经所述 TD-LTE系统输出的线性调频脉冲测 量信号并得到接收的线性调频脉冲测量信号的自相关值;  Receiving a chirp measurement signal outputted by the TD-LTE system at a corresponding subcarrier frequency point and obtaining an autocorrelation value of the received chirp signal measurement signal;
根据所述自相关值得到所述正交频分复用信号载波中心频点的频偏和时 延;  And obtaining, according to the autocorrelation value, a frequency offset and a delay of a center frequency point of the orthogonal frequency division multiplexed signal carrier;
基于得到的频偏和时延进行无线信道响应合成处理得到无线信道冲击响 应强度值。 Wireless channel response synthesis processing based on the obtained frequency offset and delay to obtain a wireless channel impact response Should be the intensity value.
在本发明的一种实施例中, 基于得到的频偏和时延进行无线信道响应 合成处理得到无线信道冲击响应强度值之前, 还包括:  In an embodiment of the present invention, before the wireless channel response synthesis process is performed based on the obtained frequency offset and delay to obtain the wireless channel impulse response strength value, the method further includes:
根据所述载波中心频点的频偏和时延推算所述正交频分复用信号符号带 宽内至少一个其他子载波频点的频偏和时延。  Deriving a frequency offset and a delay of at least one other subcarrier frequency point in the symbol bandwidth of the orthogonal frequency division multiplexed signal according to a frequency offset and a time delay of the carrier center frequency point.
在本发明的一种实施例中, 根据所述正交频分复用信号的符号带宽和符 号周期确定测量子载波频点和测量釆样时刻包括:  In an embodiment of the present invention, determining the measurement subcarrier frequency point and the measurement sampling time according to the symbol bandwidth and the symbol period of the orthogonal frequency division multiplexing signal includes:
在所述正交频分复用信号的符号带宽内等间隔选择 个子载波频点作为 测量子载波频点, 所述 N/大于等于 1 ;  And selecting, according to a symbol bandwidth of the orthogonal frequency division multiplexing signal, a subcarrier frequency point as a measurement subcarrier frequency point, wherein the N/ is greater than or equal to 1;
在所述正交频分复用信号的符号周期内等间隔选择^个釆样时刻作为测 量釆样时刻, 所述 ^大于等于 1。  The sampling time is selected at equal intervals in the symbol period of the orthogonal frequency division multiplexed signal as the measurement sampling time, and the ^ is greater than or equal to 1.
在本发明的一种实施例中, 在所述测量子载波频点上根据所述测量釆样 时刻生成线性调频脉冲测量信号包括:  In an embodiment of the invention, generating the chirp measurement signal according to the measurement time instant on the measurement subcarrier frequency point includes:
在每个测量子载波频点上, 在每个测量釆样时刻生成一个线性调频脉冲 测量信号; 生成的线性调频脉冲测量信号的频域宽和时域宽度分别小于等于 所述正交频分复用信号的子载波带宽和奈奎斯特釆样周期。  At each measurement subcarrier frequency point, a chirp measurement signal is generated at each measurement sampling time; the frequency domain width and the time domain width of the generated chirp measurement signal are respectively less than or equal to the orthogonal frequency division complex Use the subcarrier bandwidth of the signal and the Nyquist sampling period.
在本发明的一种实施例中, 将所述线性调频脉冲测量信号调制处理后输 入所述 TD-LTE系统的无线信道包括:  In an embodiment of the present invention, the wireless channel input to the TD-LTE system after the chirp measurement signal is processed and processed comprises:
利用 N/xNf阶二维扰码 C对所述线性调频脉冲测量信号进行调制得到激 励信号, 所述 NfxNt阶二维扰码 C中的元素 为 +1或 -1; 所述 m大于等于 0, 小于等于 -1; 所述 n大于等于 0, 小于等 The chirp signal is modulated by the N/xN f- order two-dimensional scrambling code C to obtain an excitation signal, and the element in the N f xN t- order two-dimensional scrambling code C is +1 or -1; Greater than or equal to 0, less than or equal to -1; the n is greater than or equal to 0, less than, etc.
将得到的激励信号输入所述 TD-LTE系统的无线信道。  The resulting excitation signal is input to the wireless channel of the TD-LTE system.
在本发明的一种实施例中, 在相应的子载波频点上接收经所述 TD-LTE 系统输出的线性调频脉冲测量信号并得到接收的线性调频脉冲测量信号的自 相关值包括: 设置 N 2N个信号接收器, 所述 N/为选择的子载波频点个数; 所述 N为 对所述正交频分复用信号的最大频偏值除以所述正交频分复用信号的子载波 带宽得到的值进行取整; In an embodiment of the present invention, the auto-correlation value of the chirp measurement signal outputted by the TD-LTE system and received by the TD-LTE system at the corresponding sub-carrier frequency point and obtained is: Setting N 2N signal receivers, the N/ is a selected number of subcarrier frequency points; the N is a maximum frequency offset value of the orthogonal frequency division multiplexed signal divided by the orthogonal frequency division Rounding up the value obtained from the subcarrier bandwidth of the signal;
利用所述信号接收器在相应的子载波频点上接收经所述 TD-LTE系统输 出的线性调频脉冲测量信号并输出接收的线性调频脉冲测量信号的自相关值 R。  The chirp signal outputted by the TD-LTE system is received by the signal receiver at a corresponding subcarrier frequency point and the autocorrelation value R of the received chirp signal measurement signal is output.
在本发明的一种实施例中, 根据所述自相关值得到所述正交频分复用信 号载波中心频点的频偏和时延包括:  In an embodiment of the present invention, obtaining a frequency offset and a delay of the center frequency of the orthogonal frequency division multiplexing signal carrier according to the autocorrelation value includes:
利用所述^^<^阶二维扰码 C对所述自相关值 进行时域和频域的二维 滑动相关计算, 得到所述正交频分复用信号载波中心频点的频偏 /和时延7。  Performing a two-dimensional sliding correlation calculation of the autocorrelation value in the time domain and the frequency domain by using the two-dimensional scrambling code C of the ^^<^ step, obtaining a frequency offset of the center frequency of the orthogonal frequency division multiplexing signal carrier/ And delay 7.
在本发明的一种实施例中, 根据所述载波中心频点的频偏推算所述正 交频分复用信号符号带宽内至少一个其他子载波频点的频偏和时延为: 根据 所述载波中心频点的频偏和时延推算所述正交频分复用信号符号带宽内其他 所有子载波频点的频偏和时延。  In an embodiment of the present invention, estimating a frequency offset and a delay of at least one other subcarrier frequency point in a symbol bandwidth of the orthogonal frequency division multiplexing signal according to a frequency offset of the carrier center frequency point: The frequency offset and the delay of the carrier center frequency point are used to estimate the frequency offset and delay of all other subcarrier frequency points in the symbol bandwidth of the orthogonal frequency division multiplexed signal.
在本发明的一种实施例中, 根据所述载波中心频点的频偏推算所述正 交频分复用信号符号带宽内其他所有子载波频点的频偏包括:  In an embodiment of the present invention, calculating, according to the frequency offset of the carrier center frequency point, a frequency offset of all other subcarrier frequency points in the symbol bandwidth of the orthogonal frequency division multiplexing signal includes:
根据所述频偏 /,利用多普勒频偏理论计算公式计算得到所述激励信号的 到达角 φ  Calculating the angle of arrival of the excitation signal using the Doppler frequency offset theory calculation formula according to the frequency offset /
Fc - f 二 Fc ∞s(p F c - f two F c ∞s(p
c  c
所述 为所述载波中心频点频率, 所述/为正交频分复用信号载波中心 频点的频偏, 所述 V为所述 TD-LTE系统当前的速度 , 所述 c为光速;  The frequency of the carrier center frequency, the / is the frequency offset of the center frequency of the orthogonal frequency division multiplexing signal carrier, the V is the current speed of the TD-LTE system, and the c is the speed of light;
取所述激励信号在各子载波频点上的到达角都为 φ, 将该到达角 φ带入 多普勒频偏理论计算公式得到各子载波频点上频偏值: fk 二 Fk—Fk—∞S (p The angle of arrival of the excitation signal at each subcarrier frequency point is φ, and the angle of arrival φ is brought into the Doppler frequency offset theoretical calculation formula to obtain the frequency offset value at each subcarrier frequency point: Fk 二F k— F k—∞S (p
c  c
所述 为第 k个子载波频点的频率, 所述 Λ为第 k个子载波频点的频 偏, 所述 k大于等于 1 , 小于等于所述正交频分复用信号符号带宽内的子载 波频点个数。  The frequency is the frequency of the kth subcarrier frequency point, the Λ is the frequency offset of the kth subcarrier frequency point, and the k is greater than or equal to 1, and is less than or equal to the subcarrier within the symbol bandwidth of the orthogonal frequency division multiplexed signal. Frequency points.
在本发明的一种实施例中, 根据所述载波中心频点的时延推算所述正 交频分复用信号符号带宽内其他所有子载波频点的时延包括:  In an embodiment of the present invention, estimating, according to a delay of the carrier center frequency point, a delay of all other subcarrier frequency points in the symbol bandwidth of the orthogonal frequency division multiplexing signal includes:
取所述正交频分复用信号符号带宽内各子载波频点的时延都等于7。  The delay of each subcarrier frequency point in the symbol bandwidth of the orthogonal frequency division multiplexing signal is equal to 7.
在本发明的一种实施例中, 基于得到的所有子载波频点的频偏和时延进行无 线信道响应合成处理得到无线信道冲击响应强度值包括: In an embodiment of the present invention, the wireless channel impulse response strength value obtained by performing the wireless channel response synthesis processing based on the obtained frequency offset and delay of all subcarrier frequency points includes:
根据多普勒频偏的数据对经典多径信道模型进行无线信道合成处理:
Figure imgf000007_0001
The wireless channel synthesis processing is performed on the classical multipath channel model according to the Doppler frequency offset data:
Figure imgf000007_0001
p k 所述 d)为无线信道冲击响应强度值, 所述 p表示时延个数, 所述 k表 示频偏个数, 所述^¾为第 p个时延、 第 k个频偏的多径信号分量的信号强度 值; 所述 Λι为第 kl个频偏, 所述 kl大于等于 1 , 小于等于所述 K; 所述 为第 pi个时延, 所述 pi大于等于 1 , 小于等于所述 P; 所述 (t- )为时刻 t 输入的单位脉冲信号在时延 τρ处的响应脉冲, t为当前测量的时刻。 Pk, the d) is a wireless channel impulse response strength value, the p represents the number of delays, the k represents the number of frequency offsets, and the ^3⁄4 is the p-th delay, the k-th frequency-off multipath a signal strength value of the signal component; the Λι is the k1th frequency offset, the k1 is greater than or equal to 1, and less than or equal to the K; the pi is the pi delay, the pi is greater than or equal to 1, and less than or equal to the P; (t-) is the response pulse of the unit pulse signal input at time t at time delay τ ρ , and t is the current measurement time.
为了解决上述问题, 本发明实施例还提供了一种 TD-LTE系统无线信道 响应测量装置, 所述 TD-LTE系统具有多径无线信道, 相对地面的速度大于 等于 300千米每小时; 所述测量装置包括测量参数确定模块、 测量信号生成 模块、 测量信号处理模块、 测量信号接收模块、 第一计算模块和合成处理模 块;  In order to solve the above problem, an embodiment of the present invention further provides a TD-LTE system radio channel response measuring apparatus, where the TD-LTE system has a multipath radio channel, and a speed relative to the ground is greater than or equal to 300 km/h; The measuring device comprises a measurement parameter determination module, a measurement signal generation module, a measurement signal processing module, a measurement signal receiving module, a first calculation module and a synthesis processing module;
所述测量参数确定模块设置为根据所述 TD-LTE系统的正交频分复用信 号的符号带宽和符号周期确定测量子载波频点和测量釆样时刻; 所述测量信号生成模块设置为在所述测量子载波频点上 4艮据所述测量釆 样时刻生成线性调频脉冲测量信号; The measurement parameter determining module is configured to be based on the orthogonal frequency division multiplexing signal of the TD-LTE system The symbol bandwidth and the symbol period of the number determine the measurement subcarrier frequency point and the measurement sample time; the measurement signal generation module is configured to generate the chirp measurement at the measurement subcarrier frequency point according to the measurement sample time signal;
所述测量信号处理模块设置为将所述线性调频脉冲测量信号调制处理后 输入所述 TD-LTE系统的无线信道;  The measurement signal processing module is configured to modulate the chirp measurement signal into a wireless channel of the TD-LTE system;
所述测量信号接收模块设置为在相应的子载波频点上接收经所述 TD-LTE 系统输出的线性调频脉冲测量信号并得到接收的线性调频脉冲测量 信号的自相关值;  The measurement signal receiving module is configured to receive a chirp measurement signal outputted by the TD-LTE system at a corresponding subcarrier frequency point and obtain an autocorrelation value of the received chirp signal measurement signal;
所述第一计算模块设置为根据所述自相关值得到所述正交频分复用信号 载波中心频点的频偏和时延;  The first calculating module is configured to obtain a frequency offset and a delay of a center frequency point of the orthogonal frequency division multiplexing signal carrier according to the autocorrelation value;
所述合成处理模块设置为基于得到的频偏和时延进行无线信道响应合成 处理得到无线信道冲击响应强度值。  The synthesis processing module is configured to perform a wireless channel response synthesis process based on the obtained frequency offset and delay to obtain a wireless channel impulse response strength value.
在本发明的一种实施例中, 还包括第二计算模块, 设置为在所述合成处 理模块基于得到的频偏和时延进行无线信道响应合成处理得到无线信道冲击 响应强度值之前, 根据所述第一计算模块得到的载波中心频点的频偏和时延 推算所述正交频分复用信号符号带宽内至少一个其他子载波频点的频偏和时 延。  In an embodiment of the present invention, the method further includes: a second calculating module, configured to: before the synthesizing processing module performs a radio channel response synthesis process based on the obtained frequency offset and delay to obtain a radio channel impulse response strength value, according to the The frequency offset and the delay of the carrier center frequency point obtained by the first calculation module are used to estimate the frequency offset and the delay of at least one other subcarrier frequency point in the symbol bandwidth of the orthogonal frequency division multiplexed signal.
在本发明的一种实施例中, 所述测量参数确定模块包括频点确定子模块 和釆样时刻确定子模块;  In an embodiment of the present invention, the measurement parameter determination module includes a frequency point determination submodule and a sample time determination submodule;
所述频点确定子模块设置为在所述正交频分复用信号的符号带宽内等间 隔选择 N/个子载波频点作为测量子载波频点, 所述 N/大于等于 1 ;  The frequency point determining submodule is configured to select N/s subcarrier frequency points as measurement subcarrier frequency points in an equal interval within a symbol bandwidth of the orthogonal frequency division multiplexing signal, where the N/ is greater than or equal to 1;
所述釆样时刻确定子模块设置为在所述正交频分复用信号的符号周期内 等间隔选择 Nf个釆样时刻作为测量釆样时刻, 所述 ^大于等于 1。 The sampling time determination sub-module is configured to select N f sample times at equal intervals in the symbol period of the orthogonal frequency division multiplexing signal as the measurement sample time, wherein the ^ is greater than or equal to 1.
在本发明的一种实施例中,所述测量信号生成模块包括 N/个信号产生器, 各信号产生器用于在对应的测量子载波频点上, 在每个测量釆样时刻生成一 个线性调频脉冲测量信号, 生成的线性调频脉冲测量信号的频域宽和时域宽 度分别小于所述正交频分复用信号的子载波带宽和奈奎斯特釆样周期。 In an embodiment of the present invention, the measurement signal generating module includes N/signal generators, and each signal generator is configured to generate one at each measurement sampling frequency point on a corresponding measurement subcarrier frequency point. The chirp signals are measured, and the frequency domain width and the time domain width of the generated chirp signal are smaller than the subcarrier bandwidth and the Nyquist sample period of the orthogonal frequency division multiplexed signal, respectively.
在本发明的一种实施例中, 所述测量信号处理模块包括信号处理子模块 和信号注入子模块;  In an embodiment of the present invention, the measurement signal processing module includes a signal processing submodule and a signal injection submodule;
所述信号处理子模块用于利用 NfxNt阶二维扰码 C对所述线性调频脉冲 测量信号进行调制得到激励信号, 所述 N,Nf阶二维扰码 C中的元素 cm,n为 +1或 -1 ; 所述 m大于等于 0 , 小于等于 -1; 所述 n大于等于 0 , 小于等于 Nt-V, The signal processing sub-module is configured to modulate the chirp signal measurement signal by using an N f xN t- order two-dimensional scrambling code C to obtain an excitation signal, where the element c m in the N, N f- order two-dimensional scrambling code C , n is +1 or -1; the m is greater than or equal to 0, less than or equal to -1; the n is greater than or equal to 0, less than or equal to N t -V,
所述信号注入子模块用于将得到的激励信号输入所述 TD-LTE系统的无 线信道。  The signal injection sub-module is configured to input the resulting excitation signal into a wireless channel of the TD-LTE system.
在本发明的一种实施例中, 所述测量信号接收模块包括 N 2N个信号接 收器, 所述信号接收器用于在相应的子载波频点上接收经所述 TD-LTE系统 输出的线性调频脉冲测量信号并输出接收的线性调频脉冲测量信号的自相关 值 所述 N/为选择的子载波频点个数; 所述 N为对所述正交频分复用信号 的最大频偏值除以所述正交频分复用信号的子载波带宽得到的值进行取整。  In an embodiment of the present invention, the measurement signal receiving module includes N 2N signal receivers, and the signal receiver is configured to receive the chirp output by the TD-LTE system at a corresponding subcarrier frequency point. Pulse measuring a signal and outputting an autocorrelation value of the received chirp measurement signal, wherein the N/ is a selected number of subcarrier frequency points; and the N is a division of a maximum frequency offset value of the orthogonal frequency division multiplexed signal The value obtained by the subcarrier bandwidth of the orthogonal frequency division multiplexed signal is rounded.
在本发明的一种实施例中,所述第一计算模块包括二维滑动计算子模块, 用于利用所述 N/xNf阶二维扰码 C对所述自相关值 进行时域和频域的二维 滑动相关计算, 得到所述正交频分复用信号载波中心频点的频偏 /和时延7。 In an embodiment of the present invention, the first calculation module includes a two-dimensional sliding calculation sub-module, configured to perform time domain and frequency on the autocorrelation value by using the N/xN f- order two-dimensional scrambling code C. The two-dimensional sliding correlation calculation of the domain obtains the frequency offset/and delay of the center frequency of the orthogonal frequency division multiplexed signal carrier.
在本发明的一种实施例中, 所述第二计算模块包括频偏计算子模块, 用于根据所述频偏/,利用多普勒频偏理论计算公式计算得到所述激励信号的 到达角 φ  In an embodiment of the present invention, the second calculation module includes a frequency offset calculation submodule, configured to calculate an angle of arrival of the excitation signal according to the frequency offset/, using a Doppler frequency offset theoretical calculation formula Φ
Fc - f 二 Fc ∞s(p F c - f two F c ∞s(p
c 所述 Fc为所述载波中心频点频率,所述/为正交频分复用信号载波中心 频点的频偏, 所述 V为所述 TD-LTE系统当前的速度, 所述 c为光速; 以及用于取所述激励信号在各子载波频点上的到达角都为 将该到达 角 带入多普勒频偏理论计算公式得到各子载波频点上频偏值: The F c is the frequency of the carrier center frequency, the / is the frequency offset of the center frequency of the orthogonal frequency division multiplexing signal carrier, and the V is the current speed of the TD-LTE system, the c For the speed of light; And the angle of arrival for taking the excitation signal at each subcarrier frequency point is to bring the angle of arrival into the Doppler frequency offset theoretical calculation formula to obtain the frequency offset value at each subcarrier frequency point:
Λ ϋ cos Λ ϋ cos
C 所述 i¾为第 k个子载波频点的频率, 所述 Λ为第 k个子载波频点的频 偏, 所述 k大于等于 1 , 小于等于所述正交频分复用信号符号带宽内的子载 波频点个数。  C is the frequency of the kth subcarrier frequency point, the Λ is the frequency offset of the kth subcarrier frequency point, and the k is greater than or equal to 1, less than or equal to the symbol bandwidth of the orthogonal frequency division multiplexed signal. The number of subcarrier frequency points.
在本发明的一种实施例中, 所述第二计算模块还包括时延计算子模块, 用于取所述正交频分复用信号符号带宽内各子载波频点的时延都等于 τ。 在本发明的一种实施例中, 所述合成处理模块包括无线信道冲击响应 强度值获取子模块, 设置为根据多普勒频偏的数据对经典多径信道模型进行 无线信道合成处理:
Figure imgf000010_0001
In an embodiment of the present invention, the second calculation module further includes a delay calculation submodule, configured to take a time delay of each subcarrier frequency point in the symbol bandwidth of the orthogonal frequency division multiplexing signal to be equal to τ . In an embodiment of the present invention, the synthesizing processing module includes a radio channel impulse response intensity value obtaining submodule configured to perform radio channel synthesizing processing on the classical multipath channel model according to the Doppler frequency offset data:
Figure imgf000010_0001
p k 所述 d)为无线信道冲击响应强度值, 所述 p表示时延个数, 所述 k表 示频偏个数, 所述^¾为第 p个时延、 第 k个频偏的多径信号分量的信号强度 值; 所述 Λι为第 kl个频偏, 所述 kl大于等于 1 , 小于等于所述 K; 所述 为第 pi个时延, 所述 pi大于等于 1 , 小于等于所述 P; 所述 (t - )为时刻 t 输入的单位脉冲信号在时延 τρ处的响应脉冲, t为当前测量的时刻。 可见, 本发明实施例中的测量信号釆用的是在时域和频域能取得最优化 分辨率的线性调频脉冲测量信号, 因此在时域和频域上可同时得到准确的测 量结果, 基于该测量结果得到的无线信道冲击响应强度值在时域和频域上也 都更为准确。 其次, 在本发明实施例中, 在进行合成处理得到无线信道冲击响应强度 值之前, 还可进一步根据得到的正交频分复用信号载波中心频点的频偏和时 延推算出正交频分复用信号符号带宽内至少一个其他子载波频点的频偏和时 延, 例如推算出正交频分复用信号符号带宽内所有其他子载波频点的频偏和 时延, 然后基于得到的所有子载波频点的频偏和时延进行合成计算, 进而使 得到的无线信道冲击响应强度值更为准确。 Pk, the d) is a wireless channel impulse response strength value, the p represents the number of delays, the k represents the number of frequency offsets, and the ^3⁄4 is the p-th delay, the k-th frequency-off multipath a signal strength value of the signal component; the Λι is the k1th frequency offset, the k1 is greater than or equal to 1, and less than or equal to the K; the pi is the pi delay, the pi is greater than or equal to 1, and less than or equal to the P; (t - ) is the response pulse of the unit pulse signal input at time t at time delay τ ρ , and t is the current measured time. It can be seen that the measurement signal in the embodiment of the present invention uses the chirp measurement signal that can obtain the optimal resolution in the time domain and the frequency domain, so that accurate measurement results can be obtained simultaneously in the time domain and the frequency domain, based on The wireless channel impulse response intensity values obtained by the measurement are also more accurate in the time domain and the frequency domain. Secondly, in the embodiment of the present invention, before performing the combining process to obtain the wireless channel impulse response intensity value, the orthogonal frequency can be further calculated according to the obtained frequency offset and time delay of the carrier center frequency point of the orthogonal frequency division multiplexing signal. Frequency offset and delay of at least one other subcarrier frequency in the bandwidth of the multiplexed signal symbol, for example, deriving the frequency offset and delay of all other subcarrier frequencies in the symbol bandwidth of the orthogonal frequency division multiplexed signal, and then based on The frequency offset and delay of all subcarrier frequency points are combined and calculated, so that the obtained wireless channel impulse response intensity value is more accurate.
附图概述 BRIEF abstract
图 1为本发明实施例一提供的 TD-LTE系统无线信道响应测量方法示意 图;  FIG. 1 is a schematic diagram of a method for measuring a wireless channel response of a TD-LTE system according to Embodiment 1 of the present invention; FIG.
图 2为本发明实施例一提供的对线性调频脉冲测试信号进行二维扰码调 制的示意图;  2 is a schematic diagram of performing two-dimensional scrambling code modulation on a chirp test signal according to Embodiment 1 of the present invention;
图 3为本发明实施例一提供进行二维滑动相关计算的示意图;  FIG. 3 is a schematic diagram of performing two-dimensional sliding correlation calculation according to Embodiment 1 of the present invention; FIG.
图 4为本发明实施例一提供的 TD-LTE系统无线信道响应测量装置的结 构示意图一;  4 is a schematic structural diagram 1 of a TD-LTE system radio channel response measuring apparatus according to Embodiment 1 of the present invention;
图 5为本发明实施例一提供的 TD-LTE系统无线信道响应测量装置的结 构示意图二。  FIG. 5 is a second schematic structural diagram of a wireless channel response measuring apparatus for a TD-LTE system according to Embodiment 1 of the present invention.
本发明的较佳实施方式 Preferred embodiment of the invention
下文中将结合附图对本发明的实施例进行详细说明。 需要说明的是, 在 不冲突的情况下, 本申请中的实施例及实施例中的特征可以相互任意组合。  Embodiments of the present invention will be described in detail below with reference to the accompanying drawings. It should be noted that, in the case of no conflict, the features in the embodiments and the embodiments in the present application may be arbitrarily combined with each other.
实施例一:  Embodiment 1:
本实施例提供的 TD-LTE系统测量方法, 主要针对具有多径无线信道、 且相对地面的速度大于等于 300 千米每小时的 TD-LTE 系统, 例如高铁 TD-LTE系统。 本实施例中的测量过程请参见图 1所示, 包括:  The measurement method of the TD-LTE system provided in this embodiment is mainly for a TD-LTE system having a multipath wireless channel and a speed of 300 km/h or more relative to the ground, such as a high-speed rail TD-LTE system. The measurement process in this embodiment is shown in Figure 1, including:
步骤 101 : 根据待测 TD-LTE系统的正交频分复用信号 (OFDM信号) 的符号带宽和符号周期确定测量子载波频点和测量釆样时刻; Step 101: Orthogonal Frequency Division Multiplexing (OFDM signal) according to the TD-LTE system to be tested The symbol bandwidth and symbol period determine the measurement subcarrier frequency and the measurement time;
步骤 102: 在确定的测量子载波频点上才艮据测量釆样时刻生成线性调频 脉冲测量信号;  Step 102: Generate a chirped pulse measurement signal according to the measured time of the measurement at the determined measurement subcarrier frequency point;
步骤 103:将线性调频脉冲测量信号调制处理后输入 TD-LTE系统的无线 信道;  Step 103: modulate the chirp measurement signal into a wireless channel of the TD-LTE system;
步骤 104: 在相应的子载波频点上接收经所 TD-LTE 系统输出的线性调 频脉冲测量信号并得到接收的线性调频脉冲测量信号的自相关值;  Step 104: Receive a chirp measurement signal output by the TD-LTE system at a corresponding subcarrier frequency point and obtain an autocorrelation value of the received chirp measurement signal;
步骤 105: 根据得到的自相关值得到正交频分复用信号载波中心频点的 频偏和时延;  Step 105: Obtain a frequency offset and a delay of a center frequency point of the orthogonal frequency division multiplexing signal carrier according to the obtained autocorrelation value;
步骤 106: 基于得到的频偏和时延进行无线信道响应合成处理得到无线 信道冲击响应强度值。  Step 106: Perform a radio channel response synthesis process based on the obtained frequency offset and delay to obtain a radio channel impulse response strength value.
在本实施例中, 为了进一步提升测量结果的准确性, 在上述步骤 106之 前, 步骤 105之后, 还可包括:  In this embodiment, in order to further improve the accuracy of the measurement result, before step 106, after step 105, the method may further include:
才艮据步骤 105得到的载波中心频点的频偏和时延推算正交频分复用信号 符号带宽内至少一个其他子载波频点的频偏和时延。 然后步骤 106中则是基 于得到的所有频偏和时延进行合成处理, 得到更为精确的无线信道冲击响应 强度值。 下面对上述各步骤进行详细说明。  The frequency offset and delay of at least one other subcarrier frequency point in the symbol bandwidth of the orthogonal frequency division multiplexed signal are estimated according to the frequency offset and delay of the carrier center frequency obtained in step 105. Then, in step 106, all the frequency offsets and delays obtained are combined to obtain a more accurate wireless channel impulse response intensity value. The above steps will be described in detail below.
对于上述步骤 101 ,对于高铁 TD-LTE这类系统而言,无线信道对其无线 传输的影响主要来源与收发信机之间高速相对运动引起的多普勒频率偏移在 OFDM信号内引起子载波间符号干扰。 因此, 需要根据 TD-LTE中 OFDM信 号的符号周期 I、 带宽 、 奈奎斯特釆样周期!^ 以及子载波带宽 „ 设 置测量参数, 优先保证信道测量在频域的分辨率小于或等于 同时使得 信道测量的时域分辨率尽可能小于或等于 T  For the above step 101, for a system such as the high-speed railway TD-LTE, the main influence of the wireless channel on its wireless transmission is the Doppler frequency offset caused by the high-speed relative motion between the transceiver and the transceiver, causing subcarriers in the OFDM signal. Inter-symbol interference. Therefore, it is necessary to follow the symbol period I, bandwidth, and Nyquist sampling period of the OFDM signal in TD-LTE! ^ and subcarrier bandwidth „ Set the measurement parameters to ensure that the resolution of the channel measurement in the frequency domain is less than or equal to at the same time, so that the time domain resolution of the channel measurement is as small as possible or equal to T
由于无线信道测量的基本原理是注入激励信号, 然后对激励信号进行相 干检测, 从而获得无线信道对信号的时间延迟、 相位偏移以及频率偏移, 所 以激励源信号本身的时域和频域宽度直接决定了无线信道测量的时域和频域 分辨率。 信号分析理论给出信号的时域和频域宽度分别为:
Figure imgf000013_0001
其中, S ( )表示信号的频谱函数, ( 表示信号的时域函数, U 示信号的时域函数的共轭, 和 分别表示信号的频域宽度和时域宽度。
Since the basic principle of wireless channel measurement is to inject an excitation signal, and then perform coherent detection on the excitation signal, thereby obtaining a time delay, a phase offset, and a frequency offset of the signal of the wireless channel. The time domain and frequency domain resolution of the wireless channel measurement are directly determined by the time domain and frequency domain width of the excitation source signal itself. The signal analysis theory gives the time domain and frequency domain width of the signal:
Figure imgf000013_0001
Where S ( ) represents the spectral function of the signal, (representing the time domain function of the signal, the conjugate of the time domain function of the U signal, and the frequency domain width and time domain width of the signal, respectively).
基于上述分析可知, 首先需保证产生的激励信号的频域宽度小于等于 Bsubc; 在此基础上, 使得激励信号的时域宽度尽可能小。 但是, 信号的时频 测不准原理指出, 任意一个信号, 其时域和频域的宽度满足, ff al,Based on the above analysis, it is first required to ensure that the frequency domain width of the generated excitation signal is less than or equal to B subc ; on this basis, the time domain width of the excitation signal is made as small as possible. However, the principle of time-frequency uncertainty of the signal indicates that the width of the time domain and the frequency domain of any one of the signals is satisfied, ff al,
Figure imgf000013_0002
(2) 其中上式中的 ' )表示信号的时域函数的赫尔米特变换, e > 表示信 号时域表达式和频域表达式的相关系数。
Figure imgf000013_0002
(2) where ' ) in the above equation represents the Hermitian transformation of the time domain function of the signal, and e > represents the correlation coefficient of the signal time domain expression and the frequency domain expression.
理论证明, 线性调频脉冲能够使得上述式 (2)中等号成立, 取得在时域和 频域最优化的分辨率。 线性调频脉冲的基本表达式为:  The theory proves that the chirp can make the above formula (2) medium, and obtain the optimized resolution in the time domain and the frequency domain. The basic expression of a chirp is:
其中, 上式中的 α、 β是待定系数, w。表示信号载波频率, t表示时间。 在上述分析的基础上, 测量参数选择过程具体说明如下: Among them, α and β in the above formula are undetermined coefficients, w. Indicates the signal carrier frequency and t represents time. Based on the above analysis, the measurement parameter selection process is described as follows:
①根据式 (1)和 (3)可得到线性调频脉冲的时域和频域宽度:
Figure imgf000013_0003
" ― " " 2 (4)
1 According to equations (1) and (3), the time domain and frequency domain width of the chirp can be obtained:
Figure imgf000013_0003
" ― "" 2 (4)
②令符号奈奎斯特釆样周期 ∞ /£;和子载波带宽 分别等于线性调频 脉冲的时域和频域宽度, 可以计算线性调频脉冲的参数 a和 β的值; 当然, 理论上也可分别选择小于符号奈奎斯特釆样周期 Τ 的釆样周期和子载波 带宽 Bsubc的带宽分别等于线性调频脉冲的时域和频域宽度, 然后计算得到计 算线性调频脉冲的参数《和 的值; The symbolic Nyquist sampling period ∞ / £; and the subcarrier bandwidth are respectively equal to the time domain and frequency domain width of the chirp, and the values of the parameters a and β of the chirp can be calculated; of course, theoretically, respectively Selecting the sampling period smaller than the symbol Nyquist sample period 和 and the bandwidth of the subcarrier bandwidth B subc are equal to the time domain and frequency domain width of the chirp, respectively, and then calculating Calculate the value of the parameter "harmonic" of the chirp;
③在正交频分复用信号的符号带宽 Bs内均匀选择 (即等间隔选择) Nf 子载波频点 ^ (考虑复杂度与准确性的折中, 优选根据无线信道相干带宽的 估测值进行选取)作为测量子载波频点, N/大于等于 1 , I大于等于 1 , 小于 等于 N/; 为了提高测量结果的精度,优选 N/的取值大于等于 2,下面以 N/的取 值为 10进行说明; 3 uniformly select (ie, equally spaced selection) N f subcarrier frequency points within the symbol bandwidth B s of the orthogonal frequency division multiplexing signal (considering the compromise between complexity and accuracy, preferably based on the estimate of the coherence bandwidth of the radio channel) The value is selected as the measurement subcarrier frequency point, N/ is greater than or equal to 1, I is greater than or equal to 1, less than or equal to N/; In order to improve the accuracy of the measurement result, it is preferable that the value of N/ is greater than or equal to 2, and the following is taken as N/ A value of 10 is used for explanation;
在正交频分复用信号的符号周期内均勾选择^个釆样时刻 ^ (考虑复杂 度与准确性的折中, 建议根据无线信道相干时间的估测值进行选取)作为测 量釆样时刻, ^大于等于 1 , ·大于等于 1 , 小于等于 为了提高测量结果 的精度, 优选 ^的取值大于等于 2, 下面也以 ^的取值为 10进行说明。  In the symbol period of the orthogonal frequency division multiplexing signal, select a sampling time ^ (considering the compromise between complexity and accuracy, it is recommended to select according to the estimated value of the radio channel coherence time) as the measurement time ^ is greater than or equal to 1, and is greater than or equal to 1, less than or equal to the accuracy of the measurement result. Preferably, the value of ^ is greater than or equal to 2, and the value of ^ is also described below.
④根据 TD-LTE系统相对地面的速度等情况以及 TD-LTE系统使用的载 波/ c, 估算出 TD-LTE系统的信号最大传输时间延迟 ¾ax和频率偏移 /max,以 供后续步骤使用, 具体过程如下: 4 According to the speed of the TD-LTE system relative to the ground and the carrier/ c used by the TD-LTE system, the maximum transmission time delay of the TD-LTE system is estimated to be 3⁄4ax and the frequency offset/ max for subsequent steps. The process is as follows:
通常高铁沿线基站间隔 2-3km, 高铁列车运行在基站覆盖区间内, 假设 发送信号功率为 1W , 直射路径信号接收功率约为 l/(¼d4)= 1/(4TT15004)=3.5* 10-8W。通常, 当多径信号分量功率小于直射路径信号功率的 1%后, 其余多径信号分量可以忽略。 此时多径信号接收功率为 3.5*10-1QW, 对应 d4 = 1/(½3.5*10-10W), 即传输距离为 4.7km。 Usually, the base station along the high-speed railway is 2-3km apart. The high-speed train runs within the coverage area of the base station. Assuming that the transmitted signal power is 1W, the direct path signal receiving power is about l/(1⁄4d 4 )= 1/(4TT1500 4 )=3.5* 10- 8 W. Generally, when the multipath signal component power is less than 1% of the direct path signal power, the remaining multipath signal components can be ignored. At this time, the multipath signal receiving power is 3.5*10 - 1Q W, corresponding to d 4 = 1/(1⁄23.5*10 - 10 W), that is, the transmission distance is 4.7km.
最大传输时延(4.7-1.5 ) km/c=10us。  Maximum transmission delay (4.7-1.5) km/c=10us.
列车运行速度约为 300kmph, 最大频率偏移约为: f c -cos^=2Ghz*300kmph/c*cosO = 555Hz (5) The train runs at a speed of approximately 300kmph and the maximum frequency offset is approximately: f c -cos^=2Ghz*300kmph/c*cosO = 555Hz (5)
c  c
上式(5 )中的 为中心频点频率, V为 TD-LTE系统相对地面的速度, c 为光速。  In the above equation (5) is the center frequency frequency, V is the speed of the TD-LTE system relative to the ground, and c is the speed of light.
经上述过程确定好了各测量参数后, 进入上述步骤 102和 103 , 在确定 的测量子载波频点上根据测量釆样时刻生成线性调频脉冲测量信号, 对生成 的线性调频脉冲测量信号进行处理后注入 TD-LTE系统。 本实施例中在确定 的每个测量子载波频点上,在每个釆样时刻生成一个线性调频脉冲测量信号, 根据上述分析过程可知, 生成的线性调频脉冲测量信号的频域宽和时域宽度 分别小于等于正交频分复用信号的子载波带宽和奈奎斯特釆样周期。 After the measurement parameters are determined by the above process, the above steps 102 and 103 are entered, and the chirp measurement signal is generated according to the measurement time at the determined measurement subcarrier frequency point, and the generation is performed. The chirped pulse measurement signal is processed and injected into the TD-LTE system. In this embodiment, a chirp measurement signal is generated at each sampling sub-carrier frequency point at each sampling time. According to the above analysis process, the frequency domain width and time domain of the generated chirp signal measurement signal are known. The widths are respectively less than or equal to the subcarrier bandwidth of the orthogonal frequency division multiplexed signal and the Nyquist sampling period.
在上述步骤中, N/和^取的取值都为 10, 也即存在 10个测量子载波频 点 W! , w2 和 10个釆样时刻 t10 在第一个测量侧载波频点上, 将对应的为 和 10个釆样时刻 t2 ^带入上述式(3 ) 即可得到该频 点上的 10个线性调频脉冲测量信号; 对应的, 在其他测量子载波频点上生成 线性调频脉冲测量信号的过程相同。 下面结合附图测试信号的生成过程进行 说明。 In the above steps, both N/ and ^ take values of 10, that is, there are 10 measurement subcarrier frequency points W!, w 2 and 10 sample times t 10 on the first measurement side carrier frequency point. The corresponding chirped time t 2 ^ is brought into the above equation (3) to obtain 10 chirped pulse measurement signals at the frequency point; correspondingly, linearity is generated at other measured subcarrier frequency points. The process of FM pulse measurement signals is the same. The following describes the generation process of the test signal in conjunction with the drawings.
请参见图 2所示, 本实施例釆用的信号产生器为声表面波色散换能器, 因为其截断率边缘很陡峭, 具有很好的时域和频域自相关特性, 体积很小, 潜在成本低。 对应的, 本实施例选择 N/个信号产生器, 根据上述计算得到的 α、 β以及确定的 和 i在相应的频点上同时生成、 发送线性调频脉冲测量信 号 x(t-mTc-Tc/2,f-Bc/2), 其中, m为线性调频脉冲的序号 (即第 m个发送的 线性调频脉冲) , Tc为线性调频脉冲的脉冲周期, t为当前信号时刻, f为当 前信号频率, Be为线性调频脉冲的带宽。 在本实施例中, 为了提高测量激励 信号的检测信噪比, 本实施例中对生成的测试信号的处理包括对生成的线性 调频脉冲测量信号进行二维扰码调制。 请参见下式所示:  Referring to FIG. 2, the signal generator used in this embodiment is a surface acoustic wave dispersion transducer, because the edge of the cutoff rate is steep, and has good time domain and frequency domain autocorrelation characteristics, and the volume is small. The potential cost is low. Correspondingly, in this embodiment, N/signal generators are selected, and the chirped pulse measurement signal x(t-mTc-Tc/ is simultaneously generated and transmitted according to the above calculated α, β and the determined sum i at the corresponding frequency points. 2, f-Bc/2), where m is the sequence number of the chirp (ie, the mth transmitted chirp), Tc is the pulse period of the chirp, t is the current signal moment, and f is the current signal frequency , Be is the bandwidth of the chirp. In the present embodiment, in order to improve the detection signal-to-noise ratio of the measurement excitation signal, the processing of the generated test signal in this embodiment includes two-dimensional scrambling code modulation on the generated linear FM pulse measurement signal. Please see the following formula:
「 1 : Δ/72 = Δ" = 0
Figure imgf000015_0001
« 1: Am≠ 0 or ΔΜ≠ 0
" 1 : Δ/72 = Δ" = 0
Figure imgf000015_0001
« 1: Am≠ 0 or ΔΜ≠ 0
(6) (6)
其中, 式(6 ) 中的 C表示 N/xNf阶二维扰码(cra,„为 +1或 -1 ) , 且具有 比较理想的自相关特性, ^ 分别表示自相关运算过程中, 扩频码 在时 域和频域两个维度上的距离。 利用二维扰码 C对产生的线性调频脉冲测量信 号进行调制具体为: 利用扩频码 调制对应子载波 和釆样时刻 上生成 的线性调频脉冲测量信号, 请参见图 2所示。 然后进行功率归一化保证各信 号功率的一致性以及求和得到激励信号; 将得到的激励信号注入 TD-LTE系 统的无线信道。 Wherein, C in the formula (6) represents a two-dimensional scrambling code of the N/xNf order (c ra , „ is +1 or -1 ), and has an ideal autocorrelation property, ^ respectively represents an autocorrelation operation process, The distance between the frequency code in the two dimensions of the time domain and the frequency domain. The chirp measurement signal generated by the two-dimensional scrambling code C pair The modulation is specifically performed by: using a spreading code to modulate the corresponding subcarrier and the chirp measurement signal generated at the time of sampling, as shown in FIG. 2 . Then, power normalization is performed to ensure consistency of each signal power and summation to obtain an excitation signal; and the obtained excitation signal is injected into a wireless channel of the TD-LTE system.
在本实施例中, 在上述步骤 104中, 为了在接收端的每一个可能的频点 上接收到线性调频脉冲测量信号并输出其自相关值 R, 在接收端设置 N N 个信号接收器, 其中 N/为选择的子载波频点个数, N为对正交频分复用信号 的最大频偏值除以正交频分复用信号的子载波带宽得到的值进行取整后得到 的值, 本实施例中的取整可以向上取整, 也可以向下取整, 具体取整方式可 根据当前的具体应用场景选定。  In this embodiment, in the above step 104, in order to receive the chirp measurement signal at each possible frequency point of the receiving end and output its autocorrelation value R, NN signal receivers are set at the receiving end, where N / is the number of selected subcarrier frequency points, and N is a value obtained by dividing the maximum frequency offset value of the orthogonal frequency division multiplexed signal by the value obtained by dividing the subcarrier bandwidth of the orthogonal frequency division multiplexed signal, The rounding in this embodiment may be rounded up or rounded down. The specific rounding mode may be selected according to the current specific application scenario.
选定好信号接收器后, 利用所选定的信号接收器在相应的子载波频点上 接收经 TD-LTE系统输出的线性调频脉冲测量信号并输出接收的线性调频脉 冲测量信号的自相关值 。 请参见图 3所示, 针对某一个信号的自相关值计 算公式为:
Figure imgf000016_0001
After selecting the signal receiver, the selected signal receiver receives the chirp measurement signal outputted by the TD-LTE system at the corresponding subcarrier frequency and outputs the autocorrelation value of the received chirp measurement signal. . Referring to Figure 3, the formula for calculating the autocorrelation value of a signal is:
Figure imgf000016_0001
其中上式 (7)中的 Μτ和 NB分别为时域线性脉冲信号个数和频域线性脉冲 个数, Tc和 Bc分别表示脉冲信号的时间长度和脉冲信号的频域宽度。 Μ τ and N B in the above equation (7) are the number of time-domain linear pulse signals and the number of frequency-domain linear pulses, respectively, and T c and B c represent the time length of the pulse signal and the frequency domain width of the pulse signal, respectively.
在得到各线性调频脉冲测量信号的自相关值后, 上述步骤 105根据得 的自相关值得到正交频分复用信号载波中心频点的频偏和时延的过程请参 J¾ 图 3所示, 其包括:  After obtaining the autocorrelation values of the chirped pulse measurement signals, the above step 105 obtains the frequency offset and the delay of the carrier center frequency point of the orthogonal frequency division multiplexed signal according to the obtained autocorrelation value, as shown in FIG. , which includes:
利用上述^^<^阶二维扰码 C对得到的自相关值 W进行时域和频域的二 维滑动相关计算(具体的二维滑动相关计算的过程请参见虚线框所示) , 得 到正交频分复用信号载波中心频点的频偏/和时延 τ, 也即得到 TD-LTE系统 接收激励信号的实时时延和频偏值, 生成对应的时延和频偏测量记录。 在本 实施例中, 在该记录中还可记录当前实时测量的时间 t 以及被测的 TD-LTE 系统当前的位置信息 LOC; 当前的位置信息和时间信息可以准确的反应测试 时间以及测试时 TD-LTE系统所处的工作环境, 更便于后续的统计分析。 Using the above-mentioned ^^<^ order two-dimensional scrambling code C, the obtained autocorrelation value W is subjected to two-dimensional sliding correlation calculation in time domain and frequency domain (for the specific two-dimensional sliding correlation calculation process, please refer to the dotted line box), The frequency offset/and delay τ of the center frequency of the orthogonal frequency division multiplexing signal carrier, that is, the real-time delay and the frequency offset value of the received excitation signal of the TD-LTE system are obtained, and corresponding delay and frequency offset measurement records are generated. In this embodiment, the current real-time measurement time t and the measured TD-LTE can also be recorded in the record. The current location information of the system LOC; the current location information and time information can accurately reflect the test time and the working environment in which the TD-LTE system is in operation, which is more convenient for subsequent statistical analysis.
在本实施例中,理论上得到载波中心频点的频偏/和时延 τ后, 即可得到 无线信道冲击响应强度值。 但在本实施例中, 为了进一步提升测量精度, 在 进行合成处理之前,还包括根据载波中心频点的频偏/和时延 τ推算正交频分 复用信号符号带宽内至少一个其他子载波频点的频偏和时延; 然后基于得到 的所有频偏和时延进行合成处理得到更为精确的无线信道冲击响应强度值。 在本实施例中, 为了使得到的测量结果尽可能精确, 优选根据载波中心频点 的频偏/和时延 τ推算正交频分复用信号符号带宽内其他所有子载波频点的频 偏和时延。 具体如下:  In this embodiment, after theoretically obtaining the frequency offset/and delay τ of the carrier center frequency point, the wireless channel impulse response intensity value is obtained. However, in this embodiment, in order to further improve the measurement precision, before performing the synthesizing process, the method further includes estimating at least one other subcarrier in the symbol bandwidth of the orthogonal frequency division multiplexing signal according to the frequency offset/and delay τ of the carrier center frequency point. The frequency offset and delay of the frequency point; then based on all the obtained frequency offsets and delays, a more accurate wireless channel impulse response intensity value is obtained. In this embodiment, in order to make the obtained measurement result as accurate as possible, it is preferable to estimate the frequency offset of all other subcarrier frequency points in the symbol bandwidth of the orthogonal frequency division multiplexing signal according to the frequency offset/and delay τ of the carrier center frequency point. And time delay. details as follows:
根据载波中心频点的频偏 f推算正交频分复用信号符号带宽内其他所有 子载波频点的频偏包括:  Calculating the frequency offset of all other subcarrier frequencies in the symbol bandwidth of the orthogonal frequency division multiplexed signal according to the frequency offset f of the carrier center frequency point includes:
根据载波中心频点的频偏 /,利用多普勒频偏理论计算公式计算得到激励 信号的到达角 φ·.  According to the frequency offset of the carrier center frequency, the angle of arrival of the excitation signal is calculated by using the Doppler frequency offset theory calculation formula.
Fc - f 二 F^c~∞s (p (8) 上式中, ^为载波中心频点频率, /为正交频分复用信号载波中心频点 的频偏, V为所述 TD-LTE系统当前的速度, c为光速; F c - f 2 F ^ c ~ ∞ s (p (8) where ^ is the carrier center frequency frequency, / is the frequency offset of the center frequency of the orthogonal frequency division multiplexed signal carrier, and V is the TD - the current speed of the LTE system, c is the speed of light;
然后取激励信号在各子载波频点上的到达角都为^ 将该到达角 带入 多普勒频偏理论计算公式得到各子载波频点上频偏值: fk 二 Fk - Fk ^∞S (p (9) 上式中, 为第 k个子载波频点的频率, Λ为第 k个子载波频点的频 偏, k大于等于 1 ,小于等于正交频分复用信号符号带宽内的子载波频点个数。 Then, the angle of arrival of the excitation signal at each subcarrier frequency point is ^. The angle of arrival is brought into the Doppler frequency offset theoretical calculation formula to obtain the frequency offset value of each subcarrier frequency: fk II F k - F k ^ ∞S (p (9) where the frequency of the kth subcarrier frequency point, Λ is the frequency offset of the kth subcarrier frequency point, k is greater than or equal to 1, less than or equal to the symbol bandwidth of the orthogonal frequency division multiplexing signal The number of subcarrier frequency points.
另外, 根据电磁场理论, 正交频分复用信号符号带内各个子载波在无线 信道中传播的时间延迟之差非常小, 可以忽略不计, 因此本实施例中取正交 频分复用信号符号带宽内各子载波频点的时延都等于 τ。 In addition, according to the electromagnetic field theory, each subcarrier in the orthogonal frequency division multiplexing signal symbol band is wireless. The difference of the time delays of propagation in the channel is very small and can be neglected. Therefore, in this embodiment, the delay of each subcarrier frequency point in the symbol bandwidth of the orthogonal frequency division multiplexing signal is equal to τ.
得到子载波频点的频偏和时延后, 上述步骤 106进行无线信道响应合成 处理得到无线信道冲击响应强度值的过程如下:  After obtaining the frequency offset and delay of the subcarrier frequency, the process of obtaining the wireless channel impulse response strength value by performing the wireless channel response synthesis processing in the above step 106 is as follows:
根据多普勒频偏的数据对经典多径信道模型进行无线信道合成处理: ) =∑∑ W5it― τρ ) ( W (ιο) Perform wireless channel synthesis on the classical multipath channel model based on the Doppler shift data: ) =∑∑ W 5it― τ ρ ) ( W (ιο)
p k 上式中, /ζ , 为无线信道冲击响应强度值, ρ表示时延个数, k表示频 偏个数, f 为第 p个时延、第 k个频偏的多径信号分量的信号强度值; Λι为 第 kl个频偏, 所述 kl大于等于 1 , 小于等于所述 K; 所述 为第 pi个时 延, 所述 pi大于等于 1 , 小于等于所述 P; 所述 (t -^)为时刻 t输入的单位 脉冲信号在时延 τρ处的响应脉冲, t为当前测量的时刻。 Pk In the above formula, /ζ is the wireless channel impulse response intensity value, ρ is the number of delays, k is the number of frequency offsets, and f is the signal of the p-th delay and the k-th frequency-off multipath signal component. The strength value; Λι is the kl frequency offset, the k1 is greater than or equal to 1, less than or equal to the K; the pi is the pi, the pi is greater than or equal to 1, and less than or equal to the P; -^) The response pulse of the unit pulse signal input at time t at time delay τ ρ , t is the time of the current measurement.
经上述步骤, 针对每次测量我们都能得到一个较为精确的/^ J) , 然后针 对每次测量得到的 /7(t, iT) , 计算其时域和频域的自相关, 具体如下:  Through the above steps, we can get a more accurate /^ J) for each measurement, and then calculate the autocorrelation of time domain and frequency domain for each measurement of /7(t, iT), as follows:
1 1
R(At,Ar) = '
Figure imgf000018_0001
( Vt +■ Α一ί, τ+ Ατ) (11)
R(At,Ar) = '
Figure imgf000018_0001
(Vt +■ Α一ί, τ+ Ατ) (11)
trial i=  Trial i=
上式中, R(At, AT)为测量得到的无线信道响应的时间 -延迟二维自相关函 数, At为无线信道响应样本在时间域内的偏移量, Δτ为无线信道响应样本在 延迟域内的偏移量, ^为无线信道响应的样本数量, (ί + Λί, τ+Λτ)为无线信 道响应样本在经过时间偏移和延迟偏移后的共轭。  In the above formula, R(At, AT) is a time-delay two-dimensional autocorrelation function of the measured wireless channel response, At is the offset of the wireless channel response sample in the time domain, and Δτ is the wireless channel response sample in the delay domain. The offset, ^ is the number of samples of the wireless channel response, (ί + Λί, τ+Λτ) is the conjugate of the wireless channel response sample after the time offset and delay offset.
然后对信道响应的时域和频域自相关做傅里叶变换, 即可得到被测 TD-LTE无线信道的统计特征, 包括: 时间延迟语、 多普勒扩展语、 角度扩展 谱、 相干时间以及相干带宽等统计参数。 实施例二: Then, the Fourier transform is performed on the time domain and the frequency domain autocorrelation of the channel response, and the statistical characteristics of the measured TD-LTE radio channel are obtained, including: time delay language, Doppler spread, angle spread spectrum, coherence time And statistical parameters such as coherence bandwidth. Embodiment 2:
本实施例提供了一种 TD-LTE系统测量装置, 可用于对具有多径无线信 道、 且相对地面的速度大于等于 300千米每小时的 TD-LTE系统进行有效的 测量。 请参见图 4所示, 本实施例提供的 TD-LTE系统测量装置包括测量参 数确定模块、 测量信号生成模块、 测量信号处理模块、 测量信号接收模块、 第一计算模块和合成处理模块, 其中:  The present embodiment provides a TD-LTE system measurement apparatus, which can be used for effectively measuring a TD-LTE system having a multipath wireless channel and having a speed of 300 km/h or more relative to the ground. Referring to FIG. 4, the TD-LTE system measurement apparatus provided in this embodiment includes a measurement parameter determination module, a measurement signal generation module, a measurement signal processing module, a measurement signal receiving module, a first calculation module, and a synthesis processing module, where:
测量参数确定模块设置为根据 TD-LTE系统的正交频分复用信号的符号 带宽和符号周期确定测量子载波频点和测量釆样时刻;  The measurement parameter determination module is configured to determine the measurement subcarrier frequency point and the measurement sampling time according to the symbol bandwidth and the symbol period of the orthogonal frequency division multiplexing signal of the TD-LTE system;
测量信号生成模块设置为在测量子载波频点上根据测量釆样时刻生成线 性调频脉冲测量信号;  The measurement signal generating module is configured to generate a linear FM pulse measurement signal according to the measurement sample time at the measurement subcarrier frequency point;
测量信号处理模块设置为将线性调频脉冲测量信号处理后输入 TD-LTE 系统的无线信道;  The measurement signal processing module is configured to process the chirp measurement signal and input the wireless channel of the TD-LTE system;
测量信号接收模块设置为在相应的子载波频点上接收经 TD-LTE系统输 出的线性调频脉冲测量信号并得到接收的线性调频脉冲测量信号的自相关 值;  The measurement signal receiving module is configured to receive the chirp measurement signal outputted by the TD-LTE system at a corresponding subcarrier frequency point and obtain an autocorrelation value of the received chirp measurement signal;
第一计算模块设置为根据自相关值得到正交频分复用信号载波中心频点 的频偏和时延;  The first calculating module is configured to obtain a frequency offset and a delay of a carrier center frequency point of the orthogonal frequency division multiplexing signal according to the autocorrelation value;
合成处理模块设置为基于得到的频偏和时延进行无线信道响应合成处理 得到无线信道冲击响应强度值。  The synthesis processing module is configured to perform a wireless channel response synthesis process based on the obtained frequency offset and delay to obtain a wireless channel impulse response strength value.
在本实施例中, 为了提升测量结果的准确性, 请参见图 5所示, TD-LTE 系统测量装置还可包括第二计算模块, 设置为在合成处理模块基于得到的频 偏和时延进行无线信道响应合成处理得到无线信道冲击响应强度值之前, 根 据第一计算模块得到的载波中心频点的频偏和时延推算所述正交频分复用信 号符号带宽内至少一个其他子载波频点的频偏和时延。  In this embodiment, in order to improve the accuracy of the measurement result, as shown in FIG. 5, the TD-LTE system measurement apparatus may further include a second calculation module, configured to perform, on the basis of the obtained frequency offset and delay, by the synthesis processing module. Before obtaining the wireless channel impulse response strength value by the wireless channel response synthesis processing, estimating at least one other subcarrier frequency in the symbol bandwidth of the orthogonal frequency division multiplexing signal according to the frequency offset and delay of the carrier center frequency point obtained by the first calculation module The frequency offset and delay of the point.
下面对上述各功能模块的结构进行进一步详细的说明。 本实施例中的测量参数确定模块包括频点确定子模块和釆样时刻确定子 模块; The structure of each of the above functional modules will be further described in detail below. The measurement parameter determination module in this embodiment includes a frequency point determination submodule and a sample time determination submodule;
频点确定子模块设置为在正交频分复用信号的符号带宽内均匀选择 N/个 子载波频点作为测量子载波频点, 所述 N/大于等于 1 ;  The frequency point determining submodule is configured to uniformly select N/subcarrier frequency points as the measurement subcarrier frequency points in the symbol bandwidth of the orthogonal frequency division multiplexing signal, where the N/ is greater than or equal to 1;
釆样时刻确定子模块设置为在所述正交频分复用信号的符号周期内均匀 选择 Nf个釆样时刻作为测量釆样时刻, 所述 ^大于等于 1。 The sample time determination submodule is configured to uniformly select N f sample times in the symbol period of the orthogonal frequency division multiplexed signal as the measurement sample time, wherein the ^ is greater than or equal to 1.
测量子载波频点和测量釆样时刻的具体确定过程在此不再赘述。  The specific determination process of measuring the subcarrier frequency point and measuring the sampling time is not described here.
本实施例中, 由于线性调频脉冲能够取得在时域和频域最优化的分辨 率。 本实施例釆用线性调频脉冲信号作为测试信号输入。 线性调频脉冲信号 的产生过程在实施例一种已有明确的说明, 在此不再赘述。 本实施例中的测 量信号生成模块包括 N/个信号产生器, 各信号产生器用于在对应的测量子载 波频点上, 在每个测量釆样时刻生成一个线性调频脉冲测量信号, 生成的线 性调频脉冲测量信号的频域宽和时域宽度分别小于正交频分复用信号的子载 波带宽和奈奎斯特釆样周期。 本实施例中的信号产生器优选釆用声表面波色 散换能器来实现。 当然也可釆用其他能生成上述线性调频脉冲信号的其他装 置实现。  In this embodiment, since the chirp is capable of obtaining the resolution optimized in the time domain and the frequency domain. In this embodiment, a chirp signal is used as a test signal input. The process of generating the chirp signal is clearly described in the embodiment, and will not be described herein. The measurement signal generating module in this embodiment includes N/signal generators, and each signal generator is configured to generate a chirp pulse measurement signal at each measurement sampling frequency at a corresponding measurement sub-carrier frequency, and generate a linearity. The frequency domain width and the time domain width of the FM pulse measurement signal are respectively smaller than the subcarrier bandwidth and the Nyquist sample period of the orthogonal frequency division multiplexed signal. The signal generator in this embodiment is preferably implemented by a surface acoustic wave dispersion transducer. Of course, other device implementations that generate the chirp signals described above can be used.
本实施例中, 测量信号处理模块包括信号处理子模块和信号注入子模 块; 其中,  In this embodiment, the measurement signal processing module includes a signal processing submodule and a signal injection submodule;
信号处理子模块设置为利用 N/xNf阶二维扰码 C对线性调频脉冲测量信 号进行调制得到激励信号, N/xNf阶二维扰码 C中的元素 为 +1或 -1 ; m大 于等于 0, 小于等于 -1 ; n大于等于 0, 小于等 其具体处理过程请 参见实施例一; The signal processing sub-module is configured to modulate the chirp signal by using the N/xNf-order two-dimensional scrambling code C to obtain an excitation signal, and the element in the N/xN f- order two-dimensional scrambling code C is +1 or -1; m is greater than Equivalent to 0, less than or equal to -1; n is greater than or equal to 0, less than, etc. See the first embodiment for the specific processing procedure;
信号注入子模块设置为将信号处理子模块得到的激励信号输入 TD-LTE 系统的无线信道。 为了保证在可能的频点上都能接收到线性调频脉冲测试信 号, 本实施例中的测量信号接收模块包括 N 2N个信号接收器, 信号接收器 用于在相应的子载波频点上接收经 TD-LTE系统输出的线性调频脉冲测量信 号并输出接收的线性调频脉冲测量信号的自相关值 其中, N/为选择的子 载波频点个数; N为对所述正交频分复用信号的最大频偏值除以所述正交频 分复用信号的子载波带宽得到的值进行取整。 本实施例中的信号接收器也优 选釆用声表面波色散换能器来实现, 其得到各线性调频脉冲测量信号的自相 关值 W的具体过程请参见实施例一所示。 The signal injection sub-module is configured to input the excitation signal obtained by the signal processing sub-module into the wireless channel of the TD-LTE system. In order to ensure that the chirp test signal can be received at the possible frequency, the measurement signal receiving module in this embodiment includes N 2N signal receivers, and the signal receiver And configured to receive a chirp measurement signal outputted by the TD-LTE system at a corresponding subcarrier frequency point and output an autocorrelation value of the received chirp signal measurement signal, where N/ is a selected number of subcarrier frequency points; N is a value obtained by dividing a maximum frequency offset value of the orthogonal frequency division multiplexed signal by a subcarrier bandwidth of the orthogonal frequency division multiplexed signal. The signal receiver in this embodiment is also preferably implemented by using a surface acoustic wave dispersion transducer. For the specific process of obtaining the autocorrelation value W of each chirp measurement signal, please refer to the first embodiment.
本实施例中的第一计算模块包括二维滑动计算子模块, 设置为利用上述 N/XNf阶二维扰码 C对图 3所示的自相关值 R进行时域和频域的二维滑动相 关计算, 得到正交频分复用信号载波中心频点的频偏/和时延 τThe first calculation module in this embodiment includes a two-dimensional sliding calculation sub-module, and is configured to perform time domain and frequency domain two on the autocorrelation value R shown in FIG. 3 by using the above N /X N f- order two-dimensional scrambling code C. The dimensional sliding correlation calculation obtains the frequency offset/and delay τ of the center frequency point of the orthogonal frequency division multiplexed signal carrier.
本实施例中的第二计算模块包括频偏计算子模块, 设置为根据信号载波 中心频点的频偏/, 利用多普勒频偏理论计算公式(见实施例一中的式(7 ) ) 计算得到所述激励信号的到达角 φ 以及用于取激励信号在各子载波频点上 的到达角都为 φ , 将该到达角 φ带入多普勒频偏理论计算公式得到各子载波 频点上频偏值, 具体计算公式请参见实施例一种的式(8 ) 。  The second calculation module in this embodiment includes a frequency offset calculation sub-module, which is set to calculate the formula according to the frequency offset of the center frequency of the signal carrier, and uses the Doppler frequency offset theory (see equation (7) in the first embodiment). Calculating the angle of arrival φ of the excitation signal and the angle of arrival of the excitation signal at each subcarrier frequency point is φ, and bringing the angle of arrival φ into the Doppler frequency offset theoretical calculation formula to obtain the frequency of each subcarrier. Point the frequency offset value. For the specific calculation formula, please refer to the equation (8) of the embodiment.
第二计算模块还包括时延计算子模块, 设置为取正交频分复用信号符号 带宽内各子载波频点的时延都等于 τ。  The second calculation module further includes a delay calculation sub-module configured to take the time delay of each sub-carrier frequency point within the symbol bandwidth of the orthogonal frequency division multiplexing signal to be equal to τ.
本实施例中的合成处理模块包括无线信道冲击响应强度值获取子模块, 设置为根据多普勒频偏的数据对经典多径信道模型进行无线信道合成处理得 到为无线信道冲击响应强度值/^ , τ) , 具体计算公式请参见实施例一中的式 ( 9 ) 。  The synthesis processing module in this embodiment includes a wireless channel impulse response strength value acquisition sub-module, and is configured to perform wireless channel synthesis processing on the classical multipath channel model according to the Doppler frequency offset data to obtain a wireless channel impulse response intensity value/^ , τ), the specific calculation formula, please refer to the formula (9) in the first embodiment.
通过上述各功能模块的协同工作, 针对每次测量都能得到一个较为精确 的 h(t, , 然后利用统计分析模块, 针对每次测量得到的 /z(t, i:) , 计算其时域和 频域的自相关, 然后对信道响应的时域和频域自相关做傅里叶变换, 即可得 到被测 TD-LTE无线信道的统计特征, 包括: 时间延迟语、 多普勒扩展语、 角度扩展语、 相干时间以及相干带宽等统计参数。 应当理解的是, 本领域普通技术人员可以理解上述方法中的全部或部分 步骤和上述各功能模块可通过程序来指令相关硬件完成, 上述程序可以存储 于计算机可读存储介质中, 如只读存储器、 磁盘或光盘等。 可选地, 上述实 施例的全部或部分步骤也可以使用一个或多个集成电路来实现。 相应地, 上 述实施例中的各模块 /单元可以釆用硬件的形式实现, 也可以釆用软件功能模 块的形式实现。 本发明不限制于任何特定形式的硬件和软件的结合。 可见, 本发明实施例中的测量信号釆用在时域和频域能取得最优化分辨 率的线性调频脉冲测量信号, 在时域和频域上可同时得到准确的测量结果, 基于该测量结果得到的无线信道冲击响应强度值在时域和频域上也都更为准 确。 同时, 在本发明实施例中, 在进行合成处理得到无线信道冲击响应强度 值时, 还可进一步根据得到的正交频分复用信号载波中心频点的频偏和时延 推算出正交频分复用信号符号带宽内所有其他子载波频点的频偏和时延, 然 后基于得到的所有子载波频点的频偏和时延进行合成计算, 进而使得到的无 线信道冲击响应强度值更为准确。 以上实施例仅用以说明本发明的技术方案而非限制, 仅仅参照较佳实施 例对本发明进行了详细说明。 本领域的普通技术人员应当理解, 可以对本发 明的技术方案进行修改或者等同替换, 而不脱离本发明技术方案的精神和范 围, 均应涵盖在本发明的权利要求范围当中。 Through the cooperative work of the above functional modules, a more accurate h(t, can be obtained for each measurement, and then the time domain is calculated by using the statistical analysis module for /z(t, i:) obtained for each measurement. And the autocorrelation of the frequency domain, and then the Fourier transform of the time domain and the frequency domain autocorrelation of the channel response, the statistical characteristics of the measured TD-LTE radio channel, including: time delay language, Doppler extension language Statistical parameters such as angle extension, coherence time, and coherence bandwidth. It should be understood that those skilled in the art can understand that all or part of the above steps and the above various functional modules can be completed by a program to instruct related hardware, and the above program can be stored in a computer readable storage medium, such as a read only memory. , disk or CD, etc. Alternatively, all or part of the steps of the above embodiments may also be implemented using one or more integrated circuits. Correspondingly, each module/unit in the foregoing embodiment may be implemented in the form of hardware, or may be implemented in the form of a software function module. The invention is not limited to any specific form of combination of hardware and software. It can be seen that the measurement signal in the embodiment of the present invention is used for the chirp measurement signal with the optimal resolution in the time domain and the frequency domain, and the accurate measurement result can be obtained simultaneously in the time domain and the frequency domain, based on the measurement result. The obtained wireless channel impulse response intensity values are also more accurate in both the time domain and the frequency domain. In the embodiment of the present invention, when performing the combining process to obtain the wireless channel impulse response intensity value, the orthogonal frequency can be further calculated according to the obtained frequency offset and time delay of the carrier center frequency point of the orthogonal frequency division multiplexing signal. Frequency offset and delay of all other subcarrier frequency points in the bandwidth of the multiplexed signal symbol, and then based on the obtained frequency offset and delay of all subcarrier frequency points, and then the combined calculation of the impact value of the wireless channel To be accurate. The above embodiments are only intended to illustrate the technical solutions of the present invention and are not to be construed as limiting the invention. A person skilled in the art should understand that the technical solutions of the present invention may be modified or equivalent, without departing from the spirit and scope of the present invention, and should be included in the scope of the claims of the present invention.
工业实用性 Industrial applicability
通过本发明实施例可以在 TD-LTE系统中得到更为准确的无线信道冲击 响应强度值。  A more accurate wireless channel impulse response strength value can be obtained in the TD-LTE system by using the embodiment of the present invention.

Claims

权 利 要 求 书 Claim
1.一种时分长期演进 TD-LTE系统无线信道响应测量方法, 包括: 才艮据所述 TD-LTE系统的正交频分复用信号的符号带宽和符号周期确定 测量子载波频点和测量釆样时刻;  A time division long-term evolution TD-LTE system radio channel response measurement method, comprising: determining a measurement sub-carrier frequency point and measurement according to a symbol bandwidth and a symbol period of an orthogonal frequency division multiplexing signal of the TD-LTE system Time of the moment;
在所述测量子载波频点上根据所述测量釆样时刻生成线性调频脉冲测量 信号;  Generating a chirped pulse measurement signal according to the measurement sample time at the measurement subcarrier frequency point;
将所述线性调频脉冲测量信号调制处理后输入所述 TD-LTE系统的无线 信道;  And modulating the chirped pulse measurement signal into a wireless channel of the TD-LTE system;
在所述测量子载波频点上接收经所述 TD-LTE系统的无线信道输出的线 性调频脉冲测量信号并得到接收的线性调频脉冲测量信号的自相关值 R; 才艮据所述自相关值 R得到所述正交频分复用信号载波中心频点的频偏和 时延;  Receiving, on the measurement subcarrier frequency point, a chirp measurement signal outputted by the radio channel of the TD-LTE system and obtaining an autocorrelation value R of the received chirp measurement signal; according to the autocorrelation value R obtaining a frequency offset and a delay of a center frequency point of the orthogonal frequency division multiplexed signal carrier;
基于得到的所述频偏和所述时延进行无线信道响应合成处理得到无线信 道冲击响应强度值。  And performing wireless channel response synthesis processing based on the obtained frequency offset and the delay to obtain a wireless channel impulse response strength value.
2.如权利要求 1所述的 TD-LTE系统无线信道响应测量方法, 其中, 基 于得到的所述频偏和所述时延进行无线信道响应合成处理得到无线信道冲击 响应强度值之前, 还包括:  The TD-LTE system radio channel response measurement method according to claim 1, wherein before the radio channel response synthesis process is performed based on the obtained frequency offset and the delay to obtain a radio channel impulse response strength value, the method further includes :
根据所述载波中心频点的频偏和时延推算所述正交频分复用信号符号带 宽内至少一个其他子载波频点的频偏和时延。  Deriving a frequency offset and a delay of at least one other subcarrier frequency point in the symbol bandwidth of the orthogonal frequency division multiplexed signal according to a frequency offset and a time delay of the carrier center frequency point.
3.如权利要求 2所述的 TD-LTE系统无线信道响应测量方法, 其中, 根 据所述正交频分复用信号的符号带宽和符号周期确定测量子载波频点和测量 釆样时刻包括:  The TD-LTE system radio channel response measurement method according to claim 2, wherein determining the measurement subcarrier frequency point and the measurement sample time according to the symbol bandwidth and the symbol period of the orthogonal frequency division multiplexed signal comprises:
在所述正交频分复用信号的符号带宽内等间隔选择 个子载波频点作为 测量子载波频点, 所述 N/大于等于 1 ;  And selecting, according to a symbol bandwidth of the orthogonal frequency division multiplexing signal, a subcarrier frequency point as a measurement subcarrier frequency point, wherein the N/ is greater than or equal to 1;
在所述正交频分复用信号的符号周期内等间隔选择^个釆样时刻作为测 量釆样时刻, 所述 ^大于等于 1。 Selecting a sample time at equal intervals in the symbol period of the orthogonal frequency division multiplexed signal as a test When the quantity is sampled, the ^ is greater than or equal to 1.
4.如权利要求 3所述的 TD-LTE系统无线信道响应测量方法, 其中, 将 所述线性调频脉冲测量信号调制处理后输入所述 TD-LTE系统的无线信道包 括:  The TD-LTE system radio channel response measurement method according to claim 3, wherein the radio channel input to the TD-LTE system after the chirp measurement signal is modulated and processed comprises:
利用 NfxNt阶二维扰码 C对所述线性调频脉冲测量信号进行调制得到激 励信号, 所述 N Nt阶二维扰码 C中的元素 为 +1或 -1; 所述 m大于等于 0, 小于等于 -1; 所述 n大于等于 0, 小于等 The chirp signal is modulated by the N f xN t- order two-dimensional scrambling code C to obtain an excitation signal, and the element in the NN t- order two-dimensional scrambling code C is +1 or -1; 0, less than or equal to -1; the n is greater than or equal to 0, less than, etc.
将得到的激励信号输入所述 TD-LTE系统的无线信道。  The resulting excitation signal is input to the wireless channel of the TD-LTE system.
5.如权利要求 4所述的 TD-LTE系统无线信道响应测量方法, 其中, 根 据所述自相关值得到所述正交频分复用信号载波中心频点的频偏和时延包 括:  The TD-LTE system radio channel response measurement method according to claim 4, wherein obtaining a frequency offset and a delay of the center frequency of the orthogonal frequency division multiplexed signal carrier according to the autocorrelation value comprises:
利用所述^^<^阶二维扰码 C对所述自相关值 进行时域和频域的二维 滑动相关计算, 得到所述正交频分复用信号载波中心频点的频偏 /和时延7。  Performing a two-dimensional sliding correlation calculation of the autocorrelation value in the time domain and the frequency domain by using the two-dimensional scrambling code C of the ^^<^ step, obtaining a frequency offset of the center frequency of the orthogonal frequency division multiplexing signal carrier/ And delay 7.
6.如权利要求 5所述的 TD-LTE系统无线信道响应测量方法, 其中, 根 据所述载波中心频点的频偏推算所述正交频分复用信号符号带宽内至少一个 其他子载波频点的频偏和时延包括: 根据所述载波中心频点的频偏和时延推 算所述正交频分复用信号符号带宽内其他所有子载波频点的频偏和时延。  The TD-LTE system radio channel response measurement method according to claim 5, wherein at least one other subcarrier frequency in the symbol bandwidth of the orthogonal frequency division multiplexed signal is estimated according to a frequency offset of the carrier center frequency point The frequency offset and the delay of the point include: estimating a frequency offset and a delay of all other subcarrier frequency points in the symbol bandwidth of the orthogonal frequency division multiplexing signal according to the frequency offset and the time delay of the carrier center frequency point.
7.如权利要求 6所述的 TD-LTE系统无线信道响应测量方法, 其中, 根 据所述载波中心频点的频偏推算所述正交频分复用信号符号带宽内其他所有 子载波频点的频偏包括:  The TD-LTE system radio channel response measurement method according to claim 6, wherein all other subcarrier frequency points in the symbol band of the orthogonal frequency division multiplexed signal are estimated according to the frequency offset of the carrier center frequency point. The frequency offset includes:
才艮据所述正交频分复用信号载波中心频点的频偏 /,利用以下的多普勒频 偏理论计算公式计算得到所述激励信号的到达角 φ  According to the frequency offset / of the center frequency of the orthogonal frequency division multiplexed signal carrier, the arrival angle of the excitation signal is calculated by using the following Doppler frequency offset theoretical calculation formula φ
Fc - f = Fc -co>^ F c - f = F c -co>^
c  c
所述 为所述载波中心频点频率, 所述/为正交频分复用信号载波中心 频点的频偏, 所述 V为所述 TD-LTE系统当前的速度 , 所述 c为光速; 取所述激励信号在各子载波频点上的到达角都为 φ, 将该到达角 φ带入 所述多普勒频偏理论计算公式得到各子载波频点上频偏值: The frequency of the carrier center frequency, the / is an orthogonal frequency division multiplexing signal carrier center Frequency offset of the frequency point, the V is the current speed of the TD-LTE system, and the c is the speed of light; the angle of arrival of the excitation signal at each subcarrier frequency point is φ, and the angle of arrival is φ Bringing the Doppler frequency offset theory calculation formula to obtain the frequency offset value at each subcarrier frequency point:
Λ ϋ cos Λ ϋ cos
C 所述 为第 k个子载波频点的频率, 所述 Λ为第 k个子载波频点的频 偏, 所述 k大于等于 1 , 小于等于所述正交频分复用信号符号带宽内的子载 波频点个数;  C is the frequency of the kth subcarrier frequency point, the Λ is the frequency offset of the kth subcarrier frequency point, the k is greater than or equal to 1, and is less than or equal to the sub-band within the symbol bandwidth of the orthogonal frequency division multiplexed signal. Number of carrier frequency points;
根据所述载波中心频点的时延推算所述正交频分复用信号符号带宽内其 他所有子载波频点的时延包括:  Deferring the delay of all other subcarrier frequencies in the symbol bandwidth of the orthogonal frequency division multiplexing signal according to the delay of the carrier center frequency point includes:
取所述正交频分复用信号符号带宽内各子载波频点的时延都等于 τ。  The delay of each subcarrier frequency point in the symbol bandwidth of the orthogonal frequency division multiplexing signal is equal to τ.
8.如权利要求 7所述的 TD-LTE系统无线信道响应测量方法, 其中, 基 于得到的所有子载波频点的频偏和时延进行无线信道响应合成处理得到无线 信道冲击响应强度值包括:  The TD-LTE system radio channel response measurement method according to claim 7, wherein the radio channel response response strength value obtained by performing radio channel response synthesis processing based on the obtained frequency offset and delay of all subcarrier frequency points comprises:
根据多普勒频偏的数据按照下式对经典多径信道模型进行无线信道合成 处理:
Figure imgf000025_0001
According to the data of Doppler frequency offset, the wireless channel synthesis processing is performed on the classical multipath channel model according to the following formula:
Figure imgf000025_0001
p k 所述 d)为无线信道冲击响应强度值, 所述 p表示时延个数, 所述 k表 示频偏个数, 所述^¾为第 p个时延、 第 k个频偏的多径信号分量的信号强度 值; 所述 Λι为第 kl个频偏, 所述 kl大于等于 1 , 小于等于所述 k; 所述 为第 pi个时延, 所述 pi大于等于 1 , 小于等于所述 P, 所述 (t- )为时刻 t 输入的单位脉冲信号在时延 τρ处的响应脉冲, t为当前测量的时刻。 Pk, the d) is a wireless channel impulse response strength value, the p represents the number of delays, the k represents the number of frequency offsets, and the ^3⁄4 is the p-th delay, the k-th frequency-off multipath a signal strength value of the signal component; the Λι is the k1th frequency offset, the k1 is greater than or equal to 1, and less than or equal to the k; the pi is the pi delay, the pi is greater than or equal to 1, and less than or equal to the P, the (t-) is a response pulse of the unit pulse signal input at the time t at the time delay τ ρ , and t is the current measurement time.
9.一种时分长期演进 TD-LTE系统无线信道响应测量装置, 包括测量参 数确定模块、 测量信号生成模块、 测量信号处理模块、 测量信号接收模块、 第一计算模块和合成处理模块; 9. A time division long term evolution TD-LTE system wireless channel response measuring device, comprising a measurement parameter a number determination module, a measurement signal generation module, a measurement signal processing module, a measurement signal receiving module, a first calculation module, and a synthesis processing module;
所述测量参数确定模块设置为: 根据所述 TD-LTE系统的正交频分复用 信号的符号带宽和符号周期确定测量子载波频点和测量釆样时刻;  The measurement parameter determining module is configured to: determine a measurement subcarrier frequency point and a measurement sampling time according to a symbol bandwidth and a symbol period of the orthogonal frequency division multiplexing signal of the TD-LTE system;
所述测量信号生成模块设置为: 在所述测量子载波频点上 4艮据所述测量 釆样时刻生成线性调频脉冲测量信号;  The measurement signal generating module is configured to: generate a chirp measurement signal according to the measurement sampling time at the measurement subcarrier frequency point;
所述测量信号处理模块设置为: 将所述线性调频脉冲测量信号调制处理 后输入所述 TD-LTE系统的无线信道;  The measurement signal processing module is configured to: convert the chirp measurement signal into a wireless channel of the TD-LTE system after being modulated;
所述测量信号接收模块设置为: 在所述测量子载波频点上接收经所述 TD-LTE 系统输出的线性调频脉冲测量信号并得到接收的线性调频脉冲测量 信号的自相关值  The measurement signal receiving module is configured to: receive a chirp measurement signal outputted by the TD-LTE system at the measurement subcarrier frequency point, and obtain an autocorrelation value of the received chirp measurement signal
所述第一计算模块设置为: 根据所述自相关值 R得到所述正交频分复用 信号载波中心频点的频偏和时延;  The first calculating module is configured to: obtain a frequency offset and a delay of a center frequency point of the orthogonal frequency division multiplexing signal carrier according to the autocorrelation value R;
所述合成处理模块设置为: 基于得到的频偏和时延进行无线信道响应合 成处理得到无线信道冲击响应强度值。  The synthesis processing module is configured to: obtain a wireless channel impulse response intensity value by performing a wireless channel response synthesis process based on the obtained frequency offset and delay.
10.如权利要求 9所述的 TD-LTE系统无线信道响应测量装置,还包括第 二计算模块, 其设置为: 在所述合成处理模块基于得到的频偏和时延进行无 线信道响应合成处理得到无线信道冲击响应强度值之前, 根据所述第一计算 模块得到的载波中心频点的频偏和时延推算所述正交频分复用信号符号带宽 内至少一个其他子载波频点的频偏和时延。  10. The TD-LTE system radio channel response measuring apparatus according to claim 9, further comprising a second calculating module, configured to: perform, in the synthesis processing module, a radio channel response synthesis process based on the obtained frequency offset and delay Before obtaining the wireless channel impulse response strength value, estimating a frequency of at least one other subcarrier frequency in the symbol bandwidth of the orthogonal frequency division multiplexing signal according to a frequency offset and a time delay of the carrier center frequency point obtained by the first calculating module Partial and delay.
11.如权利要求 10所述的 TD-LTE系统无线信道响应测量装置, 其中, 所述测量参数确定模块包括频点确定子模块和釆样时刻确定子模块;  The TD-LTE system radio channel response measuring apparatus according to claim 10, wherein the measurement parameter determining module comprises a frequency point determining sub-module and a sampling time determining sub-module;
所述频点确定子模块设置为: 在所述正交频分复用信号的符号带宽内等 间隔选择 N/个子载波频点作为测量子载波频点, 所述 N/大于等于 1 ;  The frequency point determining sub-module is configured to: select N/s sub-carrier frequency points as measurement sub-carrier frequency points in an equal interval within a symbol bandwidth of the orthogonal frequency division multiplexing signal, where the N/ is greater than or equal to 1;
所述釆样时刻确定子模块设置为: 在所述正交频分复用信号的符号周期 内等间隔选择 Nf个釆样时刻作为测量釆样时刻, 所述 ^大于等于 1。 The sampling time determination submodule is set to: a symbol period of the orthogonal frequency division multiplexed signal The N f sample instants are selected as equal measurement intervals, and the ^ is greater than or equal to 1.
12.如权利要求 11所述的 TD-LTE系统无线信道响应测量装置, 其中, 所述测量信号处理模块包括信号处理子模块和信号注入子模块;  The TD-LTE system radio channel response measuring apparatus according to claim 11, wherein the measurement signal processing module comprises a signal processing submodule and a signal injection submodule;
所述信号处理子模块设置为: 利用 N/xNf阶二维扰码 C对所述线性调频 脉冲测量信号进行调制得到激励信号,所述 N/XNf阶二维扰码 C中的元素 cm,n 为 +1或 -1 ; 所述 m大于等于 0, 小于等于 -1; 所述 n大于等于 0, 小于等 于 The signal processing sub-module is configured to: modulate the chirp measurement signal by using an N/xN f- order two-dimensional scrambling code C to obtain an excitation signal, and the element in the N /X N f- order two-dimensional scrambling code C c m , n is +1 or -1; the m is greater than or equal to 0, less than or equal to -1; the n is greater than or equal to 0, less than or equal to
所述信号注入子模块设置为: 将所述信号处理子模块得到的激励信号输 入所述 TD-LTE系统的无线信道。  The signal injection sub-module is configured to: input an excitation signal obtained by the signal processing sub-module into a wireless channel of the TD-LTE system.
13.如权利要求 12所述的 TD-LTE系统无线信道响应测量装置, 其中, 所述第一计算模块包括二维滑动计算子模块,其设置为: 利用所述^^^阶二 维扰码 C对所述自相关值 R进行时域和频域的二维滑动相关计算, 得到所述 正交频分复用信号载波中心频点的频偏/和时延 τ。  The TD-LTE system radio channel response measuring apparatus according to claim 12, wherein the first calculating module comprises a two-dimensional sliding computing sub-module, which is configured to: use the ^^^ step two-dimensional scrambling code C performs a two-dimensional sliding correlation calculation on the autocorrelation value R in the time domain and the frequency domain to obtain a frequency offset/and a delay τ of the center frequency point of the orthogonal frequency division multiplexed signal carrier.
14.如权利要求 13所述的 TD-LTE系统无线信道响应测量装置, 其中、 所述第二计算模块包括频偏计算子模块和时延计算子模块; 所述频偏计算子 模块设置为:  The TD-LTE system radio channel response measuring apparatus according to claim 13, wherein the second calculating module comprises a frequency offset calculating submodule and a delay calculating submodule; and the frequency offset calculating submodule is set as:
才艮据所述正交频分复用信号载波中心频点的频偏 f, 利用以下多普勒频 偏理论计算公式计算得到所述激励信号的到达角 φ:  According to the frequency offset f of the center frequency point of the orthogonal frequency division multiplexing signal carrier, the arrival angle φ of the excitation signal is calculated by using the following Doppler frequency offset theoretical calculation formula:
Fc - f 二 Fc ∞s(p F c - f two F c ∞s(p
c 所述 为所述载波中心频点频率,所述/为正交频分复用信号载波中心 频点的频偏, 所述 V为所述 TD-LTE系统当前的速度 , 所述 c为光速;  c is the carrier center frequency frequency, the / is the frequency offset of the center frequency of the orthogonal frequency division multiplexing signal carrier, the V is the current speed of the TD-LTE system, and the c is the speed of light ;
以及取所述激励信号在各子载波频点上的到达角都为 φ, 将该到达角 φ 带入所述多普勒频偏理论计算公式得到各子载波频点上频偏值: fk 二 Fk—Fk—∞S (p And taking the excitation signal at each subcarrier frequency point of the angle of arrival is φ, the angle of arrival φ is brought into the Doppler frequency offset theoretical calculation formula to obtain the frequency offset value of each subcarrier frequency point: Fk 二F k— F k—∞S (p
c  c
所述 i¾为第 k个子载波频点的频率, 所述 Λ为第 k个子载波频点的频 偏, 所述 k大于等于 1 , 小于等于所述正交频分复用信号符号带宽内的子载 波频点个数;  The i3⁄4 is the frequency of the kth subcarrier frequency point, the Λ is the frequency offset of the kth subcarrier frequency point, and the k is greater than or equal to 1, and is less than or equal to the sub-band within the symbol bandwidth of the orthogonal frequency division multiplexed signal. Number of carrier frequency points;
所述时延计算子模块设置为取所述正交频分复用信号符号带宽内各子载 波频点的时延都等于 τ。  The delay calculation sub-module is configured to take the time delay of each sub-carrier frequency point in the symbol bandwidth of the orthogonal frequency division multiplexing signal to be equal to τ.
15、如权利要求 14所述的 TD-LTE系统无线信道响应测量装置, 其中, 所述合成处理模块包括无线信道冲击响应强度值获取子模块, 其设置为根据 多普勒频偏的数据按照以下公式对经典多径信道模型进行无线信道合成处 理:
Figure imgf000028_0001
The TD-LTE system radio channel response measuring apparatus according to claim 14, wherein the synthesizing processing module comprises a radio channel impulse response intensity value obtaining submodule, which is set to follow the data according to the Doppler frequency offset according to the following The formula performs wireless channel synthesis processing on the classical multipath channel model:
Figure imgf000028_0001
p k 所述 d)为无线信道冲击响应强度值, 所述 p表示时延个数, 所述 k表 示频偏个数, 所述^¾为第 p个时延、 第 k个频偏的多径信号分量的信号强度 值; 所述 Λι为第 kl个频偏, 所述 kl大于等于 1 , 小于等于所述 K; 所述 为第 pi个时延, 所述 pi大于等于 1 , 小于等于所述 P; 所述 (t- )为时刻 t 输入的单位脉冲信号在时延 τρ处的响应脉冲, t为当前测量的时刻。 Pk, the d) is a wireless channel impulse response strength value, the p represents the number of delays, the k represents the number of frequency offsets, and the ^3⁄4 is the p-th delay, the k-th frequency-off multipath a signal strength value of the signal component; the Λι is the k1th frequency offset, the k1 is greater than or equal to 1, and less than or equal to the K; the pi is the pi delay, the pi is greater than or equal to 1, and less than or equal to the P; (t-) is the response pulse of the unit pulse signal input at time t at time delay τ ρ , and t is the current measured time.
16、 一种计算机程序, 包括程序指令, 当该程序指令被无线信道响应测 量装置执行时, 使得该装置可执行权利要求 1-8任一项所述的方法。 16. A computer program comprising program instructions which, when executed by a wireless channel responsive measuring device, cause the apparatus to perform the method of any of claims 1-8.
17、 一种载有权利要求 16所述计算机程序的载体。  17. A carrier carrying the computer program of claim 16.
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