WO2008044268A1 - Transmitter apparatus and transmitting method - Google Patents

Transmitter apparatus and transmitting method Download PDF

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Publication number
WO2008044268A1
WO2008044268A1 PCT/JP2006/319992 JP2006319992W WO2008044268A1 WO 2008044268 A1 WO2008044268 A1 WO 2008044268A1 JP 2006319992 W JP2006319992 W JP 2006319992W WO 2008044268 A1 WO2008044268 A1 WO 2008044268A1
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Prior art keywords
phase
signal
constant envelope
means
envelope signals
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PCT/JP2006/319992
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French (fr)
Japanese (ja)
Inventor
Kazuhiko Ikeda
Takashi Izumi
Takashi Enoki
Shoichi Fujita
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Panasonic Corporation
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Priority to PCT/JP2006/319992 priority Critical patent/WO2008044268A1/en
Publication of WO2008044268A1 publication Critical patent/WO2008044268A1/en

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    • HELECTRICITY
    • H03BASIC ELECTRONIC CIRCUITRY
    • H03FAMPLIFIERS
    • H03F1/00Details of amplifiers with only discharge tubes, only semiconductor devices or only unspecified devices as amplifying elements
    • H03F1/02Modifications of amplifiers to raise the efficiency, e.g. gliding Class A stages, use of an auxiliary oscillation
    • H03F1/0205Modifications of amplifiers to raise the efficiency, e.g. gliding Class A stages, use of an auxiliary oscillation in transistor amplifiers
    • H03F1/0294Modifications of amplifiers to raise the efficiency, e.g. gliding Class A stages, use of an auxiliary oscillation in transistor amplifiers using vector summing of two or more constant amplitude phase-modulated signals

Abstract

An amplifier circuit capable of reducing the signal distortion, while suppressing the circuit scale to a small one. In this apparatus, amplifiers (120-1,120-2) amplify two constant envelope signals (S1(t),S2(t)), and a lossless combiner (130) combines the two constant envelope signals (GxS1(t),GxS2(t)) as amplified. A phase control signal generating part (152) generates a phase control signal for controlling the output load phase of the combined signal (GxS(t)) such that the ACLR of the combined signal (GxS(t)) to be determined by an ACLR determining part (151) is reduced. A phase shifter (140) controls, based on the phase control signal, the output load phase of the combined signal (GxS(t)).

Description

 Specification

 Transmitting apparatus and transmitting method

 Technical field

 TECHNICAL FIELD [0001] The present invention relates to a transmission apparatus and a transmission method, and in particular, LINC (Linear Amplification with

 The present invention relates to a transmission apparatus and a transmission method for amplifying a transmission signal using a nonlinear components method.

 Background art

 [0002] In recent years, in transmitters used for wireless communication and broadcasting, in order to improve frequency utilization efficiency, multi-level modulation schemes that multiplex information in the amplitude and phase directions, and OFDM modulation that multiplexes information in the frequency direction. There are many cases where signals are transmitted. These transmission methods can increase the amount of information that can be transmitted at one time, but the signal has a very large maximum power relative to the average power of the signal. Therefore, in these transmission systems, a high linearity is required for a transmission circuit that amplifies and transmits a signal. On the other hand, in order to reduce the power consumption of the transmission circuit, the transmission circuit is also required to have high power efficiency. In order to achieve both the linearity and power efficiency of the transmission circuit as described above, various methods for distortion compensation and efficiency improvement have been proposed.

 [0003] Another method of the conventional transmission circuit is called a LINC (Linear Amplification with Nonlinear Components) method. In this method, the transmission signal is split into two constant envelope signals, amplified by a nonlinear amplifier with high power efficiency, and then combined to achieve both linearity and power efficiency.

 FIG. 1 is a block diagram showing a configuration of a conventional LINC transmission circuit. In the transmission circuit 10 shown in FIG. 1, the constant envelope signal generator 11 generates two constant envelope signals S l (t) and S2 (t) from the input signal S (. These constant envelope signals Sl (t), S2 (t) is explained by equations: When the input signal S (t) is expressed by the following equation (1), two constant envelope signals S l (t), S2 (t (2) and (3), the constant envelope signals S 1 (t) and S2 (t) are constant envelope signals with a constant amplitude direction.

[0005] S (t) = V (t) 'cos {co ct + φ (t)} (1) Sl (t) = VmaxZ2-cos {oct + φ (t)} (2)

 S2 (t) = VmaxZ2'cos {coct + Θ (t)} (3) where Vmax is the maximum value of V (t), coc is the angular frequency of the carrier wave of the input signal, and φ (t) = φ (t ) + a (t), Θ (t) = (t)-α (t).

 FIG. 2 is a diagram showing signals of the transmission circuit 10 according to the conventional LINC method shown in FIG. 1 as a vector of orthogonal plane coordinates. That is, FIG. 2 is a diagram for explaining the operation of the constant envelope signal generation unit 11 of FIG. 1, and the signal vectors are displayed on the orthogonal plane change coordinates. As shown in Fig. 2, it can be seen that the input signal S (t) is represented by the sum of the two constant envelope signals Sl (t) and S2 (t) whose amplitude is VmaxZ2. As shown in FIG. 1, the two constant envelope signals Sl (t) and S2 (t) are amplified by the amplifier 12-1 and the amplifier 12-2, respectively. At this time, if the gains of the amplifier 12-1 and the amplifier 12-2 are G, the output signals of the amplifier 12-1 and the amplifier 12-2 are GXSl (t) and GXS2 (t), respectively. When these signals are vector-synthesized by the synthesizer 13, an output signal GXS (t) can be obtained. Here, each of the amplifier 12-1 and the amplifier 12-2 amplifies a constant envelope signal having a constant amplitude. Therefore, since it is possible to amplify in the nonlinear region of the amplifier 12-1 and the amplifier 12-2, that is, the saturation region, the power efficiency of the amplifier 12-1 and the amplifier 12-2 can be increased.

 [0007] However, in a LINC amplifier, the ratio of the maximum power to the average power of the transmitted signal increases as PAPR (Peak to Average Power Ratio) increases, and the transmitted signal is distorted. There is a problem.

 [0008] Hereinafter, efficiency degradation due to an increase in PAPR and generation of transmission signal distortion will be described. The LINC transmission circuit 10 shown in FIG. 1 includes amplifiers 12-1, 12-2, which are ideal class B amplifiers, and a synthesizer 13, which is an isolation synthesizer. When the reciprocal of PAPR, that is, the ratio of the average power to the maximum power of the transmitted signal is expressed as average power Z maximum power (= 1 / PAPR), the relationship between the average power Z maximum power and the efficiency of transmitter circuit 10 is shown in Figure 3A. As shown. As shown in FIG. 3A, as the average power Z maximum power decreases, that is, as PAPR increases, the efficiency of the transmission circuit 10 linearly deteriorates.

[0009] In order to suppress a decrease in efficiency of the transmission circuit 10 due to an increase in PAPR, Patent Document 1 describes that LI A lossless synthesizer or switching amplifier is used as the synthesizer 13 of the NC transmission circuit 10. By using a lossless synthesizer or a switching amplifier, no reactive power is generated in the load resistance, so that the efficiency of the transmission circuit 10 can be further improved. For example, in the LINC transmission circuit 10 shown in FIG. 1, when the amplifiers 12-1 and 12-2 are ideal class B amplifiers and the combiner 13 is a lossless combiner, the average power Z maximum power ( = 1ZP APR) and the efficiency of the transmitter circuit 10 is as shown in Fig. 3B. As shown in FIG. 3B, the decrease in the efficiency of the transmission circuit 10 is not in a linear relationship with the increase in PAPR. Because the degradation method is not linear, efficiency degradation can be reduced for signals with large PAPR.

 [0010] However, in the LINC transmission circuit 10 using a lossless synthesizer as the synthesizer 13, there is no isolation between the outputs of the two amplifiers 12-1 and 12-2. There is a problem that will occur. For this reason, it is necessary to provide an isolator in the lossless synthesizer to provide isolation between the outputs of the two amplifiers 12-1 and 12-2.

 Patent Document 1: Japanese Translation of Special Publication 2002-510927

 Disclosure of the invention

 Problems to be solved by the invention

However, if the synthesizer 13 is provided with an isolator, signal distortion can be reduced, but there is a problem that the circuit scale of the transmission circuit 10 increases due to the large parts of the isolator.

 An object of the present invention is to provide a transmission device and a transmission method capable of reducing signal distortion while keeping the circuit scale small.

 Means for solving the problem

In order to solve such a problem, the transmission apparatus according to the present invention includes a constant envelope signal generation unit that generates first and second constant envelope signals from an input signal, and the generated first and second generated envelopes. First and second amplifying means for respectively amplifying the above-described constant envelope signal, combining means for combining the first and second constant envelope signals after amplification to obtain a combined signal, and the combining And a variable phase means for controlling the phase of the signal. [0014] According to this configuration, the two constant envelope signals are generated from the input signal, the two constant envelope signals are amplified, and the two constant envelope signals after the amplification are combined to form the LINC method. Because it is possible to acquire a synthesized signal that is an amplified signal for the input signal and control the phase of the resulting synthesized signal, the signal distortion can be reduced by adjusting the output load phase of the synthesized signal. Can do.

 The invention's effect

 According to the present invention, it is possible to reduce signal distortion while keeping the circuit scale small.

 Brief Description of Drawings

[0016] FIG. 1 is a block diagram showing a main configuration of a conventional LINC transmission device.

 [Fig.2] Diagram for explaining the operation of a conventional LINC transmitter

 [Figure 3A] Figure showing the relationship between the efficiency of a conventional LINC transmitter and the average power Z maximum power

 [Figure 3B] Figure showing the relationship between the efficiency of a conventional LINC transmitter and the average power Z maximum power

 FIG. 4 is a block diagram showing a main configuration of the transmitting apparatus according to Embodiment 1 of the present invention.

 [Figure 5] Diagram showing the relationship between output load phase and ACLR

 FIG. 6 is a block diagram showing a main configuration of a transmitting apparatus according to Embodiment 2 of the present invention.

 [Figure 7] Diagram showing the relationship between output load phase and power efficiency

 FIG. 8 is a block diagram showing a main configuration of a transmitting apparatus according to Embodiment 3 of the present invention.

 FIG. 9 is a block diagram showing a main configuration of a transmitting apparatus according to Embodiment 4 of the present invention.

 FIG. 10 is a circuit diagram showing the main configuration of the synthesis unit according to the above embodiment.

 FIG. 11 is a circuit diagram showing a main configuration of a circuit equivalent to the synthesis unit according to the embodiment.

 FIG. 12 is a circuit diagram showing a main configuration of the synthesis unit according to the embodiment.

 BEST MODE FOR CARRYING OUT THE INVENTION

Hereinafter, embodiments of the present invention will be described in detail with reference to the drawings.

[0018] (Embodiment 1)

FIG. 4 shows the main configuration of the transmitting apparatus according to Embodiment 1 of the present invention. The transmitter 100 shown in Fig. 4 includes a constant envelope signal generator 110, amplifiers 120-1, 120-2, and lossless synthesis. Device 130, variable phase device 140, and control unit 150.

[0019] The constant envelope signal generator 110 generates two constant envelope signals SI (t), S2 from the input signal S (

 (t) is generated, the constant envelope signal Sl (t) is output to the amplifier 120-1, and the constant envelope signal S2 (t) is output to the amplifier 120-2.

[0020] Amplifiers 120-1 and 120-2 amplify the constant envelope signals Sl (t) and S2 (t), respectively, and eliminate the amplified constant envelope signals GXSl (t) and GXS2 (t). Output to loss synthesizer 130. In addition

, G represents the gain of the amplifiers 120-1 and 120-2.

The lossless synthesizer 130 synthesizes the constant envelope signals GXS l (t) and GXS2 (t) amplified by the amplifiers 120-1 and 120-2, and the resulting synthesized signal GXS (t) Output to variable phase shifter 140. The lossless synthesizer 130 also includes a force such as a Chireix synthesizer or a balun.

The variable phase shifter 140 controls the phase of the combined signal G X S (t) based on the phase control signal output from the phase control signal generation unit 152.

[0023] The control unit 150 includes an ACLR detection unit 151 and a phase control signal generation unit 152. The ACLR detection unit 151 measures ACLR using the combined signal GXS (t), and the measurement result is a phase control signal generation unit. Output to 152. The phase control signal generation unit 152 is connected to the ACLR detection unit 151.

A phase control signal is generated based on the ACLR measurement result, and the generated phase control signal is output to the variable phase shifter 140. The relationship between the ACLR measurement result and the phase control signal will be described later.

 Next, the operation of transmitting apparatus 100 configured as described above will be described with reference to the drawings.

 [0025] The constant envelope signal generator 110 generates two constant envelope signals SI (t) and S2 (t) from the input signal S (t), and the two constant envelope signals Sl (t) and S2 (t) is amplified by amplifiers 120-1 and 120-2, respectively. The amplified constant envelope signals GX Sl (t) and GXS2 (t) are combined by the lossless combiner 130, and the resultant combined signal GX S (t) is output to the variable phase shifter 140. The Then, the phase of the synthesized signal G X S (t) is controlled by the variable phase shifter 140 based on the phase control signal output from the phase control signal generation unit 152.

Here, the phase control signal is a measurement result of ACLR measured by ACLR detector 151. The result is generated by reference. Hereinafter, the phase control signal will be described with reference to FIG. Figure 5 shows the correspondence between the ACLR measurement results and the output load phase of the lossless synthesizer 130. The horizontal axis shows the load phase ([degrees]) and the right vertical axis shows the ACLR ([dB]). Yes. As shown in Fig. 5, it can be seen that the ACLR measurement results fluctuate greatly depending on the phase of the output load. For example, at VSW R (Voltage Standing Wave Ratio) = 3, it is clear that the ACLR measurement results are getting smaller in the range where the load phase is shown by the diagonal lines in FIG.

 That is, while monitoring the ACLR measurement result, the phase control signal for controlling the variable phase shifter 140 so as to minimize the ACLR measurement result and adjusting the output load phase is the phase control signal generator 152. By outputting the signal to the variable phase shifter 140, the phase of the variable phase shifter 140 is controlled so as to reduce the ACLR, and as a result, the signal distortion can be reduced.

 [0028] As described above, according to the present embodiment, the two constant envelope signals Sl (t) and S2 (t) are amplified by the amplifiers 120-1 and 120-2, and the amplified GX Sl is amplified. (t), GX S2 (t) is synthesized by the lossless synthesizer 130, and the variable phase shifter 140 is controlled by the phase control signal output from the phase control signal generator 152, and the synthesized signal GXS The output load phase of (t) was controlled. At this time, the output load phase of the composite signal GXS (t) is controlled so that the ACLR of the composite signal GXS (t) detected by the ACLR detection unit 151 becomes small. Therefore, it is possible to reduce signal distortion caused by a large signal component leaking out of the signal band, and it is possible to prevent an increase in circuit size.

 [0029] (Embodiment 2)

 FIG. 6 shows the main configuration of the transmission apparatus according to the present embodiment. In the transmitting apparatus according to the present embodiment shown in FIG. 6, the same components as those in FIG. 4 are denoted by the same reference numerals as those in FIG. 6 includes a current detection unit 153, a level detection unit 154, a power efficiency calculation unit 155, and a phase control signal generation unit 156 instead of the ACLR detection unit 151 and the phase control signal generation unit 152. And then.

The current detection unit 153 detects the current flowing through the amplifier 120-1 or 120-2 and outputs the obtained current value to the power efficiency calculation unit 155. The level detector 154 is a combination of The level of (t) is detected, and the obtained level value is output to the power efficiency calculation unit 155. The power efficiency calculation unit 155 calculates the power efficiency from the current value and the level value, and outputs the obtained power efficiency to the phase control signal generation unit 156. The phase control signal generation unit 156 generates a phase control signal for controlling the phase of the variable phase shifter 140 so that the calculated power efficiency is maximized, and outputs the phase control signal to the variable phase shifter 140.

[0031] Next, the operation of transmitting apparatus 100 configured as described above will be described with reference to the drawings.

 [0032] The constant envelope signal generation unit 110 generates two constant envelope signals SI (t) and S2 (t) from the input signal S (t), and the two constant envelope signals Sl (t) and S2 (t) is amplified by amplifiers 120-1 and 120-2, respectively. The amplified constant envelope signals GX Sl (t) and GX S2 (t) are synthesized by the lossless synthesizer 130, and the resultant synthesized signal GXS (t) is output to the variable phase shifter 140. The Then, the phase of the composite signal G X S (t) is controlled by the variable phase shifter 140 based on the phase control signal output from the phase control signal generation unit 156.

 Here, the phase control signal is output from the phase control signal generator 156 to the variable phase shifter 140 with reference to the power efficiency calculated by the power efficiency calculator 155. Hereinafter, the phase control signal will be described with reference to FIG. FIG. 7 shows the correspondence between the power efficiency and the output load phase in the lossless combiner 130. In addition, Fig. 7 shows the correspondence between ACLR and output phase. In Fig. 7, the horizontal axis represents the load phase ([degree]), the left vertical axis represents power efficiency (PAE) ([%]), and the right horizontal axis represents ACLR ([dB]).

 As shown in FIG. 7, it can be seen that the power efficiency varies depending on the phase of the output load.

 For example, the load phase is the value indicated by the triangle in FIG. In addition, the ACLR measurement results are getting smaller at the load phase that maximizes power efficiency. For example, in Figure 7, when the output load phase is around 45 degrees, the power efficiency is maximized. When the output power load phase is 45 degrees, the ACLR also decreases.

That is, while monitoring the power efficiency, the phase control signal for controlling the variable phase shifter 140 so as to maximize the power efficiency and shifting the output load phase is the phase control signal generator 15. By making the output from 6 to the variable phase shifter 140, it becomes possible to reliably reduce the ACLR and reduce the signal distortion while making the detection of the ACLR unnecessary.

 As described above, according to the present embodiment, the two constant envelope signals Sl (t) and S2 (t) are amplified by the amplifiers 120-1 and 120-2, and the amplified GX Sl is amplified. (t), GX S2 (t) is synthesized by the lossless synthesizer 130, and the variable phase shifter 140 is controlled by the phase control signal output from the phase control signal generator 156, and the synthesized signal GXS The output load phase of (t) was controlled. At this time, the variable phase shifter 140 is controlled so that the power efficiency calculated by the power efficiency calculation unit 155 is maximized. As a result, a large number of arithmetic processing such as A ZD conversion required for ACLR detection is not required, but ACLR is reduced, and the signal distortion caused by large ACLR and leakage of signal components outside the signal band is reduced. It is possible to prevent the enlargement of the circuit.

 [0037] (Embodiment 3)

 FIG. 8 shows the main configuration of the transmitting apparatus according to the present embodiment. In the transmitting apparatus according to the present embodiment in FIG. 8, the same components as in FIG. 4 are assigned the same reference numerals as those in FIG. In FIG. 8, a vector control signal generator 157 is added to FIG. 4, and the vector adjusters 160-1 and 160-2 are respectively connected between the constant envelope signal generator 110 and the amplifiers 120-1 and 120-2. 2 is used.

 [0038] Vector control signal generation section 157 generates a vector control signal based on the ACLR measurement result in ACLR detection section 151, and outputs the generated vector control signal to vector adjusters 160-1 and 160-2. To do. Specifically, the vector control signal generator 157 adjusts the vector adjusters 160-1 and 160-2 to obtain the combined signal GXS (t) of the two constant envelope signals SI (t) and S2 (t). The vector control signal is generated so that the measurement result of ACLR becomes smaller.

In the above description, the case where the vector control signal generation unit 157 generates a vector control signal based on the ACLR measurement result detected by the ACLR detection unit 151 has been described. Based on the power efficiency calculated by the efficiency calculation unit 155, the vector control signal generation unit 157 generates a vector control signal. [0040] The vector adjusters 160-1 and 160-2 are vectors that are output from the vector control signal generation unit 157 as vectors of the two constant envelope signals SI (t) and S2 (t). Adjust based on the control signal. As a result, in order to eliminate the path error between the two constant envelope signals after amplification and to reduce the ACLR measurement result, the vector regulators 160-1 and 160-2 have two constant envelope signals Sl (t), The phase and amplitude of S2 (t) are adjusted. The vector adjusters 160-1 and 160-2 are composed of, for example, a variable phase shifter or a variable attenuator.

 [0041] As described above, according to the present embodiment, the vector adjuster 160 before the two constant envelope signals Sl (t) and S2 (t) are amplified in the amplifiers 120-1 and 120-2. — 1, 160-2, and the vector control signal generator 157 adjusts the vectors of the two constant envelope signals Sl (t) and S2 (t) before synthesis by the ACLR detector 151. The ACLR of the detected composite signal GXS (t) was made small. As a result, the phase errors and amplitudes of the two constant envelope signals can be adjusted to reliably eliminate the path errors of the two constant envelope signals after amplification. In addition, signal distortion can be further reduced.

 [0042] (Embodiment 4)

 FIG. 9 shows the main configuration of the transmitting apparatus according to the present embodiment. In the transmitting apparatus according to the present embodiment in FIG. 9, the same components as in FIG. 4 are assigned the same reference numerals as in FIG. 4 and description thereof is omitted. FIG. 9 is different from FIG. 4 in that a capacity control signal generation unit 158 is provided instead of the phase control signal generation unit 152, the lossless synthesizer 130 and the variable phase shifter 140 are deleted, and a synthesis unit 170 is added. Take the configuration.

 FIG. 10 shows a main configuration of the synthesis unit 170. As shown in FIG. 10, the synthesizer 170 includes a path composed of a λ 4 phase shifter 171-1 and a variable capacitance diode (varactor) 172-1 mounted from a lumped constant, and a lumped constant A λ Ζ4 phase shifter 171-2 and a path composed of a variable capacitance diode (varactor) 172-2 are provided. The variable capacitance diodes 172-1 and 172-2 are connected to the subsequent stage of the λλ4 phase shifters 171-1 and 171-2, respectively.

At this time, the synthesizing unit 170 shown in FIG. 10 performs the circuit shown in FIG. 11, that is, λλ4 phase shifter 1 This is equivalent to the fact that a variable phase shifter 140 composed of a variable capacitance diode is provided after the lossless combiner 130 composed of 71-1, 171-2.

That is, in the present embodiment, the variable phase shifter 140 is configured by a variable capacitance diode, and instead of controlling the variable diode based on the ACLR measurement result in the ACLR detection unit 151, a lossless combiner 130 is implemented from lumped constant λ Ζ4 phase shifter 171— 1, 1

Each of the λ Ζ4 phase shifters 171– 1 and 171 2 is provided with variable capacitance diodes 172– 1 and 172– 2 to generate a capacitance control signal so that the ACLR measurement results are reduced. Based on the control signal output from the unit 158, the capacitance of the variable capacitance diodes 172-1, 172-2 is controlled.

 Based on the ACLR measurement result in ACLR detection unit 151, capacitance control signal generation unit 158 has variable capacitance diode 1 in synthesis unit 170 so as to minimize the ACLR measurement result.

A control signal is generated to control the capacity of 72-1, 172-2, and the generated control signal is output to variable phase diodes 172-1, 172-2.

 [0047] As described above, according to the present embodiment, combining section 170 has λΖ4 phase shifters 171-1, 17

1 2 is used to reduce the influence of the reflected wave, while the two constant envelope signals Sl (t), S after amplification

2 In the process of synthesizing (t), variable capacitance diodes 172-1 and 172-2 are installed in the subsequent stage of each λ Ζ4 phase shifter 171–1, 171–2, so that the ACLR measurement result becomes small. Since the capacitances of the variable capacitance diodes 172-1 and 172-2 are controlled, the synthesis of the two constant envelope signals Sl (t) and S2 (t) and the adjustment of the output load phase are combined into one circuit. And the circuit scale can be reduced.

 [0048] Further, a part of the capacitor of λ Ζ4 phase shifter 171—1 and the variable capacitance diode 172-1 are combined, and a part of the capacitor of λ Ζ4 phase shifter 171—2 and the variable capacitance diode 172-2 are combined. As shown in FIG. 12, the combining unit 170 may be mounted from the combined phase shifters 173-1, 173-2. As a result, the synthesis unit 170 can be further reduced.

[0049] Note that, instead of the ACLR measurement result, based on the power efficiency calculated by the power efficiency calculation unit 155, the capacitance control signal generation unit 158 has the variable capacitance diode 172 so that the power efficiency is maximized. — Generate control signal to control capacity of 1, 172— 2 Please do it.

 [0050] One aspect of the transmission apparatus of the present invention includes: constant envelope signal generation means for generating first and second constant envelope signals from an input signal; and the generated first and second constant envelopes First and second amplifying means for amplifying the line signal respectively, combining means for combining the amplified first and second constant envelope signals to obtain a combined signal, and controlling the phase of the combined signal And a variable phase means.

[0051] According to this configuration, the two constant envelope signals are generated from the input signal, the two constant envelope signals are amplified, and the two constant envelope signals after the amplification are combined to form the LINC method. for

Since the synthesized signal, which is the amplified signal for the input signal, can be obtained and the phase of the resulting synthesized signal can be controlled, signal distortion can be reduced by adjusting the output load phase of the synthesized signal. it can.

[0052] One aspect of the transmitting apparatus of the present invention is an acquisition unit that acquires an adjacent channel leakage power ratio of the composite signal after phase control by the variable phase unit, and the adjacent channel leakage power ratio is reduced. In addition, a configuration is further provided that includes control means for controlling the phase of the variable phase means.

[0053] According to this configuration, the phase of the combined signal can be controlled so as to reduce ACLR, and as a result, signal distortion can be reliably reduced.

[0054] One aspect of the transmission device of the present invention is a power efficiency calculation unit that calculates power efficiency of the transmission device, and a control that controls a phase of the variable phase unit so that the power efficiency is maximized. And means for further comprising.

[0055] According to this configuration, the phase of the combined signal can be controlled so that the power efficiency is maximized. As a result, signal distortion can be reduced while maximizing power efficiency and reducing ACLR.

[0056] One aspect of the transmission apparatus of the present invention is the first and second adjustment means for adjusting the first and second constant envelope signal vectors generated by the constant envelope signal generation means, Is further provided.

[0057] According to this configuration, the phase and amplitude of the two constant envelope signals can be adjusted to eliminate the path error between the two constant envelope signals after amplification. On the other hand, signal distortion can be reduced.

 [0058] In one aspect of the transmitting apparatus of the present invention, the combining means is implemented from a lumped constant.

 λΖ4 phase circuit power, and the variable phase means is composed of a variable capacitance diode connected to the subsequent stage of the λΖ4 phase circuit, and controls the phase of the composite signal by controlling the capacitance of the variable capacitance diode. Take the configuration.

 [0059] According to this configuration, it is possible to adjust the phase of the composite signal by generating a composite signal using a λΖ4 phase circuit implemented from lumped constants and controlling the capacitance of the varactor diode. The synthesis of two constant envelope signals and the adjustment of the output load phase of each constant envelope signal can be combined into one circuit, and the circuit scale can be reduced.

 Industrial applicability

[0060] The transmission apparatus and transmission method of the present invention can reduce signal distortion while keeping the circuit scale small, and particularly to a transmission apparatus and transmission method for amplifying and outputting a transmission signal in wireless communication. Useful.

Claims

The scope of the claims
 [1] Constant envelope signal generating means for generating first and second constant envelope signals from an input signal, and first and second amplifying the generated first and second constant envelope signals, respectively. Amplifying means,
 A synthesis means for synthesizing the first and second constant envelope signals after amplification to obtain a synthesized signal;
 Variable phase means for controlling the phase of the combined signal;
 A transmission apparatus comprising:
 [2] An acquisition unit that acquires an adjacent channel leakage power ratio of the composite signal after phase control by the variable phase unit;
 Control means for controlling the phase of the variable phase means so as to reduce the adjacent channel leakage power ratio;
 Further comprising
 The transmission device according to claim 1.
[3] power efficiency calculating means for calculating power efficiency of the transmitting device;
 Control means for controlling the phase of the variable phase means so as to maximize the power efficiency;
 Further comprising
 The transmission device according to claim 1.
[4] First and second adjustment means for adjusting vectors of the first and second constant envelope signals generated by the constant envelope signal generation means,
 Further comprising
 The transmission device according to claim 1.
[5] The synthesis means includes
 It consists of λ 回路 4 phase circuit mounted from lumped constant,
 The variable phase means includes
It consists of a variable capacitance diode connected to the latter stage of the λΖ4 phase circuit, and controls the phase of the composite signal by controlling the capacitance of the variable capacitance diode The transmission device according to claim 1.
 Generating first and second constant envelope signals from an input signal;
 First and second steps for amplifying the generated first and second constant envelope signals, respectively;
 A step of synthesizing the first and second constant envelope signals after amplification to obtain a synthesized signal;
 Controlling the phase of the combined signal;
 A transmission method.
PCT/JP2006/319992 2006-10-05 2006-10-05 Transmitter apparatus and transmitting method WO2008044268A1 (en)

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WO2011024598A1 (en) * 2009-08-27 2011-03-03 京セラ株式会社 Electrical power amplifier circuit, and transmission device and communication device using the same
WO2012086015A1 (en) * 2010-12-21 2012-06-28 富士通株式会社 Amplifying device
JP2012531095A (en) * 2009-06-18 2012-12-06 アルカテル−ルーセント High efficiency transmitter for wireless communication
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JP2012531095A (en) * 2009-06-18 2012-12-06 アルカテル−ルーセント High efficiency transmitter for wireless communication
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