WO2006035881A1 - マイクロストリップアンテナ及びマイクロストリップアンテナを用いた高周波センサ - Google Patents
マイクロストリップアンテナ及びマイクロストリップアンテナを用いた高周波センサ Download PDFInfo
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- WO2006035881A1 WO2006035881A1 PCT/JP2005/017970 JP2005017970W WO2006035881A1 WO 2006035881 A1 WO2006035881 A1 WO 2006035881A1 JP 2005017970 W JP2005017970 W JP 2005017970W WO 2006035881 A1 WO2006035881 A1 WO 2006035881A1
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- parasitic
- microstrip antenna
- feeding
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- elements
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Classifications
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- H—ELECTRICITY
- H01—ELECTRIC ELEMENTS
- H01Q—ANTENNAS, i.e. RADIO AERIALS
- H01Q3/00—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system
- H01Q3/24—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system varying the orientation by switching energy from one active radiating element to another, e.g. for beam switching
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- H—ELECTRICITY
- H01—ELECTRIC ELEMENTS
- H01Q—ANTENNAS, i.e. RADIO AERIALS
- H01Q13/00—Waveguide horns or mouths; Slot antennas; Leaky-waveguide antennas; Equivalent structures causing radiation along the transmission path of a guided wave
- H01Q13/08—Radiating ends of two-conductor microwave transmission lines, e.g. of coaxial lines, of microstrip lines
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- H—ELECTRICITY
- H01—ELECTRIC ELEMENTS
- H01Q—ANTENNAS, i.e. RADIO AERIALS
- H01Q19/00—Combinations of primary active antenna elements and units with secondary devices, e.g. with quasi-optical devices, for giving the antenna a desired directional characteristic
- H01Q19/005—Patch antenna using one or more coplanar parasitic elements
-
- H—ELECTRICITY
- H01—ELECTRIC ELEMENTS
- H01Q—ANTENNAS, i.e. RADIO AERIALS
- H01Q19/00—Combinations of primary active antenna elements and units with secondary devices, e.g. with quasi-optical devices, for giving the antenna a desired directional characteristic
- H01Q19/28—Combinations of primary active antenna elements and units with secondary devices, e.g. with quasi-optical devices, for giving the antenna a desired directional characteristic using a secondary device in the form of two or more substantially straight conductive elements
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- H—ELECTRICITY
- H01—ELECTRIC ELEMENTS
- H01Q—ANTENNAS, i.e. RADIO AERIALS
- H01Q3/00—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system
- H01Q3/44—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system varying the electric or magnetic characteristics of reflecting, refracting, or diffracting devices associated with the radiating element
-
- H—ELECTRICITY
- H01—ELECTRIC ELEMENTS
- H01Q—ANTENNAS, i.e. RADIO AERIALS
- H01Q9/00—Electrically-short antennas having dimensions not more than twice the operating wavelength and consisting of conductive active radiating elements
- H01Q9/04—Resonant antennas
- H01Q9/0407—Substantially flat resonant element parallel to ground plane, e.g. patch antenna
-
- H—ELECTRICITY
- H01—ELECTRIC ELEMENTS
- H01Q—ANTENNAS, i.e. RADIO AERIALS
- H01Q9/00—Electrically-short antennas having dimensions not more than twice the operating wavelength and consisting of conductive active radiating elements
- H01Q9/04—Resonant antennas
- H01Q9/0407—Substantially flat resonant element parallel to ground plane, e.g. patch antenna
- H01Q9/0442—Substantially flat resonant element parallel to ground plane, e.g. patch antenna with particular tuning means
Definitions
- the present invention relates to a microstrip antenna that transmits microwaves or higher frequency radio waves, and more particularly, to a technique for controlling the radiation direction of an integrated radio beam that also transmits microstrip antenna force.
- the present invention also relates to a high-frequency sensor using a microstrip antenna.
- an antenna electrode and a ground electrode are arranged on the front and back surfaces of a substrate, respectively, and a microwave high-frequency signal is applied between the antenna electrode and the ground electrode, thereby causing the antenna electrode force to move vertically.
- Microstrip antennas that transmit radio waves are known.
- the following technologies are known for controlling the radiation direction of an integrated radio wave beam that also emits microstrip antenna power.
- Patent Document 1 Japanese Patent Laid-Open No. 7-128435 (Patent Document 1), a plurality of antenna electrodes are arranged on the surface of a substrate, and a high-frequency signal is fed to each antenna electrode by switching a high-frequency switch. By changing the height, the radiation direction of the integrated radio beam is changed.
- Patent Document 2 Japanese Patent Application Laid-Open No. 9-214238
- Patent Document 2 Japanese Patent Application Laid-Open No. 9-214238
- Patent Document 3 describes a feed point switching type multi-beam antenna provided with a plurality of feeding elements and a plurality of parasitic elements on a substrate surface.
- this multi-beam antenna all or some of the plurality of feed elements can be connected to and opened from the feed terminal via the switch, and the feed element fed by the switch can be switched. This makes it possible to select radio beams with different radiation directions.
- Microstrip antenna force Object detection devices using transmitted radio waves are known!
- this object detection device by changing the radiation direction of the integrated radio beam from the microstrip antenna as described above, the radiation direction of the integrated radio beam is fixed compared to the case where the radiation direction of the integrated radio beam is fixed.
- the position and state of the object can be detected more accurately. For example, by scanning the 2D range by changing the radiation direction of the integrated wave beam that also transmits the microstrip antenna force to the XY direction, it is possible to grasp the presence and state of objects over the 2D range.
- Object detection devices can be used for a variety of purposes, for example, target detection in automatic tracking missiles and user detection in toilet devices.
- any application it is very useful to be able to change the radiation direction of the integrated radio beam transmitted by the microstrip antenna force.
- a user detection device in a toilet device if the position and state of the user are detected more accurately, the toilet cleaning device and deodorizing device can be controlled more appropriately.
- a camera may be more suitable for the purpose of accurately grasping the user's condition, but it cannot be used in a toilet device. Therefore, it is very important for an object detection device that uses radio waves to control the radiation direction of an integrated radio wave beam so that the user can be more accurately grasped.
- a frequency of 10.525 GHz or 24.15 GHz can be used for the purpose of detecting a human body, and a frequency of 76 GHz can be used for the purpose of preventing vehicle collision.
- Patent Document 1 Japanese Patent Laid-Open No. 7-128435
- Patent Document 2 JP-A-9-214238
- Patent Document 3 Japanese Patent Laid-Open No. 2003-142919
- the microwave signal is passed and blocked in the middle of the feed line that transmits the microwave signal.
- a high-frequency switch that can be selected and whose impedance to the microwave signal at a specific frequency is strictly adjusted to a predetermined appropriate value is connected to perform switching. Need to do. However, the higher the frequency, the more the characteristics of the feed line and the high frequency switch and the variation in the connection state (e.g., the relative permittivity of the substrate, the performance of the high frequency switch, the etching accuracy of the feed line pattern, the mounting position of the switch, etc.) ) Greatly affects the antenna performance. If the connection is poor, the amount of reflection of the microwave signal increases at the connection part of the high frequency switch, the amount of power supplied to the antenna through the high frequency switch decreases, or the phase amount changes to the desired direction. The radio beam can no longer be emitted.
- the excitation directions of the feed elements arranged in the horizontal direction and the vertical direction are different from each other.
- the radiation direction of the radio wave beam can be changed only at intervals.
- the radiation direction of the radio beam is determined by selecting the element to be fed, but the radiation angle is constant.
- an object of the present invention is to make the radiation direction of a radio wave beam variable with a simple configuration in a microstrip antenna.
- a microstrip antenna includes a substrate, a feeding element disposed on the front surface of the substrate, and a parasitic power disposed on the front surface of the substrate at a predetermined space between the feeding elements.
- the grounding means includes a ground electrode and a switch for connecting and disconnecting the parasitic element to the ground electrode.
- This switch has two electrical contacts connected to the parasitic element and the earth electrode, respectively, and the two electrical contacts are separated by a first gap in the ON state and in the OFF state. It is possible to use a switch that is separated by a second gap that is larger than the first gap.
- a switch having an insulating film between two electrical contacts respectively connected to the parasitic element and the ground electrode can be used as the switch.
- a MEMS switch can be used as a switch having such a structure.
- the parasitic element is disposed away from the feeding element in the excitation direction by a predetermined inter-element space, and the radio wave in the resonance frequency of the feeding element is in the air.
- the wavelength between the elements is ⁇ / 4 to ⁇ / 30, when the wavelength at is calculated.
- the parasitic element is arranged away from the feeding element in a direction perpendicular to the excitation direction by a predetermined inter-element space, and the inter-element space is ⁇ ⁇ 4 ⁇ ⁇ ⁇ 9.
- a microstrip antenna includes a plurality of parasitic elements arranged on one side of the feeding element so as to be linearly arranged with the feeding elements, and a plurality of the parasitic elements.
- a plurality of switch means corresponding to the respective elements, and the inter-element spaces of the plurality of parasitic elements are different from each other.
- a microstrip antenna includes a plurality of the parasitic elements respectively disposed on different sides of the feeding element and a plurality of the switches respectively corresponding to the plurality of parasitic elements. Means.
- a microstrip antenna includes a plurality of the parasitic elements arranged on both sides of the feeding element so as to be linearly aligned with the feeding elements, and a plurality of the parasitic elements.
- a plurality of the switch means respectively corresponding to the power supply element, the parasitic element arranged on one side of the power supply element, and the influence S on the electron beam of the parasitic element arranged on the other side S balance
- the sizes of the parasitic elements or the spaces between the elements are different!
- a microstrip antenna includes the feed element and the non-feed It further has a dielectric layer covering the front surface of the substrate including the surface of the electric element.
- a microstrip antenna includes an adjacent end surface of the adjacent feeding element and another feeding element, or an adjacent end surface of the adjacent feeding element and the parasitic element, Alternatively, it further includes a dielectric mask that covers the adjacent parasitic element and the opposing end face of another parasitic element.
- a microstrip antenna has a plurality of sub-antennas each including a set of the feeding element and the parasitic element on the front surface of the substrate, and includes a plurality of sub-antennas.
- a slit is provided in the portion of the substrate corresponding to the boundary.
- a microstrip antenna includes a plurality of sub-antennas each including a set of the feeding element and the parasitic element on the front surface of the substrate, and the plurality of sub-antennas.
- a portion of the substrate corresponding to the boundary has a shield body that is always maintained at a constant potential.
- the parasitic element can be grounded at a plurality of locations.
- the parasitic element is disposed in a direction oblique to the excitation direction of the feeding element with respect to the feeding element.
- a microstrip antenna includes a first type of one or more sub-antennas and a second type of antennas each including a set of a feeding element and a parasitic element on a front surface of a substrate.
- There are one or more sub-antennas and the first and second types of sub-antennas differ in the positional relationship of the parasitic element with respect to the feeding element.
- the parasitic element in the first type of sub-antenna, the parasitic element is arranged in a direction oblique to the excitation direction with respect to the feeding element, while in the second type of sub-antenna, the parasitic element is arranged with respect to the feeding element. It is arranged in a direction parallel to or perpendicular to the excitation direction.
- the first and second types of sub-antennas are arranged at complementary positions.
- the parasitic element is always grounded at a position near the center of one or more outer edges orthogonal to the excitation direction when in the float state. Has a point.
- a feed element can A plurality of feed points for exciting in the direction to be selected and a plurality of feed points selectively grounded to selectively enable one of the excitations by the plurality of feed points and to substantially disable the other And a grounding point.
- a plurality of feeding elements are arranged adjacent to each other without a parasitic element between them on the substrate, and the plurality of feeding elements are arranged in two.
- a plurality of parasitic elements are arranged so as to surround in dimension.
- a plurality of feeding elements are arranged adjacent to each other without a parasitic element between them on a substrate. Then, it is possible to switch between a power float state in which at least one predetermined point of the plurality of feeding elements is grounded.
- a dielectric lens is disposed in front of the feeding element and the parasitic element.
- the grounding means has an openable and closable line for releasing a high frequency from the parasitic element to the ground level, and the length of the line is equal to the high frequency. It is m times half the wavelength (m is an integer greater than 1). In another embodiment, when the line is in an open state, the flow of the part connected to the parasitic element of the line is m times half the above wavelength (m is an integer of 1 or more). Yes.
- the length force of the line is between m times one half of the wavelength of the high frequency (m is an integer of 1 or more) and the length that is not so. Selectable ⁇ This is done.
- the line has a means for adjusting an impedance (for example, a stub connected to the line or a dielectric layer covering the surface of the line). ).
- the nth harmonic on the feed element is the nth harmonic on the feed element
- n is an integer greater than or equal to 2 where the current amplitude value is at or near the minimum, and the fundamental wave A predetermined point in the area where the current amplitude value of the current becomes the maximum or in the vicinity thereof is grounded.
- the microstrip antenna includes a substantially flat first circuit unit having a control circuit for controlling the grounding means, and a high-frequency power that generates high-frequency power to be applied to the feed element.
- a substantially flat second circuit unit having an oscillating circuit is further provided, and the first and second circuit units are integrally coupled in a stacked manner on the back surface of the substrate.
- a substantially flat plate shape is provided between the substrate and the first circuit unit and between Z or the first circuit unit and the second circuit unit. Spacers are installed. The substrate, the first and second circuit units, and the spacer are integrally coupled in a stacked form.
- the feed line extends to the feed element on the high-frequency oscillation circuit force substrate on the second circuit unit.
- the feed line passes through the inside of the spacer and is surrounded by the spacer.
- the first and second circuit unit forces share the same ground electrode sandwiched between the circuit units.
- a microstrip antenna is disposed so as to surround a substrate, a feed element disposed on the front surface of the substrate, resonating in a first resonance frequency band, and the periphery of the feed element.
- a first parasitic element that resonates and a second parasitic frequency that resonates in a second resonance frequency band that is disposed on the front surface of the substrate by the loop element or the feeding element force separated by a predetermined inter-element space.
- a feeding element; and a grounding unit that switches between grounding or floating the first parasitic element and the second parasitic element.
- a high-frequency sensor using a microstrip antenna includes a substrate, a feed element disposed on the front surface of the substrate, and a front surface of the substrate. Are spaced apart from the feeding element by a predetermined inter-element space. And a grounding means for switching whether the parasitic element is grounded or floated.
- the radiation direction of the radio wave beam can be varied with a simple configuration.
- FIG. 1 is a plan view of a microstrip antenna according to an embodiment of the present invention.
- FIG. 2 is a cross-sectional view taken along the line AA in FIG.
- FIG. 3 is a diagram showing a state in which the radiation direction of a radio wave beam is changed by operating switches 120 and 124.
- FIG. 4 is a diagram showing a waveform of a microwave current flowing through a feeding element and a parasitic element to explain the principle of changing the radiation direction of a radio wave beam.
- FIG. 5 is a diagram showing an example of the relationship between the inter-element space S and the phase difference ⁇ .
- FIG. 6 is a diagram showing an example of the relationship between the phase difference ⁇ and the radiation angle of the radio wave beam.
- FIG. 7 A diagram showing an example of the relationship between the position of the grounding point of the parasitic element in the excitation direction and the radiation angle of the radio beam.
- FIG.8 An example of the radiation angle relationship when the grounding point is moved in a direction perpendicular to the excitation direction with respect to the center of the parasitic element when the grounding point position is greater than 0.25L.
- FIG. 9 is a plan view of a microstrip antenna that works according to the second embodiment of the present invention.
- FIG. 10 is a plan view of a microstrip antenna that works according to the third embodiment of the present invention.
- FIG. 11 is a diagram showing a state in which the radiation angle of the radio beam is changed by the switch operation in the microstrip antenna shown in FIG.
- FIG. 12 is a plan view showing a modification of the third embodiment.
- FIG. 13 is a plan view of a microstrip antenna that works according to a fourth embodiment of the present invention.
- FIG. 14 is a diagram showing a state in which the radiation direction of the radio beam is changed by the switch operation in the microstrip antenna shown in FIG.
- FIG. 15 is a plan view showing a modification of the fourth embodiment.
- FIG. 16 is a plan view showing another modification of the fourth embodiment.
- FIG. 17 is a plan view of a microstrip antenna that works according to a fifth embodiment of the present invention.
- FIG. 18 is a diagram showing a change in the radiation angle of the radio wave beam by switching the effective Z invalidity of each parasitic element in the microstrip antenna shown in FIG.
- FIG. 19 is a plan view and a cross-sectional view of a microstrip antenna that works on the sixth embodiment of the present invention.
- FIG. 20 is a plan view of a microstrip antenna that works according to a seventh embodiment of the present invention.
- FIG. 21 is a plan view and a cross-sectional view of a modified example of the seventh embodiment.
- FIG. 22 is a plan view and a sectional view of another modified example of the seventh embodiment.
- FIG. 23 is a plan view and a cross-sectional view of still another modified example of the seventh embodiment.
- FIG. 24 is a plan view and a cross-sectional view of a microstrip antenna that works on the eighth embodiment of the present invention.
- FIG. 25 is a plan view and a cross-sectional view of a microstrip antenna that works on the ninth embodiment of the present invention.
- FIG. 26 is a plan view of a microstrip antenna that is effective in the tenth embodiment of the present invention.
- FIG. 27 is a diagram showing a waveform of a microwave current flowing through a feeding element and a parasitic element in the tenth embodiment.
- FIG.28 shows how the radiation direction of the radio wave beam changes in the microstrip antenna shown in Fig.26.
- FIG. 29 is a diagram showing a modification of the relationship between the size of the feed element and the parasitic element applicable to the microphone strip antenna according to the present invention.
- ⁇ 30 A plan view showing a modified example regarding the arrangement of the parasitic elements.
- FIG. 31 is a plan view showing a modification of the power feeding element.
- FIG. 32 is a plan view of a microstrip antenna that works according to an eleventh embodiment of the present invention.
- FIG. 33 is a plan view of a microstrip antenna that works according to a twelfth embodiment of the present invention.
- FIG. 34 is a plan view of a microstrip antenna that works according to a thirteenth embodiment of the present invention.
- FIG. 35 is a diagram showing a comparison of radio wave inclination in the first, eleventh, twelfth and thirteenth embodiments.
- FIG. 36 is a plan view showing two modified examples of the relationship between the widths of the feeding element and the parasitic element.
- FIG. 37 is a diagram showing the radio wave inclination in the two modified examples shown in FIGS. 36A and B in comparison.
- FIG. 38 is a diagram showing the relationship between the width of the parasitic element, the inclination of the radio wave, and the strength in the two modifications shown in FIG. 36B.
- FIG. 39 is a plan view and a cross-sectional view of a microstrip antenna according to a fourteenth embodiment of the present invention.
- FIG. 40 is a diagram showing waveforms of currents flowing through the feed element and the parasitic element when the switch 322 is off and on in the fourteenth embodiment.
- FIG. 41 is a plan view of a microstrip antenna that works according to a fifteenth embodiment of the present invention.
- FIG. 43A is a cross-sectional view showing an OFF state of a MEMS switch suitable for an application for controlling the inclination of a radio wave beam
- FIG. 43B is a cross-sectional view showing an ON state of the MEMS switch.
- FIG. 44A is a cross-sectional view showing an OFF state of an electrical contact of a conventional MEMS switch
- FIG. 44B is a cross-sectional view showing an ON state of the electrical contact.
- FIG. 45A is a cross-sectional view showing an OFF state of an electrical contact of the MEMS switch shown in FIG. 43
- FIG. 45B is a cross-sectional view showing an ON state of the electrical contact.
- FIG. 46A is a cross-sectional view showing an OFF state of an electrical contact in a modified example of a switch suitable for use in controlling the inclination of a radio beam
- FIG. 46B is a cross-sectional view showing an ON state of the electrical contact.
- FIG. 47 is a plan view of a microstrip antenna that works according to the sixteenth embodiment of the present invention.
- FIG. 48 is a plan view of a microstrip antenna that is effective in a seventeenth embodiment of the present invention.
- FIG. 49 is a cross-sectional view taken along the line AA in FIG.
- FIG. 50 is a plan view of a microstrip antenna that is effective in an eighteenth embodiment of the present invention.
- FIG. 51 is a plan view of a microstrip antenna that is effective in a nineteenth embodiment of the present invention.
- FIG. 52 is a sectional view taken along line AA in FIG.
- FIG. 53 is a plan view showing a modification of the power feeding element that can be employed in the microstrip antenna of the present invention.
- FIG. 54 is a side view showing one suitable application for the microstrip antenna having the feeding element shown in FIG. 53.
- FIG. 55 is a plan view showing detection characteristics when the excitation direction of the object sensor 22 shown in FIG. 54 is the horizontal direction.
- FIG. 56 is a plan view showing detection characteristics when the excitation direction of the object sensor 22 shown in FIG. 54 is the vertical direction.
- FIG. 57 is a plan view of a microstrip antenna that is useful for the twentieth embodiment of the present invention.
- FIG. 58 is a plan view of a modification of the twentieth embodiment.
- FIG. 62 is a cross-sectional view of a microstrip antenna according to a twenty-first embodiment of the present invention.
- FIG. 63 is a cross-sectional view of a microstrip antenna that works according to a twenty-second embodiment of the present invention.
- FIG. 64 is a diagram showing the relationship between the line length T from the parasitic element 610 to the ground electrode 614 and the amount of current flowing through the parasitic element 610 when the switch 616 is on in the twenty-second embodiment.
- FIG. 65 is a plan view of the back surface of a modification of the twenty-second embodiment.
- FIG. 66 shows changes in the line length T and the current flowing through the parasitic element in the antenna shown in FIG.
- FIG. 67 shows a change in the radiation direction of the radio beam obtained by operating switch 616 in the antenna shown in FIG.
- FIG. 68 is a cross-sectional view of a microstrip antenna according to a twenty-third embodiment of the present invention.
- FIG. 69 is a sectional view taken along line AA in FIG.
- FIG. 70 is a plan view of a feed element 640 showing an example of a preferable region where a ground point 648 for reducing spurious is to be disposed.
- FIG. 71 is a cross-sectional view of a microstrip antenna according to a twenty-fourth embodiment of the present invention (extracted only from a portion corresponding to one parasitic element 610).
- FIG. 72A and 72A show the change in impedance Z at the ground point 610A of parasitic element 610A by switching on and off of switch 616 in the antenna shown in Figs. 71 and 63, respectively.
- FIG. 73 is a plan view of the back surface of the antenna showing a method for adjusting the impedance related to the parasitic element 6 10 applicable to the microstrip antenna according to the present invention (corresponding to one parasitic element 610). (Excerpt only part).
- FIG. 74 is a cross-sectional view of a microstrip antenna according to a twenty-fourth embodiment of the present invention.
- FIG. 75 is an exploded view of the twenty-fourth embodiment.
- FIG. 76 is a plan view of spacers 688 and 682 in the twenty-fourth embodiment.
- FIG. 77 is a plan view of a modification of spacers 688 and 682 shown in FIG. 76.
- FIG. 78 is a rear view of an analog circuit unit 606 in a twenty-fourth embodiment.
- FIG. 79 is a cross section of a modified example of the twenty-fourth embodiment.
- 80A to 80C are perspective views of variations of dielectric lenses applicable to the microstrip antenna of the present invention.
- FIG. 81A and FIG. 81B are a plan view and a cross-sectional view of a microstrip antenna according to a twenty-fifth embodiment of the present invention.
- FIG. 82 is a plan view of a modification of the 25th embodiment.
- FIG. 1 is a plan view of a microstrip antenna according to an embodiment of the present invention.
- 2 is a cross-sectional view taken along the line AA in FIG.
- three antenna elements 104, 102, 106 which are all rectangular conductive thin films, are formed on the front surface of a flat substrate 100 made of an electrically insulating material (for example, insulating synthetic resin). Are arranged side by side on a straight line.
- the central antenna element 102 is a feeding element that receives microwave power from a microwave signal source directly (that is, through a wire).
- the two antenna elements 104 and 106 on both sides of the feeding element 102 are parasitic elements that do not receive direct feeding.
- the excitation direction of the feed element 102 is the vertical direction in the figure, and the arrangement direction of the three antenna elements 104, 102, 106 is a direction orthogonal to the excitation direction.
- the left and right parasitic elements 104 and 106 are arranged at the position of the line object with respect to the central feeding element 102, that is, at the same distance from the feeding element 102, and have the same dimensions. It is.
- the dimensions of parasitic elements 104 and 106 can be almost the same as those of feeder element 102, but they can be different (the length in the excitation direction has an optimum value depending on the wavelength of the microwave used). Therefore, the range that can be arranged is narrow, but the width in the direction perpendicular to the excitation direction can be arranged in a wider range).
- the feed line 108 is in contact with a predetermined location on the back of the feed element 102 (hereinafter referred to as a feed point). It has been continued. As shown in FIG. 2, the feed line 108 is a conductive line that penetrates the substrate 100 (hereinafter, such a conductive line is referred to as a “through hole”), and the other end of the feed line 108 is on the back surface of the substrate 100. Is connected to the microwave output terminal of the microwave signal source 114, which is a one-chip IC disposed in the circuit. The feed element 102 is excited by receiving microwave power of a specific frequency (for example, 10.525 GHz, 24.15 GHz, or 76 GHz) output from the microwave signal source 114 at the feed point.
- a specific frequency for example, 10.525 GHz, 24.15 GHz, or 76 GHz
- the substrate 100 is a multilayer substrate, and a thin-film ground electrode 116 is formed as a single layer within the entire plane area of the substrate 100.
- the ground electrode 116 is connected to the ground terminal of the high-frequency signal source 114 through a ground line 115 which is a through hole.
- each of control lines 110 and 112 which are through-holes, is also connected to a predetermined location on the back of each of parasitic elements 104 and 106 (hereinafter referred to as a grounding point).
- the other ends of the control lines 110 and 112 are respectively connected to one side terminals of the switches 120 and 124 that are one-chip ICs arranged on the back surface of the substrate 100.
- the other terminals of the switches 120 and 124 are connected to the ground electrode 116 via ground lines 118 and 122 which are through holes. Switches 120 and 124 can be individually turned on and off.
- the left switch 120 By turning the left switch 120 on and off, the force with which the parasitic element 104 on the left side is connected to the ground electrode 116 and whether it is in a floating state are switched.
- the on / off operation of the right switch 124 switches the force with which the right parasitic element 106 is connected to the ground electrode 116 and whether it is in the float state.
- switches 120 and 124 it is preferable that a high-frequency switch is used. Use microwaves The impedance to the frequency needs to be strictly adjusted to a predetermined appropriate value. It is sufficient if (isolation) is good.
- the position of the feeding point of the feeding element 102 depends on the wavelength g of the microwave used on the substrate 100 in the excitation direction (vertical direction) of the feeding element 102.
- the position is away from the lower edge (or upper edge) of the feed element 102 by the optimum antenna length (approximately ⁇ g / 2) to the upper side (or lower side), and is orthogonal to the excitation direction (vertical direction in the figure).
- Direction In the direction left-right direction in the figure).
- the positions of the grounding points of the parasitic elements 104 and 106 are, for example, from the range of the width LZ2 centering on the center of the parasitic elements 104 and 106 in the excitation direction (upward and downward in the figure).
- the outer position is selected as the center position of the parasitic elements 104 and 106 in the orthogonal direction (left and right direction in the figure).
- L is the length of each parasitic element 104, 106 in the excitation direction.
- the microstrip antenna is operated by operating the switches 120 and 124 to switch which of the parasitic elements 104 and 106 is connected (grounded) to the ground electrode 116.
- the radiation direction of the radio wave beam output from the strip antenna switches to multiple directions. Since the radiation direction is determined by the positional relationship between the feed element 102 and the parasitic elements 104 and 106, it is possible to connect the feed element 102 and the microwave signal source 114 via the feed line 108 that is extremely shorter than the wavelength. Therefore, the transmission loss is low and the efficiency is good.
- this microstrip antenna is suitable for downsizing of the substrate size and low cost of manufacturing.
- FIG. 3 shows how the radiation direction of the radio wave beam is changed by the operation of the switches 120 and 124.
- the ellipse schematically indicates the radiated radio wave beam, and the angle indicated on the horizontal axis indicates the angle (radiation angle) of the radiating direction of the radio wave beam with respect to the direction perpendicular to the substrate 100.
- the angle indicated on the horizontal axis indicates the angle (radiation angle) of the radiating direction of the radio wave beam with respect to the direction perpendicular to the substrate 100.
- the radio beam is on the left side (condition Therefore, it is emitted in a slightly tilted direction.
- the radio beam is on the opposite side as shown by another broken line. In other words, it is emitted in the direction tilted to the right (left depending on the conditions).
- FIG. 4 is a diagram showing a waveform of a microwave current flowing through the feed element and the non-feed element, for explaining the principle of changing the radiation direction of the radio wave beam. This principle is commonly applied to other embodiments of the present invention as well as the embodiment shown in FIG.
- the solid curve shows the waveform of the microwave current flowing through the feed element!
- the dashed curve shows the waveform of the microphone mouth wave current flowing through the parasitic element when the parasitic element is in a float shape.
- the tilt angle (radiation angle) varies depending on the phase difference ⁇ .
- the microwave current (dashed line) of the parasitic element is delayed by a phase difference ⁇ from the microwave current (solid line) of the feeder element.
- this delayed phase difference ⁇ is greater than 180 degrees, it is actually advanced by the phase difference obtained by subtracting ⁇ from 360 degrees.
- the feed element is delayed in phase by the phase difference obtained by subtracting ⁇ from 360 degrees. Therefore, the radiation direction of the total radio wave beam is inclined from the direction perpendicular to the substrate toward the feed element that is delayed in phase.
- the above-mentioned slow phase difference ⁇ may further increase and exceed 360 degrees.
- the phase of the parasitic element is delayed by the phase difference obtained by subtracting 360 degrees from the ⁇ force. Therefore, the radiation direction of the radio beam should be tilted toward the parasitic element. become.
- the dotted curve shows the waveform of the microwave current flowing through the parasitic element when the parasitic element is grounded!
- the value of the microwave current flowing through the grounded parasitic element is very small. That is, the parasitic element is grounded
- the parasitic element is roughly set to a state substantially equal to nothing (hereinafter referred to as “invalid”).
- the radio wave beam is only slightly affected by the parasitic element, and there is almost no inclination caused by the above-described phase difference ⁇ . Therefore, by switching whether the parasitic element is floated or grounded, it is possible to switch whether the inclination in the radiation direction due to the above-described phase difference ⁇ occurs or almost disappears.
- phase difference ⁇ of the microwave current between the feeding element and the parasitic element described above is determined by various factors.
- One factor is that the feeding element and the parasitic element as shown in FIG. There is a space length (inter-element space) S between the children.
- FIG. 5 shows an example of the relationship between the inter-element space S and the phase difference ⁇ based on the results of the computer simulation performed by the inventors.
- the example shown in FIG. 5 is the difference between the inter-element space S and the phase difference ⁇ ⁇ (the delay of the parasitic element relative to the feed element; the phase difference) in one specific design example that works well with the embodiment shown in FIG. It illustrates the relationship.
- the inter-element space S force ⁇ g ( ⁇ g is the wavelength on the microwave substrate) is reached.
- the phase difference ⁇ ⁇ (lag phase difference of the parasitic element with respect to the feed element) increases from 180 degrees to 360 degrees. This means that the parasitic element is substantially advanced in phase by 360 ° minus ⁇ compared to the parasitic element.
- the advance phase difference (360— ⁇ 0) decreases from 180 degrees to 0 degrees as the inter-element space S increases.
- the delay phase difference ⁇ of the parasitic element with respect to the feeding element exceeds 360 degrees.
- the phase difference ( ⁇ 360) obtained by subtracting 360 from the ⁇ force is also shown.
- the phase of the parasitic element is delayed from that of the feed element by the phase difference ( ⁇ -360) shown in Fig. 5.
- FIG. 6 shows a phase difference ⁇ ⁇ (lag phase difference of a parasitic element with respect to a feeding element) based on the result of computer simulation performed by the inventors in the same specific design example as in FIG. And the relationship between the radiation angle (tilt angle from the direction perpendicular to the substrate) of the radio wave beam when the parasitic element is in the float state (effective).
- the radiation angle The minus sign means that the radio beam is tilted to the opposite side of the parasitic element with the feeding element as the center.
- the phase difference ⁇ ⁇ (lagging phase difference of the parasitic element relative to the feeding element) increases from 180 degrees to 360 degrees (substantially, the parasitic element relative to the feeding element).
- the phase difference decreases by 180 degrees and the force decreases to 0 degrees), and the radiation angle is approximately 30 degrees within the range where the radiation angle is negative (the radio beam tilts to the opposite side of the parasitic element). It turns out that it changes to a degree.
- the phase difference ⁇ exceeds 360 degrees (shown in Fig. 6 within a range of less than 180 degrees)
- the radiation angle becomes positive, that is, the radio beam is directed to the parasitic element side. Tilt.
- the radio wave beam tilts toward the parasitic element side or the opposite side, and the radiation angle changes.
- the inter-element space S is in the range of 0 to 2 ⁇ g
- the radio beam tilts to the opposite side of the parasitic element
- the inter-element space S exceeds 2 ⁇ g, it tilts toward the parasitic element.
- Effective change of parasitic element The amount of change in the radiation angle due to switching of Z-invalidation (that is, the radiation angle when the parasitic element is effective) is also the ground point (position of the through hole) in the parasitic element. It depends on the situation.
- FIG. 7 shows the position of the ground point on the parasitic element and the radiation angle when the parasitic element is effective (in the direction perpendicular to the substrate) in the same specific design example as in FIGS.
- the inclination angle from the angle is shown as an example.
- the position of the ground point shown in Fig. 7 means the position in the excitation direction (the direction of the length L shown in Fig. 1). It is expressed as a multiple of the length L in the excitation direction of the parasitic element shown in Fig. 1. ) Every position shown in Fig. 7 is at the center of the parasitic element in the direction perpendicular to the excitation direction.
- L is a multiple of the length L in the excitation direction of the parasitic element shown in FIG.
- the position force of the ground point is less than the central force of the parasitic element of 0.25L (Fig. 1 ).
- the emission angle may be at the maximum value.
- the position of the grounding point is greater than the central force of 0.25L (outside the range of LZ2 shown in Fig. 1), the radiation angle stabilizes at a constant value. Therefore, placing the ground point within this stable range facilitates antenna design.
- the examples shown in FIGS. 5 and 6 described above are cases where the contact points are arranged in the above stable range.
- Fig. 8 shows the relationship of the radiation angle when the ground point is moved in the direction perpendicular to the excitation direction with respect to the center of the parasitic element when the position of the ground point is larger than 0.25L from the center.
- a grounding point is provided in the range of ⁇ 0.1 W, and the upper end (solid line graph in the figure) or lower end A similar radiation state can be obtained even if a grounding point is placed on any of the (broken line graph).
- FIG. 9 is a plan view of a microstrip antenna that works according to the second embodiment of the present invention.
- elements having substantially the same functions as those of the above-described embodiment are denoted by the same reference numerals, and redundant description will be omitted below.
- parasitic elements 130 and 132 are disposed on the upper side and the lower side of the feeding element 102 in the drawing, respectively. That is, these three antenna elements 130, 102, 132 are arranged in a straight line in the excitation direction of the feed element 102 (vertical direction in the figure).
- the grounding point of the parasitic elements 1 30 and 132 is also located outside the 0.25L central force in the excitation direction of the parasitic elements 130 and 132, and the control lines 134 and 136, which are through holes, are connected to it.
- a microwave signal source that feeds the feeding element 102 and a switch that switches whether the parasitic elements 130 and 132 are grounded are provided on the back surface of the substrate 100. .
- the feed point (feed line 108) of the feed element 102 is in a position biased toward the lower edge of the feed element 102.
- the dimension of the parasitic element 130 that has a farther feeding point force that is, the upper side
- the width Wc in the direction perpendicular to the excitation direction is close to the feeding point.
- the dimensions of the parasitic element 136 (in particular, the lower side) It is larger than the width Wd) in the intersecting direction.
- the inter-element space Sc for the former feeding element 102 is shorter than that of the latter Sd.
- the element widths Wc and Wd are adjusted so that the current amplitudes of the parasitic elements 130 and 132 are the same.
- the inter-element spaces Sc and Sd are adjusted so that the current phases of the parasitic elements 130 and 132 are the same. Such adjustment balances the effects of the non-powered elements 130 and 132 on the radio beam. If the inter-element spaces Sc and Sd are set larger than about 1.5 times the element length, the parasitic elements 130 and 132 are the same size and the inter-element spaces Sc and Sd are also Even if they are the same, the parasitic elements 130 and 132 can be balanced (however, the change width of the radiation direction of the radio wave beam is so small as about 10 degrees or less, for example).
- the radiation direction of the radio wave beam having the power of the microstrip antenna can be switched to a direction perpendicular to the substrate 100, a direction inclined upward by a predetermined angle, and a direction inclined downward by a predetermined angle.
- FIG. 10 is a plan view of a microstrip antenna that works according to the third embodiment of the present invention.
- parasitic elements 140 and 142 are added to the outer left and right ends in addition to the same configuration as shown in FIG. Control lines 144 and 146, which are through holes, are also connected to the external non-powered elements 140 and 142, respectively. Then, by operating the switch on the back surface of the substrate (not shown), it is possible to switch between the external parasitic elements 140 and 142 to be in a floating state or to be grounded.
- symbols SW1, SW2, SW3, and SW4 shown in the vicinity of each parasitic element are names of switches for switching effective Z invalidity of each parasitic element (see FIG. 11 below).
- FIG. 11 shows a state in which the radiation angle of the electric wave beam is changed by the switch operation in the microstrip antenna shown in FIG.
- the radiation angle of the radio wave beam can be changed with a large change width. It is possible to switch to the right Z left. Also on the outside (ie far from the feed element 102) By switching the effective Z ineffective of each of the parasitic elements 140 and 142, the radiation angle of the radio wave beam can be switched to the right Z to the left with a small change width.
- a plurality of parasitic elements are arranged in a straight line on each of the right and left sides of the feeding element, so that the radiation direction of the radio wave beam is set to be perpendicular to the substrate. It can be changed in multiple steps on the right and left sides of the direction.
- FIG. 12 is a plan view showing a modification of the above-described third embodiment.
- parasitic elements 140 and 142 are added to the outside of the configuration shown in FIG. That is, three parasitic elements are arranged in a straight line on each of the right side and the left side of the feeding element 102.
- Each of these six parasitic elements 104, 106, 140, 142, 150, and 152 is the same as that of each parasitic element in the embodiment described above for switching the effective Z invalidity.
- the positions of the through holes 108, 110, 112, 144, 146, 154, and 156 are staggered to facilitate the arrangement of the microwave signal source and the switch on the back of the substrate.
- the inter-element spaces Se, S f, and Sg between the parasitic elements 106, 142, and 153 on the right side and the feeder element 102 are changed by switching the effective Z and invalid of the parasitic elements 106, 142, and 153, respectively.
- the change width of the radiation direction of the radio wave to be converted is adjusted to have different desired values (for example, 30 degrees, 20 degrees, and 10 degrees).
- FIG. 13 is a plan view of a microstrip antenna that works according to the fourth embodiment of the present invention.
- the parasitic elements are provided on the left and right sides of the feed element 102 (that is, on both sides of the feed element 102 in the direction orthogonal to the excitation direction of the feed element 102), as in the configuration shown in FIG. 104 and 106 are arranged, and in the same manner as the configuration shown in FIG. 9, the parasitic elements are also provided above and below the feeder element 102 (that is, on both sides of the feeder element 102 in the direction along the excitation direction of the feeder element 102). 130 and 132 are arranged.
- the switch configuration for switching the effective Z / invalid of the parasitic elements 104, 106, 130, 132 is the same as in the above-described embodiment It is.
- symbols SW1, SW2, SW3, and SW4 shown in the vicinity of each parasitic element are names of switches for switching the effective Z invalidity of each parasitic element (see FIG. 14 below).
- FIG. 14 shows how the radiation direction of the radio wave beam is changed by the switch operation in the microstrip antenna shown in FIG.
- the vertical axis represents the vertical gradient
- the horizontal axis represents the horizontal gradient.
- the radiation direction of the radio wave beam can be tilted up, down, left, and right. I can do it. Further, since the parasitic elements 104, 106, 130, and 132 are excited by the feeding element 102 and excited in the same direction, one of the left and right parasitic elements 104 and 106 and the upper and lower parasitic elements 130, 132 are one. By selecting and enabling, the radiation direction of the radio wave beam can be tilted in the direction of about 45 degrees in plan view.
- the radiation direction of the radio wave beam can be changed at intervals of about 45 degrees. Also, by adjusting the shape and position of the parasitic elements 104 and 106 and the parasitic elements 130 and 132, the radiation direction of the radio wave beam can be tilted in the direction of 1 to 89 degrees in plan view. .
- FIG. 15 shows a modification of the fourth embodiment shown in FIG.
- the inter-element space Sh between the left and right parasitic elements 104 and 106 and the feeding element 102 and the upper and lower parasitic elements 130 and 132 and the feeding element 102 are separated.
- the inter-element space Si is different.
- the phase difference of the left and right parasitic elements 104 and 106 with respect to the feeder element 102 and the upper and lower parasitic elements 130 and 132 Accordingly, the radiation direction of the radio wave beam can be tilted in an arbitrary oblique direction in plan view.
- the ground point 136 of the lower parasitic element 132 is disposed near the terminal edge on the upper side of the parasitic element 132 (the side closer to the feeder element 102).
- the ground point 136 of the lower parasitic element 132 is arranged near the lower end of the parasitic element 132 (the side far from the feeding element 102). This is arranged on the back side of the ground point 136 of the high-frequency oscillation circuit (power supply circuit) arranged on the back side of the feeding point 108 of the feeding element 102 and the parasitic element 132 on the lower side. This is because the oscillation circuit and the switch can be arranged without interfering with each other by keeping a sufficient distance from the placed switch.
- the ground strip 136 of the lower parasitic element 132 is connected to the vicinity of the upper termination edge in the microstrip antenna of FIG. 15 as well as the microstrip antenna of FIG. You may arrange in.
- the inventors examined the characteristics of the microstrip antenna shown in FIG. 15 by experiments. As a result, it was found that the inter-element spaces Si and Sh should both be ⁇ ⁇ 2 or less in order to tilt the radiation direction of the radio wave beam at the resonance frequency.
- ⁇ is the wavelength in the air of the resonance frequency radio wave. According to the result of the computer simulation already described with reference to Fig. 5, even if the inter-element spaces Si and Sh are larger than ⁇ ⁇ 2, the radiation direction of the radio wave beam is expected to be tilted. However, according to this experiment, when the inter-element spaces Si and Sh are larger than ⁇ 2, the radio beam hardly tilts at the resonance frequency, and it is possible to tilt at a frequency higher than the resonance frequency.
- the inter-element space Si in the vertical direction is about ⁇ ⁇ 4 ⁇
- the left-to-right (direction perpendicular to the excitation direction) inter-element space Sh is about ⁇ While it is desirable to be within the range of ⁇ 4 to about ⁇ 9, it is particularly desirable to be within the range of about ⁇ 5 to about ⁇ / 9.
- the microstrip antenna having the structure shown in FIG.
- FIG. 16 shows another modification of the fourth embodiment shown in FIG.
- parasitic elements 160, 162, 164, 166 are also arranged in the direction of 45 degrees oblique to the feed element 102. .
- the resolution in the radiation direction of the radio wave beam in plan view is even more powerful than in the fourth embodiment shown in FIG. Also, the gain can be improved.
- FIG. 17 is a plan view of a microstrip antenna that works according to the fifth embodiment of the present invention.
- a plurality of parasitic elements 104, 140, 150, and 170 are linearly arranged on one side (for example, the right side in the figure) of the feeding element 102.
- the configuration for switching the effective Z invalidity of the parasitic elements 104, 140, 150, and 170 is the same as in the other embodiments.
- symbols SW1, SW2, SW3, and SW4 shown in the vicinity of each parasitic element are names of switches for switching the effective Z / invalidity of each parasitic element (refer to FIG. 18 below).
- At least one of these parasitic elements 104, 140, 150, 170 is delayed with respect to the feeding element 102; ⁇ phase difference ⁇ (Figs. (Refer to Fig. 5 and 6), the inter-element space is set at a position of 2 g or more. Have been).
- the other inner parasitic elements 104, 140, 150 are slow relative to the feeder element 102; ⁇ phase difference ⁇ (see Figures 5 and 6) is within the range of 180 degrees to 360 degrees (in effect, leading phase difference) (Ie, based on Figs. 5 and 6, the inter-element space is located at a position less than 2 ⁇ g).
- FIG. 18 shows a change in the radiation angle of the radio wave beam by switching the effective Z invalidity of each parasitic element in the microstrip antenna shown in FIG.
- the radio wave beam is tilted toward the parasitic element 170.
- the radio wave beam is tilted toward the opposite side. In this case, the radiation angle can be changed by selecting which of the parasitic elements 104, 140, and 150 is to be effective.
- FIG. 19A is a plan view of a microstrip antenna that works according to the sixth embodiment of the present invention
- FIG. 19B is a cross-sectional view of the microstrip antenna.
- a feeding element 102 and a plurality of parasitic elements 180, 180,... are arranged on a substrate 100.
- the feeding element 102 and the parasitic element Almost all surface area force of substrate 100 including the surface of 180, 180,...
- the configuration of the microwave switch are the same as those of the other embodiments described above.
- the microwave wavelength g on the substrate 100 is larger than when the dielectric layer 190 is not present (the front surface of the antenna is in contact with air). Shorter.
- the antenna element can be miniaturized and the space between the elements can be reduced, and the antenna can be miniaturized. This is particularly advantageous when it is desired to increase the number of parasitic elements in order to improve the resolution of radio wave radiation direction changes.
- the dielectric constant of the dielectric layer 190 is as high as possible.
- the thickness of the dielectric layer 190 is preferably about 0.1 to 0.2 mm, for example, in order to achieve the above-described advantages and not to reduce the power of the radio wave beam excessively.
- FIG. 20 is a plan view of a microstrip antenna that works according to the seventh embodiment of the present invention.
- a plurality of feed elements 102 and 202 are arranged on the same substrate 100.
- the parasitic elements 104 and 202 are arranged at positions separated from the respective feeding elements 102 and 202 by a predetermined inter-element space S.
- Feed elements 102 and 202 are separated by a distance D that does not interfere with each other.
- the non-interference distance D is, for example, at least three times the size of each feed element.
- radio wave beam radiated from the set of the first feed element 102 and the parasitic element 104 and the radio beam emitted from the set of the second feed element 202 and the parasitic element 204 are integrated.
- the total radio wave beam is narrowed more sharply than when there is only one set of feeding element and parasitic element.
- radio wave directionality (antenna Force The maximum radiation intensity (WZSr) in a specific direction with respect to the total output power (W) and gain are improved.
- WZSr radio wave directionality
- the number of sets of the feed element and the parasitic element is two. However, by increasing the number, the directionality and gain can be further improved.
- FIG. 21A shows a plan view of a modification of the seventh embodiment shown in FIG.
- FIG. 21B shows a cross-sectional view of the modification.
- the adjacent feed elements 102 and 202 are covered with the end faces 102A and 202A force dielectric mask 206 facing each other. Due to the action of the dielectric mask 206, the wavelength g of the radio wave radiated from the end faces 102A and 202A is shortened, so that the non-interference distance D for preventing the feeding elements 102 and 202 from interfering with each other is reduced. It can be shortened from the case of FIG. As a result, the entire antenna can be reduced in size, and the total radio wave beam can be narrowed down accordingly, so that the directionality and gain can be improved.
- 22A and 22B show a plan view and a cross-sectional view, respectively, of another modification of the seventh embodiment shown in FIG.
- FIGS. 23A and 23B are a plan view and a cross-sectional view, respectively, of another modification of the seventh embodiment shown in FIG.
- the feed element 102 and the opposing face force dielectric masks 210 and 212 of the feed elements 104 and 106 on both sides adjacent to the feed element 102 are covered.
- the opposing end faces of the inner parasitic elements 104, 106 and the outer parasitic elements 130, 132 are also covered with dielectric masks 214, 216.
- the end faces facing each other of all adjacent antenna elements are covered with the dielectric mask s.
- the thicknesses of the dielectric masks 210, 212, 214, and 216 may differ depending on the location. By adjusting the thickness of the dielectric mask 210, 212, 214, 216, the size of the inter-element space for obtaining a desired phase difference can be adjusted, or a predetermined inter-element space force can be obtained. The phase difference can be adjusted.
- FIG. 24A is a plan view of a microstrip antenna that works on the eighth embodiment of the present invention.
- FIG. 24B is a cross-sectional view of a portion surrounded by a dotted circle in FIG. 24A of the microstrip antenna.
- a plurality of (for example, four) sub antennas 220, 222, 224, and 226 having the same structure as that shown in FIG. Be beaten! Slits (that is, air layers) 230, 232, 234, and 236 are provided in the portion of the substrate 100 corresponding to the boundary between the sub antennas 220, 222, 224, and 226. Therefore, the sub-antennas 220, 222, 224, and 226 are substantially separated by an air layer.
- the radio beams from the plurality of sub-antennas 220, 222, 224, and 226 are integrated to obtain a radio beam that is strongly focused, that is, high!
- a radio beam that is strongly focused that is, high!
- the distance between the sub-antennas 220, 222, 224, and 226 does not matter due to mutual interference between the parasitic elements of different sub-antennas (for example, the parasitic elements 240 and 242 shown in FIG. 24B).
- the distance is chosen so that it is as small as possible. Such a distance is typically a distance of one wavelength or more in the air of the microwave used.
- the mutual interference between the sub-antennas 220, 222, 224, and 226 described above is caused by the propagation of microwaves through the substrate 100 between the antenna elements, and the propagation of microwaves in the air. There is something that happens.
- the slit (air layer) 230, 232, 234, 236 in the substrate 100 makes it difficult for microwaves to be transmitted through the surface and the interior of the substrate 100, and therefore between the sub-antennas 220, 222, 224, 226.
- Mutual interference is suppressed.
- FIG. 25A is a plan view of a microstrip antenna that works on the ninth embodiment of the present invention.
- FIG. 25B is a cross-sectional view of a portion surrounded by a dotted circle in FIG. 25A of the microstrip antenna.
- the microstrip antenna shown in Figs. 24A and 24B has a configuration basically similar to that shown in Fig. 24. This is the boundary between sub antennas 220, 222, 224, and 226.
- a shield body 260 connected to the ground electrode 116 that is not a slit (that is, always maintained at a constant potential (ground potential)) is provided on the portion of the substrate 100 to be formed. Since the electromagnetic field coupling between the end face of the parasitic element located near the boundary between the sub-antennas 220, 222, 224, and 226 toward the shield body 260 and the shield body 260 becomes stronger, the parasitic element The intensity of radiation radiated into the air becomes smaller on the boundary side.
- Fig. 26 is a plan view of a microstrip antenna that works in the tenth embodiment of the present invention.
- each of the parasitic elements 104 and 106 has a plurality of (for example, two) grounding points. As described with reference to FIG. 1, both of the grounding points are arranged outside the range of the width LZ2 in the excitation direction with the center of each of the parasitic elements 104 and 106 as the center.
- the symbols SW1, SW2, SW3, and SW4 attached near the reference numbers of the respective ground points are names of switches for grounding the respective ground points (see Fig. 28).
- FIG. 27 shows a waveform of a microphone mouth wave current flowing through the feed element and the parasitic element in the tenth embodiment shown in FIG.
- the waveform indicated by the alternate long and short dash line corresponds to the case where only one ground point of the parasitic element is grounded, and the waveform indicated by the dotted line grounds both of the two ground points of the parasitic element.
- the waveform indicated by the dotted line grounds both of the two ground points of the parasitic element.
- Force when both two grounding points are grounded than when only one grounding point is grounded The amplitude of the microwave current flowing through the parasitic element becomes smaller, and the parasitic element is more effectively disabled.
- FIG. 28 shows how the radiation direction of the radio wave beam changes in the microstrip antenna shown in FIG.
- FIGS. 29A to 29C show modified examples of the relationship between the size of the feed element and the parasitic element applicable to the microphone strip antenna according to the present invention.
- the feeding element and the parasitic element are substantially the same size.
- the parasitic elements 104 and 106 can be made larger than the feeding element 102 as shown in FIG. 29A, or the parasitic elements 104 and 106 can be made larger than the feeding element 102 as shown in FIG. 29B. Can be reduced.
- the parasitic elements 104 and 106 may be formed in a shape different from that of the feeder element 102 (for example, thinner).
- Fig. 30 shows a modification example regarding the arrangement of the parasitic elements.
- a plurality of parasitic elements 106 and 130 may be arranged asymmetrically with respect to the power supply element 102 in different directions (for example, directions different by 90 degrees such as the upper side and the right side).
- FIG. 31 shows a modification example related to the power feeding element.
- the radio wave radiation state can be changed in the same way.
- the resonance frequency can be adjusted by changing the width of the slit inserted into the feed element. If a slit is inserted into the feed element formed on the substrate with a laser or the like, the relative permittivity and thickness of the substrate, the feed element The resonance frequency related to the manufacturing variation of the shape can be easily manufactured within a predetermined range.
- FIGS. 32A and 32B are a sectional view and a plan view of an eleventh embodiment of the present invention
- FIGS. 33A and B are a sectional view and a plan view of a twelfth embodiment
- FIGS. 33A and B are a thirteenth embodiment. Sectional view and plan view are shown.
- the surface of the substrate 100 on which the feed element 102 is formed is covered with the dielectric layer 300.
- the parasitic elements 104 and 106 are formed on the surface of the dielectric layer 300.
- the dielectric material for the dielectric layer 300 for example, a ceramic material such as alumina or yttria can be used, or a metal oxide containing relatively high dielectric constant Ti (titanium) or a relatively dielectric material. Low rate! Metal oxide containing Si02 (silica) may be used.
- the value of ⁇ r (relative permittivity) of the dielectric layer 300 is, for example, about 10.
- the film thickness of the dielectric layer 300 is a force that can set an appropriate value according to the dielectric material. For example, the thickness when a material having an ⁇ r (relative permittivity) of about 10 is 10 m. Before and after.
- the surface of the feed element 102 is completely covered with the dielectric layer 300.
- a plurality of slits 302 are formed in a portion of the dielectric layer 300 on the surface of the feed element 102.
- the slit 302 penetrates the entire thickness of the dielectric layer 300 and exposes the feed element 102 therebelow, but this is not necessarily the case.
- the groove may be recessed to the middle of the thickness.
- the concave portion 302 and the convex portion 304 are formed in a region of the dielectric layer 300 on the surface of the power feeding element 102. In other words, the thickness of the dielectric layer 300 on the feeding element 102 is changed. In the illustrated example, the concave portion 302 and the convex portion 304 are formed in stripes parallel to the excitation direction 306. Further, in the thirteenth embodiment shown in FIGS. 34A and 34B, the entire surface of the power feeding element 102 is not covered with the dielectric layer 300 but exposed.
- FIGS. 32A and B When compared with the first embodiment shown in FIGS. 1 and 2 (a configuration in which parasitic elements 104 and 106 are arranged directly on the substrate 100), it is shown in FIGS. 32A and B to FIGS. 34A and 34B.
- the phase difference between the feeding element 102 and the parasitic elements 104 and 106 is 180. It gets closer by ° (ie gZ2). Therefore, when only one of the parasitic elements 104 and 106 is switched off, the radiation direction of the radio wave is inclined to a wider angle.
- FIG. 35 is a cross-sectional view of parasitic elements 104 and 106 in the first embodiment shown in FIGS. 1 and 2 and the eleventh to thirteenth embodiments shown in FIGS. 32A and B to 34A and B.
- the simulation calculation result of the distribution of the radio wave intensity is shown.
- the horizontal axis indicates the tilt angle toward the parasitic elements 104 and 106, where the direction perpendicular to the surface of the substrate 100 is 0 °
- the vertical axis indicates the intensity of the component in each angular direction of the radio wave.
- the thick solid line graph shows the radio wave distribution of the first embodiment shown in Figs. 1 and 2
- the thin solid line graph shows that of the eleventh embodiment shown in Figs. 32A and B
- the thick dotted line graph shows 33A and B show that of the twelfth embodiment
- the thin dotted line graph shows that of the thirteenth embodiment shown in FIGS. 34A and 34B.
- the inclination angle at which the intensity of the direction component of the radio wave shown in each graph is maximum corresponds to the inclination angle of the radio wave radiation direction in each embodiment.
- the eleventh to thirteenth embodiment has a larger inclination angle in the radio wave radiation direction than the first embodiment (thick solid line graph).
- the eleventh to thirteenth embodiments in particular, in the thirteenth embodiment (thin dotted line graph) in which the dielectric layer 300 is laminated on the region of the substrate 100 excluding the surface of the feed element 102, the radio wave is maximum. Lean on.
- the inclination angle of the radio wave can be adjusted by adjusting how the thickness is changed. .
- FIGS. 36A and 36B show two modified examples of the relationship between the widths of the feed element and the parasitic element.
- the widths of the parasitic elements 130 and 132 existing in the direction of the excitation direction 310 with respect to the feed element 102 (dimensions in the direction perpendicular to the excitation direction 310) Wc, Wd force It is the same as the width Wa of the element 102.
- the widths Wc and Wd of the parasitic elements 130 and 132 are slightly narrower than the width Wa of the feed element 102.
- FIG. 37 shows simulation calculation results of the distribution of radio wave intensity when only one of the parasitic elements 130 and 132 is disabled in the two modifications shown in FIGS. 36A and 36B.
- the horizontal axis indicates the angle of inclination toward the parasitic elements 130 and 132, with the direction perpendicular to the surface of the substrate 100 being 0 °
- the vertical axis is the intensity of the component in each angular direction of the radio wave.
- the thick solid line and dotted line graphs show the radio wave distribution of the modified example shown in FIG. 36B
- the fine V, solid line and dotted line graphs show the modified example shown in FIG. 36A (solid line graph and dotted line graph).
- the design conditions used in the simulation calculation are as follows: the relative dielectric constant of the substrate 100 is 3.26, the thickness of the substrate 100 is 0.4 mm, the excitation frequency is 11 GHz, and the size of the feed element 102 is 7.3 mm X 7.3 mm (Fig. In 36A, the size of the parasitic element is the same), the distance between the feeding element 102 and the parasitic elements 130 and 132 is 7.3 mm, and the size of the parasitic elements 130 and 132 in FIG. 36B. Is 7.3mm (excitation direction length) X 5. Omm (width).
- Fig. 38 shows the inclination angle (solid line graph) and the radio wave radiation angle when the widths Wc and Wd (horizontal axes) of the parasitic elements 130 and 132 are changed in the modification shown in Fig. 36B.
- the simulation results show how the radiant intensity (dotted line graph) changes.
- the conditions used in the simulation calculation are the same as above, but the widths Wc and Wd of the parasitic elements 130 and 132 are variously changed between 7.3 mm and 4. Omm.
- the widths Wc and Wd of the parasitic elements 130 and 132 are preferably around 5 mm.
- FIG. 39A shows a planar configuration of a microstrip antenna that works according to the fourteenth embodiment of the present invention
- FIG. 39B shows a cross-sectional configuration along the line AA of FIG. 39A.
- FIGS. 39A and 39B are a plan view and a cross-sectional view of a microstrip antenna that works according to the fourteenth embodiment of the present invention.
- the fourteenth embodiment shown in FIGS. 39A and 39B has the following additional configuration in addition to the same configuration as the fourth embodiment shown in FIG.
- another through hole 320 is connected to the feeder element 102, and this through hole 320 is connected to the switch 322 on the back surface of the substrate 110.
- the switch 322 connects or disconnects the through hole 320 from the power feeding element 102 and the ground line 324 connected to the ground electrode 116 in the substrate 100. That is, switch 322 grounds feed element 102 when it is on.
- the location of the grounding point (the point where the through hole 320 is provided) of the feed element 102 is, for example, in the vicinity of the edge farthest from the feed line 108 in the excitation direction 326 of the feed element 102 as illustrated.
- FIG. 40A shows the above-described fourteenth embodiment when the switch 322 is off
- FIG. 40B shows the parasitic element in the active state with the feed element 102 (solid line graph) when the switch 322 is on.
- the waveforms of the current flowing in elements 104, 106, 130, 132 are shown.
- the switch 322 When the switch 322 is on and the feed element 102 is connected to the ground electrode 116 as shown in FIG. 40A, B, the parasitic elements 104, 106, 130, 132 are effective. However, the antenna force radiates the amount of power extremely small.
- the amount of radiated power By switching the switch 322 between on and off while the microwave signal source power continues to be fed to the feed element 102, the amount of radiated power can be changed.
- a method of switching the microwave signal source on and off can also be adopted, but this method has a drawback that the output of the microwave signal source is not stable immediately after switching.
- the method of switching the switch 322 is, for example, an application in which the distance is measured by the time difference between the pulse radio wave output from the transmission antenna and the pulse radio wave that collides with the object to be measured and is received by the reception antenna. Suitable for.
- FIG. 41 is a plan view of a microstrip antenna that can be applied to the fifteenth embodiment of the present invention.
- one or two or more parasitic elements 330 are arranged on one side in the direction orthogonal to the excitation direction 326 of the feeding element 102, and one or more on the other side.
- the parasitic element 340 is arranged.
- the parasitic elements 330 and 340 arranged in the direction orthogonal to the excitation direction 326 have through holes 332 and 342 for invalidating each of the parasitic elements 330 and 340. Contribute to change.
- one or more parasitic elements 350 are arranged on one side in the excitation direction 326 of the power supply element 102, and one or more parasitic elements 360 are arranged on the other side.
- the parasitic elements 330 and 340 arranged in the excitation direction 326 do not have a through hole and are always in a float state, and therefore hardly contribute to changing the radiation direction of the radio wave.
- FIG. 42A shows a case where, in the fifteenth embodiment, the number of one side of the parasitic elements 330 and the other side of the parasitic elements 340 that do not contribute to the change in the radio wave radiation direction is one on each side.
- Figure 42B shows the planar shape of the radiated radio wave when the number of excited parasitic elements 330 and the parasitic elements 340 on the other side is three on each side. Show shape.
- the radio wave shape 372 shown in FIG. 42B is narrowed more narrowly in the excitation direction 326 (that is, the direction in which the parasitic elements 330 and 340 are arranged) than the radio wave shape 370 shown in FIG. 42A.
- the parasitic elements 330 and 340 contribute little to the change in the radio wave radiation direction, but prevent the spread or spread of the radio wave, thereby forming a radio wave beam that is narrower and has better directivity. Contribute.
- FIG. 43A and FIG. 43B show examples of switch structures that can be used to turn on and off the through-holes in the microstrip antennas having various structures described above.
- the switch 406 shown in FIG. 43A and FIG. 43B is based on a micro electro mechanical system (MEMS) technology for opening and closing a connection line between an antenna element (for example, a parasitic element) 402 and a ground electrode 404. It is a switch (hereinafter referred to as a MEMS switch).
- FIG. 43A shows the OFF state of the MEMS switch 406, and
- FIG. 43B shows the ON state.
- MEMS micro electro mechanical system
- the M EMS switch 406 has a movable electrical contact 408 and a fixed electrical contact 410, for example, the fixed electrical contact 410 is connected to the antenna element 402 through the through-hole 412, and the other, for example, the movable electrical contact 408. Are connected to the ground electrode 404 through the through hole 414. It should be noted that the force is not only in the OFF state shown in FIG. 43A, but even in the ON state shown in FIG. 43B, there is a mechanical opening between the fixed electrical contact 410 and the movable electrical contact 408 in the MEMS switch 406. It is a point. That is, in the ON state shown in FIG. 43B, there is a small gap between the two electrical contacts 408 and 410, and in the OFF state shown in FIG. 43A, the gap is further increased. By adopting such a structured MEMS switch 406, it is possible to create a favorable ON state and OFF state in the high frequency band of 1G to several hundred GHz.
- FIGS. 44A and 44B show the nominal OFF and ON states of the electrical contacts 420 and 432 of the conventional MEMS switch, respectively.
- 45A and 45B show the nominal OFF and ON states of the electrical contacts 408 and 410 of the MEMS switch 406 shown in FIGS. 43A and B, respectively.
- the electrical contacts 420 and 422 are separated in the nominal OFF state, and a slight gap G1 is opened between them, so that the nominal ON Contact mechanically in the state.
- the slight gap G1 shown in FIG. 44A is substantially OFF in the low frequency band, but is substantially ON in the high frequency band.
- the electrical contacts 408, 410 are separated by a sufficiently large gap G2 in the nominal OFF state, and in the nominal ON state. , Separated by a small gap G3.
- FIG. 44A and Fig. 44B in the conventional MEMS switch, the electrical contacts 420 and 422 are separated in the nominal OFF state, and a slight gap G1 is opened between them, so that the nominal ON Contact mechanically in the state.
- the slight gap G1 shown in FIG. 44A is substantially OFF in the low frequency band, but is substantially ON in the high frequency band.
- the electrical contacts 408, 410 are separated by a sufficiently large gap G2 in the nominal OFF state, and in the nominal ON state. , Separated by a small
- a sufficiently large gap G2 between the electrical contacts 408 and 410 forms a substantial OFF state even in the high frequency band. Also, as shown in Fig. 45B, there is a slight gap between the electrical contacts 408 and 410. Even with G3, this is a substantially ON state in the high frequency band.
- FIGS. 46A and 46B show a variation of the electrical contact of the switch suitable for an application for controlling the inclination of the radio wave beam.
- FIG. 46A shows the OFF state
- FIG. 46B shows the ON state.
- a thin film 424 of an insulating material such as a silicon oxide film or an insulating material is provided between the electrical contacts 408 and 410.
- the insulating thin film 424 creates a substantially OFF state for high frequencies even if there is only a small gap G4 between the electrical contacts 408 and 410.
- the gap G4 between the electrical contacts 408 and 410 is eliminated, so that a substantial ON state is created for high frequencies even with the insulating thin film 424.
- FIG. 47 is a plan view of a microstrip antenna that is useful for the sixteenth embodiment of the present invention.
- the arrangement of parasitic elements 104, 106, 130, 132 is different from that shown in FIG. That is, in the case shown in FIG. 13, the parasitic element 104, 106, 130, 132 is arranged in parallel and perpendicular to the excitation direction (up and down direction) of the force feeding element 102. 47, the parasitic elements 104, 106, 130, and 132 are arranged obliquely with respect to the feeding element 102 in the direction of excitation, for example, 45 degrees. According to the electrode arrangement shown in Fig. 47, the radio beam is narrowed more narrowly as it travels in the direction of radiation. Incidentally, according to the electrode arrangement shown in Fig.
- the radio wave beam spreads as it travels in the radiation direction. Therefore, the electrode arrangement shown in Fig. 47 is relatively well suited for the purpose of accurately detecting human bodies and objects in a narrow range, whereas the electrode arrangement shown in Fig. 13 is suitable for human bodies and objects in a wide range. It is relatively well suited for detecting applications.
- FIG. 48 is a plan view of a microstrip antenna that is effective in the seventeenth embodiment of the present invention
- FIG. 49 is a cross-sectional view taken along line AA in FIG.
- FIG. 50 shows a plan view of a microstrip antenna according to an eighteenth embodiment of the present invention.
- the third sub-antenna 449 is arranged in a positional relationship as shown in FIG. 47 with respect to the parasitic elements 442, 444, 446, and 448 force feeding elements 440.
- the fourth sub-antenna 459 is also arranged in a positional relationship as shown in FIG. 47 with respect to the parasitic elements 452, 454, 456, and 458 forces S-feed element 450.
- the two sub-antennas 429 and 439 having the electrode arrangement shown in FIG. 13 and the two sub-antennas 449 and 459 having the electrode arrangement shown in FIG. 47 and the force 2 X 2 matrix are arranged at complementary positions. .
- the two sub-antennas 429 and 439 having the electrode arrangement shown in FIG. 13 are arranged at the upper left and lower right positions in FIG. 48, and the two sub-antennas 449 and 459 having the electrode arrangement shown in FIG. Arranged in the upper right and lower left positions. All the feed elements and parasitic elements of these sub-antennas 429, 439, 449, and 459 are placed on the front surface of the substrate 100.
- a power supply line 460 for supplying high-frequency power to the power supply electrodes 420, 430, 440, and 450 is disposed on the back surface of the substrate 100 as shown in FIG. 49, and passes through through holes 460, 460,.
- Reference numeral 470 in FIG. 49 indicates an earth electrode at a ground potential, to which each of the above-mentioned parasitic elements is connected via a through hole and a switch (not shown).
- the main beam of radio waves can be narrowed down effectively by a simple structure in which a plurality of sub-antennas each having a feed element are arranged on the same substrate.
- the shape of the main beam of radio waves is affected by the distance between the feed elements.
- the spacing between the feed elements is If it becomes too wide, the main beam will be narrowed down. Unnecessary side lobes will be generated.
- the distance between the feeding elements is about ⁇ 2 to 2 ⁇ 3.
- ⁇ represents the wavelength of radio waves in the air.
- all sub-antennas 480, 482, 484, 486 forces ⁇ same as the micro-trip antenna shown in Fig. 50
- the spacing between parasitic elements of adjacent sub-antennas becomes too small, and interference may occur between these parasitic elements.
- interference occurs between parasitic elements 424 and 452, between parasitic elements 444 and 432, between parasitic elements 428 and 446, and between parasitic elements 458 and 436. There is a risk.
- the sub-antennas 429, 439, 449, and 459 having different electrode arrangements are arranged in a complementary manner, so even if the spacing between the feeding elements is as small as described above, Since the distance between the parasitic elements of the matching sub-antennas is large to some extent, the interference between the parasitic elements is small.
- FIG. 51 is a plan view of a microstrip antenna that is effective in the nineteenth embodiment of the present invention.
- FIG. 52 is a cross-sectional view taken along the line ⁇ in FIG.
- the microstrip antenna shown in FIGS. 51 and 52 has the same configuration as the microstrip antenna shown in FIG. 15, and more than one of each of the parasitic elements 104, 106, 130, and 132.
- the regular grounding points 502, 504, 506, 508 (2 in the example shown) are added.
- 502, 504, 506, 50 8 shows the excitation direction 500 of each parasitic element 104, 106, 130, 132 when each parasitic element 104, 106, 130, 132 is floated (that is, not connected to the ground electrode 514).
- High frequency power is supplied to the feeding point 108
- Reference numerals 522 and 524 denote switches for connecting and disconnecting the grounding points 110 and 112 for controlling the radiation direction of the parasitic elements 104 and 106 and the earth electrode 514.
- the parasitic elements 104, 106, 130, and 132 are still excited by simply changing the excitation direction of the elements 104, 106, 130, and 132 in the direction orthogonal to the original excitation direction 500. is there.
- the amplitude of the high-frequency current (voltage) of each parasitic element 104, 106, 130, 132 does not decrease, there is a problem that the radiation direction of the radio wave does not tilt.
- the constant grounding points 502, 504, 506, and 508 arranged at the positions above the parasitic elements 104, 106, 130, and 132 are excited in the direction orthogonal to the original excitation direction 500 described above. It acts to suppress.
- FIG. 53 shows a modification of the feed element that can be employed in the microstrip antenna according to the present invention.
- the feeding element 530 As shown in Fig. 53, two orthogonal outer edges of the feeding element 530 (a square or rectangular metal thin film formed on the substrate (background in the figure)), for example, the lower and right outer edges in the figure, There are two feeding points 532A and 532B in the vicinity of the center of each of the feeding points 532A and 532B, and feeding lines 534A and 534B are connected to the feeding points 532A and 532B, respectively.
- the feeder lines 534A and 534B are In the example shown, the microstrip line is formed on the same side of the board as the feeding element 530, but instead, it is formed on the opposite side of the board and is connected to the feeding points 532A and 532B through the through hole.
- Feed lines 534A and 534B apply high-frequency power having the same or different frequencies to feed points 532A and 532B.
- the lateral length of the feed element 530 is a length suitable for excitation at a high frequency applied to the right feed point 532A, that is, about the wavelength gA on the substrate of the radio wave of that frequency. It is chosen as 1Z2.
- the length of the feed element 530 in the vertical direction is a length suitable for excitation at a high frequency applied to the lower feed point 532B, that is, on the substrate of radio waves of that frequency.
- the wavelength is chosen to be about 1Z2 in gB.
- the feeding to the right feeding point 532A excites the feeding element 530 in the horizontal direction 538A in the figure, while the feeding to the lower feeding point 532B causes the feeding element 530 to run in the vertical direction in the figure. 53 Excited to 8B.
- grounding points 536A and 536B are provided, and through-holes (not shown) penetrating the substrate are connected to the grounding points 536A and 536B, respectively.
- the grounding points 536A and 536B are connected to the respective through-holes by turning on / off a switch (not shown) and a ground potential ground electrode (not shown) (for example, a board) Can be connected at any time.
- the excitation by the feed point on the opposite side of the one grounding point will be substantially invalidated, and only the other excitation will occur. validate. For example, when the upper grounding point 536B in the figure is connected to the ground electrode, the excitation in the vertical direction 538B by the lower feeding point 532B is substantially disabled, and the lateral 538A excitation by the right feeding point 532A. Only valid. Therefore, the radio wave 22A having a vibration waveform with electromagnetic field strength in the same lateral direction as the excitation direction 538A is emitted from the antenna.
- the excitation of lateral direction 538A by the right feed point 532A is substantially disabled, and the vertical direction of 538B by the lower feed point 532B. Only excitation is effective. Therefore, the electromagnetic field is in the same vertical direction as the excitation direction 538B.
- the radio wave 22B having a strong vibration waveform is also emitted by the antenna force.
- the frequency of the radiated radio wave can be switched by selectively connecting the grounding points 536A and 536B to the ground electrode by the switch operation.
- the feeding element 530 is provided with a plurality of feeding points 532A and 5 32B that excite the feeding element 530 in different directions and ground points 536A and 536B that invalidate the feeding points 532A and 536B.
- radio waves with different vibration waveform directions can be selectively emitted. This method is effective for vertically polarized antennas.
- FIG. 54 shows one suitable application for the microstrip antenna according to the present invention having the feed element shown in FIG.
- the application shown in FIG. 54 is an object sensor 544 for detecting the movement of an object 548 such as a person using the Doppler effect of radio waves.
- the object sensor 544 is attached to, for example, a ceiling surface or a wall surface 542 of a room, and includes a microstrip antenna (not shown) according to the present invention and a Doppler signal processing circuit (not shown) connected to the microstrip antenna.
- a microstrip antenna is used as a transmitting antenna for emitting radio waves.
- a microstrip antenna that is a transmission antenna may be used as a reception antenna, or a reception antenna may be provided separately from the transmission antenna.
- the microstrip antenna has the configuration as in any of the above-described embodiments, and can emit radio waves in different directions 34A, 34B, and 34C. Furthermore, the feed element of the microstrip antenna has a configuration as shown in FIG. 53, and by changing the excitation direction, the microstrip antenna force also changes the direction of the vibration waveform of the emitted radio wave. Become! /
- FIG. 55 and FIG. 56 show the difference in detection characteristics caused by changing the excitation direction of the microstrip antenna of the object sensor 544.
- the direction of the vibration waveform of the radio wave 550 is no matter which direction the emission direction of the radio wave 550 is. Is the horizontal direction.
- the detection sensitivity of the object sensor 544 is 5 Best for movement of object 548 in the same lateral direction as 50 vibration waveform directions.
- the direction of the vibration waveform of the electromagnetic field of the radio wave 550 is the vertical direction regardless of the emission direction. In this case, the detection sensitivity of the object sensor 544 is the best for the movement of the object 548 in the vertical direction.
- the excitation direction it is possible to change the direction component of the movement of the object with good detection sensitivity. Therefore, by using these different excitation directions in combination, for example, switching at high speed alternately, the level of the Doppler signal detected in the different excitation directions is compared to estimate the moving direction of the object 548, or It is possible to logically combine the determination results of whether or not an object is detected in different excitation directions so that it can be detected with high sensitivity regardless of which direction the object 548 moves.
- FIG. 57 is a plan view of a microstrip antenna that is useful for the twentieth embodiment of the present invention.
- FIGS. 58 and 59 each show a modification of the twentieth embodiment shown in FIG.
- a plurality of feeding elements for example, two
- a plurality of parasitic elements 562, 564, 566, 572, 574, and 576 forces S so as to surround those feeding elements 560 and 570 two-dimensionally (for example, from the vertical and horizontal directions in the figure).
- This microstrip antenna has a structure similar to an antenna array in which a single feeding element shown in FIG. 13 and a plurality of antennas having a plurality of parasitic elements that surround it two-dimensionally are arranged.
- the radio wave beam is narrower than the antenna shown in Fig.
- the reach of the aperture radio wave beam can be extended longer (when applied to an object sensor using radio wave beams, the object detection range is narrower and the aperture detection distance is Can be stretched long).
- control the state of one or more elements placed at biased positions in the parasitic elements 562, 564, 566, 572, 574, 576 to the ground force float. can do.
- the state of the group of parasitic elements arranged symmetrically for example, the group of the parasitic elements 562, 564, 566 on the right side and the group of the parasitic elements 572, 574, 576 on the left side, respectively.
- the direction of the radio wave beam can be effectively changed from side to side.
- the modification shown in Fig. 58 is an antenna array in which two antennas having the structure shown in Fig. 13 are simply arranged.
- this modification there are parasitic elements 568 and 578 between the feeding elements 560 and 570, and therefore the distance between the feeding elements 560 and 570 must be long. Unnecessary side lobes may occur due to the long distance between power supply elements 560 and 570.
- the feeding elements 560 and 570 are arranged adjacent to each other, so that it is easy to prevent the occurrence of side lobes by appropriately shortening the distance between them.
- the parasitic elements 564 and 574 sandwich the feeding elements 560 and 570 from both sides in a one-dimensional manner rather than two-dimensionally (for example, in the lateral direction).
- the parasitic power 564, 574 force is the power of the emitted radio wave, which is considerably smaller than the radio power of the feed element 560, 570, and can be obtained by controlling the state of the parasitic elements 564, 574.
- the direction change amount of the radio wave beam may be too small.
- FIG. 60 shows another modification of the microstrip antenna shown in FIG.
- ground points 580 and 582 are provided at predetermined positions (for example, the center of each element) of feeding elements 560 and 570.
- the grounding points 580 and 582 of each feed element 560 and 570 are connected to the ground electrode via a through hole and a switch (not shown) in the same manner as the contact points of each parasitic element 562, 564, 566, 572, 574 and 576. They are connected or disconnected from the ground electrode force.
- the feeding elements 560 and 570 When one of the feeding elements 560 and 570 is grounded at the grounding point, a phase difference of a high-frequency current is generated between the feeding elements 560 and 570, and the parasitic elements 562, 564, 566, 572, 574, 576 are caused by the influence. There is also a phase difference in the high-frequency current between them, and as a result, the direction of the radio wave beam changes. In many cases, the radio beam is tilted in the opposite direction to the grounded feed electrode. For example, when the right feeding electrode 580 is grounded, the radio beam is tilted to the left.
- the control of the grounding state of the feeding elements 560, 570 is avoided. Can be changed more or less vigorously. For example, if you want to tilt the radio beam to the left at a large angle, The pole 580 can be grounded and the left parasitic elements 572, 574, 576 can be grounded. Alternatively, when it is desired to tilt the radio beam to the left side at a slightly smaller angle than the previous example, the right power supply electrode 580 can be grounded, and the right parasitic elements 562, 564, 566 can be grounded.
- FIG. 61 shows still another modification of the microstrip antenna shown in FIG.
- the antenna shown in Fig. 61 has more parasitic elements 562, 5 64, 566, 572, 574, 576, 590, 592, 594, 596 force feeding elements 560, 570 than the antenna shown in Fig. 60. Besieged. As a result, it can be expected that the direction of the radio wave beam can be controlled more vigorously by narrowing the radio wave beam more narrowly and extending the reach of the radio wave beam.
- a parasitic element having a grounding point is required for impedance matching of the feeding part of the antenna by adjusting the position of the feeding point. It is preferable to perform this work with all of the grounded. Then, compared with the case where this operation is performed with all the parasitic elements kept in the flow state, the deviation in matching that occurs when the parasitic element state is switched to the ground Z float is reduced. Can do.
- FIG. 62 shows a cross-sectional view of a microstrip antenna that works according to the twenty-first embodiment of the present invention.
- a convex lens type dielectric lens 602 is disposed in front of the antenna body 600 having the structure shown in FIG. 13 (that is, in the direction in which the radio beam is emitted from the set of the feed element and the parasitic element)
- the dielectric lens 602 is integrally formed with a dielectric casing 604.
- the antenna body 600, the analog circuit unit 606 including an oscillation circuit, a detection circuit, etc., and the switch control circuit detection circuit that is, receiving the detection result when applied to an object detection device
- a digital circuit unit 608 including a circuit for determining the presence or absence of an object) is accommodated.
- the material of the dielectric lens 602 is preferably formed of a material having a relatively low relative dielectric constant, such as polyethylene, nylon, polypropylene, or a fluorine-based resin material.
- a material having a relatively low relative dielectric constant such as polyethylene, nylon, polypropylene, or a fluorine-based resin material.
- nylon or polypropylene is preferred, and when heat resistance and water resistance are also desired, such as PPS (Polyphenylene Sulfide) is preferred.
- a relatively high dielectric constant is used, and a ceramic material such as alumina or zirconium is used for the lens body, and in order to suppress reflection in the lens.
- the surface of the lens may be covered with a material having a relatively low relative dielectric constant as described above.
- the radio wave beam is narrowed by the action of the dielectric lens 602, and the gain is increased.
- the focal length of the dielectric lens 602 can be selected according to the distance range to be detected. For example, if the object detection device is installed on the ceiling of the room and you want to detect objects and people in the room, the detection distance range will be within 2.5m to 3m, so the focal length of the dielectric lens 602 is the detection distance. The maximum length of the range can be set between 2.5m and 3m.
- a method of arraying a plurality of antennas can be employed instead of or in combination with the method using the dielectric lens described above. According to this method, there is another advantage that the radiation angle of radio waves can be switched in multiple stages.
- a dielectric lens may be used in combination.
- FIG. 63 shows a cross-sectional view of a microstrip antenna that works according to the twenty-second embodiment of the present invention.
- the antenna shown in FIG. 63 has a planar structure as shown in FIG. 13, for example, and a semiconductor switch or a MEMS switch is used as the switch 616 for grounding each parasitic element 610. .
- the line for releasing the high frequency on each parasitic element 610 to the ground electrode 614 is a force including the through-hole 612 and the current path inside the switch 616. This line is thin and the length of the line when the switch 616 is turned on. Depending on T, the impedance of the line to high frequency differs. Therefore, even when the switch 614 is in the on state, a high-frequency current having a magnitude corresponding to the length of the line flows through the parasitic element 610.
- FIG. 64 shows the relationship between the line length T and the amount of current I flowing through the parasitic element 610 when the switch 614 is on!
- the line length T may be an integral multiple of one half of the wavelength g on a high frequency substrate. That is, if the line length T is m times gZ2 (m is an integer of 1 or more), impedance matching is achieved and high-frequency reflection to the parasitic element 610 is minimized.
- the line length T when the line length T is different from n times gZ2, the high frequency is reflected and flows to the parasitic element 610. Therefore, when a semiconductor switch or a MEMS switch is used as the switch 616, the line length T from each parasitic element 610 to the ground electrode 614 can be set to ⁇ gZ2 X n (n is an integer of 1 or more). desirable.
- n is an integer of 1 or more.
- FIG. 65 shows the back surface of the modified example of the 22nd embodiment shown in FIG. 63 (the surface opposite to the surface on which the parasitic element 610 exists, that is, the surface on which the electrode switch 616 is disposed).
- the plan view (extracted only for the part corresponding to one passive element 610) is shown.
- the SPDT type Single Pole
- the ground electrode 614 is used as a switch 616 for switching whether or not each parasitic element 610 is connected to the ground electrode 614.
- the end of the through hole 612 from each parasitic element 610 is connected to the end of the backside of the through-hole 612 in an elongated shape! /, And one end of the relay line 628 is connected to the relay line 628 at two locations where the line length from the parasitic element 610 is different.
- two selection terminals 622 and 624 of the switch 616 are connected to each other, and one common terminal 626 of the switch 616 is connected to the ground electrode 614.
- the line length T through the through hole 612 and the switch 616 from the parasitic element 610 to the ground electrode 614 is a predetermined integer multiple of gZ2, for example, 2 times, that is, ⁇ g.
- the selection terminal 622 is turned on, the line length T is not a predetermined integer multiple of ⁇ g / 2, so that the length of the line T is shorter than ⁇ g / 2 and shorter than 3 g / 4!
- the position of the selection terminals 622, 624 on the trunk line 628 is selected!
- FIG. 66 shows changes in line length and changes in the current flowing through the parasitic element in the antenna shown in FIG.
- FIG. 67 shows a change in the radiation direction of the radio wave beam obtained by operating switch 616 in the antenna shown in FIG. [0194]
- reference numeral 630 indicates the line length T when one selection terminal 624 of the switch 616 is turned on, which is an integral multiple of gZ2 (eg, g).
- the current flowing through element 610 is zero.
- Reference number 632 indicates the line length T when the other selection terminal 622 is on, which is not an integral multiple of ⁇ gZ2 (eg, shorter than ⁇ g and longer than 3 ⁇ gZ4).
- the current through element 610 is not zero, but is less than when switch 616 is off. Therefore, as shown in Fig. 67, the force to turn off the switch 616. Select either one of the selection terminals 622 or 624 to turn on. Since it can be changed in stages, the antenna can also change the angle of the emitted radio beam into three stages 634, 636, and 638. By using this principle, the line length T can be switched to more different lengths so that the angle of the radio wave beam can be changed more.
- FIG. 68 shows a plan view of a microstrip antenna that works according to the twenty-third embodiment of the present invention.
- FIG. 69 shows a cross-sectional view along the line AA in FIG.
- the antennas shown in FIGS. 68 and 69 have the same structure as the antenna shown in FIG. 13, and in addition to this, two predetermined points (or different from the feeding point 646 of the feeding element 640) (or 648, 648 forces are always connected to the ground electrode 652 through the snorley wheels 649, 649, respectively.
- the positions of these grounding points 648 and 648 are radiated by the antenna force without reducing the power of the fundamental frequency radio wave (fundamental wave) radiated from the antenna and maintaining the radiation angle of the fundamental wave. It is chosen for a special location that can reduce unwanted spurious (especially second and third harmonics).
- Fig. 70 shows an example of a preferable region where the grounding point 648 for reducing spurious as described above should be arranged.
- the feed element 640 is a square, and the dimension of the side is about half the wavelength ⁇ of the fundamental wave. The shape and dimensions of the feed element 640 are different.
- the radiation power of the wave can be reduced more effectively. Therefore, if a contact point is provided at or near the position where the current amplitude value of the n-th harmonic (n is an integer of 2 or more) on the feed element is minimum (that is, the position where the voltage amplitude value is maximum). The radiation power of the nth harmonic is effectively reduced. At the same time, if the contact point is at or near the position where the current amplitude value of the fundamental wave is the maximum (that is, the position where the voltage amplitude value is the minimum), the risk of damaging the radiated power of the fundamental wave is minimized. It is.
- the excitation direction of the fundamental wave is the y direction (vertical direction in the figure), and the current distribution is as shown in the graph on the left side of the figure.
- the excitation direction of the second harmonic is the X direction (lateral direction in the figure), and the current distribution is as shown in the upper graph in the figure.
- the excitation direction of the third harmonic is the y direction (vertical direction in the figure), and the current distribution is as shown on the right side of the figure.
- ⁇ , ⁇ are the fundamental, second, and third harmonic wavelengths on the substrate, respectively g2 g3
- Areas 660 and 660 indicated by (2) and (2) are in the distance range of Z6 or more and ⁇ / 2- ⁇ ⁇ 6 or less from the terminal edge (upper or lower terminal edge) in the excitation direction of the fundamental wave ,There
- the region 660, 660 is Z2 or more from the end edge (left or right end edge) in the excitation direction of the second harmonic,
- the radiation power of the second and third harmonics can be reduced.
- regions 662 and 662 indicated by finer hatching are more preferable regions.
- this region 662, 662 is the terminal edge in the excitation direction of the second harmonic ( From the left or right end edge) over Z2, ⁇ / 2 + ⁇
- the current amplitude value i of the fundamental wave is almost the maximum, and the current amplitude value i of the second and third harmonics is i.
- FIG. 71 shows a cross-sectional view of the microstrip antenna that is effective in the twenty-fourth embodiment of the present invention (only the part corresponding to one parasitic element 610 is extracted).
- the antenna shown in FIG. 71 is common in basic structure with the antenna that works in the twenty-second embodiment shown in FIG.
- the length T of the line from the parasitic element 610 to the ground electrode 614 when the switch 616 is in the ON state is gZ2 Xn (n is an integer of 1 or more). is there.
- the portion of the transmission line connected to the parasitic element 610 when the switch 616 is in the off state, that is, the grounding force of the parasitic element 610 is also on the back surface of the substrate 100.
- Transmission line length U to the end of the line in the switch U (more specifically, through hole 612, relay line 670 from through hole 612 on the back side of substrate 100 to switch 616, and inside switch 616
- the total line length of the transmission line 673) force ⁇ gZ2 ⁇ ⁇ ( ⁇ is an integer greater than or equal to 1) (for example, U gZ2).
- the length of the parasitic element 610 ⁇ Moe ⁇ 2 11 (11 is an integer of 1 or more) becomes (e.g., V Gz2).
- switch 616 is a switch that has a transmission line inside it, such as a semiconductor switch or a mechanical switch (for example, MEMS) and has a negligible loss of contact when it is on, the radio wave emitted from the antenna
- a factor that greatly affects the direction control of the sine wave is a high-frequency characteristic related to the parasitic element 610 when the switch 616 is in the off state, rather than when it is in the on state, such as impedance or phase.
- the transmission line path length U when the switch 616 is in the off state is an integral multiple of the half wavelength ⁇ gZ2 of the high-frequency signal, the impedance Z at the contact point 610A of the parasitic element 610 is close to infinity. That is, it is possible to suppress the phase of the parasitic element 610 from greatly changing due to the connection of the transmission line.
- FIGS. 72A and 72A show the switches 616 in the antenna shown in FIGS. 71 and 63, respectively. This shows the change in impedance Z at the grounding point 610A of the parasitic element 610A by switching on and off, and the direction of the radio wave radiated from the antenna.
- FIG. 72A On the left side of Figs. 72A and 72B, a state when the switch 616 is off is shown.
- Fig. 72A in the antenna of Fig. 71, when the transmission line length U is an integral multiple of the half wavelength ⁇ gZ2 of the high frequency signal, the impedance of the ground point 610A is almost infinite, The direction is perpendicular to the substrate.
- FIG. 72B in the antenna of FIG. 71, when the transmission line length U is not an integral multiple of the half wavelength ⁇ gZ2 of the high-frequency signal, the impedance of the ground point 610A is lower. The direction is inclined at an angle ⁇ 1.
- the length of the middle line 670 connected to the parasitic element 610 via the through hole 612 may be changed. Since the resonance frequency of the antenna is determined by the mutual interference between the feed element and the parasitic element, the through-hole 612, the relay line 670, and the switch 616 are connected to the parasitic element 610 and the through-hole 612 to the parasitic element 610. And the trunk line 670 and the antenna that does not connect the switch 616 are prepared, so that the resonance frequency of the former antenna is the same as the resonance frequency of the latter antenna.
- the transmission line length U can be optimized by adjusting the length.
- FIG. 73 is a plan view of the back side of the antenna (a single parasitic element 610 is shown) showing a method for adjusting the impedance associated with the parasitic element 610, which can be applied to the microstrip antenna according to the present invention. (Only the corresponding part is shown).
- a stub 676 is provided on the relay line 674 between the through hole 612 and the switch 616. If the impedance related to the parasitic element 610 is not appropriate, the impedance can be adjusted to the optimum value by cutting the stub 677. . On the contrary, the radiation angle of the radio beam can be easily changed by cutting the stub 677 and changing the optimum value of the impedance related to the parasitic element 610. Alternatively, the impedance may be adjusted to the optimum value by forming a dielectric film or layer on the relay line 674 and adjusting the dielectric constant, film thickness, or area of the dielectric film. Can do. Alternatively, the impedance can be adjusted to an optimum value by cutting the middle I line 674 itself and changing its length or thickness.
- FIG. 74 shows a cross-sectional view of a microstrip antenna that works according to the twenty-fourth embodiment of the present invention.
- FIG. 75 shows an exploded view of the microstrip antenna.
- the microstrip antenna shown in FIGS. 74 and 75 is arranged on the rear side of the antenna body 600 and the dielectric lens 602 placed on the front side of the antenna body 600, similarly to the microstrip antenna shown in FIG. An analog circuit unit 606 and a digital circuit unit 608.
- this microstrip antenna has the following unique structure. That is, as shown in FIGS. 74 and 75, the dielectric lens 602, the antenna body 600, the spacer 680, the digital circuit unit 608, the spacer 682, and the analog circuit unit 606 are arranged in this order (analog circuit unit 606 and The order of the digital circuit unit 608 is the same as that in FIG. 62), and they are fixed together by several screws 684.
- the ground electrode 700 covering almost the entire rear surface of the antenna body 600 and the ground electrode 704 covering almost the entire front surface of the analog circuit unit 606 are opposed to each other.
- the antenna body 600, the spacer 680, the analog circuit unit 606, the spacer 682, and the digital circuit unit 608 each have a substantially flat shape, and thus the antenna has a substantially rectangular parallelepiped shape as a whole.
- a dielectric lens 602 is disposed at the foremost part of the antenna, and an analog circuit unit 606 is disposed at the rearmost part.
- a portion of the screw 684 that protrudes forward from the antenna body 600 is embedded in the base of the dielectric lens 602 and surrounded by the dielectric, and is not exposed on the front surface of the antenna body 600.
- a substantially flat and thin dielectric cover 706 may be used to protect the antenna.
- the dielectric lens 602 and the dielectric cover 706 can be selected according to the application of the antenna (for example, the detection distance is long).
- a high frequency oscillation circuit 685 is provided near the center of the back of the analog circuit unit 606.
- the feed line 686 extends linearly from the high-frequency oscillation circuit 685 to the feed element 687 disposed near the center of the surface of the antenna body 600.
- the feed line 686 passes through the analog circuit unit 606, the spacer 682, the digital circuit unit 608, the spacer 680, and the antenna body 600, and is connected to the feed element on the antenna body 600.
- a coaxial cable may be used for the feed line 686 from the viewpoint of reducing transmission loss.
- the core wire of the coaxial cable is used as the feed line 686, and the coaxial metal tube force surrounding the core wire of the coaxial cable.
- the antenna body 600 covers almost the entire rear surface of the ground electrode 700 and the analog circuit unit 606 almost the entire front surface. Each is connected to a covering earth electrode 704. Box-shaped shield cover 690 force Mounted by several screws 692 on the back of the analog circuit unit 606.
- the shield cover 690 covers the outer periphery of the high-frequency oscillation circuit 685 on the back surface of the analog circuit unit 606.
- the shield cover 690 is provided with a frequency adjusting screw 694. By rotating the frequency adjusting screw 694, the circuit constant of the high-frequency oscillation circuit 685 changes (for example, the gap distance between the high-frequency oscillation circuit 685 and the shield cover 690 changes, and the capacitance of the resonance circuit changes). The oscillation frequency of the high-frequency oscillation circuit 685 is adjusted.
- Each of the spacers 680 and 682 has a force made of a conductor such as metal, or an outer surface thereof covered with a conductor film. As shown in FIG. 75, one spacer 680 is in contact with the ground electrode 702 that covers almost the entire rear surface of the antenna body 600 and the ground electrode 702 that covers almost the entire front surface of the digital circuit unit 608. , Held at ground level. The other spacer 682 is in contact with the ground electrode 703 formed on the outer periphery of the back surface of the digital circuit unit 608 and the ground electrode 702 covering almost the entire front surface of the analog circuit unit 606, and is held at the ground level. Is done. Each of the spacers 680 and 682 has a ring shape as shown in FIG.
- each of the spacers 680 and 682 has a shield tube 683 held at the ground level at the center thereof, and the feeder line 686 in the shield tube 683 is provided.
- the shield tube 683 and the feed line 686 are coaxially arranged.
- the digital circuit unit 608 is equipped with a microcomputer that controls the antenna body 600 and the sensor circuit. Also, the back of the digital circuit unit 608 Several external ports 710 are arranged on the surface.
- the external port 710 includes a signal input / output port for external input / output of various signals such as sensor signals, power supply voltage, and monitor signal, and writing of programs and data to the flash ROM built in the microcomputer described above.
- These external ports 710 protrude rearward from the back surface of the digital circuit unit 608 and penetrate the interior of the spacer 682 and the analog circuit unit 606. Therefore, as illustrated in FIG. 78, the opening force at the upper end of the external port 710 is exposed on the back surface of the analog circuit unit 606 to allow access to the digital circuit unit 608.
- the data write port may be blocked with a synthetic resin or the like in order to make it impossible for the user to rewrite data without permission after the data is written in the manufacturing stage.
- the feeder line 686 may be a short line corresponding to the thickness of the antenna having the compact laminated structure, power loss in the feeder line 686 can be reduced. Further, the oscillation frequency can be changed using the frequency adjusting screw 694.
- the presence of the spacers 680 and 682 made of a conductor that is in close contact with the ground electrodes 700, 702, 703, and 704 between the antenna body 600, the digital circuit unit 608, and the analog circuit unit 606 The ground level of 600 and analog circuit unit 606 can be made the same, ensuring good antenna performance.
- the spacers 680 and 682 having the structure shown in FIG. 77 are employed, the power supply line 686 between the antenna body 600 and the high-frequency oscillation circuit 685 can be maintained at the ground level. Get smaller.
- the antenna body 600, the digital circuit unit 608, and the analog circuit unit 606 are stacked and integrally coupled, so that radio waves radiated from the back surface (ground surface) of the antenna body 600 and high-frequency oscillation circuit 685 can be obtained. Unnecessary harmonics that are radiated are prevented from being radiated to the outside, so that the front-side radio waves of antenna body 600 can be efficiently radiated in a desired direction. it can.
- the screw 684 is embedded in the dielectric lens 602, covered with a dielectric, and is not exposed on the front surface of the antenna body 600! Therefore, the screw 684 has conductivity such as metal or gold plating. Even so, the radio wave radiated from the front surface of the antenna body 600 is prevented from interfering with the screw 684, and the radio wave can be efficiently emitted forward through the dielectric lens 602.
- FIG. 79 shows a cross-sectional view of a modification of the microstrip antenna shown in FIGS. 74 and 75.
- the antenna shown in Fig. 79 is different from the antenna shown in Figs. 74 and 75 in that the digital circuit unit 608, the ground electrode 704, and the analog circuit unit 606 are stacked and coupled together. A three-layer structure is used. The digital circuit unit 608 and the analog circuit unit 606 share the same ground electrode 704 sandwiched between them. The spacer 682 shown in FIGS. 74 and 75 does not exist. The antenna shown in Figure 79 is even more compact.
- the screw 684 is inserted and fixed from the analog circuit unit 606 side.
- the screw from the antenna body 600 side is used. It is also possible to insert 684 to fix all parts.
- a metal rod is inserted in place of the screw in the through holes for passing the screws provided at the four corners of the spacers 680 and 682, and this metal rod and the antenna body 600, the digital circuit unit 608 and the analog circuit unit 606 are inserted. It is possible to fix all parts by connecting them to the earth electrode by soldering.
- 80A to 80C show dielectric lens nominations applicable to the antenna shown in FIGS. 74 and 75 and FIG. 79 and other microstrip antennas according to the present invention.
- the dielectric lens does not necessarily need to be a spherical lens, and has various shapes protruding in the normal direction of the antenna surface, such as a triangular pyramid shown in FIG. 80A and a trapezoidal cone shown in FIG. 80B. May be. Alternatively, even when a flat dielectric plate or film as shown in FIG. 80C is used as the lens, the antenna gain can be improved. Dielectric lens By coating a photocatalytic material film on the outer surface of the lens, it is possible to prevent moisture and dirt from rain and wind from adhering to the lens, and it is possible to emit radio waves efficiently over a long period of time. .
- 81A and 81B show a plan view and a cross-sectional view, respectively, of a microstrip antenna that works on the twenty-fifth embodiment of the present invention.
- a grounding electrode 705 for providing a ground level is formed inside the substrate 700, and a feeding element 701 is arranged at the approximate center on the front surface of the substrate 700.
- a rectangular loop element 702 is arranged so as to surround the power supply element 701 at a slight distance from the power supply element 701.
- the loop-shaped element 702 has a function similar to that of the second feeding element having a larger size than the feeding element 701.
- First parasitic elements 711, 712, 713, 714 are arranged at positions away from each corner of loop-like element 702 (or feeding element 701) by a predetermined inter-element space in the diagonal direction.
- the second parasitic elements 721, 722, 723, 724 are arranged at positions away from the respective edges of the loop-shaped element 702 (or the feeding element 701) by a predetermined inter-element space in the normal direction. ing .
- Each of the first parasitic elements 711, 712, 713, and 714 has a switch for switching between a grounding force and a floating state (all four switches are not shown) and a control line (through). Hall) 731, 732, 733, and 734 are connected to each other, and these switches are arranged on the back surface of the substrate 700.
- the second parasitic elements 721, 722, 723, and 724 have switches 762 and 764 (the other two switches are not shown in the figure) that switch between ground and force-floating states. ) These switches 762 and 764 are also arranged on the back surface of the substrate 700 by being connected through 741, 742, 743, and 744, respectively.
- This microstrip antenna is a dual-frequency antenna having a first resonance frequency band and a second resonance frequency band.
- the first resonance frequency band is determined by the length of one side of the feed element 701.
- the second resonance frequency band is determined by the contour size (in particular, the length of the outer side and the line width) of the loop-shaped element 702 surrounding the power feeding element 701.
- a high-frequency signal in the second resonance frequency band is fed from the feed line 703 to the feed element 70.
- a current is excited in the loop element 702 to excite the loop element 702 in the vertical direction in the figure. In this way, resonance can be obtained at two different frequencies with the same half-wavelength (gZ2) with the same excitation direction.
- the first parasitic elements 711, 712, 713, and 714 are rectangular electrodes each having a side length of about a half wavelength ⁇ gZ2 of the first resonance frequency band, and the first resonance frequency band. Can be resonated.
- Second parasitic elements 721, 722, 723, 724 are rectangular electrodes with a side length of about half a wavelength ⁇ gZ2 in the second resonance frequency band, and resonate in the second resonance frequency band. can do.
- the microstrip antenna can be easily configured to be compact and thin, and can transmit and receive high-frequency radio beams of two different frequencies.
- Japan the use of the 10 GHz band for indoors and the 24 GHz band for outdoors is currently permitted as a frequency band for mobile object detection sensors. Therefore, in this microstrip antenna, if the shape and size of the element are determined so that the first resonance frequency band is 24 GHz and the second resonance frequency band is 10 GHz, the same microstrip antenna can be used indoors and outdoors. It can be used anywhere.
- FIG. 82 shows a plan view of a modification of the microstrip antenna shown in FIG. 81A.
- the first parasitic element 711 having the same shape and the same size as the feeding element 701 is placed at a position where the force of the loop-shaped element 702 (or the feeding element 701) is also separated by a predetermined inter-element space. 712, 713, 714 forces are self-placed.
- a second parasitic element 721 in the form of a rectangular loop having the same shape and size as the loop element 702 surrounding the feeder element 701 so as to surround each of the first parasitic elements 711, 712, 713, 714. 722, 723, 724 are arranged.
- Switches are connected to the second parasitic elements 721, 722, 723, and 724 via control lines (through holes) 741, 742, 743, and 744, respectively. Arranged on the back. By switching each switch, it is possible to switch whether to force ground each of the loop-shaped second parasitic elements 721, 722, 723, and 724 to float.
Landscapes
- Variable-Direction Aerials And Aerial Arrays (AREA)
- Waveguide Aerials (AREA)
- Radar Systems Or Details Thereof (AREA)
Abstract
Description
Claims
Priority Applications (3)
Application Number | Priority Date | Filing Date | Title |
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US11/664,292 US7773035B2 (en) | 2004-09-30 | 2005-09-29 | Microstrip antenna and high frequency sensor using microstrip antenna |
CN2005800329183A CN101032054B (zh) | 2004-09-30 | 2005-09-29 | 微带天线及使用微带天线的高频感测器 |
EP05787934A EP1804335A4 (en) | 2004-09-30 | 2005-09-29 | ANTENNA MICRORUBAN AND HIGH FREQUENCY SENSOR USING THE SAME |
Applications Claiming Priority (8)
Application Number | Priority Date | Filing Date | Title |
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JP2004285767 | 2004-09-30 | ||
JP2004-285767 | 2004-09-30 | ||
JP2004349402 | 2004-12-02 | ||
JP2004-349402 | 2004-12-02 | ||
JP2005087665 | 2005-03-25 | ||
JP2005-087665 | 2005-03-25 | ||
JP2005-180355 | 2005-06-21 | ||
JP2005180355 | 2005-06-21 |
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WO2006035881A1 true WO2006035881A1 (ja) | 2006-04-06 |
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PCT/JP2005/017970 WO2006035881A1 (ja) | 2004-09-30 | 2005-09-29 | マイクロストリップアンテナ及びマイクロストリップアンテナを用いた高周波センサ |
Country Status (7)
Country | Link |
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US (1) | US7773035B2 (ja) |
EP (1) | EP1804335A4 (ja) |
JP (1) | JP4560806B2 (ja) |
KR (1) | KR100880598B1 (ja) |
CN (1) | CN101032054B (ja) |
TW (1) | TWI273743B (ja) |
WO (1) | WO2006035881A1 (ja) |
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KR100920018B1 (ko) | 2007-03-23 | 2009-10-05 | 박정숙 | 광대역/2주파 마이크로스트립 패치 안테나 및 배열 안테나 |
WO2017150054A1 (ja) * | 2016-03-04 | 2017-09-08 | 株式会社村田製作所 | アレーアンテナ |
JPWO2017150054A1 (ja) * | 2016-03-04 | 2018-11-29 | 株式会社村田製作所 | アレーアンテナ |
US10476149B1 (en) | 2016-03-04 | 2019-11-12 | Murata Manufacturing Co., Ltd. | Array antenna |
WO2023073853A1 (ja) * | 2021-10-28 | 2023-05-04 | Fcnt株式会社 | アンテナ装置及び無線通信装置 |
Also Published As
Publication number | Publication date |
---|---|
CN101032054A (zh) | 2007-09-05 |
EP1804335A1 (en) | 2007-07-04 |
EP1804335A4 (en) | 2010-04-28 |
KR100880598B1 (ko) | 2009-01-30 |
KR20070051928A (ko) | 2007-05-18 |
JP2008312263A (ja) | 2008-12-25 |
JP4560806B2 (ja) | 2010-10-13 |
TW200627713A (en) | 2006-08-01 |
US7773035B2 (en) | 2010-08-10 |
CN101032054B (zh) | 2011-11-30 |
US20080088510A1 (en) | 2008-04-17 |
TWI273743B (en) | 2007-02-11 |
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