WO2005112238A2 - Standby operation of a resonant power convertor - Google Patents
Standby operation of a resonant power convertor Download PDFInfo
- Publication number
- WO2005112238A2 WO2005112238A2 PCT/IB2005/051553 IB2005051553W WO2005112238A2 WO 2005112238 A2 WO2005112238 A2 WO 2005112238A2 IB 2005051553 W IB2005051553 W IB 2005051553W WO 2005112238 A2 WO2005112238 A2 WO 2005112238A2
- Authority
- WO
- WIPO (PCT)
- Prior art keywords
- power supply
- resonant power
- resonant
- switching
- output
- Prior art date
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Classifications
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
- H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
- H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
- H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
- H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/337—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only in push-pull configuration
- H02M3/3376—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only in push-pull configuration with automatic control of output voltage or current
-
- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
- Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
- Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
Definitions
- the present invention relates to a power supply.
- the invention relates to a standby mode of operation of a resonant type of power supply.
- the present invention relates to standby power supply of a resonant type of power supply that has low power losses at little to no additional cost.
- the present invention is particularly relevant for devices that require a normal power supply as well as a low power standby mode such as Consumer Electronics devices.
- the losses in this mode may be a multiple of the required standby power.
- the resonant type of power supply operates in a burst mode operation. In this case the resonant type of power supply is completely switched off periodically. During a switch on process, hard switching cannot be avoided.
- a control loop in a burst mode operation locks only after a while in which timeslot no power can be converted. This further decreases efficiency of power conversion and it requires larger output filter. It would take quite some effort to design the burst mode operation.
- a last concept requires an additional converter that is only operational in stand-by mode. Obviously this brings additional components and costs.
- an object of the present invention to provide a resonant power supply that comprises a standby power supply and/or a light load operation mode. It is another object of the invention to provide a resonant power supply that comprises a standby power supply with little power loss, little to none additional cost and that is easy to design. Another object of the invention is to provide a resonant power supply that can be driven at low loads and exhibiting a substantially reduced power loss. It is also an object of the invention to provide a power supply driver integrated circuit for a resonant power supply that comprises a standby power supply and/or a light load operation mode.
- a resonant power supply operating in sub-critical mode (i.e., far below Resonance Frequency (f0)) but keeping zero voltage switching, and thus switching virtually loss-less. Start-up losses are avoided, which would permanently occur due to hard switching events in any burst mode operation.
- the inventor proposes to switch off one or more outputs while keeping one or more others in stand-by mode (in case of a converter with at least two outputs). This will save power switches at a secondary side of the resonant power supply.
- a resonant power supply with dual output control has been described in related patent applications (see attorney dockets PHDEO 10138 and PHDEO 10249).
- a conventional resonant power supply design is mainly determined by no- or light-load operation at maximum input voltage. Since the power deliverable in the proposed sub-critical operation mode can cover such a light load operation as well, the converter design has yet only to cope with nominal and peak power. This in turn results in a simplified transformer and eventually in reduced inverter currents.
- Fig la shows a typical diagram of a resonant power supply with a non- grounded (left) and a grounded resonant capacitor (right);
- Fig. lb shows a (prior art) typical low load (or stand-by) waveforms of a resonant power supply by operating far above resonance;
- Fig. 2a shows building blocks of a resonant power supply in accordance with the invention;
- FIG. 2b shows waveforms of a resonant power supply in accordance with a preferred mode of the invention with a sub-critical low load (stand-by or low load) operation several times below Resonance Frequency.
- Fig. 3 shows waveforms details of fig. 2 between tO and tl of a resonant power supply in accordance with the invention;
- Fig. 4 shows a resonant power supply, in accordance with the invention, with two half- wave rectified outputs with a stand-by mode that does not require an output power switch in stand-by mode;
- Fig. 5 shows a flowchart diagram of normal and standby mode operation of a resonant power supply in accordance with the invention;
- Fig. 6 shows a flowchart diagram of standby mode operation of a resonant power supply in accordance with the invention
- Fig. 7 shows a flowchart diagram of standby mode operation switching of a resonant power supply in accordance with the invention.
- the same reference numeral refers to the same element, or an element that performs substantially the same function.
- Fig la shows a resonant power supply 100 with a non-grounded (left) and a grounded resonant capacitor (right).
- Resonant power supply 100 comprises driver/controller 102, half-bridge 104, transformer 106 and output/load 108.
- an inverter is formed by a half-bridge 104 (with SI, S2), which is the most usual configuration.
- SI, S2 the most usual configuration.
- a person skilled in the art will understand that the invention applies to a full-bridge converter as well.
- a full-bridge converter may be advantageous for applications that require a higher output power and/or universal mains input voltage. Other configuration may be used as well.
- Fig. lb shows prior art characteristic waveforms at stand-by operation of resonant power supply 100.
- Fig. lb shows capacitor (input) current IC 152, reflected output current lo (x 10) 154, capacitor voltage VC (bold) 156, switch node voltage VS 158, driver voltage VD1 160 and driver voltage VD2 162. Most of the capacitor's current IC is reactive since only a small fraction lo is converted to the output.
- Fig. 2a shows building blocks 250 of a resonant power supply in accordance with the invention.
- Building blocks 250 comprise a control block 252 (e.g., SBM-control: Stand-By Mode-control), a driver 254 and an inverter formed by half bridge 256 (which comprises switches SI and S2, a common configuration).
- a half bridge a full- bridge is possible too and can be advantageous for higher output power and/or universal mains input voltage.
- any combination of the blocks could form an individual IC (Integrated Circuit).
- the most preferable solutions would be integration of control block 252 and driver 254 or of all three blocks 252, 254 and 256.
- This IC may preferably comprise more functions like its own supply means, the output voltage control in normal operation, overcharge protection (voltage, current, power, temperature), capacitive mode protection, or others.
- control block 252 For reasons of clarity, only input- and output-signals and signal processing blocks used for control block 252 are shown. Some of the signals may be aheady acquired for other functions too. VC e.g., can be used for over power protection. Vo (output voltage in case the resonant power supply has a single output ) is typically already used for output voltage control. The way that signals VC and V-out are sensed and provided to the control block 252 are well known by a person skilled in the art. The proposed SBM refers in particular to driving and sensing a resonant power supply, as shown and explained using the following Figures. In a typical embodiment, no additional elements are required in the circuitry of a resonant power supply.
- Mode can indicate that one of the following operations is required a) stand-by, b) normal operation.
- Two additional, e.g., optional operation modes c) start-up and d) light- load can either be derived from VDC and/or V-out or as well be determined by the mode signal.
- VC is used to watch the transient state of the resonant power supply in order to determine the switching times. Although sensing the resonant capacitor's voltage is probably the cheapest way, measuring alternatively the capacitor's current is possible, too. In case of this solution the following signal processing has to be adapted: maximum of VC translates to negative zero crossing of IC, and negative corresponds to zero crossing of VC to minimum of IC.
- Vo is the output voltage in case the resonant power supply has a single output.
- Vo is either again a single output voltage (namely that one providing the standby) or V-out comprises two output voltages Vol and Vo2, which are the directly controlled output voltages of the DOC.
- the latter option is used for the startup and light-load mode.
- VDC is most likely already a power input of the control/driver IC. However it may be used as a signal for the start-up mode as well.
- T-on is the on-time signal of the switch SI.
- T-off is the on-time signal of the switch S2. Trd is the so-called dead time when none of the switches is supposed to be conductive.
- These three parameters are the controlling variables of the power supply.
- the other above- mentioned functions either take over the control if none of the SBM modes are required or -in case of the protection functions- they may be active at the same time.
- Fig. 2b shows a proposed sub-critical low load (e.g., stand-by) operation several times below Resonance Frequency in accordance with an embodiment of the present invention.
- FIG. 2b shows capacitor (input) current IC 202, reflected output current lo 204, capacitor voltage VC (bold) 206, switch node voltage VS 208, driver voltage VDl 210 and driver voltage VD2 212.
- the ON-time functions as controlling variable.
- the OFF time (Toff) still arranges for zero voltage switching of the half-bridge by (e.g.) referring to the capacitor voltage VC only in terms it's of peak value and zero crossing.
- Fig. 2b corresponding current- and voltage-waveforms are displayed for the same converter and the same period of time resulting from applying the proposed controlling scheme.
- Fig. 3 shows in more detail one switching action of Fig. 2b.
- FIG. 3 shows capacitor (input) current IC 302, reflected output current lo 304, capacitor voltage VC (bold) 306, switch node voltage VS 308, driver voltage VDl 310 and driver voltage VD2 312.
- the ON-time period determines the stand-by power delivered to the output.
- Ton is bigger than P-output is bigger and vice versa.
- Toff enables switching only at negative zero crossing of VC which maintains ZVS and at a given minimum required inductive current ICO by measuring VC0 falling short of a given threshold VCOth.
- the stand-by mode (SBM) is accomplished by keeping switch S2 closed (VD2 high) and SI open (VDl low), which results in waveforms of a LC oscillator with a certain damping.
- the capacitor voltage VC is monitored. If its peak value VCO falls -due to damping- short of a given threshold VCOth (after time ToffD) the bridge is switched on as soon as the next negative zero crossing of VC is detected (after further time Toffl). The dead time is adjusted in the known manner.
- the On-time Ton of SI is used as the variable controlling the output voltage in SBM, because it determines the energy delivered to the output.
- the threshold VCOth corresponds to the negative peak value of capacitor (input) current IC and ensures zero voltage switching. It is determined by the resonant capacitor and the output capacitance Coss as specified for the switches SI and S2. ICO can be used for enabling so-called soft-switching or more specific ZVS.
- the VCOth control implies that, in event an extremely low power is required at the output (let say below some lOmW), the frequency (VCOth) may be so much reduced that not enough current ICO is left in advance to the switching event for a complete ZVS to be possible. This however is still better than hard switching.
- the switching frequency in the proposed sub-critical mode in the example of Fig. 2b is l/(Ton + Toff), about 31 kHz, as opposed to about 350 kHz in prior art Fig. lb. Compared to the conventional (prior art) low load operation shown in Fig.
- Resonance Frequency (fO) is the resonance (characteristic) frequency of the converter if the load current is zero. The switching frequency at normal operation is always bigger than fO (i.e.
- Start-up switching frequency can be, within known start-up control means, even several times above the rated maximum normal (steady- state) switching frequency, which is given by the minimum output power and at maximum input voltage (i.e. at minimum gain).
- the SBM operation frequency typically lies below fO. In SBM, the converter is excited with pulses, shorter than one half-cycle of the load resonant frequency.
- the converter oscillates either immediately with Resonance Frequency (in all cases except start-up) or for several further cycles with load- resonance and then continues oscillating at no load resonance. Since the SBM approach assumes a moderately damped system, the number of periods between SBM switching events may be 2 to 20 (with 2 refers to start-up mode, otherwise 4 to 20). In SBM, only one of the output rectifier diodes of the converter in Fig. la is conducting because the voltage at the transformer's main inductance becomes highly asymmetric according to the extreme duty cycle with which the converter is excited.
- Fig 4 shows a related converter of another embodiment of a resonant power supply 400 (a related converter) that makes use of the circumstance described in the previous two paragraphs.
- Resonant power supply 400 comprises driver/controller 402, half-bridge 404, transformer 406 and output/load 408.
- Resonant power supply 400 (shown with a Dual Output Control or DOC) experiences at one output (Vo2) a quasi switch-off while the other output Vol keeps its nominal voltage.
- Fig. 4 shows resonant power supply 400 with two, half- wave rectified, outputs (DOC). During stand-by operation at output Vol, the voltage Vo2 lessens to about 1/10 of its nominal value. A power switch (which is usually employed if that output has to be disconnected from the load in stand-by mode) can therefore be saved.
- the output filters are suitable already for nominal operation with the half- wave rectification waveforms.
- the ripple current usually determines the size of the capacitors, at least in case of electrolytic types, so that the resulting ripple voltages are negligible.
- a resonant type of power supply with dual output control has been described in prior art (PHDE010138, PHDE010249).
- An output switch is typically required when an output must be disconnected from the load in stand-by mode in a conventional resonant power supply.
- Another preferred embodiment of the invention comprises a variation of the control method. Keeping the pulse length constant and varying the switching frequency can control the SBM output voltage as well. An advantage of this method is that the pulse length can be set to a practical minimum. The advantage of the above feedback is that minimum current operation is always ensured.
- a similar control scheme can be applied with reverted signals for SI and S2.
- Fig. 5 shows a flowchart diagram of normal and standby mode operation of a resonant power supply in accordance with the invention.
- SBM control driving sequence
- a SBM operation has a sub-critical Ton-controlled zero voltage switching.
- Fig. 5 describes a first of three flowcharts representing three levels of hierarchy of a preferred SBM operation. Fig. 5 depicts the highest level of the hierarchy of operation.
- state NOM 502 which may be the default state of a controller, it can switch to state SBM (Stand By Mode) 510 through three conditions.
- a first condition is the start-up condition, SUC 504.
- Fig. 6 shows a flowchart diagram of standby mode operation of a resonant power supply in accordance with the invention. State SBM 510 of Fig. 5 is shown descended in hierarchy in the flowchart of Fig. 6.
- condition intNOMC2 600 is assessed steadily, which decides the return to state NOM 502.
- Condition intNOMC2 600 can be, e.g., VC0th-max ⁇ VC0th-min, or fs>fsSBM-max, or refer to the control error. This will be explained below.
- Condition SUC 610 may be set by state NOM 502 in terms of a predefined time interval (pulse, long enough to charge the output capacitor(s) with that max SBM power). As long as it lasts the system is supposed to run in SBM at a predefined power limit regardless of the instantaneous control error.
- Fig. 7 shows a flowchart diagram of standby mode operation switching of a resonant power supply in accordance with the invention.
- running of Ton at one of its limits indicates that either too much or too little power is converted (and adjusted accordingly in state dec(VCOth) 612 and state inc(VC0th) 614).
- VC ⁇ vo(system) 716.
- Arrow NOM simply indicates that in case of nominal operation the NOM block controls the driver voltages.
- VC is further evaluated in terms of negative zero crossing detection in state NZC 708. In case of such a zero crossing and if VCO is low enough (as controlled in the outer loop Fig. 6) the pulse with a length Ton (as also controlled there) is again given to the driver (which then further may introduce e.g. a preset dead time).
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- Engineering & Computer Science (AREA)
- Power Engineering (AREA)
- Dc-Dc Converters (AREA)
Abstract
Description
Claims
Priority Applications (3)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
US11/569,079 US20090207635A1 (en) | 2004-05-18 | 2005-05-11 | Standby Operation of a Resonant Power Convertor |
JP2007517545A JP2007538487A (en) | 2004-05-18 | 2005-05-11 | Resonant power converter standby operation |
EP05739755A EP1751840A2 (en) | 2004-05-18 | 2005-05-11 | Standby operation of a resonant power convertor |
Applications Claiming Priority (2)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
EP04300292 | 2004-05-18 | ||
EP04300292.2 | 2004-05-18 |
Publications (2)
Publication Number | Publication Date |
---|---|
WO2005112238A2 true WO2005112238A2 (en) | 2005-11-24 |
WO2005112238A3 WO2005112238A3 (en) | 2006-03-02 |
Family
ID=35240958
Family Applications (1)
Application Number | Title | Priority Date | Filing Date |
---|---|---|---|
PCT/IB2005/051553 WO2005112238A2 (en) | 2004-05-18 | 2005-05-11 | Standby operation of a resonant power convertor |
Country Status (5)
Country | Link |
---|---|
US (1) | US20090207635A1 (en) |
EP (1) | EP1751840A2 (en) |
JP (1) | JP2007538487A (en) |
CN (1) | CN1954481A (en) |
WO (1) | WO2005112238A2 (en) |
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WO2007148271A3 (en) * | 2006-06-20 | 2008-03-06 | Koninkl Philips Electronics Nv | Method for operating a resonant power converter |
WO2009004582A1 (en) * | 2007-07-04 | 2009-01-08 | Nxp B.V. | Standby operation of a resonant power converter |
WO2009098640A1 (en) * | 2008-02-04 | 2009-08-13 | Nxp B.V. | Method of operating a resonant power converter and a controller therefor |
WO2010115976A1 (en) * | 2009-04-09 | 2010-10-14 | Stmicroelectronics S.R.L. | Method and circuit for avoiding hard switching in resonant converters |
WO2010124987A1 (en) * | 2009-04-27 | 2010-11-04 | Conti Temic Microelectronic Gmbh | Control device for the voltage-absent switching of a switching element of a voltage converter |
EP2251967A3 (en) * | 2009-05-11 | 2010-12-08 | Intersil Americas Inc. | Control mode for ZVS converter at resonant operating frequencies |
ITMI20102347A1 (en) * | 2010-12-22 | 2012-06-23 | St Microelectronics Srl | CONTROL DEVICE FOR A DC-DC CONVERTER. " |
WO2013010782A2 (en) | 2011-07-15 | 2013-01-24 | Nxp.B.V. | Resonant converter control |
TWI465026B (en) * | 2008-07-25 | 2014-12-11 | Cirrus Logic Inc | Resonant switching power circuit, method of controlling switching in resonant switching power circuit and integrated circuit controller |
US9065350B2 (en) | 2011-07-15 | 2015-06-23 | Nxp B.V. | Resonant converter control based on a voltage difference |
US9634571B2 (en) | 2012-10-18 | 2017-04-25 | Philips Lighting Holding B.V. | Driver device and driving method for driving a load |
EP3334026A1 (en) | 2016-12-09 | 2018-06-13 | Nxp B.V. | Dual output power converter and method for operating a dual output power converter |
US10116199B1 (en) | 2018-01-25 | 2018-10-30 | Nxp B.V. | Apparatus and method for linearization of the control inputs for a dual output resonant converter |
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- 2005-05-11 US US11/569,079 patent/US20090207635A1/en not_active Abandoned
- 2005-05-11 EP EP05739755A patent/EP1751840A2/en not_active Withdrawn
- 2005-05-11 WO PCT/IB2005/051553 patent/WO2005112238A2/en not_active Application Discontinuation
- 2005-05-11 JP JP2007517545A patent/JP2007538487A/en not_active Withdrawn
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WO2007148271A3 (en) * | 2006-06-20 | 2008-03-06 | Koninkl Philips Electronics Nv | Method for operating a resonant power converter |
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US8174851B2 (en) | 2006-06-20 | 2012-05-08 | Koninklijke Philips Electronics N.V. | Method for operating a resonant power converter |
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CN113162423A (en) * | 2021-04-08 | 2021-07-23 | 矽力杰半导体技术(杭州)有限公司 | Control circuit, control method and resonant converter |
CN113162423B (en) * | 2021-04-08 | 2024-05-24 | 矽力杰半导体技术(杭州)有限公司 | Control circuit, control method and resonant converter |
Also Published As
Publication number | Publication date |
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CN1954481A (en) | 2007-04-25 |
JP2007538487A (en) | 2007-12-27 |
US20090207635A1 (en) | 2009-08-20 |
WO2005112238A3 (en) | 2006-03-02 |
EP1751840A2 (en) | 2007-02-14 |
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