WO2004051851A1 - Driver for switching circuit and drive method - Google Patents

Driver for switching circuit and drive method

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Publication number
WO2004051851A1
WO2004051851A1 PCT/IB2003/005291 IB0305291W WO2004051851A1 WO 2004051851 A1 WO2004051851 A1 WO 2004051851A1 IB 0305291 W IB0305291 W IB 0305291W WO 2004051851 A1 WO2004051851 A1 WO 2004051851A1
Authority
WO
Grant status
Application
Patent type
Prior art keywords
gate
voltage
time
control
transistor
Prior art date
Application number
PCT/IB2003/005291
Other languages
French (fr)
Inventor
Philip Rutter
Original Assignee
Koninklijke Philips Electronics N.V.
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date

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Classifications

    • HELECTRICITY
    • H02GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02MAPPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00Details of apparatus for conversion
    • H02M1/38Means for preventing simultaneous conduction of switches
    • HELECTRICITY
    • H02GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02MAPPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00Conversion of dc power input into dc power output
    • H02M3/02Conversion of dc power input into dc power output without intermediate conversion into ac
    • H02M3/04Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
    • H02M3/10Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M3/145Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M3/155Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/156Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
    • H02M3/158Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load
    • H02M3/1588Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load comprising at least one synchronous rectifier element
    • HELECTRICITY
    • H03BASIC ELECTRONIC CIRCUITRY
    • H03KPULSE TECHNIQUE
    • H03K17/00Electronic switching or gating, i.e. not by contact-making or -braking
    • H03K17/04Modifications for accelerating switching
    • H03K17/041Modifications for accelerating switching without feedback from the output circuit to the control circuit
    • H03K17/0412Modifications for accelerating switching without feedback from the output circuit to the control circuit by measures taken in the control circuit
    • H03K17/04123Modifications for accelerating switching without feedback from the output circuit to the control circuit by measures taken in the control circuit in field-effect transistor switches
    • HELECTRICITY
    • H03BASIC ELECTRONIC CIRCUITRY
    • H03KPULSE TECHNIQUE
    • H03K17/00Electronic switching or gating, i.e. not by contact-making or -braking
    • H03K17/04Modifications for accelerating switching
    • H03K17/042Modifications for accelerating switching by feedback from the output circuit to the control circuit
    • H03K17/04206Modifications for accelerating switching by feedback from the output circuit to the control circuit in field-effect transistor switches
    • YGENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02BCLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B70/00Technologies for an efficient end-user side electric power management and consumption
    • Y02B70/10Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion
    • Y02B70/14Reduction of losses in power supplies
    • Y02B70/1458Synchronous rectification
    • Y02B70/1466Synchronous rectification in non-galvanically isolated DC/DC converters

Abstract

A driver circuit includes monitoring circuitry (32, 34, 36) for monitoring the states of high and low side switches (6, 8). The driver circuit has an adjustable delay for turning on the transistors (6, 8). The delay is decreased when the monitoring circuit detects that a voltage corresponding to one transistor passes a predetermined voltage V1 before a voltage corresponding to the other transistor passes another predetermined point V2, and vice versa.

Description

DESCRIPTION

DRIVER FOR SWITCHING CIRCUIT AND DRIVE METHOD

The invention relates to switching circuit, drive circuitry for such a circuit and a method of driving a switching circuit, and particularly but not exclusively to a switching voltage converter circuit.

A wide variety of switching regulators are commonly used to generate voltages.

One type of converter, a synchronous dc-dc converter, is illustrated schematically in Figure 1. An input voltage Vjn is applied between input terminals 2,4. A pair of transistors, here field effect transistors 6,8, are connected between the input terminals 2,4. The transistor 6 adjacent to the input terminal 2 is known as the control FET or high side transistor, and the transistor 8 adjacent to the ground is known as the synchronous (sync) FET or low side transistor. The high side is relatively more positive than the low side, though it is not necessary that either the high or the low side has any particular relationship to ground. The node between the transistors 6, 8 is known as the switch node 10.

The switch node feeds through an inductor 12 and across a capacitor 14 to an output 16.

A control circuit 18 has one input on an input control terminal 20 and another input fed from the output 16 via a feedback path 21. The control circuit 18 supplies control signals to control the FETs 6,8 to maintain a constant voltage at the output by switching transistors 6,8 off and on alternately. The control signals are alternating signals which cause the control and sync FETs to conduct alternately. The mark-space ratio is varied, i.e. the ratio of the time for which the control FET conducts to the time the sync FET conducts is modulated, to achieve the desired voltage on the output 16.

Examples of such dc-dc converters include those presented in WO98/49607 to Intel Corporation and US5,479,089 to Lee. One feature of synchronous dc-dc converters is that it is not generally desired to switch on both high and low side transistors 6,8 simultaneously. If both transistors are on, the input voltage is short-circuited by current passing directly between the two input terminals 2,4 through the control and sync FETs. The phenomenon is known as "shoot-through". Accordingly, the control circuit 18 is generally arranged to ensure that only one of the two transistors 6,8 is on at a time.

This is conventionally carried out by monitoring two voltages. The voltage at the switch node 10 is monitored to prevent the switching on of the low side transistor 8 until the high side transistor 6 is switched off. The voltage at the gate of the low side transistor 8 is monitored to prevent the high side transistor switching on until the low side transistor 8 is switched off. WO98/49607 describes a circuit of this type, as does US 5,479,089 to Lee.

The dead time when neither FET is conducting depends on the transistor threshold voltage and the capacitance of the sync FET, which vary widely due to manufacturing spread of parameters of the chosen FET, as well as according to the individual choice of FET. This means that a control IC has to use conservative estimates of these parameters to produce a dead time that will avoid shoot through. This is generally a longer dead time than would be possible if the control circuit were optimised for the specific FETs used.

The present trend is to increase switching and clock speeds, which increases the significance of the dead time during which neither high or low side transistor 6,8 is on. It would be beneficial to reduce this time.

One circuit that aims to reduce this dead time is that described in WO02/063752 to Philips. The voltage on the drive node 10 is monitored and compared with a predetermined voltage, generally of opposite sign to the output voltage. When the control FET 6 switches off, the inductor continues to draw current through the parasitic body diode of the sync FET 8. The body diode drops about 0.6V, and so assuming that the input and output voltages are positive, the voltage at the drive node 10 becomes negative when the control FET is switched off. WO02/063752 accordingly uses the voltage at the drive node falling below a predetermined value to trigger the turning on of the sync FET to ensure that the sync FET is not switched on until the control FET is switched off.

However, although such a circuit reliably avoids shoot through, there remains an appreciable dead time, when neither FET is switched on, of at least the delay time of the driver plus the turn-on time of the FET. This dead time is about 30ns using current technology.

Another approach is described in US6,396,250. In this circuit, controllable delays are provided on the inputs to gate transistors, controlled by a feedback loop with the signal taken from the switch node. The inventors have realised that although this circuit delivers some benefits there are disadvantages from taking the control signal from the switch node in this way.

As switching speeds increase still further, it would be beneficial to reduce the dead time as much as possible.

Accordingly, in one aspect there is provided a drive circuit for a switching circuit, comprising: first and second gate control outputs for connection to the gates of respective first and second insulated gate transistors; first and second gate drivers connected to the first and second gate control outputs respectively for driving the respective gates to switch the first and second insulated gate transistors on and off alternately; and monitoring circuitry for monitoring the voltages on first and second monitor points and hence the state of the first and second transistors respectively, the first monitor point being one of the first gate control output and a switch node between first and second transistors and the second monitor point being the second gate control output, wherein the drive circuitry is arranged: to drive the second gate driver to switch off the second insulated gate transistor and then after a controllable delay D to drive the first gate driver to switch on the first insulated gate transistor; to compare the time that the voltage on the first monitor point passes a first predetermined voltage and the time that the voltage on the second monitor point passes a second predetermined voltage; and to decrease the delay D if the second time is before the first time and to increase the delay D if the second time is after the first time. The circuitry allows the dead time to be reduced to a minimum without needing excessively complex additional circuitry.

By using timing information related to each transistor separately rather than by just taking a feedback signal from the switch node as in US6, 396,250 the circuit can track the turn on times of each transistor in a consistent and reliable manner.

The transistors may be connected in series at a switch node. The first monitor point may be the switch node. Alternatively, the first monitor point may conveniently be the first gate. The benefits of these approaches will be defined in more detail below.

The delay D may be increased or decreased by a predetermined amount. The predetermined amount may be in the range 0.5ns to 10ns, preferably 1 ns to 5 ns. By using a predetermined amount in this range, especially in the preferred range, the deadtime can be reduced to zero even as changes in operating currents and temperature during operation affect the switching time of the components - the system is capable of adjusting rapidly enough to cope with these variations. Further, this range allows good stability. If the delay is decreased in steps that are too large, then the gate signals may overlap to such and extend that both FETs will be fully on and "shoot through" will occur, thus increasing losses. Therefore, the steps must be small enough to avoid significant shoot through.

Alternatively, the delay D can be varied by a variable amount - for example the greater the time difference between the first and second times the more D may be adjusted on each cycle. The predetermined voltages may be selected based on the components used for the insulated gate field effect transistors.

The first and second predetermined voltages may be in the range 1 V to

2V; this voltage allows good control for a variety of output voltages. In circuits operating only at higher voltage range, the predetermined voltages may vary more widely. For example, for a 12V output, the predetermined voltage may be in the range 1V to 10V. The voltages may be the same, and may preferably be at a level roughly corresponding to the threshold voltages of the transistors.

For a p-channel insulated gate transistor, the corresponding predetermined voltage may be 1 V to 2V below the p-channel source voltage. In a preferred embodiment, the drive circuit is arranged: to switch off the second one of the insulated gate transistors and after a second delay E to switch on the first one of the insulated gate transistors; to compare the time that the voltage on the first gate control output passes a third predetermined voltage and the time that the voltage on the second gate control output passes a fourth predetermined voltage; and to decrease the second delay E if the fourth time is after the third time and increasing the second delay E if the fourth time is before the third time. This enables the drive circuitry to set the delay D to be different from the second delay E, thereby allowing the delays for the first and second transistors to be set separately. Conveniently, the third voltage equals the first voltage and the fourth voltage equals the second voltage.

The invention also relates to a switching circuit comprising a drive circuit as set out above and upper and lower insulated gate transistors each having gate, source and drain, the gates of the upper and lower insulated gate transistors being connected to corresponding gate control outputs of the drive circuitry.

The predetermined voltages may be within 1V of the threshold voltage of the insulated gate transistors.

In embodiments, the first monitor point is the first gate control output. This symmetrical arrangement avoids the need for a separate connection to the switch node, since the drive circuit has both the first and second gate control outputs available within it. Also, by not needing to monitor the switch node difficulties with noise at the switch node are avoided.

In an alternative embodiment the first monitor point is the switch node. Taking the first transistor to be the high side transistor, the source of the first transistor effectively floats on the oscillating switch node voltage, meaning that the gate source voltage shifts relative to ground. By monitoring the switch node instead of the gate voltage there is no need to take account of the varying reference voltage of the high side transistor. Moreover, variations in the threshold voltage of the first transistor no longer need to be taken into account. Preferably, the predetermined voltages are in the range 1V to 2V with respect to the ground of the low side transistor - this range allows the driver to work with as wide a range of conversion (output) voltages respectively.

In another aspect there is provided a switching converter circuit with control and sync insulated gate transistors each having gate, source and drain, the control and sync insulated gate transistors being connected together in series with a switch node for driving a load insulated gate transistors; and drive circuitry connected to the gates of the insulated gate transistors for switching the control and sync insulated gate transistors on and off alternately, wherein the drive circuitry is arranged: to switch off the sync insulated gate transistor and switch on the control insulated gate transistors after a delay D; to monitor the voltages at first and second monitor points, the first monitor point being the switch node or the gate voltages of the control transistor and the second monitor point being the gate voltage of the sync transistor; to compare the time that the voltage on the first monitor point falls below a first predetermined voltage and the time that the voltage on the second monitor point rises above a second predetermined voltage; and to decrease the delay D if the second time is after the first time and to increase the delay D if the second time is before the first time.

In a further aspect, the invention relates to a method of driving a converter circuit having control and sync insulated gate transistors each having gate, source and drain, the upper and lower insulated gate transistors being connected together in series and having a switch node therebetween for connection to a load; the method including the steps of: (a) switching off a first one of the insulated gate transistors; (b) switching on the second one of the insulated gate transistors after a delay D; (c) monitoring the voltages at first and second monitor points, the first monitor point being one of the gate of the first transistor and the switch node and the second monitor point being the gate of the second transistor; and (d) comparing the time that the voltage on the first monitor point passes a first predetermined voltage and the time that the voltage on the second monitor point passes a second predetermined voltage; (e) decreasing the delay D if the second time is after the first time and increasing the delay D if the second time is before the first time; and (f) switching on the first and second transistors alternately, repeating steps (a) to (e) above when switching on the second transistor and switching off the first transistor.

For a better understanding of the invention, embodiments of the invention will now be described, purely by way of example, with reference to the accompanying drawings, in which:

Figure 1 shows a prior art buck converter circuit; Figure 2 shows a switching converter circuit according to a first embodiment of the invention;

Figures 3(a) to 3(c) show voltages in the first embodiment of the invention; and

Figure 4 shows a second embodiment of the invention.

Referring to Figure 2, a high-side (control) FET 6 is connected via switch node 10 in series with a low-side (sync) FET 8 between a high-side line connected to high-side input terminal 2 and ground connected to low-side input terminal 4. Switch node 10 is connected through inductor 12 and across capacitor 14 to output 16 which may be connected to a load. The load may be, for example, a micro processor.

Drive circuitry 18 drives the gates 38 of the high-side 6 and low-side 8 FETs. An input signal is provided on terminal 20. In this embodiment, the input signal is a pulse-width modulated signal generated by a suitable generator. The generator is not shown in the drawings since suitable generation schemes are well known to the skilled person. The generation scheme may in particular use feedback from output 16 to control the mark- space ratio of the signal input at terminal 20 and hence to control the voltage output at output 16.

A first gate driver circuit 22 and a second gate driver circuit 24 are arranged to provide suitable signals on first and second gate control outputs 26, 28. These are connected in turn to the gates of the high-side FET 6 and the low-side FET 8 respectively. The gate drivers 22, 24 both include circuitry to turn off the respective transistor in response to a signal pulse on signal input 20, and to turn on the respective transistor after a predetermined delay on receipt of the opposite sign of pulse on signal input 20. Such circuits having a controllable turn-on delay may be made in a number of ways by the skilled person. For example, some circuits are described in US 6,396,250 to Bridge.

First and second comparators 32, 34 are provided connected to first and second gate control outputs 26, 28 respectively. Each compares the voltage on the gate output with a respective predetermined voltage and provide a corresponding output signal to control unit 36. Comparators 32, 34 and control unit 36 accordingly constitute monitoring circuitry for monitoring gate voltages on the FETs 6, 8.

The control unit 36 is connected to the drive circuits 22, 24 to set the programmable turn-on delay in these circuits. In use, when the low-side FET 8 is turned off the high-side FET 6 is turned on after a programmable delay D. The voltages on the first gate control output 26 connected to high-side FET 6 is shown in Figure 3a as a dotted line, and the corresponding voltage on second gate control output 28 connected to low-side FET 8 is shown as a solid line. In the state shown in Figure 3a, the delay D is sufficiently long that the low-side FET 8 turns off long before the high-side FET 6 turns on. In this case, control unit 36 detects that the gate voltage of low-side FET 8 passes predetermined voltage V2 long before the voltage on first gate control output 26 passes voltage V1. The term "first time" will be used to describe the time relating to the first transistor and the term "second time" with be used to describe the time relating to the second transistor, even though the order of first and second times vary, for example in the initial state the second time is before the first time.

When the control unit 36 determines that the second time is before the first time the delay D is decreased by a predetermined amount of 2ns. This is repeated on each input cycle of the signal on signal input 20, with the delay being reduced by the predetermined time 2ns on each cycle until the situation in Figure 3b is reached in which the first and second times are substantially the same. The voltages V1 , V2 are selected so that in this state the dead time is reduced to around 1 to 2ns which represents a significantly reduced dead time compared to a conventional scheme, which includes the rise time which may typically be of order 12ns.

As component values change with time, for example as the components warm up, the situation in Figure 3c may occur in which the second time is after the first time. In this case, control circuitry 36 increases the delay to avoid shoot-through.

A corresponding feedback loop is used to turn on the second transistor and turn off the first transistor. A separate turn-on delay E is used for the second transistor to take account of the component variation between first and second transistors 6, 8. When the transistors are switched, the inductance of the connection, i.e. the wires and PCB, between the driver and the transistor in combination with the gate drive current will cause a voltage drop along the connection leading to an error in the sensed gate voltages. Therefore, in a preferred variation the sense connections of comparators 32,34 may be connected directly to the insulated gates of the transistors through separate connections to the connection carrying the gate drive current. Alternatively, in a multichip module implementation the comparators may be integrated in the same package as the insulated gate transistors and directly connected thereto.

In a second embodiment of the invention, the input to the first comparator 32 is taken from the switch node 10 instead of the first control output 26. This is shown in Figure 4. This works since when the high-side FET 6 is switched on the voltage on the switch node 10 rises from about -0.5V to the input voltage. Turning off the high-side FET 6 causes the switch node 10 to fall from the input voltage to about -0.5V. The reference voltage can therefore be any point between 0V and the conversion voltage, but preferably between 1 and 2V to allow the drive circuitry to work for as wide a range of conversion voltages as possible and to give a level of noise immunity, since the switch node 10 is inevitably noisy.

The benefit of the approach of Figure 4 is that threshold voltage variations of the control FET are no longer relevant. A second advantage is that the gate-source voltage of the high-side FET 6 is referenced to a source that floats high when the FET is turned on and floats low when the FET is turned off. This makes it more difficult to monitor the gate voltage signal of the high-side FET 6. By monitoring the switch node as an alternative to the gate of the high-side FET there is no such difficulty. From reading the present disclosure, other variations and modifications will be apparent to persons skilled in the art. Such variations and modifications may involve equivalent and other features which are already known in the design, manufacture and use of the switching circuit and which may be used in addition to or instead of features described herein. Although claims have been formulated in this application to particular combinations of features, it should be understood that the scope of disclosure also includes any novel feature or any novel combination of features disclosed herein either explicitly or implicitly or any generalisation thereof, whether or not it mitigates any or all of the same technical problems as does the present invention. The applicants hereby give notice that new claims may be formulated to any such features and/or combinations of such features during the prosecution of the present application or of any further applications derived therefrom.

For example, the embodiments described use the approach of the invention for turning on both transistors, but it is possible to use the approach only for turning on one transistor, and not the other.

There is no need for both the transistors to be n-channel. For example, the control FET could be p-channel. In this case, the predetermined reference voltage would be about 1V-2V lower than the threshold voltage of this transistor.

The described embodiments use steps of constant size to reach the minimum delay. However, this is not an essential feature and the skilled person will readily conceive of alternative approaches. For example, the size of the step can be proportional to the difference in time between the first and second times.

Further, although the described embodiments relate to a switching voltage converter the invention is also applicable to other switching arrangements where switches need to be operated with a minimal delay between operation.

Claims

1. A drive circuit (8) for a switching circuit, comprising: first and second gate control outputs (26, 28) for connection to the gates of respective first and second insulated gate transistors (6, 8); first and second gate drivers (22, 24) connected to the first and second gate control outputs (26, 28) respectively for driving the respective gates to switch the first and second insulated gate transistors on and off alternately; monitoring circuitry (32, 34, 36) for monitoring the voltages on first and second monitor points and hence the state of the first and second transistors (6, 8) respectively, the first monitor point being one of the first gate and a switch node (10) between first and second transistors and the second monitor point being the second gate; wherein the drive circuitry is arranged: to drive the second gate driver (24) to switch off the second insulated gate transistor (8) and then after a controllable delay D to drive the first gate driver (22) to switch on the first insulated gate transistor (6); to compare the time that the voltage on the first monitor point passes a first predetermined voltage and the time that the voltage on the monitor point passes a second predetermined voltage; and to decrease the delay D if the second time is before the first time and to increase the delay D if the second time is after the first time.
2. A drive circuit according to claim 1 wherein the first monitor point is the first gate control output (26) and the second monitor point is the second gate control output (28).
3. A drive circuit according to claim 1 wherein first and second insulated gate transistors are connected together in series at a switch node and the first monitor point is the switch node.
4. A drive circuit according to any preceding claim wherein every time the delay D is increased or decreased it is increased or decreased by a constant predetermined time.
5. A drive circuit according to claim 4 wherein the predetermined time is in the range 1 ns to 5 ns.
6. A drive circuit according to any preceding claim wherein the drive circuitry is arranged: to switch off the first insulated gate transistor (6) and after a second delay E to switch on the second insulated gate transistor (8); to compare the time that the voltage on the first monitor point passes a third predetermined voltage and the time that the voltage on the second monitor point passes a fourth predetermined voltage; and to decrease the second delay E if the fourth time is after the third time and to increase the second delay E if the fourth time is before the third time, so that the drive circuitry can set the delay D to be different from the second delay
E.
7. A switching circuit comprising: a drive circuit (18) according to any preceding claim; and first and second insulated gate transistors (6, 8) each having gate, source and drain, the gates (38) of the first and second insulated gate transistors (6, 8) being connected to corresponding gate control outputs (26, 28) of the drive circuit.
8. A switching circuit according to claim 7 wherein the predetermined voltages are within 1V of the threshold voltage of the insulated gate transistors (6, 8).
A switching converter circuit, comprising: control and sync insulated gate transistors (6, 8) each having gate, source and drain, the control and sync insulated gate transistors (6, 8) being connected together in series at a switch node (10) for driving a load; and a drive circuit (18) connected to the gates of the insulated gate transistors for switching the control and sync insulated gate transistors on and off alternately; wherein the drive circuit (18) is arranged: to switch off the sync insulated gate transistor (8) and switch on the control insulated gate transistor (6) after a delay D; to monitor the voltages at first and second monitoring points, the first monitor point being the switch node or the gate voltage of the control transistor
(6) and the second monitor point being the gate voltage of the sync transistor
(8); to compare the time that the voltage on the first monitoring point falls below a first predetermined voltage and the time that the voltage on the second monitoring point rises above a second predetermined voltage; and to decrease the delay D if the second time is after the first time and to increase the delay D if the second time is before the first time.
10. A method of driving a converter circuit having first and second insulated gate transistors (6, 8) each having gate, source and drain, the method including the steps of:
(a) switching off the first insulated gate transistor (6);
(b) switching on the second insulated gate transistor (8) after a delay D;
(c) monitoring the voltages at first and second monitor points, the first monitor points being one of the gate of the first transistor (6) and a switch node (10) between first and second transistors, and the second monitor point being the gate of the second transistor (8); and (d) comparing the time that the voltage on the first monitor point passes a first predetermined voltage and the time that the voltage on the second monitor point passes above a second predetermined voltage; (e) decreasing the delay D if the second time is after the first time and increasing the delay D if the second time is before the first time; and
(f) switching on the first and second transistors (6, 8) alternately, repeating steps (a) to (e) above when switching on the second transistor and switching off the first transistor.
11. A method according to claim 10 further comprising:
(g) switching off the second insulated gate transistor (8) and switching on the first insulated gate transistor (6) after a second delay E which may be different from the delay D;
(h) monitoring the voltages at the first and second monitor points; (i) comparing the third time that the voltage on the second monitor point falls below a third predetermined voltage and the fourth time that the voltage on the first monitor point rises above a fourth predetermined voltage; (j) decreasing the second delay E if the fourth time is after the third time and increasing the second delay E if the fourth time is before the third time; and repeating steps (g) to (j) above when switching on the first transistor (6) and switching off the second transistor (8) as the transistors are switched on alternately.
12. A method according to claim 10 or 11 wherein the delay is increased or decreased by a predetermined amount in the range 1 ns to 5 ns on each cycle.
13. A method according to any of claims 10 to 12 wherein the first monitor point is the gate of the control transistor respectively.
14. A method according to any of claims 10 to 12 wherein the first and second insulated gate transistors (6, 8) are connected together in series and have a switch node (10) therebetween for connection to a load, and in which the first monitor point is the switch node.
PCT/IB2003/005291 2002-11-29 2003-11-19 Driver for switching circuit and drive method WO2004051851A1 (en)

Priority Applications (2)

Application Number Priority Date Filing Date Title
GB0227792A GB0227792D0 (en) 2002-11-29 2002-11-29 Driver for switching circuit and drive method
GB0227792.9 2002-11-29

Applications Claiming Priority (4)

Application Number Priority Date Filing Date Title
JP2004556618A JP2006508629A (en) 2002-11-29 2003-11-19 Driver and driving method for the switching circuit
US10536247 US7205821B2 (en) 2002-11-29 2003-11-19 Driver for switching circuit and drive method
EP20030772487 EP1568132B1 (en) 2002-11-29 2003-11-19 Driver for switching circuit and drive method
DE2003635961 DE60335961D1 (en) 2002-11-29 2003-11-19 Driver circuit for switching device and driving method therefor

Publications (1)

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WO2004051851A1 true true WO2004051851A1 (en) 2004-06-17

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Country Status (7)

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US (1) US7205821B2 (en)
EP (1) EP1568132B1 (en)
JP (1) JP2006508629A (en)
CN (1) CN100421353C (en)
DE (1) DE60335961D1 (en)
GB (1) GB0227792D0 (en)
WO (1) WO2004051851A1 (en)

Cited By (7)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JP2007116846A (en) * 2005-10-21 2007-05-10 Fujitsu Ten Ltd Switching regulator
EP1876693A1 (en) * 2006-07-04 2008-01-09 Infineon Tehnologies AG Method for driving a transistor half-bridge
DE102009010753A1 (en) * 2009-02-26 2010-09-09 Hüttinger Elektronik GmbH & Co. KG To determine the switch time point of semiconductor switches, in a plasma power supply, a control signal is used without a direct current operating voltage
FR2964274A1 (en) * 2010-08-26 2012-03-02 St Microelectronics Sa Converter has decoupage
US8836308B2 (en) 2010-10-28 2014-09-16 Transphorm Japan, Inc. Step-down type DC-DC regulator
GB2513322A (en) * 2013-04-22 2014-10-29 Harvard Engineering Plc Power supply
US9537399B2 (en) 2011-10-19 2017-01-03 Melexis Technologies Nv Direct current control with low E-M emission

Families Citing this family (19)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
WO2008137935A1 (en) * 2007-05-07 2008-11-13 Harman International Industries, Incorporated Automatic zero voltage switching mode controller
US7880454B2 (en) * 2007-12-21 2011-02-01 L&L Engineering Llc Methods and systems for control of switches in power regulators/power amplifiers
US8299820B2 (en) * 2008-09-30 2012-10-30 Infineon Technologies Austria Ag Circuit including a resistor arrangement for actuation of a transistor
US8829946B2 (en) 2008-09-30 2014-09-09 Infineon Technologies Austria Ag Circuit for driving a transistor dependent on a measurement signal
EP2285191A1 (en) * 2009-07-13 2011-02-16 Nxp B.V. Overload protection
JP5794855B2 (en) * 2011-08-05 2015-10-14 トランスフォーム・ジャパン株式会社 Driving circuit and power supply of the power supply
US8933679B2 (en) * 2011-12-07 2015-01-13 Maxim Integrated Products, Inc. Adaptive dead-time control
US9231477B2 (en) * 2013-04-23 2016-01-05 Nvidia Corporation Control of a soft-switched variable frequency buck regulator
DE102013208574A1 (en) * 2013-05-08 2014-11-13 Robert Bosch Gmbh Controlling a half-bridge
DE102013208813A1 (en) * 2013-05-14 2014-11-20 Robert Bosch Gmbh Controlling a half-bridge
KR101529149B1 (en) * 2013-09-02 2015-06-17 엘에스산전 주식회사 Three phase aprratus for driving gate
CN104579267A (en) * 2013-10-18 2015-04-29 施耐德电器工业公司 Pulse drive circuit and pulse drive method
US9653996B2 (en) * 2013-10-28 2017-05-16 Infineon Technologies Americas Corp. Adaptive off time control scheme for semi-resonant and hybrid converters
US9130552B2 (en) * 2013-11-05 2015-09-08 Texas Instruments Incorporated Cross-conduction detector for switching regulator
JP6277691B2 (en) * 2013-11-28 2018-02-14 株式会社オートネットワーク技術研究所 Control signal generation circuit and the circuit device
US9231573B2 (en) * 2014-05-30 2016-01-05 Taiwan Semiconductor Manufacturing Company, Ltd. Delay controlling circuit for driving circuit, driving circuit having delay controlling circuit, and method of operating driving circuit
US9537400B2 (en) * 2014-08-29 2017-01-03 Infineon Technologies Austria Ag Switching converter with dead time between switching of switches
JP6304191B2 (en) * 2015-10-20 2018-04-04 トヨタ自動車株式会社 Power converter
WO2018008333A1 (en) * 2016-07-04 2018-01-11 日立オートモティブシステムズ株式会社 Inverter driving device

Citations (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US5408150A (en) * 1992-06-04 1995-04-18 Linear Technology Corporation Circuit for driving two power mosfets in a half-bridge configuration
US5479089A (en) * 1994-12-21 1995-12-26 Hughes Aircraft Company Power converter apparatus having instantaneous commutation switching system
US6175225B1 (en) * 1999-07-02 2001-01-16 U.S. Philips Corporation Switching arrangement and switch component for a DC-DC converter
JP2001258269A (en) * 2000-03-15 2001-09-21 Kawasaki Steel Corp Soft switching dc-dc converter

Family Cites Families (5)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US2479089A (en) * 1943-12-01 1949-08-16 Jan Jongerius N V Leveling device for raising platforms
DE3901034C1 (en) * 1989-01-14 1990-07-19 Danfoss A/S, Nordborg, Dk Inverter
US6417653B1 (en) 1997-04-30 2002-07-09 Intel Corporation DC-to-DC converter
US6396250B1 (en) 2000-08-31 2002-05-28 Texas Instruments Incorporated Control method to reduce body diode conduction and reverse recovery losses
JP4053425B2 (en) 2001-02-06 2008-02-27 コーニンクレッカ フィリップス エレクトロニクス エヌ ヴィ Synchronous dc-dc converter

Patent Citations (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US5408150A (en) * 1992-06-04 1995-04-18 Linear Technology Corporation Circuit for driving two power mosfets in a half-bridge configuration
US5479089A (en) * 1994-12-21 1995-12-26 Hughes Aircraft Company Power converter apparatus having instantaneous commutation switching system
US6175225B1 (en) * 1999-07-02 2001-01-16 U.S. Philips Corporation Switching arrangement and switch component for a DC-DC converter
JP2001258269A (en) * 2000-03-15 2001-09-21 Kawasaki Steel Corp Soft switching dc-dc converter

Non-Patent Citations (2)

* Cited by examiner, † Cited by third party
Title
MILLS C J: "DIGITAL DEAD-TIME GENERATOR", ELECTRONIC DESIGN, PENTON PUBLISHING, CLEVELAND, OH, US, vol. 44, no. 1, 8 January 1996 (1996-01-08), pages 119 - 120, XP000551986, ISSN: 0013-4872 *
PATENT ABSTRACTS OF JAPAN vol. 2000, no. 26 1 July 2002 (2002-07-01) *

Cited By (10)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JP2007116846A (en) * 2005-10-21 2007-05-10 Fujitsu Ten Ltd Switching regulator
EP1876693A1 (en) * 2006-07-04 2008-01-09 Infineon Tehnologies AG Method for driving a transistor half-bridge
US7583111B2 (en) 2006-07-04 2009-09-01 Infineon Technologies Ag Method for driving a transistor half-bridge
DE102009010753A1 (en) * 2009-02-26 2010-09-09 Hüttinger Elektronik GmbH & Co. KG To determine the switch time point of semiconductor switches, in a plasma power supply, a control signal is used without a direct current operating voltage
DE102009010753B4 (en) * 2009-02-26 2012-09-20 Hüttinger Elektronik Gmbh + Co. Kg Method for determining the switching time of a semiconductor switch
FR2964274A1 (en) * 2010-08-26 2012-03-02 St Microelectronics Sa Converter has decoupage
US8836308B2 (en) 2010-10-28 2014-09-16 Transphorm Japan, Inc. Step-down type DC-DC regulator
US9537399B2 (en) 2011-10-19 2017-01-03 Melexis Technologies Nv Direct current control with low E-M emission
GB2513322A (en) * 2013-04-22 2014-10-29 Harvard Engineering Plc Power supply
GB2513322B (en) * 2013-04-22 2016-05-04 Harvard Eng Plc Power supply

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JP2006508629A (en) 2006-03-09 application
US7205821B2 (en) 2007-04-17 grant
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CN1717869A (en) 2006-01-04 application
CN100421353C (en) 2008-09-24 grant
DE60335961D1 (en) 2011-03-17 grant
EP1568132B1 (en) 2011-02-02 grant
US20060038545A1 (en) 2006-02-23 application

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