WO2004045108A1 - Method for implementing a function of closed loop transmitting diversity on the dedicated channel - Google Patents

Method for implementing a function of closed loop transmitting diversity on the dedicated channel Download PDF

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Publication number
WO2004045108A1
WO2004045108A1 PCT/CN2003/000948 CN0300948W WO2004045108A1 WO 2004045108 A1 WO2004045108 A1 WO 2004045108A1 CN 0300948 W CN0300948 W CN 0300948W WO 2004045108 A1 WO2004045108 A1 WO 2004045108A1
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Prior art keywords
power
phase
power offset
complex
step
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PCT/CN2003/000948
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French (fr)
Chinese (zh)
Inventor
Gang Li
Hui Zhou
Hao Wang
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Huawei Technologies Co., Ltd.
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Priority to CN 02148361 priority Critical patent/CN1278505C/en
Priority to CN02148361.2 priority
Application filed by Huawei Technologies Co., Ltd. filed Critical Huawei Technologies Co., Ltd.
Publication of WO2004045108A1 publication Critical patent/WO2004045108A1/en

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    • HELECTRICITY
    • H04ELECTRIC COMMUNICATION TECHNIQUE
    • H04BTRANSMISSION
    • H04B7/00Radio transmission systems, i.e. using radiation field
    • H04B7/02Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas
    • H04B7/04Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas
    • H04B7/06Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station
    • H04B7/0613Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station using simultaneous transmission
    • H04B7/0615Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station using simultaneous transmission of weighted versions of same signal
    • H04B7/0619Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station using simultaneous transmission of weighted versions of same signal using feedback from receiving side

Abstract

The present invention discloses a method for implementing a function of closed loop transmitting diversity on the dedicated channel, which comprises: decomposing the weighting factor of every antenna into a phase complex multiplication coefficient and a power offset term , obtaining the power offset value A_dB by the conversion of power offset term, and said phase complex multiplication coefficient is the complex number of which both real part and imaginary part are ±1 or 0; phase-modulating the framing data by using the phase complex multiplication coefficient ; getting a power amplitude value by using said power offset value A_dB, and then using the obtained power amplitude value, transmitting the phase-modulated framing data in step B via the corresponding antenna, thereby implementing the weighting function of closed loop weighting factor for downlink dedicated channel. According, this invention can simplify greatly the chip design, and satisfy preferably the accuracy requirement when occupying less the chip resource.

Description

Dedicated channel implemented method of closed loop transmit diversity function Technical Field

The present invention relates to a transmit diversity technique in a mobile communication system, more particularly to a base station in a dedicated channel to achieve the WCDMA / Universal Mobile Telecommunications System (WCDMA UMTS, Wideband Code Division Multiple Access / Universal Mobile Telecommunication System) in the closed loop transmit the method of diversity function. BACKGROUND OF THE INVENTION

The base station of the mobile communication system using two types of transmit diversity to improve performance of data transmission to the user, are open loop diversity and closed loop diversity. When closed loop transmit diversity, the base station uses two antennas transmit user information. The base station according to the feedback adjustment of the antenna user terminal (UE, User Equipment) is, UE feedback bits (FBI, Feedback Information) on an uplink dedicated physical control channel (DPCCH, Dedicated Physical Control Channel) for transmission.

Closed loop transmit diversity itself has two modes of operation. In mode 1, the feedback commands the UE to control the phase adjustment so that the maximum power is received by the UE, the base station thus maintaining constant the phase of the antenna 1, antenna 2 adjusts the phase according to a moving average of two successive feedback commands. In this mode the antenna 2 may preclude the use of four different phase settings.

In mode 2, in addition to the phase adjustment, as well as amplitude adjustment, but to use feedback command four bits, four bits of the uplink DPCCH located four slots, wherein a command to adjust an amplitude, a phase adjustment command is three. Thus there are eight different signal phases and amplitudes of two different combinations, the base station transmits a total of 16 combinations.

Wherein the closed loop diversity is only applicable to a dedicated channel and a downlink shared channel (DSCH, Downlink Shared Channel) "and the open-loop diversity is used together with a dedicated channel is used for both dedicated channel but also for the common channel. Closed loop diversity herein, loop transmit diversity, dedicated channels closed loop transmit diversity is the same concept, mode 1 and mode concept 2 have been described above in which the antennas 1 and 2 can in fact be called a main antenna and a diversity antenna, in the absence of diversity (open case or closed loop), the data is only transmitted via the antenna 1, antenna 2 no data; in the case of a diversity of, in addition to data transmitted from the antenna 1, is also transmitted from the antenna 1.

In WCDMA downlink dedicated channel modulation in the base station, need to implement the closed loop transmit diversity function. The closed loop transmit diversity function weighting factor calculation decomposed, power / phase adjustment and pilots (PILOT) pattern assigned three functions. among them:

(1) weighting factor is calculated according to the demodulated frame sent dedicated physical channel (DPCH, Dedicated Physical Channel) of the uplink FBI information corresponding to each of the current time slot is calculated weighting factor of the two antennas. DPCCH and a DPCH dedicated physical data channel (DPDCH, Dedicated Physical Data Channel) composition.

(2) Power / phase adjustment is calculated using the weighting factor, each slot of the DPCH to make a plurality of line multiplication for two days;

(3) PILOT allocation pattern refers to a closed-loop diversity mode 1, the DPCH pilot transmission line orthogonal pilot pattern in two days, and the mode 2 in the same guide two days DPCH pilot line pattern.

Wherein the processing PILOT distribution pattern is relatively simple, but the calculation of the weighting factor and the complex spreading signal weighting operation is more complex. This is because the real and imaginary part weighting factor is a fraction in many cases, greater difficulties during this complex multiplication.

DPCH support closed loop mode transmit diversity transmitter shown in Figure 1. Wherein the channel coding, interleaving, and spreading portions are the same as non-diversity mode. Multiplexed signal to spreading the two transmitting antennas, and the antenna-specific weighting factors Wl and w 2 weighting. Normally a plurality of weighting factors, i.e., \ = ^ + ^, and w 2, respectively, corresponding to the amount of phase adjustment in closed loop mode 1 and closed loop mode 2 in the phase / amplitude adjustment amount. The weighting factor is determined by the UE, using the FBI field of uplink DPCCH notification bit D field of WCDMA base station. Closed loop transmit diversity mode 1 or mode 2 which mode is specified by higher layers. In mode 1, two slots on the phase of the received weighting factor w 2 obtained after the averaging, and ^ is a constant. In mode 2, the phase information (FSM ph) received by the three slots FBI obtained power information (FSM P.) Obtained by the FBI one slot, the feedback information notified by the FBI configuration (FSM, Feedback Signalling Message) to give a phase difference and transmit power of the antenna, to calculate the weighting factor W ^ PW 2. Both have some special cases, i.e. to adjust the end of the frame, initialization, and the compressed mode. The following is a specific operation in each case.

(1) adjusting frame end

At the end of each frame, for mode 1, when receiving slot (Slot) FBI 0, not in combination with the FBI on a slot 14, but 13 in combination with an upper slot; for Mode 2, each frame of the last FSM FSM pH only three bits, without FSM P. Bit, still use on a power adjustment FSM information.

Initialization (2) closed loop diversity

After link establishment uplink DPCH (downlink DPCH has been built chain case), the UE starts transmitting the FBI Sloto, the base station 1 receives only mode Sloto the FBI, in mode 2, the three bits of the incompletely received FSM ph, press table 3 the phase is initialized not received a bit FSM P. When using the antenna as the transmission power 0.5.

(3) closed loop diversity mode is a compressed mode 2 recovery

FSM If just the uplink slot 0, 4, 8, 12 resume transmission, initializing is performed; if recovery FSM transmitted in other time slots, the transmission has a first bit FSM ph incomplete FSM in a current cycle, and two-antenna power is set to be equal; until the arrival of a new cycle of FSM, is initialized.

For mode 1, only the phase information, it is necessary for the 2bit FSM weighting factor is calculated. Feedback command FBI table uplink radio frame slot and the adjustment amount of the i-th relation shown in FIG. Phase adjustment amount may be ascertained from Table 1 FSM. FSMph 0 1 2 3 4 5 6 7 8 9 10 11 12 13 14

0 0 π / 2 0 π / 2 0 π / 2 0 π / 2 0 π / 2 0 π / 2 0 π / 2 0

1 π - π / π -π / π - π / π - π / π - π / π -π / π 1 / π

2222222

Table 1

Then (1) is calculated by the following formula 2 of the antenna weighting factor,

Σcos (^) Σsin (^.)

w-, = "■ + j

( 1 )

^ t ^ e {θ, π , π 12, -π weighting factor 12] The antenna 1 is constant:. w i = 1 /

For mode 2, by FSM P. , FSM ph calculates the transmission power of two antennas (power- antl, power- ant2) and the retardation (phase- diff) (abbreviation phase).

Table FSM P 2 is a closed loop mode 2 signaling message shown in FIG. Correspondence between the transmit power. Table FSM ph corresponding relationship between a subfield with a closed loop mode, the antenna 2 of the signaling message shown in FIG. 3 phase.

Phase (°) between the two antennas FSM ph

000 180

001-135

011-90

010-45

1100

11145

10190

After obtaining 100,135 antennas transmit power power- antl, power_ant2 phase and phase- diff, a weighting factor W is calculated by the following equation (2) ^ PW 2. power _ antl

w:

power _ antl exp (y phase- diff)

Writing (2) Equation (2) is a vector representation, Wl of the top row indicates, represents the lower row w 2.

Common design approach is based on the design requirements of accuracy, an integer register stored value after prescribing the value includes a fractional portion, additionally register designated number of decimal places. Since the closed loop transmit diversity needs to calculate the weighting factor multiplication and the spread code data, so this method during the design becomes more complicated complex multiplication. Not only particularly large amount of computation, but also takes up a lot of resources.

From the foregoing closed loop diversity weighting factor calculation formula can be seen, the general form of a complex weighting factor is Aexp (j phase_diff), phase difference values, the weighting factor may be value A, - A, Aj, - Aj, 2 - 1 2 a (1 + j ), 2- 1 2 a (l -j), 2- 1/2 a (- 1 + j), 2 a 1/2 a (- 1 - j) . A value of 0 and is 1.5 1/2 0.2 1/2 0.8 and 12. These data directly after the complex weighting factor and multiplies spreading, to take a lot of chip resources, but also more difficult to achieve. SUMMARY

In view of this, the main object of the present invention is to provide a diversity function implemented method of transmitting a dedicated channel loop in order to reduce computational complexity, reduce the occupancy of system resources.

A method for implementing a dedicated channel closed loop transmit diversity function provided by the invention, which are calculated based on feedback from the mobile terminal 1 and the antenna 2 antenna weighting factors, further comprising: A. a weighting factor of each antenna is decomposed and the phase of the complex coefficient multiplying power offset term, and in terms of a power offset term to obtain a plurality of 1 or 0 power offset A_dB, the phase of the complex coefficient multiplying real and imaginary part are ±;

B. The phase of the complex multiplication using the coefficient data set of frame phase adjustment;

C. Using the power offset acquired A-dB power amplitude value, then the power amplitude value obtained by using the framing step B is performed after the phase adjustment data emitted in the corresponding antenna.

Step A, the power offset can be taken by the term power offset to give 20 times the log.

Step C obtaining power amplitude value of the power control module calculates the dB value of the power may be power offset by subtracting the A-dB, then check the power quantization table by using a difference between the two obtained.

When the step A power offset term is 1/2 and 0.8 1 0.5 2, A-dB power offset, respectively -3.01dB and -0.97dB.

Step A power offset is a power offset term and taken to give the product of 2 n, and then multiplied by the number of 20, wherein n is an integer;

Step C acquired power amplitude value corresponding to the power control module is calculated by subtracting the value of the power dB power offset A-dB, to obtain the corresponding value of the power amplitude quantization table by using a difference between the two power search , then the power amplitude value right by n bits obtained.

Step A, the power offset term to 0.2 1/2, A-dB power offset is -0.97dB, n is 1.

Step 1 of the antenna weighting factors corresponding to the phase A complex multiplication factor of 0.

Step B may comprise:

BL, the phase of the complex coefficient multiplying all possible values ​​of binary coding, may all be determined for all values ​​of 1 or 0 according to a complex real and imaginary part are ±, total of eight;

B2, the framing data with the phase of the complex multiplier coefficients for all possible values ​​of the binary-coded multiplexing multiplication, eight kinds of results obtained;

B3, the real part of the result of eight kinds selected from sequentially input to the first plurality, a second plurality of sequentially input the imaginary part is selected, said plurality is selected from the eight selected from more than one classifier;

B4, obtained in Step A phase of the complex multiplying factor is selected as a selection signal of the first plurality and second plurality of sorter, and a first plurality of data selected from the output of the real portion of the second plurality of data selected from the output It is the imaginary part of the complex number combination of real and imaginary portions of a multiplication factor and the phase of the complex data set of frame multiplexing multiplication results after completion of the phase adjustment of the frame data set.

The present invention uses a new fixed-point optimization algorithms, as the closed loop transmit diversity scheme of key technologies, a good solution to the problems of the prior art problems. Wherein the closed-loop transmit diversity weighting factor characteristics, the phase of the complex is decomposed into a weighting factor multiplication factor, the power offset and the number of right shifts divided into three parts; Accordingly, the complex multiplication also decomposed coefficient weighting as multiple choice, power quantizing three parts list offset and shift operation, phase adjustment and power adjustment, and ultimately the effect of the closed loop diversity weighting factor for weighting the downlink dedicated channel data. Which greatly simplifies the design of the chip, while taking up less chip resources are better meet the accuracy requirements. Compared with the prior art, the method according to the present invention has the following advantages:

(1) The prior art directly using a complex weighting factor as a calculation result of the diversity of closed loop transmit, not only the hardware implementation complexity, resource-intensive, but also affects the WCDMA downlink dedicated channel modulation power control, the present invention is by weighting factor optimization of decomposition, is not only simple, but also facilitate power control of a dedicated physical channel;

Algorithm CLTD complex weighting factor (2) Since the downlink shared channel using attendant dedicated channel weighting factor of the closed loop transmit diversity, so the use of the downlink dedicated channel also simplifies the implementation of closed loop transmit diversity function downlink shared channel, easy achieve a downlink shared channel power control process. BRIEF DESCRIPTION OF DRAWINGS

Figure 1 is a schematic diagram of a closed loop transmit diversity function of the prior art;

FIG 2 phase adjustment of the antenna in FIG. 2 embodying the principles of the present disclosure. Embodiment of the present invention.

The following describe a specific implementation of the method of closed loop transmit diversity according to the present invention:

Modes 1 and 2 of the complex weighting factor may be factored into three parts:

(A) phase of the complex multiplying factor: a real and imaginary part are a plurality of C 1 or ± 0;

(b) a power offset term: a 2- 1/2 - A decimal between 2 1/2;

c) right shifts: / 2 n is determined by the demagnification l.

These three parts are different implementations:

(1) real, the imaginary part of the complex data are ± framing C and 0 or 1 when making a complex multiplication, considering the particularity of the multiplier, adder and may be employed to achieve the selector shown in Figure 2;

(2) To avoid wide multiplication, A is multiplied by the decimal implementation is as follows: A conversion rate of success in decibels A- dB (the -3.01dB <A- dB 3.01dB), check the power quantized power control module first subtracting dB power offset table before A- dB. When the WCDMA downlink physical channel modulation to achieve channel power weighted according to channel power in dB, check the power quantization table to obtain a power amplitude value of the channel, thus achieving the above-described fractional A can be completed together during this lookup operation, takes little additional resources. And the A method of extracting by between 0.5-1 l / 2 n, thus improving operation precision.

(3) Method multiplied by l / 2 n is the last needed right by n bits in the power control module. Of course, if the power is increased if there is no offset term l / 2 n times n bits to the right does not exist.

A weighting factor mode single-cylinder exploded comparison, the weighting factor of the antenna 1 \ ^ is a constant, taking the number obtained after the power offset -3.01dB, the antenna weighting factor w 2 by the equation (1) is calculated, there are four seed value, which value is determined by the 2-bit FSM command using the specific. Antenna weighting factor for the right by 2 bits and the decomposed phase of the complex coefficient multiplication of two parts, the entire antenna pattern 1 and a weighting factor decomposition of the antenna 2 shown in Table 4, it can be seen from Table 4, the antenna 2 simply weighting factor (l + j) / 2, (lj) / 2, (-l + j) / 2, - (l + j) / 2, since the data is divided by 2 is equivalent to the right of storage register a shift, right shift bits can be decomposed into a complex coefficient and phase.

Table 4

Calculation of the weighting factor for Mode 2 look-up table based on Table 2 and 3 FSM commands obtained transmit power and phase, decomposition is more complex, as shown in Table 5. Table 5 is based on a weighting factor lookup FSM commands 2 and 3, Equation 2 is calculated by the weighting factor mode 2 is obtained. 2 which in turn are divided into two cases Antenna 1 and Antenna.

The value of the weighting factor of the antenna 1 is very simple, 0.2, 0.5 or 0.8 prescribing three decimal places. Wherein 0.8 1/2 0.5 12 taken 201og operation obtained -0.97dB, i.e. 20 χ log0.8 1 2 = -. 97 and 3.01 dB, i.e. 20> <log0.5 1/2 = -3.01, and 0.2 1 / 2 direct logarithmic arithmetic value smaller, so do first treatment by 2, and then taking the operands obtained -0.97dB, i.e., 20 x log (2 0.2 1/2) = - 0.97, which right shifts respectively set to 1 to ensure that restore the original value. Weighting factor in addition to the antenna 2 decimals evolution, also multiplied by the amount of phase adjustment, the final phase of the complex multiplication can be decomposed into coefficients, right shifts, and a power offset of three parts.

Mode 2 is a weighting factor of 3 bits and 1 bit FSM ph FSM P. 4-bit FSM command is calculated, and the 2-bit mode only one FSM command, the FSM commands the antenna 1, antenna 2, the parameters in Table 5. The correspondence relation is also manifested. Mode 2 shown in Table 5 is an exploded weighting factor.

table 5

As can be seen from Table 5, in mode 2, the weighting factors Wl antennas may be decomposed into a power offset to the right and two bits of the specific value of the FSM instructions related to both of them. 2, the antenna weighting factor w 2 can be decomposed into a power offset, right shifts, and phase of the complex multiplying factor of three parts, they are also the values determined by the value of the FSM. When either mode 1 or mode 2, the antenna 2 is an exploded weighting factors will form a real and imaginary part are a plurality of C ± 1 or 0, and sets the plurality of C complex multiplication data frames, the data frame changes the group phase, so that the complex C may be referred to as phase complex multiplication factor. Suppose group represented by frame data of I + jQ, where I represents the real part, Q represents the imaginary part, taking into account the phase of the complex multiplication coefficient values, then the phase of the complex set of frame data after the multiplication result of complex coefficient multiplication only 8 possible. For ease of implementation, the phase of the complex multiplying factor encoded selection signal, a phase of the phase selection signal from 0, up to 7, is expressed in binary. Table 6 shows the correspondence table selection signal to the phase of the complex multiplication factor.

Table 6

Table 6 Relationship between the phase selection signal based on the complex multiplication calculation result can be easily achieved phase I and Q channel data adjustment circuit, as shown in FIG. As can be seen from the figure, the phase adjustment of the output data are the I I, -I, -Q, Q, I + Q, - (I + Q), QI, IQ, corresponding to the calculation result in Table 6 complex multiplication the real part; the Q output of phase adjustment data are Q, -Q, I, -1, QI, IQ, I + Q, - (I + Q) 'corresponding to the imaginary part in the complex multiplication calculation result of table 6 in . Since there is a phase 2 ^ antenna complex multiplication coefficient, only the antenna 2 is required for the phase adjustment shoving.

In the present invention, the weighting factors modes 1 and 2 are exploded boundaries formed in 2 1/2 - 2 1/2 A between decimal, the decimal A logarithmic operation by taking into values in dB A_dB, referred to as the power offset, and the right number of bits n that act on the modulated downlink dedicated channel power control module. During modulation downlink dedicated channel, the encoded data after physical framing, by channelization code spreading, and then scrambling code complex multiplication to obtain scrambled data, and finally the power output from the power control module of the scrambled after the data is modulated output. Thus, the power control of the downlink dedicated channel is an important feature point modulation, to realize the main inner loop power control, the power increase is limited and power balancing control in a power module. The output power control data directly affects the scrambling a dedicated channel. Therefore, after the power control module calculates the dedicated channel for each domain specific power dB value, it needs to be subtracted power offset loop diversity A_dB, and then check the power quantization table to obtain a corresponding power amplitude value, at which time closed-loop diversity right shift count value of the power amplitude shift processing for closed loop diversity weighting factor for the effect of the weighting data of the downlink dedicated channel.

In summary, the present invention is a closed loop transmit diversity in accordance with the characteristics of the weighting factor, the weighting factor multiplication coefficient phase of the complex is decomposed into C, power offset A- dB and three parts of n bits right; Accordingly, the complex multiplication coefficient weighting It is also divided into multiple choice, a power quantization table offset and shift operation of three parts, which greatly simplifies the design of the chip. The algorithm can also take up less chip resources better meet the accuracy requirements.

Table 7 is a power quantization table used in the present invention, in the method of the present invention, power is obtained by table look-up to 7, wherein the address includes a power value (i.e., the aforesaid power dB value) corresponding thereto, and , the values ​​for the visual representation, where the power to represent the decimal value of the amplitude, but the use of power amplitude value in the binary representation of the actual operation. Specific use is to take power amplitude value data to be transmitted to do multiplication, and then sent through an antenna. Power amplitude value determines the energy transmission data, it can be seen from Table 7, the greater the power value of the address, the smaller the value of the power amplitude, and vice versa. Case of transmit diversity, and only the transmission data of the antenna 1 is not present; and when present transmit diversity antennas 1 and 2 are to transmit data, thus requiring the power of the two antennas are decreased, referred to herein as a power amplitude value to the same only one antenna when the same transmission power. Decrease power amplitude value of the address value requires an increase in power, so in this sense, to address power value plus an offset, the previously calculated result obtained is a negative A-dB, it can subtract the negative achieve "plus" effect, that is, to achieve increased power address value, reducing the value of the power amplitude effect. Power to power the power to power amplitude to amplitude power power power to power the web address of the web site value value value value value value Address value Address value

1 7,607 46 2,083 91 570 136 156

2 7,392 47 2,024 92 554 137 152

3 7,182 48 1,967 93 539 138 147

4 6,978 49 1,911 94 523 139 143

5 6,780 50 1,857 95 508 140 139

6 6,588 51 1,804 96 494 141 135

7 6,401 52 1,753 97 480 142 131

8 6,219 53 1,703 98 466 143 128

9 6,043 54 1,655 99 453 144 124

10 5,871 55 1,608 100 440 145 121

11 5,705 56 1,562 101 428 146 117

12 5,543 57 1,518 102 416 147 114

13 5,386 58 1,475 103 404 148 111

14 5,233 59 1,433 104 392 149 107

15 5,084 60 1,392 105 381 150 104

16 4,940 61 1,353 106 370 151 101

17 62 4,800 1,314 10,736,015,299

63 18 4,664 1,277 10,835,015,396

64 19 4,531 1,241 10,934,015,493

65 20 4,403 1,206 11,033,015,590

66 21 4,278 1,171 11,132,115,688

22 67 4,157 1,138 11,231,215,785

23 4,039 68 1,106 11,330,315,883

69 24 3,924 1,075 11,429,415,981

70 25 3,813 1,044 11,528,616,078

26 71 3,705 1,014 11,627,816,176

27 3,599 7,298,611,727,016,274

28 3,497 7,395,811,826,216,372

29 3,398 7,493,111,925,516,470

30 3,302 7,590,412,024,816,568

31 3,208 7,687,812,124,116,666

32 3,117 7,785,412,223,416,764

33 3,029 7,882,912,322,716,862

34 2,943 7,980,612,422,116,960

35 2,859 8,078,312,521,417,059

36 2,778 8,176,112,620,817,157

37 2,699 8,273,912,720,217,255

38 2,623 8,371,812,819,717,354

39 2,548 84 6,981,291,911,745,240 2,476 8,567,813,018,617,551

41 2,406 8,665,913,118,017,649

42 2,337 8,764,013,217,517,748

43 2,271 88622133170178

44 2,207 89604134165179

45 2,144 90587135161180

Table 7

In the present invention, in addition to expressly indicated uplink dedicated physical channel, a dedicated channel default all referring to the downlink dedicated physical channel. Is called the uplink UE to the base station, the base station is the downlink to UE.

DPCH and an uplink sub-DPDCH DPCCH, DPDCH transmitting data, DPCCH transmits control information. Wherein the FBI field has a DPCCH, which is used to notify the base station to adjust the phase or amplitude. Each uplink dedicated physical channel frame length is 10ms, divided into 15 time slots, the length of each slot is T sl. t = 2560 chips, corresponding to one power control period.

Downlink DPDCH into DPCH and also DPCCH, DPDCH transmitting data, DPCCH transmits control information. Wherein there DPCCH TPC, TFCI, Pilot three domains. Each frame of length 10ms downlink dedicated physical channel is divided into 15 slots, each of length Tslot = 2560 chips, corresponding to one power control period.

Claims

Claims
1, a method for implementing a dedicated channel closed-loop transmission diversity function, wherein feedback information of the mobile terminal ranking calculate the antenna weighting factors 1 and antenna 2, characterized in that the method further comprises the steps of:
A. Each antenna weighting factor for the decomposition phase of the complex coefficient and multiplying a power offset terms, and the power obtained by converting the offset term power offset A-dB, the phase of the complex coefficient multiplying real and imaginary part are a plurality of ± 1 or 0;
B. The phase of the complex multiplication using the coefficient data set of frame phase adjustment;
C. Using the power offset acquired A-dB power amplitude value, then the power amplitude value obtained by using the framing step B is performed after the phase adjustment data emitted in the corresponding antenna.
2. The method according to claim 1, wherein said step A power offset is obtained by taking the power offset multiplied by the number of 20 entries.
3. The method according to claim 2, wherein the step of obtaining said C power amplitude value is a power control module calculates the dB value of power by subtracting the power offset A-dB, two reuse check the power difference value obtained by the quantization table.
4. The method according to claim 2, wherein, when step A, a power offset terms and 0.8 0.5 1 2 1/2, the power offset A- dB respectively -3.01dB and - 0.97dB.
5. The method of claim 1, wherein said step A power offset is a power offset term and the product of 2 n, the logarithm multiplied by 20 and then, where n is an integer ; step C acquired power amplitude value corresponding to the power control module is calculated by subtracting the power dB power offset value of the _ (18, utilizing the difference of both the search power quantization table to obtain the corresponding power amplitude value, then the power amplitude value right by n bits obtained.
6. The method according to claim 5, wherein said step A power offset term to 0.2 1/2, A-dB power offset is -0.97dB, n is 1.
7. The method according to claim 1, wherein step A of antenna weighting factors corresponding to a phase of the complex multiplying factor is zero.
8. The method of claim 1, wherein step B comprises:
BL, the phase of the complex coefficient multiplying all possible values ​​of binary coding, it is all possible values ​​Gen honestly, the imaginary part are ± 1 or 0 is determined for all plural, total of eight;
B2, the framing data with the phase of the complex multiplier coefficients for all possible values ​​of the binary-coded multiplexing multiplication, eight kinds of results obtained;
B3, the real part of the result of eight kinds selected from sequentially input to the first plurality, a second plurality of sequentially input the imaginary part is selected, said plurality is selected from the eight selected from more than one classifier;
B4, obtained in Step A phase of the complex multiplying factor is selected as a selection signal of the first plurality and second plurality of sorter, and a first plurality of data selected from the output of the real portion of the second plurality of data selected from the output It is the imaginary part of the complex number combination of real and imaginary portions of a multiplication factor and the phase of the complex data set of frame multiplexing multiplication results after completion of the phase adjustment of the frame data set.
PCT/CN2003/000948 2002-11-11 2003-11-11 Method for implementing a function of closed loop transmitting diversity on the dedicated channel WO2004045108A1 (en)

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US8634495B2 (en) 2001-05-31 2014-01-21 Google Inc. System, method and apparatus for mobile transmit diversity using symmetric phase difference
US7792207B2 (en) 2001-05-31 2010-09-07 Magnolia Broadband Inc. Communication device with smart antenna using a quality-indication signal
US9166665B2 (en) 2001-05-31 2015-10-20 Google Inc. System, method and apparatus for mobile transmit diversity using symmetric phase difference
US8249187B2 (en) 2002-05-09 2012-08-21 Google Inc. System, method and apparatus for mobile transmit diversity using symmetric phase difference
US7505741B2 (en) 2002-11-01 2009-03-17 Magnolia Broadband Inc. Processing diversity signals using a delay
US7418067B1 (en) 2003-04-14 2008-08-26 Magnolia Broadband Inc. Processing diversity signals at a mobile device using phase adjustments
US7430430B2 (en) 2003-12-16 2008-09-30 Magnolia Broadband Inc. Adjusting a signal at a diversity system
US7272359B2 (en) 2004-01-26 2007-09-18 Magnolia Broadband Inc. Communicating signals according to a quality indicator using multiple antenna elements
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US7783267B1 (en) 2005-06-23 2010-08-24 Magnolia Broadband Inc. Modifying a signal in response to quality indicator availability
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US7746946B2 (en) 2005-10-10 2010-06-29 Magnolia Broadband Inc. Performing a scan of diversity parameter differences
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US7796717B2 (en) 2005-11-02 2010-09-14 Magnolia Brandband Inc. Modifying a signal according to a diversity parameter adjustment
US8351882B2 (en) 2005-11-03 2013-01-08 Google Inc. Amplifying a transmit signal using a fractional power amplifier
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