WO1990013958A1

WO1990013958A1 - Receiver for quadraphase modulation signals

Info

Publication number: WO1990013958A1
Application number: PCT/NL1990/000064
Authority: WO
Inventors: Seiichi Mita; Johannes Wilhelmus Maria Bergmans
Original assignee: N.V. Philip's Gloeilampenfabrieken; Hitachi, Ltd.
Priority date: 1989-05-08
Filing date: 1990-05-07
Publication date: 1990-11-15
Also published as: EP0417272B1; US5278868A; DE69031330D1; EP0417272A1; JPH02292918A; DE69031330T2

Abstract

In a receiver of quadraphase modulation signals, a receiver of quadraphase modulation signals which is provided with two kinds of equalizers being different in each sine and cosine phases, together with and equalizer extracting a clock signal.

Description

Receiver for quadraphase modulation signals

The present invention relates to a recorder or a signal transmission apparatus, and especially to a system of transmission and reception which is excellent in a signal-to-noise ratio.

As for a system of transmission of digital signals, a system called a quadraphase modulation system has been proposed. A signal subjected to quadraphase modulation has few low-frequency components, and therefore it is suitable for the signal transmission in a system, such as a magnetic recording system and a communication system using metal wires, which does not allow low-frequency signals to pass through. This system will be summarized by using a functional block diagram of Figure 2 and a waveform diagram of Figure 3. It is assumed that data ... a_2n, ^a2n+1 • • • ^are -^"i^ven ^^{rom a} signal source to an input end of a quadraphase modulation transmitter. These data are converted into parallel data of an even-number series and an odd-number series by a serial-parallel converter and modulated simultaneously by sine modulator and a cosine modulator. When the data after modulated are denoted by ... b_4n, b_4n+1, b_4n+2, b_4n+3 ^ _{the fo}ιι_owing relationships are established. ^b4n " ^a2n ^b4n+1 ^{= a}2n+1 ^b4n+2 = ^"a2n ^b4n+3 ⁼ ~^a2n+1 (1)

As is seen from these relationships, the series of even orders of b₄_, b_4n+2 are made to correspond to the series of an even order of a _n, while the series of odd orders of b_4n+1, b_4n+3 are made to correspond to the series of an odd order of 2_n+-_| independently of the above, according to this quadraphase modulation system. When the series of the even and odd numbers of a_n are modulated independently as shown in (b) and (c) of Fig. 3 and then added up, accordingly, a waveform after subjected to quadraphase modulation as shown in (d) of Fig. 3 is obtained. In this case, 0, +1, 0 and -1 covering a period of 2T together is a fundamental waveform as shown in Figure 4(a). According to this modulation system, in other words, every two bits of input data are put in a block and coded, and therefore one period is composed of two bits. The series of (b) and (c) of Fig. 3 have a phase difference of just 90 degrees from each other in relation to this period. Therefore, the former series is called sine modulation and the latter cosine modulation.

In a receiver of quadraphase modulation, first the deterioration in a frequency characteristic caused in the course of transmission is compensated by an equalizer of Fig. 2. Then, the data are binary-coded and the waveform in (d) of Fig. 3 is restored. Next, this binary-coded waveform is discriminated and regenerated at points of ... S_4n, S_(4n+1)l S_(4n+2) ... and ... S_4n+1, S_(4n+2)+1, ^s ₍4n+1₎+2 shown in (e), and thereby data shown in (f) are obtained. These data are further passed through a parallel-serial converter, and thereby the original data shown in (g) are regenerated. The above is the gist of the quadraphase modulation system, and the further details thereof are described in IEEE Trans, on Magnetics, Vol. MAG-15, No. 6, 1465 -1467 by J.A. Bixby, etc.

The fundamental waveform for cosine modulation according to the quadraphase modulation system is 0, +1, 0 and -1 covering together the period of "2T shown in Fig. 4(a). This fundamental waveform needs to be subjected to waveform equalization so as not to cause an intersymbol interference to a code series which is sine-modulated and shifted by T/2 therefrom. According to the prior art, the equalization is conducted so that an impulse response of the above-mentioned fundamental waveform has such a waveform as shown in (b) of Fig. 4. When this impulse response is denoted by Ir(t), in other words, it is given as lr(0) = +1 Ir(-T) = -1

Ir(-nT/2) = 0 (2) where n ≠ 0 and n f 1.

An equalized waveform of sine modulation in relation to a fundamental wave is obtained likewise by shifting an equalized waveform of cosine modulation by T/2 as indicated by a dotted line. By the equalization stated above, the original pulse series can be discriminated and regenerated without any intersymbol interference at any points of ... S_4n, S₄{_n+1), S_4n+2, S_4n+3 ... as shown in Fig. 4 (c). For this purpose, accordingly, it is only required to select sampling points in series of (S _n, S_4(n+1*,), (S(_4n+1j, ^S ₍4n+1₎+1^ ^{an< otners or} sampling points in series of (S_4n+2, S_4n+3), (S_{( n+1)+2}, S_(4n+1)+3) by the procedures of (e), (f) and

(g) of Fig. 3, for instance, and to discriminate and regenerate the data of each phase.

A frequency band necessary for realizing the waveform of (b) is determined by a pulse width of a fundamental waveform. Now, since the value of the width of fundamental waveform is T/2 as shown in Fig. 4(a), a Nyquist rate is 1/T. Since the pulse width of the original signal is T, on the other hand, the Nyquist rate in this case is 1/(2T). In other words, the quadraphase modulation system necessitates a transmission band twice as wide as NRZ. Noise increases as a required band widens, and this causes a disadvantage that the number of bit errors also increases.

The present invention furnishes an optimum method of equalization of a fundamental waveform of the quadraphase modulation system and thereby solves the problem of the increase in a frequency band, which is shortcoming of this modulation system. As is seen from the equation (1), the fundamental waveform after sine modulation has the relationship of b_4n = -b _n+2 = a_2n. When either b_4n or b_4n+2 is known, therefore, the other is determined uniquely therefrom. The same can be said with regard to cosine modulation as well. Paying attention to this respect, the present invention limits the points of discrimination of data to one point for the data series of sine modulation or cosine modulation during the period of 2T (said points are two in the prior-art system), and, instead, gives an impulse response which requires a smaller band than in the prior-art system. Figure 5 shows an example of the impulse response meeting the above-stated conditions in regard to the fundamental waveform of 0, -1, 0 and +1 of cosine modulation. When this impulse response is given by Iw (t), Iw (2nT) = Iw ((2n-1/2)T)

= 0 where n f 0 Iw (-3T/2) ≠ 0 Iw (-T) 0 Iw (-T/2) = q Iw (0) = 0 Iw (T/2) = p

Iw (T) ψ 0 (3) Values E. and a give the amplitudes of the impulse response at sampling points respectively. In the case when q> p herein, the impulse response for sine modulation is obtained by inverting the time base of the fundamental waveform of cosine modulation as is seen from Fig. 5. In the case when p = q, the fundamental waverform of the cosine modulation needs only to be symmetrical with respect to points around T = 0 as shown in Fig. 6, while the fundamental waveform of the sine modulation has a shape obtained by putting forward said waveform in phase by T/2.

When the equalization is so executed as to have such an impulse response as described above, the point of the time 0, i.e. the sampling point S4_n+2, is not affected by the fundamental wave of the cosine modulation indicated by a solid line as is apparent from Figs. 5 and 6, and therefore the data series sine-modulated at this point can be discriminated and regenerated. The data series cosine-modulated at the time -T/2, i.e. the sampling point S4_n+1, is discriminated and regenerated, likewise, without being affected by the sine-modulated data series indicated by a dotted line. As the result, the data of Fig. 5(d) are discriminated and regenerated. What should be noted herein is that data of b _₊._j = a_2n+-_j are obtained at the sampling point S4_₊< and data of b_4n+2 = -a_2n at the sampling point S4_n+2. That is, the sequence of the regenerated data turns reverse. Consideration needs to be given to this respect with regard to a regenerating circuit.

While an interval between zero cross points of the prior- art impulse response given by the equation (2) is T, an interval between zero cross points of the impulse response of the equation (3) is 1.5 T, and thus it is widened in about 1.5 times or above at least. Herein the interval between zero cross points means a time interval between zero point at the time 0 of the impulse response and a zero point nearest to said point. As described above, the system of equalization according to the present invention can reduce a band necessary for transmission of the quadraphase modulation waveform to about 2/3 of that according to the prior-art system. The present invention will be described in detail hereunder with reference to Figure 1. Transmitted data are equalized first by an equalizer 1 according to the prior-art system shown in Fig 4, and the data thus equalized are divided into three and supplied to a transversal filter 2, a transversal filter 3 and a quadraphase clock signal generator 4. In the transversal filters 2 and 3, it is only required to convert the waveforms shown in Fig. 4 (b) into those shown in Fig. 5 (b). This can be realized basically by deteriorating the high- frequency characteritic of the waveforms of Fig. 4 (b) and further by giving phase distortion thereto. In other words, the coefficients of the transversal filters 2 and 3 may be given as the impulse response of the frequency characteristic obtained as the result of dividing the frequency characteristic of the impulse responses of the fundamental waveforms of Fig. 4 (b) by the frequency characteristic of the impulse response of the fundamental waveform of Fig. 5 (b). This method is known well generally. What should be noted herein is that the coefficients of the transversal filters 2 and 3 are different naturally from each other because of a difference in the impulse response between the fundamental wave of cosine modulation and that of sine modulation as shown in Fig. 5 (b) and therefore two kinds of filters need to be employed separately. Next, outputs of these filters are binary-coded at prescribed sampling points by comparators 5 and 6 respectively and supplied to a parallel- serial converter 7. In the output of this converter, data are given in the sequence of ... a_2n+1, -a_2n in everey two bits as shown in previously, and so the time base is reversed. This time base is inverted by a time base converter 8. As the result, the data are regenerated in the right sequence of ... -a _n, ^a2n+1 ••* ^However» the polarity of the signal is inverted, and therefore it is inverted again two bits apart by a signal polarity inverter 9. The original data series is restored correctly by the above processes. Besides, the coefficients of the transversal filters 2 and 3 turn identical in the symmetrical impuls responses shown in Fig. 6. Therefore a circuit having necessary characteritics can be constructed only by using one filter 10 as shown in Fig. 7.

According to the present invention, as described above, the quadraphase modulation waveform can be demodulated in a transmission band of about 2/3 of a conventioal one, and so data demodulation can be implemented with an excellent SN ratio. As the result, data communication little accompanied by a transmission error and having high reliability can be attained.

Figure 1 is a diagram showing a construction of a receiver for quadraphase modulation which is one embodiment of the present invention;

Figure 2 is a diagram showing a conventional example of a transmitter-receiver of a quadraphase modulation system;

Figure 3 is a waveform diagram of each part of the quadraphase modulation system; Figure 4 is a diagram of the quadraphase modulation system;

Figure 5 is a diagram showing an example of equalized waveforms of the quadraphase modulation system according to the present invention; Figure 6 is a diagram showing another example of equalized waveforms of the quadraphase modulation system according to the present invention; and

Figure 7 is a diagram showing another example of construction of a receiver for quadraphase modulation according to the present invention.

Claims

Claims.

1. In a receiver of quadraphase modulation signals, a receiver of quadraphase modulation signals which is provided with two kinds of equalizers being different in characteristic for each of sine and cosine phases, together with and equalizer extracting a clock signal.

2. In a receiver of quadraphase modulation signal, a receiver of quadraphase modulation signals which is provided with a time base converter inverting the time base of signals and a signal polarity converter inverting the polarity of signals in every two bits as a unit.

3. In a receiver of quadraphase modulation signals, a receiver of quadraphase modulation signals which is provided with and equalizer for regenerating data, a time base converter inverting the time base of the data and the signal polarity converter inverting the polarity of signals, in every two bits as a unit together with the equalizer extracting the clocc signal.