WO1980002779A1

WO1980002779A1 - A high repetition rate power pulse generator

Info

Publication number: WO1980002779A1
Application number: PCT/US1980/000620
Authority: WO
Inventors: F Schwarz
Original assignee: F Schwarz
Priority date: 1979-05-30
Filing date: 1980-05-27
Publication date: 1980-12-11
Also published as: EP0029067A1; EP0029067B1; ATE42432T1; DE3072153D1; EP0029067A4; US4355351A

Abstract

Class of power converters which extract electrical energy from a source of a.c. or d.c. power, transform this energy to a desired and closely controlled voltage level for use by a pulse demanding load such as a pulsed radar or laser system, without the use of a d.c. link anywhere in the converter system and without the use of low frequency power filters. Included is the description of techniques for a class of transformerless galvanic isolation between system input and output terminals and controlled voltage scaling.

Description

DESCRIPTION

A High Repetition Rate Power Pulse Generator

Technical Field

This invention relates to power converters which transform electric energy from a polyphase a.c. or a d.c. source to a recurrent train of discrete quantities of energy. These quantities of energy can be utilized in pulseforming networks which feed a pulse energy demanding load for a recurrent succession of operation. Typical loads of this kind are pulsed laser or radar systems.

Background Art

Static power converters of the kind as just described are well known in the art. One representative kind consists of a cascaded succession of: (1) a three-phase full wave rectifier; (2) a low frequency d.c. filter to smooth the remnants of the a.c. content in the rectified a.c. voltage; (3) a regulating type of d.c. to d.c. converter with a built in voltage scaling device such as a transformer; and (4) an output filter to smooth the effects of the internal operation of the aforesaid d.c. to d.c. converter. The output power of the aforesaid output filter is then used to charge. a discharge capacitor which, at times, is isolated from the above described source of supply and then connected to a pulse energy requiring load, such as a laser system. The above named power converter system performs therefore, a valuable and needed function in present day technology.

This present day state-of-the-art system also embodies the functions of passive low frequency filters to smooth the above explained a.c. ripple content of the rectified a.c. power and of a dissipative waveshaping of the charging voltage for the aforesaid charging capacitor. Furthermore, the described system requires accurate feedback control electronics to stabilize the voltage for the aforesaid discharge capacitor. Passive low frequency filters are inherently bulky, have a heavy physical weight, and are costly. The efficiency of charging capacitors via a dissipative-resistive element, is limited to 50 percent at best, the balance of energy is dissipated, or transformed to heat in the aforesaid resistive elements. Thus more energy is transformed into heat in this process than transferred for a useful purpose to the aforesaid discharge capacitor. The extent of this necessary heat dissipation in the series resistive element of a capacitor charging process is also documented in my doctorate dissertation "A Class of Nonlinear Active Filter for Electric Energy Conversion", Cornell University, 1965. The above said resistive element(s) is (are) often partially or wholly embodied in power controlling solid state elements such as power transistors. The need to let the converter's output voltage follow the replica of a reference signal, which often takes, partially, the form of a ramp function, requires close guidance of the power flow by way of a feedback control system with all of the therewith associated stability problems. These problems cause a certain degree of complexity of the electronic control system. The state-of-the-art power converters for pulsed loads, as described above, thus involve a substantial bulk of apparatus caused by low frequency filters, substantial heat development requiring adequate provisions for cooling and thus entailing physical bulk of apparatus, and substantial complexity of the electronic control system for purpose of its dynamic stabilization, and thus embodying functional hazards. Disclosure of the Invention

This invention comprises a type of power converter which transforms directly polyphase a.c. or d.c. energy to controllable trains of recurrent discrete quantities, of energy by way of interposition of a nonlinear and nondissipative resonant high frequency link between the source of supply and the pulse forming discharge capacitor. A significant part of this high frequency link comprises switch controlled series resonant circuits to provide natural commutation of switched currents, especially when thyristors are being used. This technique results in high efficiencies of power conversaion at relatively high internal switching pulse frequencies, presently in the order of up to 100 kHz. The flow of electric energy is controlled and smoothed by an active filtering process and all passive low frequency filters and the therewith associated bulk and cost are avoided.

The high internal frequency allows an output pulse repetition rate of approximately one-tenth of the internal pulse frequency, thus presently an output pulse repetition rate (PRR) in the order of 10 kHz. Accordingly, it is an object of this invention to improve the technology of power supply systems for pulse powered loads, such as laser and radar systems by the direct extraction of energy from an a.c. or d.c. source and its accurately measured nondissipative transfer to the discharge capacitor of the load's pulse forming network.

It is a further object of this invention to apply active filtering techniques for the purpose of replacing all low frequency filters which are otherwise used to suppress the ripple voltages which emanate from a.c. supply sources.

It is yet another object of this invention to apply nondissipative processes of energy transfer and voltage waveshaping in order to achieve a high efficiency of operation.

It is another further object of this invention to perform the aforesaid transfer of energy without the use of a d.c. link anywhere in the system, especially in its output circuits.

It is yet a further object of this invention to operate with a relatively high internal frequency in order to allow load pulse frequencies in excess of 10 kHz at power levels of kilowatts and beyond.

It is yet another, further object of this invention to facilitate the turn-on and turn-off of switching elements by way of their operation within internal resonant circuits. It is, furthermore, yet another object of this invention to depose a controllable, accurately measured charge on the aforesaid discharge capacitor, independent of supply line variations and variations of its power circuit component characteristics due to aging or changes of environmental conditions. It is, furthermore, yet another, further object of this invention to scale the d.c. input voltage or the apparent d.c. input voltage of an a.c. powered converter to a desired level by way of a resonant circuit which includes a LC ladder-network and without the use of an internal high voltage transformer.

Brief Description of Drawings

The above mentioned and other objects of the invention will become apparent from the following detailed description of the invention when read in conjunction with the attached drawings in which:

Fig. 1 is a block diagram of the a.c. or d.c. to discrete pulse power converter in its preferred embodiment, using direct conversion from a low power frequency to a high internal frequency by way of a cyclo-up converter, followed by a voltage sealer in the form of a high frequency power transformer-rectifier, for transfer of energy to the pulse discharge capacitor.

Fig. 2 shows the critical current and voltage waveforms of the converter for the purpose of elucidation of the novel aspects of its functional mechanism;

Fig. 3 is a block diagram of the here disclosed converter in which a capacitor multiplier is substituted for the high voltage scaling function of the power transformer.

Best Mode for Carrying Out the Invention

In the drawings, inductors, capacitors, transformers, rectifiers and controlled rectifiers are designated by conventional symbols and by reference characters L, C, XF, D and CR, with various subscripts, respectively. In the specification and claims, the reference characters for inductors, capacitors, diodes and controlled rectifiers may also be used as algebraic symbols to represent the inductance in Henrys and the capacitance in Farads of the several parts. In each case the sense of the usage will be clear from the context. The invention will be described as it is applied with the use of series resonant circuits, as shown in Fig. 1. However, this invention is not restricted to its use, as shown in Figs. 1 and 3. It is readily applied to types of systems which transfer energy from an a.c. or d.c. source of any kind to any load which requires a periodic and uniform train of pulses of electric power or a programmable aperiodic and non-uniform train of such pulses or any combination thereof. Converters employing series resonant circuits for controlled .and continuous transfer of energy are well known in the art and are described primarily in U. S. Patent 4,096,557 issued June, 1978; U. S. Patent 3,953,779 issued April 1976; my articles in the IEEE Transactions on Industrial Electronics and Control Instrumentatio IECI-17 and 23 of May 1970 and 1976, respectively; U. S. Patent 3,659,184 issued April 1972; Bedford, B. D. and Hoft, R. G., "Principles of Inverter Circuits", Wiley, New York 1964. A transformerless uncontrollable voltage sealer is described by Cockcroft, J. D., in the Proceedings of the Royal Society, Vol. 136, p. 619, London, 1932. The invention is now further described with reference to the attached figures and should be read in close context with the first two above named references. Referring now specifically to Fig. 1, the converter derives its energy from a polyphase generator 61, indicated here as a three phase sine wave supply line. The polyphase a.c. power enters the power converter via a polyphase a.c. high frequency (a.c.-h.f.) filter 62. This filter has a cut-off frequency that is lower than twice the lowest internal converter frequency, but which is approximately two orders of magnitude or more above the low frequency of the polyphase supply line. The purpose of this filter is to isolate the effects of internal converter operation from the supply lines of a.c. power. A filter of rather moderate electrical and physical size is required to suppress high frequency components of the harmonic content which is generated in the currents of the individual phases of the a.c. supply lines, and are caused by the converter operation.

The significant part of the process of extraction of energy from the polyphase supply line and its transformation to power pulses is carried out as follows. The switching matrix 63 transfers electrical power from the three phase source 61 to the series resonant circuit consisting of the capacitor C₁ and the inductor L₁. This resonant circuit is terminated in the reflection of C_o1 of the discharge capacitor C_o, which is reflected back into the resonant circuit via the output rectifier diode bridge 64 and the transformer

XF, which is identified as system element 2. The rectifier bridge 64 causes the development of a voltage V₂ on the primary winding W₁ of the transformer XF, which always opposes the direction of flow of the resonant current i₁ in the aforesaid resonant circuit. The aforesaid resonant circuit is, therefore, terminated in the reflection C_o1 = a²C_o of the output capacitor C_o, which is modified in magnitude by the square of the turns ratio N₂/N₁ = a, of the windings W₂ and W₁ of the aforesaid transformer XF, with the understanding that winding W₁ has N₁ turns and winding W₂ has N₂ turns, wound around the commonly enclosed magnetic flux path of the transformer core. The aforesaid switch matrix 63 selects at any time the phase pair with the largest voltage difference e. - e. (i,j = 1,2,3; i ≠ j), when compared to the other then prevailing phase voltage differences in the same a.c. supply system. Power is then extracted in the logically following succession from the above-identified phase pairs and used to generate the resonant current carrier i₁ as described in the first two above cited references and elucidated in the thereafter following fourth reference. A quasi-sinusoidal resonant current i₁ with a frequency in the order of 10 kHz or 100 kHz is thus generated and possibly modulated, as described in the aforesaid references and as illustrated in Fig. 2(al).

The aforesaid resonant current i₁ in winding W₁ of the transformer XF causes the flow of a current i₂= i₁/a in the winding W₂ of the same transformer. The rectified current |i₂| charges the capacitor C_o to a voltage:

where : n = the number of the successive half cycles of i₂ when countring from the time when v - 0; k = index l,2,...n for each of the n half cycles as defined above

No charge is removed from the capacitor C_o during the above described process, so that equation (1) remains valid until the just described process of charging of the capacitor C_o is altered,

The objective of the here described process is to charge capacitor C_o with a number of not more than N half cycles or pulses of the current i₂ to a nominal voltage V_o as prescribed by the requirements for the here presented converter. The voltage V_o eventually reaches, after a number of N-1 half cycles of the secondary resonant current i ₂ , a magnitude :

This means in words that the voltage v_o of the capacitor has reached after the (N-1)th cycle a magnitude v_o (N-1), which is smaller than its nominal target V_o, but that the addition of further charge contained in another half cycle of I i₂ I may cause the said voltage v_o to exceed its intended target V_o.

A mechanism is now described which secures that the said voltage vo will remain within a tolerance of ± ΔV_o of the nominal value V_o, so that at the termination of the charging time T_ch of the capacitor C_o its voltage will be within the limits :

V_o - ΔV_o < v_o (T_ch) < V_o + ΔV_o (3) where :

T_ch = t_N-1 + T_of This is illustrated in Figs. 2(d1) and 2(d2) where N-1 is arbitrarily chosen so that N-1 = 9 and thus t_n-1 = t₉.

The capacitor voltage v_o satisfies then the conditions described with the inequality (2), addition of the charge of one more half cycle of |i₂| would cause an increase of the voltage of capacitor v_o beyond its limits as defined by the inequality (3) above. The charging process is at the point in time t = t_{N - 1}; its (N-1)th cycle is illustrated as the 9th cycle in Figs. 2 (dl) and 2(d2) at the time t₉. Each of the said charging cycles corresponds to one of the one half cycles of the secondary resonant current i₂. The Nth charging cycle of the capacitor C_o is initiated notwithstanding the fact that a completion of this cycle would lead to a violation of the inequality (3) and thus fail to secure a compliance of v_o with the intended purpose, as required by this inequality (3). The voltage of the capacitor C_o thus starts to rise according to :

An instant of time T_ch = t_N-1 + T_of is eventually reached when: v_o (T_ch) = V_o - L_o li₁| (5) when

L_o = 2ε_o/i₁ ² and ε_o = the energy which will be yet conveyed to the capacitor C_o after a command to fire the thyristors CR31 and CR32 and thus to short circuit the transformer XF by way of its tertiary winding W₃ is given. The primary resonant current i₁ is monitored by a current sensor in the form of a current transformer CT as shown in Fig. 1. The resulting signal is rectified by the rectifier RCT and then conveyed to an attenuator 44, which reduces this rectified signal by an appropriate factor K_CT. The therefrom resulting signal is added in the summer 43 to the voltage v_o of capacitor C_o after its attenuation by the attenuator 41 by a factor K_o. The output of the summer 43 is then compared to a reference signal E_R by a discriminator 42. All of these system components are part of the output voltage detector and stabilizing subsystem illustrated within the block 40 of Fig. 1. The above cited constants K_CT and K_o are so dimensioned that the discriminator 42 emits a signal when the condition stated in equation (5) occurs. The aforesaid signal of the comparator 42 energizes the firing pulse generators 45 and 46 which in turn "fire" thyristors CR31 and CR32. Winding W₃ of the transformer XF is thus short-circuited and the conditions of equation (5) are satisfied provided that an appropriate quantitative relationship is established between the magnitudes of L_o, the constants K_CT and K_o, and possibly the effect of delays in the signal transmission, including the "firing" of the above identified thyristors CR31 and CR32.

The equation (5) is derived from the energy balance:

½{v_o(T_ch)}² C_o + ½ L_oi₁ ² = ½ V_o ²C_o (6)

Equation (5) follows from (6) after differentiation of

(6) and introduction of the necessary integration constant C_i = 0 since the concerned voltages v_o and V_o are identical in (5) and (6) as is the term ½L_oi₂ ² = 0 for i₁ = 0. The constant L_o is established by an analytical/experimental process, as is well known in the art. The range of tolerance, defined by the inequality (3) allows to accommodate minor variations that may be rooted in the tolerances caused by the physical structures of the concerned components. Refinements of the described process can be applied if necessary, as known to those experienced in the art. Some significant aspects of the here described process are illustrated in Figs. 2(a2), 2(b2), 2(c) and 2(d2). The current i₃ originates after thyristors CR31 and CR32 are fired as shown in Fig. 2 (c). This current i₃ satisfies Ampere's law of equal ampere-turns with respect to the current i₁. The voltage which was previously induced in winding W₂ of the transformer XF collapses therefore and the diodes DOi (1 = 1,2,3,4) in the output rectifier bridge 64 are "cut off" after the energy ε_o, as defined above, has been discharged into the output capacitor C_o. It is seen in Figs. 2(b2) and 2(a2) that the current i₂ is reduced to zero after the time interval T_ch, notwithstanding the fact that the primary resonant current i₁ continues to flow and even increases temporarily in amplitude, as qualitatively indicated in Fig. 2(a2). The option to short circuit the power transformer XF in the above described manner without causing undue stresses in the system is a unique property of the power converters employing series resonant circuits, as here described for the here intended purpose. An explanation of the therewith associated phenomena is contained in the first, second and fourth references cited above. Discharge of the capacitor C_o via its pulse demanding load at the time T_op is implied by the steep fall of the voltage v_o at that time, as illustrated in Fig. 2(d2). The converter resumes its charging process shortly thereafter as implied by the repetition of the "staircase" voltage v_o in the thereupon following time interval T_ch+1.

The individual charge intervals T_ch ≠ T_ch+1 need not to be equal, depending upon the degree of discharge of the capacitor C_o, changes in the input voltages e_i (i = 1,2,3), the respective time value of e_i - e_j as defined above, and changes of component characteristics due to aging, variations of their temperature and other related causes. Yet, the here presented mechanism will satisfy the inequality (3) independent of the above enumerated phenomena, which could otherwise cause a deviation of v_o (T_ch) from its nominal value V_o in excess of a required and predetermined limit ΔV_o. This is achieved without the use of low frequency power filters and without the use of a d.c. "link" between the converter and its load, the discharge capacitor C_o. Also, nowhere is a dissipative process of voltage wave-shaping applied.

It is obvious to those skilled in the art that one could connect a source of d.c. power to any pair of input terminals in the block 61 of Fig. 1. It is also obvious to those skilled in the art that one could then remove the capacitors C12, C13 and C23 of the input filter 62 and all but two diodes Dij (j = 1 through 6) in the block 63 of Fig. 1 if the polarity of the thus connected d.c. source is positive at the terminal marked e_i (i = 1,2) with respect to the terminal e_j (j = 2,3) with a lower index. The remaining two diodes can be shorted since they may serve no other purpose in this case. The then ensuing operation of the converter will be exactly the same as in the above described case in which the electric energy is derived from a polyphase a.c. supply source.

In another embodiment of the same invention, a power converter which can generate a recurrent sequence of high voltage pulses as explained above, is now described with reference to Fig. 3. It is assumed that the a.c. power is derived from the three phases with voltages e₁, e₂ and e₃ in block 61, as illustrated in and discussed with reference to Fig. 1. This power is then processed by the high frequency filter in block 62 as described above. The switch matrix 63 comprises diodes Dij (j = 1 through 6) which operate in conjunction with a half bridge rather than a full bridge version of the here presented converter and as described in the above cited references. The material in the above cited references teaches that the functional philosophy and the external characteristics of half and full bridge converters of the here described class are identical except for a factor of two concerning maximum current and voltage stresses in the respective switching components, even though the product of these aforesaid stresses remains constant for both versions of the here presented converter when compared at the same impedance and the same power level. Presentation of the converter in its full bridge configuration in Fig. 1 and in its half bridge configuration in Fig. 3 is, therefore, a matter of convenience and an indication of the multiplicity of possible forms of implementation.

The primary resonant circuit of Fig. 3 consists of one inductor L₁₁ and the capacitors C₁₁ and C₁₂. All of these elements are arranged in series. This aforesaid series combination also includes the one half switching bridge consisting of thyristors CR₁₁ and CR₁₂in the antiparallel diodes D₁₁ and D₁₂. The same aforesaid series combination also includes the primary winding W₁ of the low or medium voltage power transformer XF. The concept of a primary and a secondary series resonant circuit is explained in further detail with reference to Fig. 3 of the second above cited reference.

Now, continuing with the description of Fig. 3, the winding W₂ of the transformer XF and the individual loops consisting of the inductors L_o(2i-1), the diodes D_(2i-1) and the capacitors C_o(2i-1) (i = 0,1,2...N), form the path of current flow of the secondary resonant current i₂ for the condition that i₂ > 0. This current i₂ in the designated "forward" direction, here called i₂ ⁺, branches then into its components i_2,i which flow through the individual loops consisting of the corresponding elements L_oi, D_i and

C_oi, as defined above, and consistent with Kirchoff's laws when the currents i_2,i are flowing. These currents i_2,i obey, furthermore, the law that :

and (i_2,i)_av = (i_{2 ,i+2})_av (8)

provided that the individual loop impedances are dimensioned accordingly. The reverse direction i₂- of the current i₂ is analogously divided into its components i₂-_,i+1, which flow through individual loops consisting of the corresponding elements L_oi+1, D_i+1 and series configurations of c_oi.

Equations (7) and (8) hold for the elements of i₂- as much as for i₂ ⁺, with the appropriate interpretation of indici.

The ensuing process of voltage multiplication by the number N of capacitors is described in the last named above cited reference. Thus if a voltage v_o1 = aq e_s*_av develops over the first stage C_o1 of the output capacitor C_o and if this capacitor C_o consists of a series arrangement of N such capacitors C_{o( 2i- 1 )} as defined above, then

or N times the voltage v_o1 over the first stage C_o1 of the output capacitor C_o. The above cited statement, well known to those skilled in the art, has withstood the test of time. However, the then reported innovation (1) did not include the element of efficiency which is needed for power applications and cannot be implemented with the use of inefficien RC networks, as stated and substantiated at the outset of this specification. The network which is described in the last named above cited reference does not include series inductors anywhere in the system. All diodes carry, therefore, peaking currents which cause substantial dissipation in the paths of conduction of the current i₂. Furthermore did the then reported innovation (2) not include the element of controllability in the sense that the output voltage v_o need not be an integer multiple of the output voltage of a transformer winding which is connected to the points b' - c' of the discussed capacitor multiplier system. It is recalled here that the here disclosed invention includes the potential for efficient power transfer from the source of electric enerqy to the load concurrent with impedance matching or voltage scaling and output voltaqe stabilization and/or control independent of external and/or internal effects such as input voltage variations or changes of component characteristics due to aging, variations of environmental conditions and other causes which could affect the occurrence of the intended transfer of energy.

The resonant current used for the power transfer in the here disclosed invention is limited by the nondissipative resonant series impedance rather than by dissipative RC circuits of the old art. There is therefore in principle, no limit to the efficiency of power transfer. The capacitor-multiplier as described with reference to Fig. 3 is being powered from a power converter employinq series resonant circuits as described in the first, second and fourth above cited references. This class of the aforesaid power converters has the output characteristic of a controllable current source. Furthermore, these converters can be devised to function as voltaqe limited current sources by application of the appropriate feedback techniques, as is well known to those skilled in the art, and as also explained in the above cited references. The converter which is being explained with reference to Fig. 3 can therefore control the power transfer from a source of enerqy to its load, usinq its own functional mechanism, unlike the prior art.

The control mechanism enclosed in block 40 of Fig. 3 functions exactly as previously described with reference to Figs. 1 and 2. However, only one polarity of the voltage of the secondary windinq W₂ of transformer XF is now being blocked by the thyristor CR31 in the time interval T_of in order to stop a further supply of current i₂ to the capacitor multiplier for the purpose of stopping a further increase of the output voltage v_o of the converter. More explicitly, it is explained that the current i₂ ⁺ which emanates from the terminal b' of the aforesaid winding W₂ and enters the capacitor multiplier, is at the time T_ch shunted via thyristor

CR31 to the terminal c' of the same winding W₂ of the transformer XF. This current i₂ ⁺ cannot contribute from then on to a further build-up of the converter's output voltage v_o because the transformer XF is now short circuited in the i₂ ⁺ direction. The reverse direction i₂- of the current i₂ does not contribute to the increase of v_o because of the half bridge "driving" circuit of the converter. The ensuing current and voltage waveforms are an analogue of the waveforms shown in Fig. 2 except for the fact that the pushpull character of the waveforms depicted in said Fig. 2 is reduced to the effects of a half wave rectifier process. The corresponding effect and its interpretation is well known to those skilled in the art. The process of control by way of shorting transformer XF at the time T_ch is exactly the same as disclosed with reference to Figs. 1 and 2. Control via the third winding W₃ in Fig. 1 can be avoided if the thyristors CR31 and CR32 are placed there across the winding W₂ of the transformer XF. Both thyristors CR31 and CR32 are needed in that case, because of the push-pull character of the full bridge type converter of Fig. 1. The third winding W, of the transformer XF in Fig. 1 was introduced for the purpose of convenience of electronic mechanization and of explanation of a principle rather than to indicate a unique form of physical implementation.

A transformerless version of the converter of Fig. 3 is obtained if point b is connected to point b' and point c is connected to point c'. The transformer XF can then be removed and the transformer ratio a = 1. The system which ensues from the above indicated connections functions exactly as described above for a 1:1 transformer. Yet a galvanic separation of the source of electric energy and the load is retained through capacitors C₁₁ and C₁₂. The reference node of the output circuit can thus assume any voltage with respect to the reference node of the source of electric energy, provided the capacitors C₁₁ and C₁2 can withstand the concerned difference of potential in addition to the voltage excursions which are needed for the operation of these capacitors by the converter's functional mechanism. The above described galvanic isolation can be removed by connecting point d to d', thus shorting capacitor C₁₂ if so desired. The size of capacitor C₁₁ has then to be adjusted accordingly. The inductor L₁₁ can be reduced to zero if all inductors

L_o(2i-1) can be reduced to zero so that L_i1 = L₁ , or any meaningful combination thereof, as well understood to those skilled in the art. The inductance value L_o, as defined with reference to equation (5) is interpreted accordingly, as is well known to those skilled in the art.

In the writing of this specification, preferential use has been made of symbols and numbering used in the first four of the above cited references for the purpose of consistency and simplicity of notation. This includes the factor q ⋍ 1 , which can be interpreted as a roughly approximate value for the efficiency of the concerned class of converter systems.

What is claimed is:

Claims

1. A high frequency link converter for the controlled transfer of electric energy from a source of electric power to a storage element of electric energy connected to a pulse demanding load with each of its said source of electric power and said energy storage element operating with at least two power system connectors, comprising in combination: first high frequency filter means; first matrix of switch means; first capacitor means; inductor means connected to said first capacitor means forming a series resonant circuit with said first capacitor means; control set of switch means; voltage scaling means; second matrix of switch means; energy storage means; means to connect said connectors of said source via said first high frequency filter means to said first matrix of switch means; means to connect said first matrix of switch means to said series resonant circuit; means to connect said series resonant circuit via said voltage scaling means to said second matrix of switch means; means to connect said control set of switch means to said voltage scaling means; means to connect said second matrix of switch means to said energy storage means and to said load; first control means to energize selected elements of said first matrix of switch means capable to control the flow of current from said source into said resonant circuit and the exchange of energy between said resonant circuit and elements of said first high frequency filter means; said first control means including current sensor means for providing a current sensor output in accordance with the current flow relative to said first capacitor means; a current reference source; means providing a first algebraic summing output of said current sensor output and said current reference source output; integrator means for integrating said first algebraic summing output; means receiving the output of said integrator means for activating conduction of said first matrix of switch means to control the average current for each closed cycle of oscillation of operation of said resonant circuit; second control means to energize all elements of said control switch means to interrupt the flow of current from said resonant circuit to said voltage sealer as to prevent then the further accumulation of energy in said energy storage means; a voltage reference source; means for sensing of the signal indicating the state of energy of said energy storage means and providing an energy sensor output; means providing a second algebraic summing output of said energy sensor output and of said current sensor output; signal discriminator means; means to convey said second algebraic summing output and the output of said voltage reference source to said signal discriminator means which emits an output signal of its own when said second algebraic summing output exceeds the level of said voltage reference source; and means to energize all elements of said control switch means by said output signal of said discriminator.

2. A converter as set forth in claim 1, wherein said source of electric energy is a d.c. source and where a selection of means, as identified in claim 1, is further specified, but not restricted to the following: d. c. power source; first matrix of switch means; first capacitor means; voltage sealer means; inductor means connected to said first capacitor means forming a series resonant circuit with said capacitor means; a first series resonant circuit comprising said first switch means connected in series with said first capacitor means and said voltage sealer means; a second series resonant circuit comprising said second switch means, connected in series with said firstcapacitor means and said voltage sealer means; means connecting the first and the second resonant circuit across said power source; first control means enabling alternate conduction of said first and second switch means to provide alternate direction resonant current linking said source of power to said voltage sealer during alternate charging of said capacitor means; said alternate charging of said capacitor means providing alternate potentials which oppose said alternate conduction of said first and second switch means thereby alternately terminating conduction of said first and second switch means; and means connected to said first and second series resonant circuit for enabling discharge of said capacitor means between said alternate direction resonant currents to limit the voltage of said capacitor means.

3. A converter to control the transfer of power from a source of electric energy via a set of at least two power connectors to a load with intervening voltage scaling and control, comprising: a first matrix of switch means consisting of a set of passive switch means and a first and a second controllable switch means; second matrix of switch means; first set of high frequency filter means comprising a first and a second filter subset; second set of high frequency filter means; first capacitor means; inductor means to said first capacitor means forming a series resonant circuit with said first capacitor means; voltage sealer means; a first series resonant circuit comprising saidfirst switch means connected in series with said first capacitor means and said voltage sealer means; a second series resonant circuit comprising said second switch means, connected in series with said first capacitor means and said voltage sealer means; means to connect said power system connectors to said first subset of high frequency filter means and to said set of passive switch means; means to connect said set of passive switch means to said second subset of high frequency filter means and to said first and second controllable switch means; means to control said first and second controllable switch means to derive electric energy via said first subset of high frequency filter means and via said set of passive switch means from said power system connectors for the transfer of this energy to said resonant circuit and the exchange of energy with said second subset of high frequency filter means; first control means enabling alternate conduction of said first and second switch means to provide alternate direction resonant current linking said source of power to said voltage sealer during alternate charging of said capacitor means; said alternate charging of said capacitor means providing alternate potentials which oppose said alternate conduction of said first and second switch means, thereby alternately terminating conduction of said first and second switch means; means connected to said first and second series resonant circuit for enabling discharge of said capacitor means between said alternate direction resonant currents to limit the voltage of said capacitor means; means to connect said voltage sealer means to sai second matrix of switch means; and means to connect said second matrix of switch means to said second set of high frequency filter means in parallel to said load.

4. A converter as set forth in claim 1, wherein said source of electric energy is a polyphase a.c. source and where a selection of means, as identified in claim 1, is further specified, but not restricted to the following: polyphase a.c. power source; set of power source connectors; first set of high frequency filter means; capacitor means; inductor means connected to said capacitor means forming a series resonant circuit with said capacitor means; first matrix of switch means in the form of a set of controllable switch means; means to connect each of the phases of said polyphase a.c. power source to said set of controllable switch means and to said first set of high frequency filter means; means to connect said set of controllable switch means to said resonant circuit; said set of controllable switch means capable of controlling supply and return current between said set of power source connectors and said resonant circuit; control means connected for selectively energizing at least two switch means of each of said set of controllable switch means in accordance with the available potential between one pair of said power source connectors to transfer electric power from said polyphase a.c. power source to said resonant circuit through successive alternate power flows into and out of either side of said series resonant circuit and into and out of said pair of power source connectors.

5. Voltage sealer means, as identified in either claims 1, 2, or 3, consisting of high frequency power transformer means.

6. A series resonant circuit which is used in a power converter for the transfer of electric energy from a source of electric energy to a load, comprising: first and second series capacitor means; first and second series inductor means; first matrix of switch means; second matrix of switch means; second set of high frequency filter means; means to connect the terminals of said source of electric energy to said first matrix of switch means; means to provide two connecting links between the first said matrix of switch means and the second said matrix of switch means via said series capacitor and said series inductor to form one single resonant circuit whereby said first series capacitor and first series inductor means form one of the said connecting links between said matrices, the second of said series capacitor means and the second of said series inductor means form the second of said connecting links between the two said matrices of switch means so that the said connecting links provide galvanic isolation between said two matrices; means to connect said second set of high frequency filter means to said second matrix of switch means and concurrently to said load; and means to control the power flow through said resonant circuit.

7. A nominally nondissipative capacitor voltage sealer transforming a.c. current emanating from a controllable high frequency current source at one voltage level to another controllable voltage level and comprising: controllable source of a.c. current; voltage reference means; second set of filter capacitor means, consisting of a series combination of individual capacitors; set of energy pump capacitor means consisting of another series combination of individual capacitors; set of individual inductor means; second matrix of switch means consisting of individual unidirectionally conducting switches; means to connect said individual unidirectionally conducting switches to said series combinations of individual capacitors forming said second set of filter capacitor means so that pairs of two of said unidirectionally conducting switches constitute individual series combinations which are connected in parallel with each of said individual capacitors of said second set of filter capacitor means, where one terminal of each of these two said unidirectionally conducting switches is connected to one terminal of each of the said individual capacitors of said set of filter capacitor means, so that these said unidirectionally conducting switches can conduct current only against the voltage potential on each of the said individual capacitors of the second set of filter capacitor means; means to connect each junction of each of said pairs of individual unidirectionally conducting switches to the second terminal of one of said set of individual inductor means and means to connect each first terminal' of said individual inductor means to one of the individual capacitors of said set of energy pump capacitor means, staring with the junction of the pair of individual unidirectionally conducting switches which is associated with the first said individual capacitor of the set forming the second set of filter capacitor means located at the lowest voltage potential; means to connect the second terminal of the first said inductor means to the aforesaid junction of unidirectionally conducting switches and the first terminal of the same aforesaid inductor means to the lower potential terminal of the first of the individual capacitors of said set of energy pump capacitor means; means to connect the junction of said pair of unidirectionally conducting switches which parallel the second individual capacitor of said second set of filter capacitor means, which is connected to the aforesaid first capacitor of the same set, to the second terminal of a second individual inductor of said set of inductor means and to connect the first terminal of said inductor means to the junction of said first and its adjoining second individual capacitor of said set of energy pump capacitor means; means to connect, in succession, the junction of the pair of said unidirectionally conducting switch means which parallel the third individual capacitor of said second set of filter capacitor means, via a third individual inductor of said set of individual inductor means to the third individual capacitor of said set of energy pump capacitor means which adjoins said second individual capacitor of said same set and so on, until a desired number of individual capacitors in said second set of filter capacitor means is achieved to generate the desired output voltage over said second set of filter capacitors; means to connect one terminal of said controllable a.c. source to the lower potential terminal of said first individual capacitor of the second set of filter capacitor means and the second terminal of the aforesaid current source to the lower potential terminal of said first individual capacitor of said set of energy pump capacitor means; means to control the output of said current source and thus control the output current of said capacitor voltage sealer; and means to control the output voltage of said capacitor voltage sealer by the .application of means to control said controllable a.c. current source with the use of the difference of said output voltage and of said voltage reference means.

8. A system as set forth in either claims 1, 3, 6 or 7 wherein said switch means include electronic deivces.

9. A system as set forth in either claims 1, 3, 6 or 7 wherein said switch means include thyristors.

10. A system as set forth in either claims 1, 3, 6 or 7 wherein said control means include: variable reference signal means and full wave rectifier means to provide a rectified output of said variable reference signal means to serve as said current reference output.

11. A converter as set forth in claim 1, in which the means as defined in claim 3 assume the functions of the equally named means in claim 1.

12. A converter as set forth in either claims 1 or 3, in which said series resonant circuit as defined in claim 6 assumes the function of the series resonant circuit in said claims 1 or 3.

13. A converter as defined in either claims 1 or 3, in which said voltage sealer means and the therewith associated means are assumed by the means defined in claim 7.