US7664191B2 - Method of symbol detection for MIMO dual-signaling uplink CDMA systems - Google Patents
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- US7664191B2 US7664191B2 US11/191,103 US19110305A US7664191B2 US 7664191 B2 US7664191 B2 US 7664191B2 US 19110305 A US19110305 A US 19110305A US 7664191 B2 US7664191 B2 US 7664191B2
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- 238000001514 detection method Methods 0.000 title claims abstract description 50
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- 238000000034 method Methods 0.000 title claims description 22
- 238000004422 calculation algorithm Methods 0.000 claims abstract description 34
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- 238000004891 communication Methods 0.000 description 5
- 238000013461 design Methods 0.000 description 5
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- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04B—TRANSMISSION
- H04B7/00—Radio transmission systems, i.e. using radiation field
- H04B7/02—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas
- H04B7/04—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas
- H04B7/06—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station
- H04B7/0686—Hybrid systems, i.e. switching and simultaneous transmission
- H04B7/0689—Hybrid systems, i.e. switching and simultaneous transmission using different transmission schemes, at least one of them being a diversity transmission scheme
-
- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
- H04L1/00—Arrangements for detecting or preventing errors in the information received
- H04L1/0001—Systems modifying transmission characteristics according to link quality, e.g. power backoff
-
- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
- H04L1/00—Arrangements for detecting or preventing errors in the information received
- H04L1/02—Arrangements for detecting or preventing errors in the information received by diversity reception
- H04L1/06—Arrangements for detecting or preventing errors in the information received by diversity reception using space diversity
- H04L1/0618—Space-time coding
- H04L1/0637—Properties of the code
- H04L1/0643—Properties of the code block codes
-
- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
- H04L1/00—Arrangements for detecting or preventing errors in the information received
- H04L1/02—Arrangements for detecting or preventing errors in the information received by diversity reception
- H04L1/06—Arrangements for detecting or preventing errors in the information received by diversity reception using space diversity
- H04L1/0618—Space-time coding
- H04L1/0637—Properties of the code
- H04L1/0656—Cyclotomic systems, e.g. Bell Labs Layered Space-Time [BLAST]
-
- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04B—TRANSMISSION
- H04B7/00—Radio transmission systems, i.e. using radiation field
- H04B7/02—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas
- H04B7/04—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas
- H04B7/06—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station
- H04B7/0613—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station using simultaneous transmission
- H04B7/0667—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station using simultaneous transmission of delayed versions of same signal
- H04B7/0669—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station using simultaneous transmission of delayed versions of same signal using different channel coding between antennas
Definitions
- This invention relates to communication systems and, more particularly to the multi-input multi-output (MIMO) communication systems.
- MIMO multi-input multi-output
- REF. 2 1456-1467, July 1999]
- REF. 2 multiuser
- Such schemes can be directly applied to the multiuser (MU) systems yielding an MU SM system or an MU STC system.
- MU multiuser
- the data streams of all the users must be transmitted under the same mode and cannot be switched. This is very inflexible and cannot achieve the best performance for a general system link requirement and/or wide channel conditions.
- each user's data stream can be either orthogonal space-time block encoded for transmit diversity or spatially multiplexed for high spectral efficiency according to the channel conditions.
- a flexible MIMO transceiver is suggested for uplink CDMA systems over the frequency-selective channels as depicted in FIG. 1 .
- the data streams transmitted form each mobile terminal can be either spatial multiplexed (e.g., vertical Bell laboratories layered space-time, V-BLAST) for achieving high data rate or orthogonal space-time block encoded (e.g., orthogonal space-time block code, O-STBC) for transmit diversity.
- spatial multiplexed e.g., vertical Bell laboratories layered space-time, V-BLAST
- orthogonal space-time block encoded e.g., orthogonal space-time block code, O-STBC
- the received data is despread, linearly combined with the channel matrix followed by an ordered successive interference cancellation (SIC) algorithm to detect the transmitted symbols from each mobile terminal.
- SIC ordered successive interference cancellation
- the receiver could suffer from the large dimension data processing.
- the algebraic structure of the O-STBCs and through judiciously exploiting it, it can be shown that an attractive block-wise implementation of the SIC algorithm can be achieved to restore the algorithm complexity back.
- this invention proposes a 2-stage group SIC detection algorithm in the dual signaling system, and this can reduce the computational complexity.
- the proposed flexible MIMO transceiver can be applied to the B3G high-speed uplink communications.
- FIG. 1 shows the proposed receiver-transmitter configuration of this invention, in which a dual-signaling transmitter and a block-wise SIC detector is proposed.
- FIG. 2 shows the structure of a matched filter channel matrix F, of this invention.
- FIG. 3 shows the implementation of the symbol detection based on an iterative block-wise SIC algorithm with low computational complexity, which proposed in this invention.
- FIG. 4 shows the average bit error rate (BER) of SM transmission and of dual-signaling transmission
- FIG. 5 shows the average bit error rates versus signal/noise ratio (SNR) for three different detection methods in a dual-signaling system over a Ricean multiplex fading channel.
- L q P
- L q NK
- the space-time codeword matrix of the q th user can be represented as:
- a q,l ⁇ N ⁇ K is a space-time modulation matrix.
- ⁇ tilde over (s) ⁇ q,l (k): Re ⁇ s q,l (k) ⁇ when 1 ⁇ l ⁇ L q
- ⁇ tilde over (s) ⁇ q,l (k): Im ⁇ s q,l-L q (k) ⁇ when L q +1 ⁇ l ⁇ 2L q
- the space-time coded data streams of each user are spread using spreading code and transmitted from N antennas through a frequency-selective fading channel with L c resolvable paths.
- the receiving end uses M ( ⁇ N) antennas.
- y(k) ⁇ C M(G+L C ⁇ 1) be the received chip-sampled space-time data vector at the k th symbol period, where G is a Spreading Factor. Due to the time latency caused by STBC transmission signal, the inventors collecting y(k) during the interval of K consecutive symbols yields the following space-time data matrix (suppose Q users are symbol synchronized).
- H q ⁇ M(G+Lc — 1) ⁇ N is the MIMO channel matrix from q th user to receiving end
- H q includes the effect of spread spectrum code, and is static and constant during the interval of K consecutive symbols.
- V(k) ⁇ C M(G+Lc ⁇ 1) ⁇ K is the matrix of the channel noise matrix.
- the inventors propose to use an equivalent vectorized linear model.
- the inventors re-number the NK symbols s q,l (k) of each SM user (i.e., q ⁇ S M ), so that the n th data group s q,l (k) of K th symbol, for (n ⁇ 1)K+1 ⁇ l ⁇ nK, can be transmitted from the n th antenna.
- H c ⁇ 2KM(G+L c l) ⁇ 2LT is the equivalent overall (Q users) MIMO channel matrix
- s c ( k ): [ ⁇ tilde over (s) ⁇ 1 T ( k ) . . . ⁇ tilde over (s) ⁇ Q T ( k )] T ⁇ 2L T
- (5) is the symbol vector transmitted by all user terminals
- v c (k) is the resulting noise item.
- the F matrix have an appealing structure.
- the inventors collect the all elements in F first, and then put them all together to examine how F is actually like. Based on the characteristics of a channel, the data stream of each user can be processed by STBC to obtain the transmit diversity, or by SM to obtain high spectrum efficiency. This leads to two signal prototypes, one for a particular signaling. Besides, among all interference signatures, there are three distinct canonical building blocks need to be identified: two of which reflect the “intra-class” interference between each pair of distinct SM or STBC users, and the other is for the “inter-class” user interference.
- F p,q is a sub-matrix of F, representing the interference signature between the p th and the q th user's data streams. Therefore, if F p,q ⁇ • P ⁇ P if p, q ⁇ S •D , F p,q ⁇ • NP ⁇ NP if p, q ⁇ S •M , and F p,q ⁇ • P ⁇ NP if p ⁇ S •D and q ⁇ S •M .
- Zero-Forcing Law The inventors shall first consider the Zero-Forcing (ZF) based SIC detection algorithm, in which the optimum detection order at each iteration is found based on the maximum SNR criterion, based on REF. 1.
- Equation (8) shows that, for 1 ⁇ l ⁇ L T , the l th symbol decision statistics, that is, the l th element of s d (k) is simply the desired symbol contaminated by an additive noise e l T F ⁇ 1 v (k), where e l is the l th unit-standard vector of • L T . It is straightforward to verify that the noise power is:
- equation (9) means that the (average) SNR of l th decision channel can be completely determined by [F ⁇ 1 ] l,l , the l th diagonal element of the noise covariance matrix F ⁇ 1 .
- Smal [F ⁇ 1 ] l,l implies large SNR in the l th channel noise, and hence better detection accuracy the l th symbol decision statistics to yield.
- the optimum detection order at the initial state is obtained by searching for the index 1 ⁇ l ⁇ L T at which [F ⁇ 1 ] l,l is minimal.
- the determination of the optimal index requires the explicit knowledge of diagonal elements of F ⁇ 1 .
- each P ⁇ P block diagonal sub-matrix of X is a (non-zero) scalar multiple I P
- each P ⁇ P block off-diagonal sub-matrix of X belongs to (P).
- the detected user's signal is cancelled from the received signal (4), yielding a “modified” data model for detection at the next stage.
- H c,i is obtained from H c by removing i block(s) of P column (corresponding to the previously detected signals). Since F i is simply obtained from F by removing the i block(s) of P column and rows, we have: F i ⁇ F (L ⁇ i), (11) and F i ⁇ 1 ⁇ (L ⁇ i). (12) Based on the foregoing discussions, the inventors conclude that the block-wise detection can thus be done likewise at each iteration. The corresponding detection order and the weight matrix can be calculated in an analogue way as:
- the MMSE based SIC detector is also capable of per iteration jointly detecting a block of P symbols in essentially the same manner as in the ZF case.
- the inventors will introduce that the MMSE SIC detector can be also implemented in the same block-wise manner.
- the MMSE weight matrix minimizing E ⁇ s c (k) ⁇ W 0 T z(k) ⁇ 2 ⁇ is obtained as:
- the major calculation load of the SIC algorithm is the successive matrix intersions throughout all iterations.
- the inventors will show that how the knowledge of the imbedded structure of F and it's inverse matrix F ⁇ 1 , can further help to reduce the calculation load.
- the special structure of F there is an efficient way of finding F ⁇ 1 by solving a set of linear equations of relatively small dimensions based on the Cholesky decomposition.
- the inverse matrix required at each iteration can be calculated based on the parameters available in the previous stage.
- G and E are L T ⁇ L matrices whose j th columns are the (jP) th columns of F ⁇ 1 and I LT respectively.
- G and E are L T ⁇ L matrices whose j th columns are the (jP) th columns of F ⁇ 1 and I LT respectively.
- the Hermitian property of F ⁇ 1 moreover limits the number of the “actual” non-zero unknowns in each g j .
- Equation (20) thus provides a simple recursive formula for calculating F i ⁇ 1 , based on the block of sub-matrices F i-1 and F i-1 ⁇ 1 , without any “direct” matrix inversion operations.
- the overall low-complexity implementation of F i for 1 ⁇ i ⁇ L ⁇ 1, is illustrated in FIG. 3 .
- the above recursive approach for calculating F i ⁇ 1 can basically be deemed as a block based implementation of the method in [“A fast recursive algorithm for optimum sequential signal detection in a BLAST system,” IEEE trans. Signal Processing, vol. 51, no. 7, pp. 1722-1730, July 2003] introduced for the conventional symbol-wise SIC algorithm.
- the receiver could suffer from a large dimension data processing through the conventional symbol-wise SIC algorithm [“A fast recursive algorithm for optimum sequential signal detection in a BLAST system”, IEEE trans. Signal Processing, vol. 51, no, 7, pp. 1722-1730, July 2003].
- a “two-stage group SIC” detector is proposed to suggest that it could first detect the group of those STBC streams by the block-wise SIC algorithm mentioned above since they may appear to be relatively robust to channel conditions. With this done, by removing the detected STBC streams from the data y c (k), the SIC algorithm can turn back to the conventional symbol-wise realization for recovering the group of remaining SM streams.
- the corresponding detection order of the 2-stage group SIC algorithm may not be actually optimal leading to a possible performance loss. It is also noticed that even in the optimal order sorting, the symbol-wise SIC algorithm, in fact, can be done as all the STBC streams have been detected.
- FIG. 5 shows the average BER of the three detection methods.
- the SIC based solution and the Naguib's method which is basically a PIC scheme combined with an ML-based sorting mechanism, attain roughly the same performance.
- the ML ordering search of the Naguib's method suffers from large computational load, especially when the number of users, or symbol constellation size, is large.
- the Stamouli's method which relies on some linear transformation to each time decouple a user's signal from the data for detection, incurs a performance loss. This is because, unlike the proposed SIC solution, in which the involved nulling-and-cancellation procedures can increase the receive diversity order layer after layer, the Stamouli's decoupling-based approach merely retains an identical diversity order for each layer.
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Abstract
Description
Symbol Notations: |
1 | de-multiplexer | ||
2 | space-time encoder | ||
3 | spread spectrum code | ||
4 | spread spectrum decoder and diversity | ||
combiner (using Hc for linear combining) | |||
5 | |
||
6 | |
||
7 | orthogonal matrix | ||
8 | implementation of low complexity | ||
detection algorithm (1st iteration) | |||
9 | implementation of low complexity | ||
detection algorithm (2nd iteration) | |||
10 | implementation of low complexity | ||
detection algorithm (Lth iteration) | |||
M | mobile station | ||
S | base station | ||
TD | transmitted multi-users' data stream | ||
MD | multi-input multi-output channel matrix H | ||
DD | detected multi-users' data stream | ||
L T :=PQ D +NKQ M (1)
wherein Hqε M(G+Lc
- (A1) The symbol data stream sq(k), for 1≦q≦Q are i.i.d with zero mean and variance is σs 2.
- (A2) Each element of noise V(k) is spatially and temporally white with zero mean and variance σν 2.
- (A 3) Suppose that at least one user's data is transmitted by STBC mode, and hence QD≧1.
- (A 4) Suppose N≦4, hence the length of symbol block is Pε{2,4}, based on
REF 2.
y c(k):=[{tilde over (y)} T(k) . . . {tilde over (y)} T(k+K−1)]T =H c s c(k)+v c(k), (4)
s c(k):=[{tilde over (s)} 1 T(k) . . . {tilde over (s)} Q T(k)]Tε 2L
is the symbol vector transmitted by all user terminals, vc(k) is the resulting noise item. Through dispreading and linearly combing for yc(k) with channel matrix Hc, a Matched-Filtered (MF) data vector can be obtained as follows.
z(k):=H c T y c(k)=Fs c(k)+
wherein
F:=H c T H cε 2L
- (1) When p, qεSD, then Fp,qε(P). And Fq,q=αqqIPo
- (2) When p, qεSM, then each of P×P sub-matrix of Fp,qε•NP×NP is a scalar multiple of IP.
- (3) When pεSD and qεSM, then each of P×P sub-matrix for Fp,qε•NP×NP is belong to (P)o
TABLE 1 |
Summary of the structure of complex-valued |
matched-filtered cross-coupling matrix Fp,q |
Complex-Valued Constellation |
N = 2 (K = 2) | N = 3 or 4 (K = 8) | ||
p, q ∈ SD | p = q : Fq,q = αqI4 | p = q : Fq,q = αqI8 |
p ≠ q : Fp,q ∈ O(4) | p ≠ q : Fp,q ∈ U(8) | |
| ||
p, q ∈ SM | | |
| | |
| | |
p ∈ SD q ∈ SM | | |
| ||
| ||
III •Block-Wise SIC SYMBOL DETECTION
s d(k):=F −1 z(k)=s c(k)+F −1
Besides, the ZF weight matrix can be calculated from the corresponding indexed columns of F−1, as W0=F−1[eP(
F i −1:=(H c,i T H c,i)−1ε (L
FiεF(L−i), (11)
and
Fi −1ε(L−i). (12)
Based on the foregoing discussions, the inventors conclude that the block-wise detection can thus be done likewise at each iteration. The corresponding detection order and the weight matrix can be calculated in an analogue way as:
FG=E, (17)
LL T g j =
F i −1 =
where Bi-1 T
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TW094115211A TWI303128B (en) | 2005-05-11 | 2005-05-11 | A method of symbol detection for mimo dual-signaling uplink cdma systems |
TW094115211 | 2005-05-11 | ||
TW94115211A | 2005-05-11 |
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Cited By (2)
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US20080159203A1 (en) * | 2006-12-29 | 2008-07-03 | Choi Yang-Seok | Wireless communications mode switching apparatus and methods |
US20100124301A1 (en) * | 2008-11-18 | 2010-05-20 | Electronics And Telecommunications Research Institute | Method for re-ordering multiple layers and detecting signal of which the layers have different modulation orders in multiple input multiple output antenna system and receiver using the same |
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KR100789289B1 (en) | 2006-11-10 | 2007-12-28 | 한국과학기술원 | Method for modified v-blast symbol detection under channel uncertainies for correlation mimo systems |
US8433359B2 (en) * | 2009-12-03 | 2013-04-30 | Intel Corporation | Uplink power control scheme |
CN102111354B (en) * | 2010-10-20 | 2013-10-23 | 东南大学 | Linear minimum mean square error (LMMSE) detection method for multiple input multiple output-orthogonal frequency division multiplexing (MIMO-OFDM) |
EP3171527B1 (en) * | 2014-07-15 | 2019-06-19 | LG Electronics Inc. | Method by which mimo receiver processes reception signal by aligning plurality of layers by re group unit |
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Title |
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A. Stamoulis, N. Al-Dhahir, et al "Further Results on Interference Cancellation and Space-Time Block Codes" Proc. 35th Asilomar Conf. Signals, Systems, and Computers, vol. 1, pp. 257-261, 2001. |
Ayman Naguib, Nambi Seshadri, et al, "Applications of Space-Time Block Codes and Interference Suppression for High Capacity and High Data Rate Wireless Systems" Proc. 32nd Asilomar Conf. Signals, Systems, and Computers, vol. 2, pp. 1803-1810 AT&T Labs, NJ, USA, IEEE 1998. |
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Cited By (4)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
US20080159203A1 (en) * | 2006-12-29 | 2008-07-03 | Choi Yang-Seok | Wireless communications mode switching apparatus and methods |
US7894382B2 (en) * | 2006-12-29 | 2011-02-22 | Intel Corporation | Wireless communications mode switching apparatus and methods |
US20100124301A1 (en) * | 2008-11-18 | 2010-05-20 | Electronics And Telecommunications Research Institute | Method for re-ordering multiple layers and detecting signal of which the layers have different modulation orders in multiple input multiple output antenna system and receiver using the same |
US8116396B2 (en) * | 2008-11-18 | 2012-02-14 | Electronics And Telecommunications Research Institute | Method for re-ordering multiple layers and detecting signal of which the layers have different modulation orders in multiple input multiple output antenna system and receiver using the same |
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TW200640178A (en) | 2006-11-16 |
US20060268809A1 (en) | 2006-11-30 |
TWI303128B (en) | 2008-11-11 |
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