US7170961B2  Method and apparatus for frequencydomain tracking of residual frequency and channel estimation offsets  Google Patents
Method and apparatus for frequencydomain tracking of residual frequency and channel estimation offsets Download PDFInfo
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 US7170961B2 US7170961B2 US10/042,780 US4278002A US7170961B2 US 7170961 B2 US7170961 B2 US 7170961B2 US 4278002 A US4278002 A US 4278002A US 7170961 B2 US7170961 B2 US 7170961B2
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 H—ELECTRICITY
 H04—ELECTRIC COMMUNICATION TECHNIQUE
 H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
 H04L27/00—Modulatedcarrier systems
 H04L27/26—Systems using multifrequency codes
 H04L27/2601—Multicarrier modulation systems
 H04L27/2647—Arrangements specific to the receiver
 H04L27/2655—Synchronisation arrangements
 H04L27/2668—Details of algorithms
 H04L27/2673—Details of algorithms characterised by synchronisation parameters

 H—ELECTRICITY
 H04—ELECTRIC COMMUNICATION TECHNIQUE
 H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
 H04L27/00—Modulatedcarrier systems
 H04L27/26—Systems using multifrequency codes
 H04L27/2601—Multicarrier modulation systems
 H04L27/2647—Arrangements specific to the receiver
 H04L27/2655—Synchronisation arrangements
 H04L27/2657—Carrier synchronisation
 H04L27/2659—Coarse or integer frequency offset determination and synchronisation

 H—ELECTRICITY
 H04—ELECTRIC COMMUNICATION TECHNIQUE
 H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
 H04L27/00—Modulatedcarrier systems
 H04L27/26—Systems using multifrequency codes
 H04L27/2601—Multicarrier modulation systems
 H04L27/2647—Arrangements specific to the receiver
 H04L27/2655—Synchronisation arrangements
 H04L27/2657—Carrier synchronisation
 H04L27/266—Fine or fractional frequency offset determination and synchronisation

 H—ELECTRICITY
 H04—ELECTRIC COMMUNICATION TECHNIQUE
 H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
 H04L27/00—Modulatedcarrier systems
 H04L27/26—Systems using multifrequency codes
 H04L27/2601—Multicarrier modulation systems
 H04L27/2647—Arrangements specific to the receiver
 H04L27/2655—Synchronisation arrangements
 H04L27/2689—Link with other circuits, i.e. special connections between synchronisation arrangements and other circuits for achieving synchronisation
 H04L27/2695—Link with other circuits, i.e. special connections between synchronisation arrangements and other circuits for achieving synchronisation with channel estimation, e.g. determination of delay spread, derivative or peak tracking
Abstract
Description
This application relates to commonly assigned copending U.S. patent application Ser. No. 09/966,419, filed Sep. 27, 2001, titled “Method and Apparatus for Channel Estimation,” by Patrick VandenameeleLepla, the disclosure of which is hereby incorporated by reference in its entirety for all purposes.
Not Applicable
Not Applicable
The present invention relates in general to communication systems, and in particular to methods and systems for improving various aspects of communication systems utilizing multicarrier transmission techniques such as orthogonal frequency division multiplexing.
Wireless personal communication devices have proliferated over the past several years. Integration of more functionality such as multimedia capabilities into these devices has created an ever increasing demand for enhanced broadband communication methodologies. Unlike satellite communication where there is a single direct path from a transmitter to a receiver, personal wireless communication devices must operate in a multipath environment. Multipath propagation is caused by the transmitted signal reflecting off of objects such as buildings, automobiles, trees, etc., that may be encountered along the signal path. This results in the receiver receiving multiple copies of the transmitted signal each having different delay, attenuation and phase shift depending on the length of the path and the material composition of the objects along the path. The interference between the multiple versions of the transmitted signal, referred to as intersymbol interference (ISI), is a common problem that can severely distort the received signal.
Orthogonal frequency division multiplexing (OFDM) is one type of multicarrier data transmission technique that has had some success in addressing ISI, distortion and other problems associated with multipath environments. OFDM divides the available spectrum into multiple carriers, each one being modulated by a low rate data stream. Multiple user access is achieved by subdividing the available bandwidth into multiple channels, that are then allocated to users. The orthogonality of the carriers refers to the fact that each carrier has an integer number of cycles over a symbol period. Due to this, the spectrum of each carrier has a zero at the center frequency of each of the other carriers in the system. This results in no interference between the carriers, allowing them to be spaced as close as theoretically possible. Each carrier in an OFDM signal has a very narrow bandwidth, thus the resulting symbol rate is low. This results in the signal having a high tolerance to multipath delay spread, as the delay spread must be very long to cause significant intersymbol interference. Coded orthogonal frequency division multiplexing (COFDM) is the same as OFDM except that forward error correction is applied to the signal before transmission. This is to overcome errors in the transmission due to lost carriers from frequency selective fading, channel noise and other propagation effects. In the description presented herein, the terms OFDM and COFDM are used interchangeably.
In OFDM the subcarrier pulse used for transmission is chosen to be rectangular. This allows the task of pulse forming and modulation to be performed by an inverse discrete Fourier transform (IDFT). IDFT is implemented very efficiently as an inverse fast Fourier transform (IFFT) which would then require only an FFT at the receiver end to reverse the process. In order to accurately reproduce the transmitted signal, the receiver must estimate and compensate for various distortions in the received signal, including channel transfer function, carrier frequency offset and clock frequency offset.
The channel transfer function reflects the effect of the propagation channel on a transmitted signal, including multipath delay effects. A number of techniques are known for estimating and compensating for the channel. Channel estimation may be performed in the receiver either in the time domain (i.e., before the receiver performs the FFT on the received signal) or in the frequency domain (i.e., after the receiver performs the FFT on the received signal). Compensation for the channel using the channel estimate is generally performed in the frequency domain.
Carrier frequency offset (CFO) arises from the finite tolerance of RF components used in the transmitter and receiver. Even though the transmitter frequency is usually known to the receiver, due to RF tolerance, the frequency at which the receiver operates may not match exactly. This offset causes a phase shift in the received signal. Additionally, in systems where the transmitter or receiver is mobile, Doppler effects may also give rise to carrier frequency offsets. In order to provide accurate reproduction of the transmitted signal, this CFOinduced phase shift must be estimated and compensated by the receiver.
Clock frequency offset (CLO) arises from a mismatch between the sampling rate at the receiver and the sampling rate at the transmitter; again, the mismatch causes a phase shift in the received signal that must be estimated and compensated by the receiver. In addition, CLO may cause synchronization errors if the receiver assigns too many or too few samples to a symbol. Some OFDM standards, such as the 802.11a standard, reduce the complexity of the clock and carrier frequency offset problem by requiring that the carrier frequency and clock frequency in the receiver be derived from the same oscillator. But these standards do not eliminate the problem since the frequency of the receiver's oscillator will in general not exactly match the frequency of a transmitter's oscillator.
A number of methods for estimating phase shifts caused by CFO and/or CLO have been proposed. Some of these methods operate on received signals in the time domain (i.e., before the FFT is performed by the receiver); these include computations based on time correlations. Others operate in the frequency domain (i.e., after the FFT is performed by the receiver) and may involve least squares or maximum likelihood computations.
Existing methods for estimating phase shifts assume that the only noise present is additive white Gaussian noise, i.e., that the noise power spectrum is independent of carrier frequency. In many implementations of OFDM, however, nonwhite noise (i.e., noise with a power spectrum that depends on frequency, such as 1/f noise) may be present due to the receiver front end electronics or other noise sources. This nonwhite noise adversely affects the existing phase estimation methods, leading to increased error rates. Thus, a need exists for a method of computing carrier frequency and clock frequency offsets that does not rely on the assumption of white noise.
The present invention provides methods and systems for efficiently implementing broadband multicarrier communication systems. In one embodiment, the invention provides a frequencydomain estimate of carrier frequency offsets that is robust against nonwhite (frequencydependent) noise. Specifically, a carrierspecific weighting factor is associated with each of the carriers of a multicarrier signal. A set of received signals and estimated channel transfer functions associated with each of the carriers are then used together with the carrierspecific weighting factors to compute a carrier frequency offset. This carrier frequency offset estimate may then be applied in a feedback loop to phasecompensate a subsequently received signal. Because greater weights are given to carriers whose frequencies include lower noise and/or carriers transmitting a known sequence of symbols, the estimate of the carrier frequency offset is improved, resulting in more reliable reproduction of a transmitted multicarrier signal by a receiver. Additionally, in embodiments where the multicarrier communication system conforms to certain standards, the carrier frequency offset estimate may be used to compute a clock frequency offset estimate. The clock frequency offset estimate may then be used to accomplish farther improvement of signal synchronization. These and other advantages flow from the methods and systems of the present invention.
According to one aspect of the present invention, in a multicarrier data communication system, a method of estimating a carrier frequency offset for a received signal is provided. The method comprises associating each of a plurality of carrierspecific weighting factors with a different one of a plurality of carriers of the multicarrier data and assigning a value to each of the plurality of carrierspecific weighting factors, the value being related to a noise power associated with the associated carrier. A carrier frequency offset estimate is then computed using the received signal, an estimate of a channel transfer function associated with the received signal, and the plurality of carrierspecific weighting factors. This carrier frequency offset estimate may then be used to phase compensate a subsequent received signal.
The values of the carrierspecific weighting factors may be assigned by measuring a noise power spectrum across the plurality of carriers, then selecting a value inversely proportional to the noise power for one of the plurality of carriers and assigning the selected value to the associated carrierspecific weighting factor. Further, in embodiments where the plurality of carriers includes a first subset of pilot carriers, which carry a known sequence of symbols, and a second subset of nonpilot carriers, a first carrierspecific weighting factor associated with one of the pilot carriers may be increased relative to a second carrierspecific weighting factor associated with one of the nonpilot carriers. Still further, in embodiments where a first carrier has an associated channel estimate that has higher reliability than a channel estimate associated with a second carrier, a first carrierspecific weighting factor associated with the first carrier may be increased relative to a second carrierspecific weighting factor associated with the second carrier.
The carrier frequency offset estimate may be computed by phasecompensating the received signal using a previous carrier frequency offset estimate; equalizing the phasecompensated signal using the estimate of the channel transfer function; computing a phase metric from the phasecompensated signal, the equalized signal, the estimate of the channel transfer function, and the plurality of carrierspecific weighting factors; computing a phase of the phase metric; and applying a loop filter to the computed phase. The phase metric may be computed by applying a threshold cutoff to the equalized signal, thereby producing a sliced signal; multiplying the phasecompensated signal for each of the plurality of carriers by the complex conjugate of the sliced signal for the carrier and by the complex conjugate of the channel estimate for the carrier, thereby obtaining a first product; multiplying the first product by the carrierspecific weight associated with the carrier, thereby obtaining a weighted product; and summing the weighted product over the plurality of carriers, thereby obtaining the phase metric.
According to another aspect of the invention, a method for processing a multicarrier signal transmitted across a channel is provided. A value is assigned to each of a plurality of carrierspecific weighting factors, each of the plurality of carrierspecific weighting factors being associated with a different one of a plurality of carriers of the multicarrier signal, and the assigned value of each carrierspecific weighting factor being related to a noise power associated with the carrier. The multicarrier signal is received and phasecompensated using a phase compensation factor, then equalized using a channel estimate. A carrier frequency offset is estimated using the phasecompensated signal, the equalized signal, the channel estimate, and the plurality of carrierspecific weighting factors. A clock frequency offset is estimated using the estimated carrier frequency offset. The phase compensation factor is updated using the estimated carrier frequency offset and the estimated clock frequency offset.
The carrier frequency offset may be estimated by computing a phase metric from the phasecompensated signal, the equalized signal, the channel estimate, and the plurality of carrierspecific weighting factors; computing a phase of the phase metric; and applying a loop filter to the computed phase. The loop filter may comprise an infinite impulse response filter. The phase metric may be computed by applying a threshold cutoff to the equalized signal, thereby producing a sliced signal; multiplying the phasecompensated signal for each of the plurality of carriers by the complex conjugate of the sliced signal for the carrier and by the complex conjugate of the channel estimate for the carrier, thereby obtaining a first product; multiplying the first product by the carrierspecific weight associated with the carrier, thereby obtaining a weighted product; and summing the weighted product over the plurality of carriers, thereby obtaining the phase metric. The clock frequency offset may be computed by multiplying the estimated carrier frequency offset by a factor inversely proportional to a carrier frequency.
According to yet another aspect of the invention, the clock frequency offset estimate may be used to provide improved synchronization of the received signal. A net time offset may be computed based on the clock offset estimate and an elapsed time. A drop instruction may be generated when the net time offset exceeds a drop threshold, the drop instruction causing a portion of the multicarrier signal to be dropped from a symbol, and an add instruction may be generated when the net time offset is below an add threshold, the add instruction causing a portion of the multicarrier signal to be added to the symbol. The elapsed time may be reset after the portion of the multicarrier signal has been added to or dropped from the symbol.
According to a further aspect of the invention, a coarse carrier frequency offset and a fine carrier frequency offset may be determined. The phase compensation factor may be updated using the coarse carrier frequency offset and the fine carrier frequency offset.
According to a still further aspect of the invention, in a multicarrier data communication system, a method of equalizing a multicarrier signal is provided. The method includes estimating a channel transfer function; compensating a received signal using a phase compensation factor, yielding a phasecompensated signal; compensating the phasecompensated signal using the estimated channel transfer function, yielding an equalized signal; estimating a phase metric using the phasecompensated signal the equalized signal, the estimated channel transfer function, and a plurality of carrierspecific weighting factors, wherein each of the carrierspecific weighting factors being associated with a different one of a plurality of carriers of the multicarrier signal and assigned a value related to a noise power associated with the carrier; estimating a carrier frequency offset using the estimated phase metric; estimating a clock frequency offset using the updated estimate of the carrier frequency offset; and updating the phase compensation factor using the estimated carrier frequency offset and the estimated clock frequency offset. The value of each of the carrierspecific weighting factors may be inversely proportional to a noise power associated with the associated carrier. Where the plurality of carriers comprises a first subset of pilot carriers and a second subset of nonpilot carriers, the carrierspecific weighting factor associated with at least one of the pilot carriers may be increased relative to the carrierspecific weighting factor associated with at least one of the nonpilot carriers.
A phase metric may be estimated by applying a threshold cutoff to the equalized signal, thereby producing a sliced signal; multiplying the phasecompensated signal for each carrier by the complex conjugate of the sliced signal for the carrier and by the complex conjugate of the estimated channel transfer function for the carrier, thereby obtaining a product; multiplying the product by the carrierspecific weight associated with the carrier, thereby obtaining a weighted product; and summing the weighted product over the plurality of carriers, thereby obtaining the phase metric.
The carrier frequency offset may be estimated by computing a phase metric from the phasecompensated signal, the equalized signal, the channel estimate, and the plurality of carrierspecific weighting factors; computing a phase of the phase metric; and applying a loop filter to the computed phase. The clock offset may be estimated by multiplying the estimated carrier frequency offset by a factor inversely proportional to the carrier frequency.
According to another aspect of the invention, in a receiver for a multicarrier data communication system, an equalizer is provided. The equalizer comprises a phase compensator configured to receive the input sample, a carrier frequency phase offset estimate, and a clock frequency phase offset estimate, and to output a phase compensated sample; a channel equalization block configured to receive a plurality of channel estimates and the phase compensated sample, and to output an equalized data sample; a carrier frequency offset estimator configured to receive the plurality of channel estimates, the phase compensated sample, and the equalized sample, and to compute and output the carrier frequency phase offset estimate using a plurality of carrierspecific weighting factors, each of the carrierspecific weighting factors being associated with a different one of a plurality of carriers of the multicarrier data and having a value related to a noise power associated with the associated carrier; and a clock frequency offset estimator configured to receive the carrier frequency phase offset estimate and compute the clock frequency phase offset estimate.
The carrier frequency offset estimator may comprise a weight source configured to output the plurality of carrierspecific weighting factors; a slicer configured to receive the equalized signal and to output a sliced signal; a phase metric updater configured to receive the plurality of channel estimates, the phasecompensated signal, the sliced signal, and the plurality of carrierdependent weights, and to compute and output a phase metric; a phase computation unit coupled to the phase metric updater and configured to compute and output a phase of the phase metric; and a loop filter coupled to the phase computation unit and configured to store a plurality of values of the phase and to compute the carrier frequency phase offset estimate. The weight source may comprise a noise estimator configured to measure a noise power spectrum.
According to yet another aspect of the invention, a multicarrier data communication system is provided. The system comprises a transmitter and a receiver. The transmitter includes a demodulator/deserializer configured to convert an input data stream into a parallel plurality of multicarrier signals; a frequencydomain to timedomain converter having an input coupled to the modulator/deserializer and configured to transform the parallel plurality of multicarrier signals from frequency domain into time domain at an output; a guard period insertion block coupled to the frequencydomain to timedomain converter and configured to insert a guard period in the output of the frequencydomain to timedomain converter; a serializer coupled to an output of the guard period insertion block and configured to perform a parallel to serial conversion on the signal; and a digitaltoanalog converter coupled to the serializer and configured to convert the digital signal into an analog signal and to transmit the analog multicarrier time domain signal across a channel. The receiver includes an analogtodigital converter coupled to receive the analog signal and configured to convert the analog signal into a digital signal; a deserializer coupled to the analogtodigital converter and configured to convert the digital signal into a plurality of parallel signals; a channel estimator coupled to an output of the deserializer and configured to compute a channel transfer function estimate; a guard period removal block coupled to an output of the channel estimator and configured to remove the guard period; a timedomain to frequencydomain converter coupled to an output of the guard period removal block; an equalizer coupled to an output of the timedomain to frequencydomain converter, configured to equalize the signal using the channel estimates and further configured to compensate for a carrier frequency offset and a clock offset using a carrier frequency offset estimate that includes a plurality of carrierspecific weighting factors, each of the carrierspecific weighting factors being associated with a different one of a plurality of carriers of the multicarrier data and having a value related to a noise power associated with the associated carrier; and a serializer/demodulator coupled to the output of the equalizer and configured to generate an output data stream.
The multicarrier data communication system may also include a preliminary carrier frequency offset estimation block coupled between the deserializer and the guard period removal block, the preliminary carrier frequency offset estimation block configured to output a preliminary estimate of carrier frequency offset. The equalizer may be configured to receive the preliminary estimate of carrier frequency offset for use in compensating for the carrier frequency offset.
The following detailed description along with the accompanying drawings will provide a better understanding of the nature and advantages of the present invention.
In one embodiment, the present invention provides an estimate of carrier frequency offset and clock frequency offset that is robust against the presence of nonwhite noise. Referring to
At the receiver end, an analogtodigital (A/D) converter 116 receives the analog signal and converts it into a digital signal. The digital timedomain signal is first deserialized by a deserializer 118. Optionally, a preliminary estimation of and compensation for carrier frequency offset (CFO) is performed by a preliminary CFO estimator 120. A number of techniques for estimating carrier frequency offset in the time domain are known in the art and may be applied in preliminary CFO estimator 120. When preliminary CFO estimator 120 is used, a preliminary CFO estimate may be provided to downstream components.
The signal is then fed into a channel estimator 122, which computes channel estimates, for instance by processing a training sequence that is embedded in the data stream at the transmitter end. One embodiment of a channel estimator 122 that can be advantageously employed in communication system 100 is described in detail in the abovecrossreferenced copending U.S. patent application Ser. No. 09/966,419, titled “Method and Apparatus for Channel Estimation.” Other channel estimators may also be used. The channel estimates are provided as an output for later use by downstream components, either by adding the channel estimates back into the data stream or by providing a separate data path (not shown). In either case, the data stream from channel estimator 122 is applied to a block 124 which determines the beginning of each symbol and removes the guard period from the timedomain signal. With the guard period removed, an FFT block 126 transforms the timedomain signal into a frequency domain signal.
An equalizer 128 receives the output of FFT block 126 and generates an equalized output signal. Equalizer 128 includes a phase estimator 130 and a phase compensator 132. Phase estimator 130 produces estimates of the carrier frequency offset and clock frequency offset, taking into account frequencydependent (nonwhite) noise in the system, as will be described further below. Phase compensator 132 uses phase estimates provided by phase estimator 130 to compensate the received signal. Equalizer 128 also performs channel equalization on the signal using the channel estimates received from channel estimator 122. The equalized signal is then serialized by a serializer 134 and demodulated by a block 136 to generate an output data stream.
It is to be understood that the data communication system as depicted in
Equalizer 128 provides phase compensation via a feedback loop. The received signal R is input to phase compensator 132, which adjusts the phase of received signal R by multiplying it by exp(j2πφ), where φ is an estimate of the total phase offset, including both carrier and clock frequency offsets. Phase compensator 132 produces a phasecompensated signal R′. Phasecompensated signals R′ are provided to phase estimator 130, which uses the signals R′ together with other data to generate a carrier frequency offset (CFO) estimate (dF) and a clock frequency offset (CLO) estimate (dClk). These estimates are in turn used by phase compensator 132 to compute total phase offset φ for compensating subsequent signals.
Phasecompensated signal R′ is also provided to a division block 205, which performs compensation for the channel transfer function by dividing the phasecompensated signal R′ by channel estimates (H) provided by a channel estimate source 210. Channel estimate source 210 may comprise a memory for storing channel estimates received from channel estimator 122 of
Phase estimator 130 receives phasecompensated signal R′, equalized signal X, and channel estimates H as inputs, and provides phase offset estimates dF and dClk to compensate phase block 132. Phase estimator 130 also receives a sliced signal ({circumflex over (X)}), which is derived from equalized signal X by slicer 215, which applies a hard threshold cutoff. Phase estimator 130 comprises CFO estimator 220 and CLO estimator 225, which will now be described in more detail.
For each carrier k, phase metric updater 305 computes a carrier phase metric component (C_{k}). In general, the phase difference between a phasecompensated sample R_{k}′ and a corresponding sliced sample {circumflex over (X)}_{k }may be obtained by multiplying R_{k}′ by the complex conjugate of {circumflex over (X)}_{k }(denoted {circumflex over (X)}_{k}*). An improved estimate of the phase offset may be obtained if phasecompensated sample R_{k}′ is first multiplied by the complex conjugate of the corresponding channel estimate H_{k }(denoted H_{k}*). This reduces any phase change introduced by the channel while giving greater weight to carriers in which the channel transfer function is large, i.e., where the signal is strongest. Thus, carrier phase metric component C_{k }is given by:
C _{k} =H _{k} *{circumflex over (X)} _{k} *R _{k}′.
Carrier phase metric components C_{k }are computed for each carrier k.
A phase metric (PM) is then computed by forming a weighted sum of carrier phase metric components C_{k}, where each C_{k }is weighted by the corresponding carrier dependent weight w_{k}:
Phase metric updater 305 provides phase metric PM as a complex number to arctan block 315. Arctan block 315 computes and outputs the phase of phase metric PM, using the wellknown property that for any complex number Z, the phase of Z is given by arctan(Im Z/Re Z), where Im Z is the imaginary part of Z and Re Z is the real part of Z.
Arctan block 315 is followed by a loop filter 320, which combines current and previously computed phase values to determine the CFO estimate dF. In one embodiment, loop filter 320 is advantageously implemented as an infinite impulse response filter, in which all previously received phase values are used, but the weight given to each value decreases with the time since receipt. Such filters are well known in the art, and it will be appreciated that an infinite impulse response filter provides stability in the feedback loop without unnecessarily compromising the responsiveness of the CFO estimate dF. However, other loop filters, such as time averaging over a fixed number of symbol periods, may also be employed.
Exemplary techniques for selecting values for the carrierdependent weights w_{k }will now be described. As stated above, for each carrier k, weight source 310 provides a carrierdependent weight w_{k }to be used in computing phase metric PM. The values of the carrierdependent weights are controlled to account for the effect of frequencydependent noise in the system, so that those carrier frequencies that are subject to greater noise are given relatively less weight in determining phase metric PM, while carrier frequencies subject to less noise are given relatively greater weight. Preferably, a noise power spectrum is estimated for the carriers k, and the values of weights w_{k }are selected to be inversely proportional to the noise power spectrum. Other relationships between noise power and weight may also be used. Although the carrierdependent weights w_{k }may be selected to be normalized (e.g., by requiring Σw_{k}=1), it will be appreciated that this is not necessary because only the phase, not the amplitude, of phase metric PM is of interest.
Numerous techniques for estimating a noise power spectrum are known in the art, and any such technique may be employed in weight source 310. For instance, in embodiments where the frequencydependent noise is dominated by noise within the receiver electronics, the noise power spectrum may be measured offchip and values for carrierdependent weights w_{k }programmed into weight source 310.
In other embodiments, carrierdependent weights w_{k }may be measured in real time from the data itself. For example,
Noise estimator 410 may also be configured to generate weights during a calibration event when no data is being transmitted over channel 114 of
Accordingly, noise estimator 410 may be configured to receive the calibration signal Calib as shown in
In addition, in some implementations of OFDM, a subset of the carriers transmit a known sequence of symbols to be used by the receiver for computing channel estimates and for other purposes. These “pilot” carriers provide reliable estimates of phase offset because the transmitted signal in each pilot carrier is known. Thus, weight source 310 or noise estimator 410 may be configured to increase the carrierdependent weights w_{k }for the pilot carriers relative to other carriers. This feature may be implemented in combination with any of the above or other methods of estimating a noise power spectrum.
As another example, in some implementations of OFDM, some of the carriers provide more reliable channel estimates than others, and the reliability of the channel estimate for each carrier is known in advance. For example, the channel estimation system and method disclosed in the abovecrossreferenced U.S. patent application Ser. No. 09/966,419 provides a channel estimate that has a known reliability distribution for the carriers. Reliability may be measured, e.g., by relative uncertainty in the channel estimate, by absolute uncertainty in the channel estimate, or by other standard measures. In such implementations, weight source 310 or noise estimator 410 may be configured to increase or decrease the carrierdependent weight w_{k }as a function of the known reliability of the channel estimate for the carrier, thereby giving greater relative weight to carriers with more reliable channel estimates. This feature may also be implemented in combination with any of the above or other methods of estimating a noise power spectrum.
It will be appreciated that the foregoing examples of a weight source do not exhaust the possibilities for estimating a noise power spectrum and computing weights. Indeed, any noise estimation technique that provides an estimate of a noise power spectrum may be used.
Returning to
CLO estimate dClk represents the difference between the sampling clock rates in the transmitter and the receiver. As described above, this difference may lead to errors if the receiver incorrectly identifies the beginning of a symbol. In some embodiments, CLO estimator 225 may be used to provide improved synchronization, as will now be described.
A signal Adropped is sent to equalizer 128 by guard period removal block 124 when it has added or dropped a signal either in response to a received add or drop command or on the basis of its internal synchronization algorithms (a number of which are known in the art). The signal Adropped is received by phase compensator 132, which then shifts the phase by one sample; the shift may be either up or down, depending on whether signal Adropped indicates an add or a drop. Signal Adropped is also provided to Add/Drop module 550, causing a reset of the elapsed time.
In many implementations, it is advantageous to perform a preliminary estimation of and compensation for CFO in the time domain, for instance via preliminary CFO block 120 of
In such an implementation, there may remain a residual CFO that is not removed by the timedomain estimation. For instance, a typical timedomain estimation algorithm cannot adequately deal with phase offsets in the presence of nonwhite noise (i.e., a noise power spectrum that depends on carrier frequency). In addition, preliminary CFO block 120 generally does not estimate or compensate for clock offset.
The phase offset estimation procedures described above are equally useful in such implementations. For example,
FCFO is provided as an input to phase compensator 632 and to CLO estimator 625. CCFO is provided as an input to CLO estimator 625. CLO estimator 625 is similar to previously described CLO estimator 225, except that the CFO estimate used is the sum of CCFO, FCFO and a residual CFO estimate dFres provided by residual CFO estimator 620. The operation of residual CFO estimator 620 is essentially the same as described above with regard to
The preliminary carrier frequency offset estimates CCFO and FCFO may also be used during system initialization. For example, in the embodiment of
The present invention thus provides various methods and systems that efficiently implement broadband multicarrier communication systems. Estimation of carrier frequency offset according to the present invention results in reduced error in the presence of nonwhite noise. In addition, the present invention provides improved synchronization by using an estimate of clock frequency offset derived from the carrier frequency offset estimate.
While a detailed description of exemplary embodiments of the invention has been presented, it will be appreciated that various alternatives, modifications, and equivalents are possible. For instance, weight source 310 may be implemented using any noise estimation technique, and its inputs and outputs may be varied accordingly. It is further to be understood that any of the functional blocks in equalizer 128 may be implemented by a combination of hardware and/or software, and that in specific implementations some or all of the functionality of some of the blocks may be combined. Also, while the techniques described herein are particularly well suited for wireless communication systems using OFDM, similar advantages can be realized when applying the same to wireline systems, and in general any system requiring compensation for phase errors induced by carrier frequency offsets. The scope of the present invention is thus not limited to the specific embodiments described, and is instead defined by the following claims and their fall breadth of equivalents.
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