US3819961A - Arrangement for generating ultrasonic oscillations - Google Patents

Arrangement for generating ultrasonic oscillations Download PDF

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Publication number
US3819961A
US3819961A US00319982A US31998273A US3819961A US 3819961 A US3819961 A US 3819961A US 00319982 A US00319982 A US 00319982A US 31998273 A US31998273 A US 31998273A US 3819961 A US3819961 A US 3819961A
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United States
Prior art keywords
oscillator
integrator
transducer
control
frequency
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Expired - Lifetime
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US00319982A
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English (en)
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R Verlet
I Bourgeois
H Daniels
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US Philips Corp
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US Philips Corp
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    • B—PERFORMING OPERATIONS; TRANSPORTING
    • B06—GENERATING OR TRANSMITTING MECHANICAL VIBRATIONS IN GENERAL
    • B06B—METHODS OR APPARATUS FOR GENERATING OR TRANSMITTING MECHANICAL VIBRATIONS OF INFRASONIC, SONIC, OR ULTRASONIC FREQUENCY, e.g. FOR PERFORMING MECHANICAL WORK IN GENERAL
    • B06B1/00—Methods or apparatus for generating mechanical vibrations of infrasonic, sonic, or ultrasonic frequency
    • B06B1/02—Methods or apparatus for generating mechanical vibrations of infrasonic, sonic, or ultrasonic frequency making use of electrical energy
    • B06B1/0207—Driving circuits
    • B06B1/0223—Driving circuits for generating signals continuous in time
    • B06B1/0238—Driving circuits for generating signals continuous in time of a single frequency, e.g. a sine-wave
    • B06B1/0246—Driving circuits for generating signals continuous in time of a single frequency, e.g. a sine-wave with a feedback signal
    • B06B1/0253—Driving circuits for generating signals continuous in time of a single frequency, e.g. a sine-wave with a feedback signal taken directly from the generator circuit
    • B—PERFORMING OPERATIONS; TRANSPORTING
    • B06—GENERATING OR TRANSMITTING MECHANICAL VIBRATIONS IN GENERAL
    • B06B—METHODS OR APPARATUS FOR GENERATING OR TRANSMITTING MECHANICAL VIBRATIONS OF INFRASONIC, SONIC, OR ULTRASONIC FREQUENCY, e.g. FOR PERFORMING MECHANICAL WORK IN GENERAL
    • B06B2201/00—Indexing scheme associated with B06B1/0207 for details covered by B06B1/0207 but not provided for in any of its subgroups
    • B06B2201/50—Application to a particular transducer type
    • B06B2201/55—Piezoelectric transducer

Definitions

  • a control circuit for a transducer comprising a tunable oscillator for driving the transducer at resonance, and a feedback loop responsive to the transducer comprising a phase detector which develops a series of pulse width modulated binary pulses, a DC. source, an integrator, and various switching means to control the tunable oscillator.
  • the invention relates to a control circuit for a transducer having a natural resonant frequency, comprising a tunable oscillator having an output circuit coupled to said transducer for applying to said transducer an alternating voltage and an alternating current to vibrate said transducer at its natural resonant frequency, said voltage and said current having a sine phase difference, control switching means having an operative and a nonoperative state, being connected to said oscillator for controlling the duration of the cycle of operation, phase detecting means coupled to said output circuit for detecting the variations in said phase difference and for developing an output signal in response to said variations.
  • the arrangement according to the invention may be utilized for transducers of the piezomagnetic and the piezoelectric type which are operated either in parallel resonance or in series resonance.
  • phase detecting means is arranged to produce an output signal in the form of a series of width modulated binary pulses, said width varying in dependance upon said variations in phase difference;
  • control circuit further comprises a dc. supply source, integrator means, means for applying the d.c.
  • F 16. 1 shows an arrangement according to the invention
  • F l0. 2 shows a modification of the arrangement shown in FIG. 1.
  • the ultrasonic energy for exciting a transducer 1 at its natural resonant frequency f of, for example, 20 kHz is derived from an amplifier 2 which is fed by an oscillator 3 at a frequency which is substantially equal to said natural resonant frequency f said transducer 1 for this purpose being connected to the output terminals 4, 5 of the amplifier 2.
  • the transducer 1 is of the piezo-electric type and is constituted by two rings la and lb of piezoelectric material on which a constant pressure is exerted by means of two end pieces 1d and l f. For this purpose these end pieces are secured to a central bolt lg.
  • the rings la and 1b are separated from each other and from the end pieces 1d and If by thin ringshaped soft copper electrodes 1h, 1k, 1m.
  • support In coupled to ground, and an amplitude transformer 1p are connected to the end piece 1 f.
  • the said natural resonant frequency of the transducer determines a longitudinal oscillation state (mode), while a transducer is obtained which has a high quality factor of, for example, 500 1,000.
  • an automatic frequency correction (AFC) loop comprising a phase detector 6 whose output circuit is coupled to a frequencydeterrnining member 7 of the oscillator 3, while a signal dependent on the voltage between the output terminals 4, 5 is applied to this phase detector on the one hand and a signal dependent on the current applied to the transducer is applied on the other hand for automatic correction of the oscillator frequency.
  • AFC automatic frequency correction
  • the signal dependent on the voltage between the output terminals 4, 5 is derived after phase shifting by means of a phase shifting network 11 from a central tap of a potential divider constituted by two resistors 8, 9 and the signal dependent on the current applied to the transducer is derived from a resistor 10.
  • the arrangement is furthermore provided with an electronically formed start-stop device 12 which in this embodiment is'shown as a switch 13 for the sake of simplicity and is provided with two contact terminals 14, 15 and which is connected to the positive terminal of a directvoltage source 16, the contact terminal 14 of said switch being coupled to the direct current circuit of the oscillator 3.
  • the oscillator is switched on by means of this switch by connecting the contact terminal 14 to the positive terminal of the voltage source and it is switched off by connecting said positive terminal to the contact terminal 15 of the switch.
  • the oscillator frequency follows the natural resonant frequency of the transducer which in turn varies as a result of the variation of a load. Due to this load variation the mutual phase difference between oscillator output current and voltage varies so that a corresponding variation of the output voltage of the phase detector is realized, which varies the oscillator frequency in such a manner that the variation of said mutual phase difference is counteracted.
  • the arrangement shown includes the phase shifting network 11 which introduces a suitable phase shift between the two input signals from the phase detector.
  • the output circuit of the phase detector 6 is connected,
  • a frequency follower arrangement (18, 19, 20, 21) provided with an integrator 18 which in this embodiment has the form of a capacitor connected to the frequency-determining element 7 of the oscillator 3.
  • the integrator 18 is connected to a first and a second control circuit 19 and 21 which apply oppositely directed control currents.
  • a switch 20 is coupled to the start-stop device 12 being connected to the first control circuit 19 said switch adjusting the integrator 18 at a given voltage value every time after the oscillator 3 is switched off, and by which voltage value the oscillator 3 is tuned through the frequencydetermining element 7 at a defined rest frequency.
  • the second control circuit 21 includes an intermittently operating switching device 33 which is controlled by a pulsatory signal generated by the phase detector 6 which to this end is formed as a pulse duration modulator.
  • the first control circuit is constituted by a current source 19 while the switch 20, likewise as the capacitor 18 operating as an integrator, is provided between the output terminals 22, 23 of the current source 19.
  • the current source 19 in this embodiment is constituted by a transistor 24, for example, of the pnp-type whose emitter is connected through an emitter resistor 25 and whose base is connected through a Zener diode 26 to the positive terminal of a direct voltage source 27.
  • the base of this transistor 24 is connected through a resistor 28 to a terminal having a fixed reference potential, in this embodiment to ground potential.
  • the output terminals 22, 23 of the current source 19 are connected to the collector of the transistor 24 and to the terminal of fixed reference potential (ground potential), respectively.
  • the Zener diode 26 operates as a stabilizing element, so that this current source applies a stabilized direct current to the capacitor 18.
  • the switch 20, provided between the output terminals 22, 23, is constituted by a transistor 29 of the npntype whose emitter circuit is connected to the output terminal 23 and whose collector circuit is connected to the output terminal 22, while for limitation of the current through transistor 29 a collector resistor 30 is included in its collector circuit.
  • the base of the transistor 29 is connected to a central tap of a potential divider constituted by a cascade arrangement of resistors 31 and 32, which cascade arrangement is provided between the contact terminal 15 of the switch 13 included in the start-stop device and a point of fixed potential (ground potential).
  • the second control circuit 21 is constituted by a transistor 33 of the npn-type whose collector is connected to the output terminal 22 of the current source 19 and whose emitter is connected through an emitter resistor 34 to the negative terminal of the direct voltage source 27.
  • the transistor 33 is intermittently operative because its base is connected to the output of the phase detector 6, constituted as a pulse duration modulator.
  • this phase detector may be formed, for example, by two Schmitt triggers one of which provides a pulse series I as a function of the value of the current through resistor 10 and the other provides a pulse series V as a function of the voltage across resistor 9.
  • pulse series are subsequently applied to a gating circuit from which exclusively an output pulse is derived when, for example, a pulse is present in the pulse series I and a pulse is absent in the pulse series V, which pulses are directly applied to the base of the transistor 33.
  • a pulse series which controls the value of the current through the transistor 33 and whose pulse duration is determined by the phase angle between oscillator output current and output voltage is derived from the output of the pulse duration modulator 6.
  • the pulse duration modulator 6 provides, for example, a pulse signal having a period of T at a pulse duration of T/2 when using the phase-shifting network 11 with a phase shift of and with a period 2T of the oscillator oscillation, so that a distinction is made between a positive and a negative phase angle between oscillator output current and output voltage by using the 90 phaseshifting network 11.
  • pulse duration of the output pulses from pulse duration modulator 6 increases, for example, if the oscillator frequency exceeds the natural resonant frequency of the transducer and this pulse duration decreases in the reverse case, but particularly it is achieved with the embodiment of the phase detector 6 as a pulse duration modulator that a variation of the phase angle between oscillator output current and output voltage becomes quickly manifest in its output signal.
  • the oscillator 3 is adjusted at a defined rest frequency every time after it is switched off. In fact, every time after the oscillator 3 is switched off, the transistor 29 becomes conducting so that the capacitor 18 is discharged to a given constant voltage resulting in a rest frequency of the transducer being defined below its natural resonant frequency.
  • the current through transistor 29 is interrupted and the direct current from the current source 19 is applied to the capacitor 18. Since the oscillator frequency at this instant of switching on is located below the said natural resonant frequency, the current through transistor 33 is mainly interrupted by the output pulses from the pulse duration modulator 6 during a period of the oscillator oscillation so that the capacitor voltage and hence the oscillator frequency and consequently the duration of the output pulses from pulse duration modulator 6 increase until for a pulse duration of T/ 2 a balanced state is established in which with an average per unit of time as much charge is applied to the capacitor 18 by current source 19 as is derived therefrom by the control circuit 21.
  • the oscillator is tuned and stabilized at the said natural resonant frequency under all circumstances; every time after switching off, the oscillator 3 is tuned through switch 20 at a fixed defined rest frequency located below the said natural resonant frequency and after it is switched on it is detuned into the direction of and tuned at the said natural resonant frequency of the transducer.
  • the steps according to the invention lead to a very good reproducibility of the operations to be performed.
  • the oscillator, after being switched on, is not stabilized at one of the many parasitic resonant frequencies of the transducer and on the other hand the rapid operation of the frequency follower arrangement and the pulse duration modulator causes an abrupt detuning of the oscillator frequency in case of an abrupt variation of the load and hence of the natural resonant frequency of the transducer so that oscillator and transducer are again tuned to the natural resonant frequency, for example, within periods of the oscillator oscillation.
  • the rapid control of the oscillator frequency realizes an accurate tuning of the oscillator at the natural frequency.
  • This accuracy is still further increased by connecting, as is shown in the embodiment, the emitter of the transistor 33 through the emitter resistor 34 to the negative terminal of the voltage source 27. It is achieved thereby that the control circuit 21 derives a current of constant value which is smaller than the charge current from the capacitor 18 even in the absence of output pulses from pulse duration modulator 6 so that a still better defined discharge current is obtained.
  • the phase error emanating from this control amounts to less than one degree.
  • the steps according to the invention not only lead to an accurate reproducibility of the ultrasonic operations, but a particularly flexible and universal arrangement is obtained because this reproducibility of the operations is maintained for all possible values of the load as well as for all possible load variations.
  • the value of the required amplitude can be adjusted in a simple manner, namely by forming the resistor 34 in the control circuit 21 as an adjustable resistor.
  • the phase angle between oscillator output current and output voltage is determined by the values of the current derived from capacitor 18 by circuit 21 so that the oscillator and hence the transducer can be operated at any suitable frequency within the resonance curve of the transducer, which frequencies within the said resonance curve each characterize a given amplitude of the mechanical oscillation of the transducer.
  • FIG. 2 shows a modification of the frequency follower arrangement which largely corresponds to that of FIG. 1. Also in this embodiment the arrangement is provided with an integrator 18 to which a first and a second control circuit are connected, while a switch 35 coupled to the start-stop device is connected to the first control circuit and the second control circuit includes the intermittently operating switching device 33.
  • the integrator is constituted by a so-called Miller integrator consisting of an operational amplifier 37 and the conventional series resistor 38, which amplifer is shunted by a capacitor 39.
  • the control current in the first control circuit flows from the positive terminal of the direct voltage source 27 through resistors 40 and 38, capacitor 39 and the operational amplifier 37 to the negative terminal of the voltage source 27, while in the second control circuit the control current flows from the emitter of transistor 33 through the operational amplifier 37, the capacitor 39 and the resistor 38 to the collector of transistor 33.
  • the base of transistor 33 is controlled by the duration-modulated output pulses from the phase detector 6.
  • the absence of such an output pulse is in this case an output voltage of zero volts and the presence is a positive output voltage.
  • These output pulses are applied through an inverter 41, a NOR-gate 42 and a resistor 43 to the base of transistor 33.
  • the base of this transistor is also connected through a resistor 44 to the negative terminal of source 27.
  • the oscillator is tuned to a defined rest frequency every time after it is switched off.
  • the terminal 15 of the start-stop device is connected at one end to the NOR-gate 42 and at the other end to the base of the switch 35 formed as a transistor.
  • Transistor 35 together with an emitter resistor 45, is connected in parallel with the operational amplifier 37 at one end and at the other end through a second switch, likewise constituted by a transistor 46 provided with an emitter resistor 47, to the positive terminal of the 'direct voltage source 27.
  • the base of transistor 46 is coupled to the terminal15 of the start-stop device.
  • the proportioning of the resistor 30 of FIG. 1 or resistor 45 of FIG. 2 can be chosen to be such that the rest frequency of the oscillator is above and in the immediate vicinity of the natural resonant frequency.
  • the arrangement may alternatively be formed with its electrical dual elements; for example, an inductor may be used instead of a capacitor in the integrator.
  • a control circuit for a transducer having a natural resonant frequency comprising a tunable oscillator having an output circuit coupled to said transducer for applying to said transducer an alternating voltage and an alternating current to vibrate said transducer at its natural resonant frequency, control switching means having an operative and a non-operative state, means connecting said control switching means to said oscillator for controlling the duration of the oscillator cycle of operation, phase detecting means coupled to said output circuit for detecting a variation in phase difference between said alternating voltage and current and for developing an output signal comprising a series of pulse width modulated binary pulses in response to said phase variation, said pulse width varying in dependance upon said variations in phase difference, a dc supply source, integrator means, means for applying the dc.
  • Apparatus for controlling the frequency of a transducer having a natural resonant frequency comprising, a tunable oscillator having an output circuit coupled to said transducer for applying to said transducer an alternating voltage and an alternating current to operate said transducer at its natural resonant frequency, control switching means having first and second states and coupled to said oscillator for controlling the on-off oscillations thereof, phase detecting means coupled to said oscillator output circuit and responsive to a phase variation between said alternating voltage and current to develop an output signal comprising pulse width modulated pulses, the pulse width being determined by the phase angle between said alternating voltage and current, integrator means coupled to said tunable oscillator to control the oscillator frequency, a source of electric energy coupled to said integrator means to derive an integrator output signal, a first switching device controlled by said control switching means and coupled to said integrator means to control the integrator output signal so that in the first state of said control switching means the oscillator is tuned to a frequency different than said natural resonant frequency
  • said integrator means comprises a capacitor
  • said first switch comprises a semiconductor control element connected in shunt with said capacitor and with said electric energy source.
  • said energy source comprises a DC source of constant current and said first and second switching devices are connected to control the capacitor charge and discharge independently of the value of the capacitor voltage, and said phase detecting means responds to a change in the phase angle between the alternating voltage and current so as to alter the capacitor voltage and hence the oscillator frequency in a direction to counteract said phase angle change.

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  • Engineering & Computer Science (AREA)
  • Mechanical Engineering (AREA)
  • Apparatuses For Generation Of Mechanical Vibrations (AREA)
  • Oscillators With Electromechanical Resonators (AREA)
  • Stabilization Of Oscillater, Synchronisation, Frequency Synthesizers (AREA)
  • Inductance-Capacitance Distribution Constants And Capacitance-Resistance Oscillators (AREA)
US00319982A 1972-01-03 1973-01-02 Arrangement for generating ultrasonic oscillations Expired - Lifetime US3819961A (en)

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NL7200003A NL7200003A (fr) 1972-01-03 1972-01-03

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JP (1) JPS527341B2 (fr)
AT (1) AT326383B (fr)
BE (1) BE793601A (fr)
CA (1) CA984955A (fr)
CH (1) CH550511A (fr)
DE (1) DE2261712C3 (fr)
FR (1) FR2167621B1 (fr)
GB (1) GB1405187A (fr)
IT (1) IT974427B (fr)
NL (1) NL7200003A (fr)
SE (1) SE375428B (fr)

Cited By (36)

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US3889166A (en) * 1974-01-15 1975-06-10 Quintron Inc Automatic frequency control for a sandwich transducer using voltage feedback
US3967143A (en) * 1974-10-10 1976-06-29 Oki Electric Industry Company, Ltd. Ultrasonic wave generator
US3968386A (en) * 1973-08-31 1976-07-06 Siemens Aktiengesellschaft Arrangement for actuating dot-producing printing elements of a mosaic printing head
US3975650A (en) * 1975-01-30 1976-08-17 Payne Stephen C Ultrasonic generator drive circuit
US4012647A (en) * 1974-01-31 1977-03-15 Ultrasonic Systems, Inc. Ultrasonic motors and converters
FR2390879A1 (fr) * 1977-05-11 1978-12-08 Siemens Ag Montage permettant la commande automatique de la frequence d'un transducteur d'emission a ultrasons
US4184092A (en) * 1977-03-08 1980-01-15 Medtronic Gmbh Drive circuits for ultrasonic tooth treatment transducers
US4227110A (en) * 1976-11-10 1980-10-07 Westinghouse Electric Corp. Transducer control system
US4264837A (en) * 1978-03-31 1981-04-28 Paul Gaboriaud Ultrasonic atomizer with automatic control circuit
US4277710A (en) * 1979-04-30 1981-07-07 Dukane Corporation Control circuit for piezoelectric ultrasonic generators
US4371816A (en) * 1975-12-30 1983-02-01 Alfred Wieser Control circuit for an ultrasonic dental scaler
US4468581A (en) * 1981-06-25 1984-08-28 Honda Giken Kogyo Kabushiki Kaisha Drive circuit for a piezoelectric resonator used in a fluidic gas angular rate sensor
US4469974A (en) * 1982-06-14 1984-09-04 Eaton Corporation Low power acoustic fuel injector drive circuit
US4684842A (en) * 1986-03-28 1987-08-04 Nagano Keiki Seisakusho, Ltd. Gas pressure transducer
US4687962A (en) * 1986-12-15 1987-08-18 Baxter Travenol Laboratories, Inc. Ultrasonic horn driving apparatus and method with active frequency tracking
EP0247752A2 (fr) * 1986-05-12 1987-12-02 Rawson, Francis Frederick Hamilton Procédé d'accord d'un dispositif ultrasonore, dispositif et machine ultrasonore pour faire un traitement ultrasonique
US5013955A (en) * 1989-06-07 1991-05-07 Nippondenso Co., Ltd. Drive system of actuator having piezoelectric device for use in motor vehicle
US5097171A (en) * 1989-10-24 1992-03-17 Nippondenso Co., Ltd. Piezo-actuator shock absorber damping force controlling system having abnormality detection function
US5113116A (en) * 1989-10-05 1992-05-12 Firma J. Eberspacher Circuit arrangement for accurately and effectively driving an ultrasonic transducer
US5637947A (en) * 1994-01-05 1997-06-10 Technologies Gmbh & Co. Branson Ultraschall Niederlassung Der Emerson Method and apparatus for operating a generator supplying a high-frequency power to an ultrasonic transducer
US5810859A (en) * 1997-02-28 1998-09-22 Ethicon Endo-Surgery, Inc. Apparatus for applying torque to an ultrasonic transmission component
US5968060A (en) * 1997-02-28 1999-10-19 Ethicon Endo-Surgery, Inc. Ultrasonic interlock and method of using the same
US5989275A (en) * 1997-02-28 1999-11-23 Ethicon Endo-Surgery, Inc. Damping ultrasonic transmission components
EP1092446A2 (fr) 1999-10-12 2001-04-18 Lifecare Designs Limited Nébuliseur
US6274963B1 (en) 1997-04-28 2001-08-14 Ethicon Endo-Surgery, Inc. Methods and devices for controlling the vibration of ultrasonic transmission components
US20020148878A1 (en) * 2001-03-21 2002-10-17 Randy Honeck Method and apparatus for linear vibration welding
US6571643B1 (en) 1998-08-13 2003-06-03 Electronics For Imaging, Inc. Ultrasound speed measurement of temperature and pressure effects
US20030192532A1 (en) * 2002-04-12 2003-10-16 Hopkins Andrew David Nebulizer
US20080209650A1 (en) * 2005-05-03 2008-09-04 Ultreo, Inc. Oral hygiene devices
WO2008113586A2 (fr) * 2007-03-19 2008-09-25 Sauer Ultrasonic Gmbh Procédé et dispositif pour la détermination d'une courbe caractéristique de fréquence et la mise en action d'un outil à ultrasons
US20120022393A1 (en) * 2010-07-22 2012-01-26 Christian Pruckner Medical treatment device
EP2453864A1 (fr) * 2009-07-17 2012-05-23 Nektar Therapeutics Systèmes et méthodes de commande de nébuliseurs étanches
CN103302015A (zh) * 2013-06-26 2013-09-18 杭州电子科技大学 一种由一路方波驱动大功率超声波换能器的电路
US9533118B2 (en) 2009-07-17 2017-01-03 Nektar Therapeutics Systems and methods for driving nebulizers
KR101740624B1 (ko) 2009-07-17 2017-05-26 넥타르 테라퓨틱스 네거티브하게 바이어싱된 밀봉된 분무기 시스템들 및 방법들
US20210255486A1 (en) * 2018-05-09 2021-08-19 Johnson & Johnson Vision Care, Inc. Electronic ophthalmic lens for measuring distance using ultrasound time-of-flight

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DE3472901D1 (en) * 1984-09-04 1988-09-01 Med Inventio Ag Power ocillator for an ultrasonic transducer
GB8522819D0 (en) * 1985-09-16 1985-10-23 Mccracken W Control of vibration energisation
JPS61115173U (fr) * 1985-12-20 1986-07-21
DD262084A1 (de) * 1987-07-08 1988-11-16 Weinert E Messgeraetewerk Schaltungsanordnung zur elektronischen anregung eines feder-masse-schwingers in seiner resonanzfrequenz
DE4035084A1 (de) * 1990-11-05 1992-05-07 Jenoptik Jena Gmbh Anordnung zum messen linearer abmessungen auf einer strukturierten oberflaeche eines messobjektes
DE102004020895B4 (de) * 2004-04-28 2012-05-24 Endress + Hauser Gmbh + Co. Kg Vorrichtung zur Bestimmung und/oder Überwachung des Füllstandes eines Mediums
MX2017013791A (es) 2015-05-08 2018-03-01 Dow Global Technologies Llc Proceso para composiciones de poliolefina espumantes usando una mezcla de azodicarbonamida/citrato como agente nucleante.
DE102016211729A1 (de) * 2016-06-29 2018-01-04 Robert Bosch Gmbh Verfahren zum Betrieb einer Ultraschallbohrmaschine

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FR1321200A (fr) * 1961-05-01 1963-03-15 Bendix Corp Générateurs ultrasonores perfectionnés
US3447051A (en) * 1965-01-13 1969-05-27 Union Special Machine Co Control circuit for electro-mechanical devices
US3472063A (en) * 1967-04-17 1969-10-14 Branson Instr Resonant sensing device

Cited By (50)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US3968386A (en) * 1973-08-31 1976-07-06 Siemens Aktiengesellschaft Arrangement for actuating dot-producing printing elements of a mosaic printing head
US3889166A (en) * 1974-01-15 1975-06-10 Quintron Inc Automatic frequency control for a sandwich transducer using voltage feedback
US4012647A (en) * 1974-01-31 1977-03-15 Ultrasonic Systems, Inc. Ultrasonic motors and converters
US3967143A (en) * 1974-10-10 1976-06-29 Oki Electric Industry Company, Ltd. Ultrasonic wave generator
US3975650A (en) * 1975-01-30 1976-08-17 Payne Stephen C Ultrasonic generator drive circuit
US4371816A (en) * 1975-12-30 1983-02-01 Alfred Wieser Control circuit for an ultrasonic dental scaler
US4227110A (en) * 1976-11-10 1980-10-07 Westinghouse Electric Corp. Transducer control system
US4184092A (en) * 1977-03-08 1980-01-15 Medtronic Gmbh Drive circuits for ultrasonic tooth treatment transducers
FR2390879A1 (fr) * 1977-05-11 1978-12-08 Siemens Ag Montage permettant la commande automatique de la frequence d'un transducteur d'emission a ultrasons
US4175242A (en) * 1977-05-11 1979-11-20 Siemens Aktiengesellschaft Circuit arrangement for the automatic frequency control of an ultrasonic transducer
US4264837A (en) * 1978-03-31 1981-04-28 Paul Gaboriaud Ultrasonic atomizer with automatic control circuit
US4277710A (en) * 1979-04-30 1981-07-07 Dukane Corporation Control circuit for piezoelectric ultrasonic generators
US4468581A (en) * 1981-06-25 1984-08-28 Honda Giken Kogyo Kabushiki Kaisha Drive circuit for a piezoelectric resonator used in a fluidic gas angular rate sensor
US4469974A (en) * 1982-06-14 1984-09-04 Eaton Corporation Low power acoustic fuel injector drive circuit
US4684842A (en) * 1986-03-28 1987-08-04 Nagano Keiki Seisakusho, Ltd. Gas pressure transducer
EP0247752A2 (fr) * 1986-05-12 1987-12-02 Rawson, Francis Frederick Hamilton Procédé d'accord d'un dispositif ultrasonore, dispositif et machine ultrasonore pour faire un traitement ultrasonique
EP0247752A3 (fr) * 1986-05-12 1988-08-03 Rawson, Francis Frederick Hamilton Procédé d'accord d'un dispositif ultrasonore, dispositif et machine ultrasonore pour faire un traitement ultrasonique
US4687962A (en) * 1986-12-15 1987-08-18 Baxter Travenol Laboratories, Inc. Ultrasonic horn driving apparatus and method with active frequency tracking
US5013955A (en) * 1989-06-07 1991-05-07 Nippondenso Co., Ltd. Drive system of actuator having piezoelectric device for use in motor vehicle
US5113116A (en) * 1989-10-05 1992-05-12 Firma J. Eberspacher Circuit arrangement for accurately and effectively driving an ultrasonic transducer
US5216338A (en) * 1989-10-05 1993-06-01 Firma J. Eberspacher Circuit arrangement for accurately and effectively driving an ultrasonic transducer
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Also Published As

Publication number Publication date
JPS4879613A (fr) 1973-10-25
BE793601A (fr) 1973-07-02
ATA1116172A (de) 1975-02-15
CH550511A (de) 1974-06-14
SE375428B (fr) 1975-04-14
FR2167621A1 (fr) 1973-08-24
JPS527341B2 (fr) 1977-03-01
DE2261712B2 (de) 1979-12-13
NL7200003A (fr) 1973-07-05
AT326383B (de) 1975-12-10
IT974427B (it) 1974-06-20
DE2261712A1 (de) 1973-07-19
DE2261712C3 (de) 1980-08-28
FR2167621B1 (fr) 1977-04-22
GB1405187A (en) 1975-09-03
CA984955A (en) 1976-03-02

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