US20040213342A1 - Method and device for improving DFE performance in a trellis-coded system - Google Patents
Method and device for improving DFE performance in a trellis-coded system Download PDFInfo
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- US20040213342A1 US20040213342A1 US10/785,499 US78549904A US2004213342A1 US 20040213342 A1 US20040213342 A1 US 20040213342A1 US 78549904 A US78549904 A US 78549904A US 2004213342 A1 US2004213342 A1 US 2004213342A1
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- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
- H04L1/00—Arrangements for detecting or preventing errors in the information received
- H04L1/004—Arrangements for detecting or preventing errors in the information received by using forward error control
- H04L1/0045—Arrangements at the receiver end
- H04L1/0054—Maximum-likelihood or sequential decoding, e.g. Viterbi, Fano, ZJ algorithms
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- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
- H04L25/00—Baseband systems
- H04L25/02—Details ; arrangements for supplying electrical power along data transmission lines
- H04L25/03—Shaping networks in transmitter or receiver, e.g. adaptive shaping networks
- H04L25/03006—Arrangements for removing intersymbol interference
- H04L25/03012—Arrangements for removing intersymbol interference operating in the time domain
- H04L25/03019—Arrangements for removing intersymbol interference operating in the time domain adaptive, i.e. capable of adjustment during data reception
- H04L25/03057—Arrangements for removing intersymbol interference operating in the time domain adaptive, i.e. capable of adjustment during data reception with a recursive structure
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- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
- H04L25/00—Baseband systems
- H04L25/02—Details ; arrangements for supplying electrical power along data transmission lines
- H04L25/03—Shaping networks in transmitter or receiver, e.g. adaptive shaping networks
- H04L25/03006—Arrangements for removing intersymbol interference
- H04L2025/0335—Arrangements for removing intersymbol interference characterised by the type of transmission
- H04L2025/03375—Passband transmission
- H04L2025/03382—Single of vestigal sideband
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- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
- H04L25/00—Baseband systems
- H04L25/02—Details ; arrangements for supplying electrical power along data transmission lines
- H04L25/03—Shaping networks in transmitter or receiver, e.g. adaptive shaping networks
- H04L25/03006—Arrangements for removing intersymbol interference
- H04L2025/03433—Arrangements for removing intersymbol interference characterised by equaliser structure
- H04L2025/03439—Fixed structures
- H04L2025/03445—Time domain
- H04L2025/03471—Tapped delay lines
- H04L2025/03484—Tapped delay lines time-recursive
- H04L2025/0349—Tapped delay lines time-recursive as a feedback filter
-
- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
- H04L25/00—Baseband systems
- H04L25/02—Details ; arrangements for supplying electrical power along data transmission lines
- H04L25/03—Shaping networks in transmitter or receiver, e.g. adaptive shaping networks
- H04L25/03006—Arrangements for removing intersymbol interference
- H04L2025/03592—Adaptation methods
- H04L2025/03598—Algorithms
- H04L2025/03611—Iterative algorithms
- H04L2025/03617—Time recursive algorithms
Definitions
- the present invention is directed in general to digital signal processing, and in particular to receiver based methods and devices for improving decision feedback equalizer (“DFE”) performance in a trellis coded system.
- DFE decision feedback equalizer
- a DFE 10 (FIG. 1) has two filter sections, a forward filter 12 and a feedback filter 16 .
- the input to the forward filter 12 is the received data which includes the transmitted symbol sequence a k , noise n k and multipath h i .
- the input to the feedback filter 16 is the quantized equalizer output â k .
- the output of both the sections are summed 18 to form the final equalizer output ⁇ k which is also the input to the next stage in a trellis-coded system, the trellis decoder. While a DFE performs better than a linear equalizer in severe ISI, the performance is limited by error propagation through the feedback filter 16 of the DFE 10 .
- Error propagation occurs in the feedback filter 16 when the quantized equalizer output â k is not the same as the transmitted symbol a k . If an error is made in determining the symbol â k at the output of the slicer 11 , this incorrect symbol is fed back to the input of the feedback filter 16 and propagates.
- the “raw” symbol error rate (SER) at the equalizer output can be extremely high. For example, in the VSB system, at threshold in white noise the SER at the equalizer output is about 0.2.
- the increased error propagation due to these high SERs can cause the DFE to lose a couple of dB in performance as compared to the case of no error propagation. Additionally, the error propagation causes the error sequence at the equalizer output to be correlated, since it depends on past incorrect symbol decisions. This correlation has an adverse effect on the subsequent trellis decoder which is usually designed for a white noise sequence.
- MSE mean-squared-error
- DDFSE delayed decision feedback sequence estimation
- the invention has applications in any trellis coded system that utilizes a DFE for equalization, especially in cases where the SER after the equalizer is high and error propagation causes problems.
- An example is terrestrial transmission of digital TV signals.
- the invention can also be used in trellis coded systems with DFEs which are subject to colored noise interference. Again, the DFE cancels much of the interference but the adaptive predictor serves to whiten the noise further. This helps improve the trellis decoder performance.
- the invention accordingly comprises the several steps and the relation of one or more of such steps with respect to each of the others, and the apparatus embodying features of construction, combinations of elements and arrangement of parts which are adapted to effect such steps, all as exemplified in the following detailed disclosure, and the scope of the invention will be indicated in the claims.
- FIG. 1 shows a standard DFE
- FIG. 2 shows a DFE in accordance with the invention
- FIG. 3 shows a DFE in accordance with the invention during a training sequence.
- FIG. 1 is a diagram of the standard decision feedback equalizer 10 (DFE).
- the DFE includes a forward filter 12 , a slicer 14 , a feedback filter 16 and a subtractor 18 .
- Let a k be the transmitted trellis-coded symbol stream.
- the forward filter 12 is used to remove the pre echo or ghosts in the received signal.
- the slicer 14 quantizes the signal ⁇ to the nearest symbol â k . If an error is made in this quantization the error is passed to the feedback filter 16 and remains in the system. The output of the feedback filter 16 is subtracted from the output of the forward filter 12 to provide ⁇ k .
- ⁇ k is an estimate of the transmitted symbol a k plus, an error e k .
- d f is the delay through the forward equalizer
- d b is the delay in the feedback equalizer
- â k is the constellation point closet to ⁇ k .
- the error sequence e k at the equalizer output 20 is white.
- the error propagation causes this error sequence to be correlated, that is, the noise samples are no longer independent.
- the “colored” noise affects the performance of a trellis coder, because a trellis coder is optimized for performance in a channel having all white guassian noise.
- an adaptive filter 22 is placed at the output of the DFE 10 but before a trellis decoder (not shown).
- e′ k is the prediction error sequence of the equalizer output error sequence e k , it will be white see Widrow and Stearns, “Adaptive Signal Processing,” (hereby incorporated by reference), at pages 99-116), which does not affect the performance of a trellis decoder.
- the adaptive filter 22 is first placed through a training sequence as shown in FIG. 3.
- the training sequence is part of the transmitted signal.
- the adaptive filter 22 receives a training sequence which is the difference between the output of the DFE ⁇ k and the transmitted symbol sequence a k . This difference is the error e k produced by the DFE.
- This error sequence e k is then input into the adaptive filter 22 .
- g ( k+ 1) g ( k ) ⁇ x k e ( k )
- the trellis decoder uses the taps [g 1 , g 2 , . . . g Lg ] in a feedback loop, error propagation can also occur hence it is also beneficial to limit the size of the taps g during adaptation, so that the trellis decoder that uses these taps does not suffer error propagation. If g is too small, however, the efficiency of the adaptive filter is reduced. Accordingly, an additional power constraint is imposed on the LMS algorithm to limit the amplitude of the taps which reduces the error propagation in the DDFSE trellis decoder (described next).
- ⁇ k a k +e k is input to the adaptive filter 22 .
- [0033] represents the output of adaptive filter 22 as follows: As stated above, if the filter taps g are chosen to minimize e k , the SNR of the sequence y k can be improved. y k , however, is a distorted ⁇ k and includes the ISI introduced into the data stream by the adaptive filter 22 . This distortion is then compensated for in the trellis decoder by use of delayed decision feedback sequence estimation (DDFSE)as described in A. Duel-Hallen and C. Heegard, “Delayed decision-feedback Sequence Estimation,” IEEE Trans. Common., Vol. Com-37, no. 5, pp. 428-436, May 1989, hereby incorporated by reference, and as summarized below.
- DDFSE delayed decision feedback sequence estimation
Abstract
A method and device for improving DFE performance in a trellis coded system by placing a short adaptive predictive filter after the DFE in order to whiten the error sequence at the output of the DFE.
Description
- This is a Divisional of application Ser. No. 09/107,546, filed Jun. 30, 1998.
- 1. Field of the Invention
- The present invention is directed in general to digital signal processing, and in particular to receiver based methods and devices for improving decision feedback equalizer (“DFE”) performance in a trellis coded system.
- 2. Background of the Invention
- In many digital communication scenarios (e.g. telephone transmission, broadcast TV transmission, cable etc.) The transmitted signal arrives at the receiver through more than one path in addition to the direct path. This condition is called “multipath” and leads to intersymbol interference (“ISI”) in the digital symbol stream. This ISI is compensated for in the receiver through an equalizer which in many cases is a DFE as shown in FIG. 1. U.S. Pat. No. 5,572,262 shows one method of combating these multipaths.
- A DFE10 (FIG. 1) has two filter sections, a
forward filter 12 and afeedback filter 16. The input to theforward filter 12 is the received data which includes the transmitted symbol sequence ak, noise nk and multipath hi. The input to thefeedback filter 16 is the quantized equalizer output âk. The output of both the sections are summed 18 to form the final equalizer output ãk which is also the input to the next stage in a trellis-coded system, the trellis decoder. While a DFE performs better than a linear equalizer in severe ISI, the performance is limited by error propagation through thefeedback filter 16 of the DFE 10. Error propagation occurs in thefeedback filter 16 when the quantized equalizer output âk is not the same as the transmitted symbol ak. If an error is made in determining the symbol âk at the output of the slicer 11, this incorrect symbol is fed back to the input of thefeedback filter 16 and propagates. In many systems which employ error correction codes like trellis codes and/or Reed-Solomon codes to obtain very low error rates at moderate SNRs, the “raw” symbol error rate (SER) at the equalizer output can be extremely high. For example, in the VSB system, at threshold in white noise the SER at the equalizer output is about 0.2. The increased error propagation due to these high SERs can cause the DFE to lose a couple of dB in performance as compared to the case of no error propagation. Additionally, the error propagation causes the error sequence at the equalizer output to be correlated, since it depends on past incorrect symbol decisions. This correlation has an adverse effect on the subsequent trellis decoder which is usually designed for a white noise sequence. - Accordingly, it is an object of the invention to reduce the mean-squared-error (MSE) and correlation of the DFE output error sequence. This object is achieved by placing a short adaptive predictor filter after the DFE in order to whiten the error sequence. The ISI introduced into the data symbol stream by this filter is then compensated in the trellis decoder by the use of delayed decision feedback sequence estimation (DDFSE) as described in “Delayed decision-feedback sequence estimation,” by A. Duel-Hallen and C. Heegard, IEEE Trans. Commun., vol. COM-37, no. 5, pp. 428-436, May 1989.
- The invention has applications in any trellis coded system that utilizes a DFE for equalization, especially in cases where the SER after the equalizer is high and error propagation causes problems. An example is terrestrial transmission of digital TV signals.
- The invention can also be used in trellis coded systems with DFEs which are subject to colored noise interference. Again, the DFE cancels much of the interference but the adaptive predictor serves to whiten the noise further. This helps improve the trellis decoder performance.
- The invention accordingly comprises the several steps and the relation of one or more of such steps with respect to each of the others, and the apparatus embodying features of construction, combinations of elements and arrangement of parts which are adapted to effect such steps, all as exemplified in the following detailed disclosure, and the scope of the invention will be indicated in the claims.
- For a more complete understanding of the invention reference will be had to the following drawings:
- FIG. 1 shows a standard DFE;
- FIG. 2 shows a DFE in accordance with the invention; and
- FIG. 3 shows a DFE in accordance with the invention during a training sequence.
-
- after multi-path distortion and added noise nk can be written as where hi, i=0 . . . Lh−1 is the multipath channel of length lh and delay dh, and nk is the additive noise which in general is neither gaussian nor white. The
forward filter 12 is used to remove the pre echo or ghosts in the received signal. Theslicer 14 quantizes the signal ã to the nearest symbol âk. If an error is made in this quantization the error is passed to thefeedback filter 16 and remains in the system. The output of thefeedback filter 16 is subtracted from the output of theforward filter 12 to provide ãk. ãk is an estimate of the transmitted symbol ak plus, an error ek. - It can also be expressed as:
- where fi, i=0 . . . Lf−1 are the forward equalizer taps, bi, i=1 . . . Lb are the feedback taps, df is the delay through the forward equalizer, db is the delay in the feedback equalizer and âk is the constellation point closet to ãk. In the absence of error propagation, i.e. if âk=ak, the error sequence ek at the
equalizer output 20 is white. However, in most cases the error propagation causes this error sequence to be correlated, that is, the noise samples are no longer independent. The “colored” noise affects the performance of a trellis coder, because a trellis coder is optimized for performance in a channel having all white guassian noise. -
- expressed as
- where (1, g1 , g 2, g3 . . . gLg) are the taps of the adaptive filter.
-
- as
- If the filter taps are chosen so as to minimize the variance of e′k, the SNR of the sequence yk can be improved. In addition, since e′k is the prediction error sequence of the equalizer output error sequence ek, it will be white see Widrow and Stearns, “Adaptive Signal Processing,” (hereby incorporated by reference), at pages 99-116), which does not affect the performance of a trellis decoder.
- Training of the Adaptive Filter
- To minimize the error from the output of the DFE, or in other words to tune the adaptive filter taps g to the error ek, the
adaptive filter 22 is first placed through a training sequence as shown in FIG. 3. In many applications, such as digital TV, the training sequence is part of the transmitted signal. After theequalizer 10 has converged (via blind means, without using the signal ak, or trained means which uses the signal ak) theadaptive filter 22 receives a training sequence which is the difference between the output of the DFE ãk and the transmitted symbol sequence ak. This difference is the error ek produced by the DFE. - ã−a k =e k (5)
-
- g (k+1)= g (k)−μx k e (k)
- The filter taps gk are adapted using the LMS algorithm as follows where g= and e(k)=ek−1, ek−2, . . . ek−Lg]. This adaptation adapts the filter taps to minimize the mean squared, error ek 2, of the DFE.
-
- At each step of the LMS algorithm this condition is tested, and if violated, the taps are rescaled appropriately.
- The Adaptive Filter and DDFSE
-
- represents the output of
adaptive filter 22 as follows: As stated above, if the filter taps g are chosen to minimize ek, the SNR of the sequence yk can be improved. yk, however, is a distorted ãk and includes the ISI introduced into the data stream by theadaptive filter 22. This distortion is then compensated for in the trellis decoder by use of delayed decision feedback sequence estimation (DDFSE)as described in A. Duel-Hallen and C. Heegard, “Delayed decision-feedback Sequence Estimation,” IEEE Trans. Common., Vol. Com-37, no. 5, pp. 428-436, May 1989, hereby incorporated by reference, and as summarized below. -
- metric (maximum likelihood decoding):
- This equation, however, requires past symbol sequences ak−i to be saved, and each tap gi in the adaptive filter therefore introduces more memory into the system which causes the number of steps of a trellis decoder to grow exponentially with the number of taps in the
adaptive filter 22. Therefore an expanded trellis is necessary to accommodate the memory (ak−i) introduced by theadaptive filter 22. -
- following metric:
- where the sequence âk−i,j, i=1, . . . Lg is the survivor symbol sequence associated with state j in the trellis. This scheme does not expand the number of states in the original trellis, but instead introduces decision-feedback in each of the trellis states. That is, since this scheme uses âk−i, which is merely an estimate of, rather than the actual value ak−i, there is no memory introduced into the system. Since there is no memory, an expanded trellis is not required, i.e. the number of states in the trellis remains the same even with the additional
adaptive filter 22. - There is the possibility of error propagation in this implementation and hence the precaution is taken in the LMS algorithm of limiting the amplitude of the filter taps. The optimum value of P will depend on the trellis code and application. In the United States HDTV example, simulation results indicate that a value of P=0.15 gives good performance.
- It will thus be seen that the objects set forth above, among those made apparent from the preceding description, are efficiently attained and, since certain changes may be made in carrying out the above method and in the construction set forth without departing from the spirit and scope of the invention, it is intended that all matter contained in the above description and shown in the accompanying drawings shall be interpreted as illustrative and not in a limiting sense.
Claims (7)
1-2. Cancelled.
3. A device for improving DFE performance, comprising:
an input which receives an output of a DFE;
an adaptive filter having an adaptive filter input and an adaptive filter output, the adaptive filter input coupled to the input; and
an output coupled to the adaptive filter output for supplying an output signal to a DDFSE trellis decoder, which output signal is the DFE output signal with a smaller whiter error than the error in the output of the DFE.
4. The device as claimed in claim 3 , wherein the adaptive filter is adapted to receive a training sequence that adapts filter taps in the adaptive filter such that the adaptive filter acts to whiten the error in the output of the DFE.
5. The device as claimed in claim 4 , wherein the adaptive filter further includes a LMS algorithm which is used to adapt the filter taps.
7. A method of improving DFE performance, comprising the steps of:
receiving an output signal from the DFE which includes ãk+ek;
adaptively filtering ãk+ek;
providing the adaptively filtered ãk+ek to a DDFSE.
8-11. Cancelled.
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US09/107,546 US6724844B1 (en) | 1998-06-30 | 1998-06-30 | Method and device for improving DFE performance in a trellis-coded system |
US10/785,499 US20040213342A1 (en) | 1998-06-30 | 2004-02-24 | Method and device for improving DFE performance in a trellis-coded system |
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US7733952B2 (en) | 1998-11-09 | 2010-06-08 | Broadcom Corporation | Multi-pair gigabit Ethernet transceiver having adaptive disabling of circuit elements |
US7801241B2 (en) | 1998-11-09 | 2010-09-21 | Broadcom Corporation | Multi-pair gigabit Ethernet transceiver |
US20080151988A1 (en) * | 1998-11-09 | 2008-06-26 | Agazzi Oscar E | Multi-pair gigabit ethernet transceiver |
US20070183540A1 (en) * | 1998-11-09 | 2007-08-09 | Agazzi Oscar E | Multi-pair gigabit ethernet transceiver having adaptive disabling of circuit elements |
US8451885B2 (en) | 1998-11-09 | 2013-05-28 | Broadcom Corporation | Multi-pair gigabit ethernet transceiver having adaptive disabling of circuit elements |
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US9806699B2 (en) * | 2009-02-06 | 2017-10-31 | International Business Machines Corporation | Circuits and methods for DFE with reduced area and power consumption |
US9183418B2 (en) | 2010-07-01 | 2015-11-10 | Intelleflex Corporation | Half bit correlator combining for data demodulation |
US9224016B2 (en) | 2010-07-01 | 2015-12-29 | Intelleflex Corporation | Automatic gain control and baseband preintegration to reduce computation requirements at lower data rates |
US9230141B2 (en) | 2010-07-01 | 2016-01-05 | Intelleflex Corporation | RSSI estimate on variable length correlator output |
US9361488B2 (en) * | 2010-07-01 | 2016-06-07 | Intelleflex Corporation | Single or dual complex subcarrier downconversion |
US20120002762A1 (en) * | 2010-07-01 | 2012-01-05 | Intelleflex Corporation | Single or dual complex subcarrier downconversion |
US20130243066A1 (en) * | 2012-03-13 | 2013-09-19 | Lsi Corporation | Decision feedforward equalization |
US8787439B2 (en) * | 2012-03-13 | 2014-07-22 | Lsi Corporation | Decision feedforward equalization |
Also Published As
Publication number | Publication date |
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EP1038365B1 (en) | 2008-07-02 |
DE69939006D1 (en) | 2008-08-14 |
US6724844B1 (en) | 2004-04-20 |
WO2000001085A2 (en) | 2000-01-06 |
WO2000001085A3 (en) | 2000-03-30 |
EP1038365A2 (en) | 2000-09-27 |
JP2002519931A (en) | 2002-07-02 |
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