TWI386771B - Voltage regulator and ac-dc converter - Google Patents

Voltage regulator and ac-dc converter Download PDF

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Publication number
TWI386771B
TWI386771B TW98115793A TW98115793A TWI386771B TW I386771 B TWI386771 B TW I386771B TW 98115793 A TW98115793 A TW 98115793A TW 98115793 A TW98115793 A TW 98115793A TW I386771 B TWI386771 B TW I386771B
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Taiwan
Prior art keywords
voltage
transistor
coupled
node
switch
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TW98115793A
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Chinese (zh)
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TW201040684A (en
Inventor
Rogelio L Erbito Jr
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Vanguard Int Semiconduct Corp
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Description

Voltage regulator and AC to DC converter

The present invention relates to a voltage regulator, and more particularly to a voltage regulator for an AC to DC converter.

In general, the AC to DC converter can be used directly on the AC input line. In the AC-to-DC converter, the rectifier circuit can directly convert the AC input voltage from the AC line into a DC voltage with a ripple, wherein the regulator disposed at the output of the rectifier circuit can have a DC with chopping The voltage is adjusted to reduce the occurrence of chopping.

Figure 1 shows a conventional AC to DC converter 100. The AC to DC converter 100 includes a rectifier circuit 110 and a shunt regulator circuit 120. The rectifier circuit 110 can convert the high AC voltage HVAC into a high DC voltage HVDC (unipolar voltage). Due to the presence of chopping, the high DC voltage HVDC is a non-fixed voltage. In order to provide a stable high DC voltage HVDC, a high DC voltage HVDC is filtered using a smoothing capacitor C1 to reduce chopping. The shunt regulation circuit 120 includes a resistor R, a Zener diode Z, and a capacitor C2, wherein the shunt regulator circuit 120 can eliminate any remaining chopping and can maintain adjustments for different supply voltages and loads. According to the DC voltage HVDC, the resistor R and the Zener diode Z generate an adjusted DC voltage. Capacitor C2 is connected in parallel to Zener diode Z to further reduce chopping and diode noise.

The rectifier circuit 110 and the shunt regulation circuit 120 are composed of discrete resistors, capacitors, and diodes. However, the cost of discrete components is higher and will Occupy more printed circuit board area. Further, in the shunt regulation circuit 120, since the current flowing through the resistor R and the Zener diode Z continues to flow, power consumption may occur. At the same time, if the traditional voltage regulator circuit is operated under high voltage (such as 120V or 240V AC), the power consumption will be more serious. Therefore, there is a need for an ultra high voltage regulator.

The present invention provides a voltage regulator comprising: an input node for receiving a supply voltage; an output node for providing a supply voltage; a first transistor coupled to the input node and a first node a first resistor coupled between the input node and the gate of the first transistor; a second transistor coupled between the first node and the output node; an amplifier having a An inverting input terminal and a non-inverting input terminal for receiving a reference voltage; a second resistor coupled between the inverting input terminal and a ground terminal; a third transistor coupled to the first Between the two resistors and the gate of the second transistor, wherein the third transistor system is controlled by the output of the amplifier; and a fourth transistor coupled to the third transistor and the first node The gate of the fourth transistor is coupled to the gate of the second transistor.

Furthermore, the present invention provides an AC-to-DC converter comprising: an input node for receiving an AC voltage; an output node for providing a supply voltage; and a rectifier circuit for converting the AC voltage into a DC current And a voltage regulator for receiving the DC voltage to generate the supply voltage. The voltage regulator includes: a first transistor coupled between the rectifier circuit and a first node; a first resistor coupled to the first resistor a rectifier circuit and a gate of the first transistor; a second transistor coupled between the first node and the output node; an amplifier having an inverting input and receiving a reference a non-inverting input terminal; a second resistor coupled between the inverting input terminal and a ground terminal; a third transistor coupled to the second resistor and the gate of the second transistor Between the poles, wherein the third transistor system is controlled by the output of the amplifier; a fourth transistor coupled between the third transistor and the first node, wherein the gate of the fourth transistor Is coupled to the gate of the second transistor; a first switch coupled between the gate of the second transistor and the first node; and a determining circuit for using the supply voltage and the The first switch is controlled by the reference voltage. When the reference voltage is greater than a first voltage, the first switch is non-conductive, and when the reference voltage is less than a second voltage, the first switch is conductive, wherein the first voltage is greater than the second voltage.

The above and other objects, features and advantages of the present invention will become more <RTIgt;

Example:

Figure 2 shows an AC to DC converter 200 in accordance with an embodiment of the present invention. The AC-to-DC converter 200 receives a high AC voltage HVAC from the input node N in and provides a supply voltage VCC via the output node N out . The AC to DC converter 200 includes a rectifier circuit 210 and a voltage regulator 220. Due to the high barrier voltage and current characteristics, the rectifier circuit 210 is a discrete component. The rectifier circuit 210 converts the high AC voltage HVAC into a high DC voltage HVDC. The regulator 220 adjusts the high DC voltage HVDC to generate the supply voltage VCC. In one embodiment, the voltage regulator 220 can be disposed in the integrated circuit by the high voltage process capability of the integrated circuit.

Figure 3 is a block diagram showing an AC-to-DC converter internal voltage regulator 300 in accordance with an embodiment of the present invention. The voltage regulator 300 can receive the input voltage HVDC from the input node N in and supply the supply voltage VCC to the load C load via the output node N out . The voltage regulator 300 includes a main circuit 310 and a determination circuit 320. In addition, the voltage regulator 300 further includes a transistor SW1, a diode D1, a transistor M5, and a diode chain 330. SW1-based transistor coupled to the gate of transistor M2 and between the node N 1, which is used as the switching transistor for controlling whether or not the main circuit 310 to operate normally. The diode D1 is coupled between the transistor M2 and the output node Nout . The diode string 330 has four diodes D2-D5, wherein each of the two-pole systems is electrically connected by a forward conduction direction from the gate of the transistor M1 to the transistor M5. The transistor M5 is coupled between the diode string 330 and the ground GND, and the gate of the transistor M5 is coupled to the output node Nout . In this embodiment, the transistor M5 and the diode string 330 can form a protection circuit to prevent the voltage V G and the voltage V S from increasing beyond the breakdown voltage of the components in the regulator 300.

In the main circuit 310, the transistor M1 and the resistor R1 are high voltage elements which can withstand a voltage of 400 V or higher depending on the technology of the semiconductor process. During normal operation, although the high voltage component is operating at a low voltage, it will still experience a large voltage drop. The resistor R1 is coupled between the input node N in and the diode string 330 . The transistor M1 is coupled between the input node N in and the node N 1 , wherein the gate of the transistor M1 is coupled to the resistor R1 . The transistor M1 can be biased through the resistor R1 so that the transistor M1 can operate in the saturation region. Therefore, current can be supplied from the input node N in to the node N 1 . As shown in FIG. 3, the voltage V G on the gate of the transistor M1 is equal to the supply voltage VCC plus the gate-to-source voltage of the transistor M5 and the voltage drop of the four diodes, wherein the diode The voltage drop is the forward voltage across the diode D2-D5. It is worth noting that the number of diodes in the diode string 330 is determined according to different designs and applications. The transistor M2 is coupled between the node N 1 and the diode D1, and the transistor M4 is coupled between the node N 1 and the transistor M3, wherein the transistor M2 forms a current mirror pair with the transistor M4. controllable current of the output node N out to flow from the transistor M1. In addition, the gates of the transistors M2 and M4 are all coupled to the switch SW1. The current flowing through the transistor M4 is controlled by the transistor M3. The transistor M3 is coupled between the transistor M4 and the resistor R2 and controlled by the output of the amplifier 312. The amplifier 312 has an inverting input terminal (-) and a non-inverting input terminal (+), wherein the non-inverting input terminal is configured to receive the reference voltage V ref and the inverting input terminal is coupled to the resistor R2. Therefore, according to the following formula (1), the current I M2 flowing through the transistor M2 can be calculated: Where K is the ratio of the aspect ratio (W/L) of the transistor M2 to the aspect ratio of the transistor M4. It is worth noting that the width-to-length ratio of the transistor M2 is greater than the aspect ratio of the transistor M4, so the current flowing through the transistor M2 is greater than the current flowing through the transistor M4. Furthermore, the current flowing through the transistor M2 is the same as the current flowing through the transistor M1 and the diode D1, that is, the current I. The diode D1 can allow the current I to flow from the input node N in to the output node N out , but will block the reverse current from the output node N out . Current I charges the load C load so that the supply voltage VCC begins to increase.

Referring to FIG. 3, the decision circuit 320 includes a voltage dividing unit 340, two comparators 350 and 360, a control circuit 370, and four transistors M6, M7, SW2, and SW3. In this embodiment, the transistor SW2 and the transistor SW3 are transistors used as switches. The voltage dividing unit 340 is coupled between the output node N out and the ground GND, and includes resistors R3, R4, and R5. Furthermore, the voltage dividing unit 340 can provide the voltage V 1 and the voltage V 2 according to the supply voltage VCC, wherein the voltage V 1 is greater than the voltage V 2 . Department of resistor R4 is coupled between the resistors R3 and R5, the voltage V 1 is the voltage difference between the voltage V across the resistor R4 as a voltage (i.e. the voltage across the resistor R4). Comparator 350 pairs of voltage V 1 is compared with the reference voltage V ref to generate a comparison signal S c1, and the comparator 360 compares the voltage V 2 is compared with the reference voltage V ref to generate a comparison signal S c2. The control circuit 370 controls whether the switch SW2 and the switch SW3 are turned on based on the comparison signals S c1 and S c2 . Control circuit 370 includes a D-type flip-flop 372 and an inverter 374. Inverter 374 receives comparison signal S c1 to generate signal S c1B . The D-type flip-flop 372 includes a data terminal D, a reset terminal RST for receiving the signal S c1 , a clock terminal CLK for receiving the comparison signal S c2 and two output terminals Q and QB, wherein the data provided by the output terminal QB is The complement of the data provided by the output Q. The switch SW2 is coupled between the node N 2 and the ground GND, and the control end is coupled to the output terminal Q. The switch SW3 is coupled between the node N 3 and the ground GND, and the control end is coupled to the output terminal QB. The transistor M6 is coupled between the node N 1 and the node N 2 , and the transistor M7 is coupled between the node N 1 and the node N 3 , wherein the gates of the transistor M6 and the transistor M7 are respectively coupled to Node N 3 and node N 2 . In addition, the control terminal of the switch SW1 is coupled to the node N 2 .

First, the supply voltage VCC is at a low voltage level. Since the voltage V 1 is smaller than the reference voltage V ref , the comparison signal S c1 is at the logic level "1", and then the D-type flip-flop 372 is reset. Simultaneously, the comparison signal S c2 is a logic level "0". The signals provided by the output terminal Q and the output terminal QB are logic levels "0" and "1", respectively, so the switch SW2 is non-conductive and the switch SW3 is turned on. In the case where the switch SW3 is turned on, the voltage V at the node N 3 3 goes low. Next, in a case where the switch SW2 is not turned on, a low voltage level of the voltage V 3 M6 will turn-crystal, pull up on the node voltage V N 2 4. Then, the voltage V 4 is pulled up to a high voltage level, so that the switch SW1 becomes non-conductive. When the switch SW1 is non-conducting, the current mirror pair (the transistors M2 and M4) is normally operated, and the current I flowing through the transistor M2 charges the load C load to maintain the supply voltage VCC to continue to increase. In the voltage dividing unit 340, the voltage V 1 and the voltage V 2 are proportionally increased in proportion to the supply voltage VCC, wherein the voltage V 1 and the voltage V 2 can be respectively calculated according to the following formulas (2) and (3): When the supply voltage VCC continues to increase, the voltage V 1 will become higher than the reference voltage V ref . Next, the comparison signal S c1 will change from a logic level "1" to a "0", which will cause the D-type flip-flop 372 to be ready to receive the clock signal. When the supply voltage VCC continues to increase, the voltage V 2 will become higher than the reference voltage V ref , which will cause the comparison signal S c2 to change from the logic level "0" to "1". Since the D-type flip-flop 372 is an edge-triggered D-type flip-flop, the transition of the comparison signal S c2 will trigger the D-type flip-flop 372 to change its output state. The initial state of the signal provided by the output Q is a logic level "0". After the trigger occurs, since the input signal S c1B of the D-type flip-flop 372 is a logic level "1", the signal provided by the output terminal Q is changed from the logic level "0" to the logic level "1". .

After the output state of the D-type flip-flop 372 is changed, the switch SW2 is turned on and the switch SW3 is turned off. Therefore, the voltage V 4 is pulled down, causing the switch SW1 to be turned on. Then, the transistor M2 and the gate and source of the transistor M4 are short-circuited. Therefore, the transistor M2 and the transistor M4 become non-conductive, so that the current I stops flowing through the transistor M2. When the current I is stopped, the charging current of the load C load is also stopped, and then the load C load starts to discharge. Then, the supply voltage VCC will start to drop until the voltage V 1 is slightly lower than the reference voltage V ref . As previously described, when the voltage V 1 is less than the reference voltage V ref , the comparison signal S c1 becomes a logic level "1" to reset the D-type flip-flop 372. Next, the switch SW3 is turned on and the switch SW2 is turned off, so that the voltage V S is the same as the voltage V 4 . Then, the switch SW1 is non-conducting, and then the current mirror pair (the transistors M2 and M4) will start to resume operation to increase the supply voltage VCC. Therefore, the supply voltage VCC can be increased to the maximum voltage value and reduced to the minimum voltage value, wherein the maximum and minimum voltage values are determined according to the reference voltage V ref . For example, when the voltage V 2 is greater than the reference voltage V ref , the maximum voltage value of the supply voltage VCC can be determined, and when the voltage V 1 is less than the reference voltage V ref , the minimum voltage value of the supply voltage VCC can be determined, wherein The voltage V 1 and the voltage V 2 are obtained according to the equations (2) and (3), respectively. Furthermore, the maximum and minimum voltage values can form an operating window voltage of the supply voltage VCC.

By controlling whether the current I flowing through the regulator 300 is turned on, an intermittent current I can be obtained, so that the supply voltage VCC is not always maintained at the peak level, thereby reducing the average power consumption. Furthermore, the voltage regulator 300 can be placed in the integrated circuit to reduce the area and cost of the printed circuit board.

The present invention has been described above with reference to the preferred embodiments thereof, and is not intended to limit the scope of the present invention, and the invention may be modified and modified without departing from the spirit and scope of the invention. The scope of the invention is defined by the scope of the appended claims.

100,200‧‧‧AC to DC converter

110, 210‧‧‧Rectifier circuit

120‧‧ ‧ shunt regulation circuit

220, 300‧‧‧ voltage regulator

310‧‧‧ main circuit

312‧‧Amplifier

320‧‧‧Judgement circuit

330‧‧‧Diode string

340‧‧‧Voltage unit

350, 360‧‧‧ comparator

370‧‧‧Control circuit

372‧‧‧D type flip-flop

374‧‧‧Inverter

C1, C2‧‧‧ capacitor

C load ‧‧‧load

D1-D5‧‧‧ diode

GND‧‧‧ ground terminal

HVAC‧‧‧High AC voltage

HVDC‧‧‧High DC voltage

M1-M7, SW1-SW3‧‧‧O crystal

N 1 -N 3 ‧‧‧ nodes

N in ‧‧‧Input node

N out ‧‧‧output node

R, R1-R5‧‧‧ resistance

V 1 -V 4 , V G , V S ‧‧‧ voltage

VCC‧‧‧ supply voltage

VREF‧‧‧reference voltage

S c1 , S c1B , S c2 ‧‧‧ signals

Z‧‧‧Zina diode

1 is a conventional AC to DC converter; FIG. 2 is an AC to DC converter according to an embodiment of the invention; and FIG. 3 is an AC pair according to an embodiment of the invention. Block diagram of the regulator in the DC converter.

300‧‧‧Regulator

310‧‧‧ main circuit

312‧‧Amplifier

320‧‧‧Judgement circuit

330‧‧‧Diode string

340‧‧‧Voltage unit

350, 360‧‧‧ comparator

370‧‧‧Control circuit

372‧‧‧D type flip-flop

374‧‧‧Inverter

C load ‧‧‧load

D1-D5‧‧‧ diode

GND‧‧‧ ground terminal

HVDC‧‧‧High DC voltage

M1-M7, SW1-SW3‧‧‧O crystal

N 1 -N 3 ‧‧‧ nodes

N in ‧‧‧Input node

N out ‧‧‧output node

R1-R5‧‧‧ resistance

V 1 -V 4 , V G , V S ‧‧‧ voltage

VCC‧‧‧ supply voltage

VREF‧‧‧reference voltage

S c1 , S c1B , S c2 ‧‧‧ signals

Claims (19)

  1. A voltage regulator comprising: an input node for receiving a supply voltage; an output node for providing a supply voltage; a first transistor coupled between the input node and a first node; a first resistor coupled between the input node and the gate of the first transistor; a second transistor coupled between the first node and the output node; and an amplifier having an inverting input And a non-inverting input terminal for receiving a reference voltage; a second resistor coupled between the inverting input terminal and a ground terminal; a third transistor coupled to the second resistor and Between the gates of the second transistor, wherein the third transistor system is controlled by the output of the amplifier; and a fourth transistor coupled between the third transistor and the first node, wherein The gate of the fourth transistor is coupled to the gate of the second transistor.
  2. The voltage regulator of claim 1, further comprising: a first diode coupled between the second transistor and the output node for blocking a reversal from the output node Current.
  3. The voltage regulator of claim 1, further comprising: a diode string coupled to the gate of the first transistor, a plurality of second diodes connected in series; and a fifth transistor coupled between the diode string and the grounding terminal, and having a gate coupled to the output node, wherein the second The pole system is electrically connected by a forward conduction direction from a gate of the first transistor to a fifth transistor.
  4. The voltage regulator of claim 1, further comprising: a first switch coupled between the gate of the second transistor and the first node, coupled to a second node a control terminal; and a determining circuit for controlling the first switch according to the supply voltage and the reference voltage.
  5. The voltage regulator of claim 4, wherein the determining circuit comprises: a voltage dividing unit configured to provide a first voltage and a second voltage according to the supply voltage, wherein the first voltage system is greater than The second voltage; a first comparator for comparing the first voltage with the reference voltage to generate a first comparison signal; and a second comparator for the second voltage and the reference Comparing voltages to generate a second comparison signal, wherein when the first comparison signal indicates that the reference voltage is greater than the first voltage, the first switch is non-conducting, and when the second comparison signal indicates the reference voltage When the second voltage is less than the second voltage, the first switch is turned on.
  6. The voltage regulator according to claim 5, wherein the voltage dividing unit comprises: a third resistor coupled to the output node; a fourth resistor coupled to the third resistor; a fifth resistor coupled between the fourth resistor and the ground, wherein the first voltage And a voltage difference between the second voltages is a voltage across the fourth resistor.
  7. The voltage regulator of claim 5, wherein the determining circuit further comprises: a sixth transistor coupled between the first node and the second node, coupled to a third node a gate, a seventh transistor coupled between the first node and the third node, having a gate coupled to the second node; a second switch coupled to the second node and a third switch coupled between the third node and the ground end; and a control circuit for controlling the second switch according to the first comparison signal and the second comparison signal And the third switch, wherein when the first comparison signal indicates that the reference voltage is greater than the first voltage, the second switch is non-conductive and the third switch is conductive, and when the second comparison signal indicates the reference When the voltage is less than the second voltage, the second switch is turned on and the third switch is turned off.
  8. The voltage regulator of claim 7, wherein the control circuit comprises: An inverter for inverting the first comparison signal; a D-type flip-flop comprising: a data terminal for receiving the inverted first comparison signal; and a clock terminal for receiving the a second comparison signal; a reset terminal for receiving the first comparison signal; a first output terminal for providing a first output data to the second switch; and a second output terminal for providing a The second output data is to the third switch, wherein the second output data is a complement of the first output data.
  9. The voltage regulator of claim 1, wherein the second transistor and the fourth transistor form a current mirror pair, and the second transistor has a larger size than the fourth transistor.
  10. The voltage regulator of claim 1, wherein the first transistor and the first resistor are high voltage components.
  11. An AC-to-DC converter includes: an input node for receiving an AC voltage; an output node for providing a supply voltage; a rectifier circuit for converting the AC voltage into a DC voltage; and a voltage regulator And receiving the DC voltage to generate the supply voltage, comprising: a first transistor coupled between the rectifier circuit and a first node; a first resistor coupled to the rectifier circuit and the foregoing One Between the gates of the transistor, a second transistor is coupled between the first node and the output node; an amplifier having an inverting input and receiving a non-inverting input of a reference voltage a second resistor coupled between the inverting input terminal and a ground terminal; a third transistor coupled between the second resistor and the gate of the second transistor, wherein the second The third transistor system is controlled by the output of the amplifier; a fourth transistor is coupled between the third transistor and the first node, wherein the gate of the fourth transistor is coupled to the second a gate of the transistor; a first switch coupled between the gate of the second transistor and the first node, having a control end coupled to a second node; and a determining circuit for Controlling the first switch according to the supply voltage and the reference voltage, wherein when the reference voltage is greater than a first voltage, the first switch is non-conducting, and when the reference voltage is less than a second voltage, Said first switch is turned on, wherein the first voltage is larger than the second voltage line.
  12. The AC-DC converter of claim 11, wherein the voltage regulator further includes: a first diode coupled to the second transistor and the output Between the nodes to block the reverse current from the output node.
  13. The AC-DC converter of claim 11, wherein the voltage regulator further comprises: a diode string coupled to the gate of the first transistor, having a plurality of series connected in series a second diode, coupled to the diode string and the ground terminal, having a gate coupled to the output node, wherein the second diode system is The gate of a transistor is electrically connected to the forward conduction direction of the fifth transistor.
  14. The AC-DC converter of claim 11, wherein the determining circuit comprises: a voltage dividing unit for providing the first voltage and the second voltage according to the supply voltage; a first comparator And comparing the first voltage with the reference voltage to generate a first comparison signal; and a second comparator for comparing the second voltage with the reference voltage to generate a second comparison a signal, wherein when the first comparison signal indicates that the reference voltage is greater than the first voltage, the first switch is non-conductive, and when the second comparison signal indicates that the reference voltage is less than the second voltage, the first The switch is conducting.
  15. The AC-DC converter of claim 14, wherein the voltage dividing unit comprises: a third resistor coupled to the output node; and a fourth resistor coupled to the third resistor; A fifth resistor is coupled between the fourth resistor and the ground terminal, wherein a voltage difference between the first voltage and the second voltage is a voltage across the fourth resistor.
  16. The AC-DC converter of claim 14, wherein the determining circuit further comprises: a sixth transistor coupled between the first node and the second node, coupled to the first a third node, a seventh transistor coupled between the first node and the third node, having a gate coupled to the second node; a second switch coupled to the second a third switch coupled between the third node and the ground end; and a control circuit for controlling the first according to the first comparison signal and the second comparison signal The second switch and the third switch, wherein when the first comparison signal indicates that the reference voltage is greater than the first voltage, the second switch is non-conductive and the third switch is conductive, and when the second comparison signal indicates When the reference voltage is less than the second voltage, the second switch is conductive and the third switch is non-conductive.
  17. The AC-DC converter of claim 16, wherein the control circuit comprises: an inverter for inverting the first comparison signal; and a D-type flip-flop, comprising: a data terminal for receiving the inverted first comparison signal; a clock terminal for receiving the second comparison signal; a reset terminal for receiving the first comparison signal; and a first output terminal And providing a second output data to the third switch, wherein the second output data is a complement of the first output data.
  18. The AC to DC converter of claim 11, wherein the second transistor and the fourth transistor form a current mirror pair, and the second transistor has a larger size than the fourth transistor.
  19. The AC to DC converter of claim 11, wherein the first transistor and the first resistor are high voltage components.
TW98115793A 2009-05-13 2009-05-13 Voltage regulator and ac-dc converter TWI386771B (en)

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Citations (6)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US5770940A (en) * 1995-08-09 1998-06-23 Switch Power, Inc. Switching regulator
US6084450A (en) * 1997-01-14 2000-07-04 The Regents Of The University Of California PWM controller with one cycle response
US6862194B2 (en) * 2003-06-18 2005-03-01 System General Corp. Flyback power converter having a constant voltage and a constant current output under primary-side PWM control
TW200726050A (en) * 2005-12-26 2007-07-01 Fujitsu Ltd DC-DC converter and control circuit for DC-DC converter
TW200733532A (en) * 2006-01-10 2007-09-01 Rohm Co Ltd Power supply device and electronic device provided with the same
US7518348B1 (en) * 2005-04-20 2009-04-14 National Semiconductor Corporation Adaptive error amplifier clamp circuit to improve transient response of DC/DC converter with current mode control

Patent Citations (6)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US5770940A (en) * 1995-08-09 1998-06-23 Switch Power, Inc. Switching regulator
US6084450A (en) * 1997-01-14 2000-07-04 The Regents Of The University Of California PWM controller with one cycle response
US6862194B2 (en) * 2003-06-18 2005-03-01 System General Corp. Flyback power converter having a constant voltage and a constant current output under primary-side PWM control
US7518348B1 (en) * 2005-04-20 2009-04-14 National Semiconductor Corporation Adaptive error amplifier clamp circuit to improve transient response of DC/DC converter with current mode control
TW200726050A (en) * 2005-12-26 2007-07-01 Fujitsu Ltd DC-DC converter and control circuit for DC-DC converter
TW200733532A (en) * 2006-01-10 2007-09-01 Rohm Co Ltd Power supply device and electronic device provided with the same

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