TWI375387B - - Google Patents

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TWI375387B
TWI375387B TW098105251A TW98105251A TWI375387B TW I375387 B TWI375387 B TW I375387B TW 098105251 A TW098105251 A TW 098105251A TW 98105251 A TW98105251 A TW 98105251A TW I375387 B TWI375387 B TW I375387B
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Taiwan
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axis
converter
current
voltage
phase
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TW098105251A
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Chinese (zh)
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TW201032446A (en
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Univ Nat Penghu
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1375387 VI. Description of the invention: [Technical field to which the invention pertains] The present invention relates to power electronics technology, and more particularly to an input side power factor correction applied to an unbalanced three-phase AC-DC converter and a second-order chopping of the output side voltage. Control device. [Prior Art] Press, existing literature [1] Hong-Seok Song, Kwanghee Nam, stDual current control scheme for PWM converter under unbalanced conditions, IEEE Trans. Ind. Electron., vol. 46, No. 5, pp. 953 - 959, Oct. 1999. ; [2] Y. Suh, V. Tijeras and TA Lipo, "A nonlinear control of the instantaneous power in dq synchronous frame for pwm ac/dc converter under generalized
Unbalanced operating conditions,” Cow/ vol. 2, pp. 1189-1196, Oct. 2002. ; [3] Peng Xiao, Keith A. Corzine, Ganesh K. Venayagamoorthy, “Cancellation Predictive Control for Three-Phase PWM Rectifiers under
Harmonic and Unbalanced Input Conditions, IECON 2006 - 〇«, pp. 1816 - 1821, Nov. 2006.; and [4] I. Etxeberria-Otadui, U. Viscarret,; M. Caballero, A.Rufer, S. Bacha, “New Optimized PWM VSC Control Structures and Strategies Under Unbalanced Voltage Transients, M IEEE Trans. 3 1375387 /«d five/ecir〇«·, vol. 54, No. 5, pp. 2902 - 2914, Oct. 2007. It can be seen that the input unbalanced voltage does cause 120 Hz chopping, while the literature [1] proposes the operation of the dual current controller in the three-phase unbalanced pulse width modulation converter, while the literature [2] proposes the dq synchronization frame. The instantaneous power nonlinear control law is applied to a wide range of three-phase unbalanced input power supplies. In addition, the literature [5] Hong-Seok Song, In-Won Joo, Kwanghee Nam, "Source voltage sensorless estimation scheme for PWM rectifiers under unbalanced conditions , IEEE Trans. Ind. Electron., vol. 50, No. 6, pp. 1238- 1245, Dec. 2003.; [6] S. Hansen, M. Malinowski, F. Blaabjerg, and Μ. P. Kazmierkowski, "Sensorless control strategies for PWM rectifier,M in Pro c. IEEE APEC, pp. 832-838, 2000.; [7] T. Ohnuki, O. Miyashita, P. Lataire, and G. Maggetto, “Control of a three-phase PWM rectifier using estimated AC-side and DC -side voltages, IEEE Trans. Power Electron., vol. 14, pp. 222-226, Mar. 1999.; [8] D.-C. Lee and D.-S. Lim, 4<AC voltage and current sensorless Control of three-phase PWM rectifiers; 5 in Proc. IEEE PESC, pp. 588-593, 2000. Proposed that the non-sensing control law operates in the case of three-phase unbalance. However, so far, only a few existing literatures have considered the line and switch switching losses. For the three-phase AC-DC converter operating on the unbalanced input, the output side voltage of the converter is affected by 120 Hz chopping, so how to improve 4 1375387 &gt At present, the existing method, and considering the operation of the three-phase unbalanced AC-DC converter, due to the imbalance (four) and line loss, shouted the current control device to reduce the output side voltage] 2〇hz chopping, The output power is more clean and smooth, which is the primary problem to be solved by the present invention. [Inventive content] φ The main object of the present invention is to provide a DC converter for input unbalanced three-phase rise > Controlling the position, it can ride the unbalanced electric three-phase boost type AC-DC converter to suppress the voltage ripple of twice the line frequency on the output DC link, so that the output voltage is a smoother DC Supply the load required, and achieve the purpose of input unit unit power. For the purpose of the foregoing, the present invention provides a control device for input unbalanced three-phase boost type AC-DC converter, which is composed of a three-phase boost type AC-DC converter and a controller, and an AC-DC converter. There is an input side voltage sensing, a current sensor and an output side voltage sensor, a voltage sensor and a current sense detector respectively obtain the input side three-phase voltage and current and the output side DC bus voltage 'output The signal input of the voltage sensor to the voltage controller generates a current command, and the actual positive sequence d-axis and q-axis current center measured by a positive sequence q-axis current command and current sensor, and voltage sensing The actual measured I-order d-axis and q-axis voltage ^ are output to a positive-sequence current controller, and the actual negative-sequence d-axis and q-axis current measured by the current sensor are - Negative sequence d-axis current command, negative sequence q-axis current command, and 'the actual negative sequence d-axis and q-axis voltage measured by the two devices are rounded up to a negative 5 1375387' and then the positive sequence current control 11 Negative sequence current controller counts two, wide modulation module, produces six open _ __ power factor information read:! :: = ^, prostitutes money input side and said units other objects and advantages of the present invention and Gray, The Journal Bin no detailed embodiment of the Long _ Choi Chang Ang embodiment, said chosen depth understanding ^
[Embodiment] Please refer to Figure 1 to Figure 4 for the description of the 2nd, and the figure shown in the figure is the same as the hair of the present invention. The control device of the converter is mainly composed of a three-phase AC-DC converter 6 and its controller 1. The input side is a three-phase power supply 2, and the output side is a DC load 8, which is a three-phase AC-DC conversion. The device 6 is matched with the three-phase AC/DC converter controller i, the input side three-phase inductor 5, the output side voltage stabilizing capacitor 7, and an input power detector 3 1 , an output voltage sensor 3 2 and a The electric steam sensor 4·, and the three-phase AC/DC converter control w is used to output six power switching control signals to control the three-phase AC/DC converter 6, as shown in FIG. 3 The input side current and the output side are electric. In addition, the three-phase voltage on the input side and the output side (four) (the ah, the lion, the voltage sensor 3 1 , 3 2 measurement 'the voltage sensor 31, 3 2 circuit architecture diagram as shown in Figure 5 and Figure 6 The input side three-phase current, _ can be obtained by measuring the electric 6 1375387 / "l sensor 4, wherein the circuit diagram of the current sensor 4 is as shown in Fig. 7. Then continue to match the reference 8 to 12, the internal functional block of the three-phase step-up AC/DC converter controller i of the present invention includes a separately operated AC/DC converter voltage controller} 6. A pulse width modulation module 丄7 And a positive sequence current controller 11, a negative sequence current controller 12, φ a positive sequence q axis current command 13, a negative sequence d-axis current command 14 and a negative sequence Q axis current command 15 5. wherein the AC / The DC converter voltage controller 6 system calculates the voltage input command and the output voltage (7) measured value two input signals to obtain the desired positive sequence direct axis 4 current command and the positive sequence q axis current command 13 and current sense The actual positive sequence d-axis and q-axis current v measured by the detector 4 and the actual positive sequence d-axis and Q-axis measured by the voltage sensor 3 1 Pressing the heart-starting output to the positive sequence current controller is completed. Similarly, the current sensor • 4 measured the actual negative sequence d-axis and ❻ current ', and the negative sequence d, the axis current command 14 The negative sequence q-axis current command i 5 and the actual negative sequence d-axis and q-axis voltage ', gas" measured by the voltage sensor 31 are output to the negative sequence current controller 1 2; The positive sequence current controller worker adds the value generated by the negative sequence current control ^1 2 calculation, and sends the pulse width modulation module 17 to generate six switching signals for driving the AC/DC conversion. The six switches of the device 'to achieve the input side unit power factor and reduce the output side voltage secondary chopping generation 0 7 1375387 and the third figure is the circuit structure diagram of the three-phase pulse width modulation converter, where the input is The phase power supply is connected to the boost inductor and the equivalent line series resistor and the six controllable switches' output side is composed of a voltage regulator capacitor in parallel with a load. Firstly, for the convenience of the operation of the three-phase unbalanced pulse width modulation The converter does a modeling. The three-phase unbalanced input of the human-electric display can be described by the positive sequence and the negative sequence. Cheng, the mathematical description is as follows: ^=e^+e-^ = elm{Epd +jE^)+eJa(End + jEnq) (1) 7^=e;e7;+e^7;? =eJaV: + β; ) +e, (I: + β:, ® where ω is the power angular frequency, ω = 377 ~ sec, frequency / - 601⁄2. Considering the complex power of the converter seen from the side of Figure 2A, it can be expressed as: ^=1^,4 = ^(0+7^(0 (3) where ^(t)^ ^(t)^ is the component of instantaneous real and virtual work. In addition, A(t can be expressed as follows The form: p,n (0 = Pln + PM cos 2mt + sin 2mt (4) β» (〇= 0, „ + β«2 cos 2ωί+βΜί sin 2&t (5) Consider equation (5), hypothesis The instantaneous virtual work & (t) of the input pulse width modulation converter is zero, and the input side current of the converter can reach the unit power factor. In a similar way, we can also make the average input virtual work zero = 〇, to achieve the purpose of the input side current to achieve unit power, and does not affect the output voltage, because the output power 8 1375387 . related. Secondly, considering the output voltage of the three-phase unbalanced pulse width modulation converter, it can be seen from the wire type (4) that the component of the actual power has twice the line frequency when the collapse occurs. The instantaneous actual work includes the average actual work A w item. 2 w Branch,, |j into the instantaneous real power transmission to the wheel side, and determine the DC key bus voltage, but the household * ζώ and the household secret will cause 120Hz continuous wave on the output DC level. In the case of not considering line loss and switching loss, the direct 7 (four) and household (four) zero can be used to maintain the clean converter output DC level. In the invention of the invention, we consider the line loss and discuss the relationship between the line loss and the output of the electric wave; in the conventional method, the analysis of the input unit power and the analysis of the output double frequency are observed from the side A of the third figure. However, the analysis of the unit's work factor and the double frequency analysis of this issue are made in different places, the analysis of the unit work factor is observed on the A side, and the analysis of the double frequency is observed on the 6 side. At this time, The switching loss can also be observed from the B side. S s (6) _ Consider the sum of the equivalent resistance of the switching loss and the line loss, and the power loss can be written as follows: L = standby U: = & (,) + _ / (10) where (0 = + Pct Jll COS 2ωί + Pll gs sin 2ωί
Qr, (0 = + Qcl^ cos 2ωί + Q,1Jb sin 2at (7) (8) = +V:J:+V:J:+r „/;) = +v:J:+v:J:+viJ:) 9 1375387 (9) = ψυ: - v:j: - V:J:+v;j:) Therefore, the upper two and p<b2 observed from the conversion HB side can be defined as follows: (ίο) Ρχ1 ~Ρί^~Ρη,_^ (11) ~ΡΛ a2 (12) , the derivation 'considers the input side unit power factor and the round-out side wireless channel double frequency analysis, and consider the equivalent _ member loss into the whole , (10), (11) and (10), can be ^ (B): h Ιβ- lp-. (13) (e:-r,i:) (E;-RI;) (e:-r, i:) (£;-λ/;) }/;(〇! £* ~Ε: Ε; -Ε: /;(/) (£;~Λ/;) ~(E:-RI:) -( E:-RJ:) (E:-RI;) 1:{t) {E- - Λ/;) (£; _ RI;) (£; - Λ</;) /·(,) Observation (13 In order to achieve the input side current unit power factor, we must make the input average virtual power value zero, that is, 2^=0. Secondly, 'to obtain a clean output voltage level', the second frequency seen from the side The actual power and household α2 need to be set to zero. To simplify the control strategy, we use the voltage-oriented control law, the equation 13) can be simplified as follows: (14) 1375387 3 (E:~RI:)' "/;(0' 0 £; 0 £; -E: 0 {E:-R,I:)_ ./;(0. When the input side three-phase voltage can be accurately obtained by the phase-locked loop, we can make the q-axis component of the positive and negative sequence zero, and equation (14) can be simplified as follows: hd Ruler::) (E:-RI:) 7;(〇" 0 -(E:-Ό{E:-R1:) ./;(0. dRn, (E:-Rl:)JlpAt)\ (15) Equation (15) is a set of nonlinear equations whose solution is as shown below Φ 6
+36R,EJa-36R:pJ R. £φ-2^Λ φ (16)(Π) V. The above-mentioned modeling of the input unbalanced pulse-wave width modulation converter is too long. [We know that in order to achieve the input flow Units, electricity, the negative sequence current 4 of the object is rotated by your positive sequence current, and the equivalent _ and line loss electric call are taken into account, phase = can be rewritten as follows: Type dn -E,
J dp (18) 1375387 operates on the input imbalance according to the pulse width modulation converter. It can be known from equations (10) and (17) that the negative sequence current has a positive sequence current, and the positive sequence current also has - The negative sequence current_synthesis, and the negative sequence is smaller than the positive sequence_synthesis, so the negative sequence can be omitted. Therefore, based on the analysis of the previous theory, the control device proposed by the present invention mainly eliminates the secondary chopping of the output side voltage and completes the current unit of the input side. The #1 diagram is the block diagram of the control device of the present invention. The control circuit for the sequence current uses the voltage-directed control law, while the equations (17) and (10) apply to the control circuit for the negative sequence current. In order to verify the feasibility of the proposed control strategy, the circuit simulation software PSPICE is used to simulate. The following parameters are simulated:
L = 1.6mH, Rs = 0.2 ohm, Co = 2200//F, e (〇 = 100cos^ + 10cos^ Γ, ω = 120π rad/s A (〇 = 1 〇〇cos( slave-2; z7 3) +10 cos〇, + 2;r / 3) F ^ = 100 cos(6?t + 2^- / 3) +10 cos(^ -2π/3) V For the sake of comparison, we discuss three control strategies. The first method is a single voltage controller, the second method is a dual controller, and the third method is the control strategy proposed by the present invention. The equivalent line loss & varies from 0.001 to 0.2 Ω. We can observe the amplitude of the secondary chopping of the DC link voltage, and the simulation results are sequentially arranged in Figure 13, Figure 14, and Figure 15, respectively, corresponding to the first method: a single controller that uses voltage steering, The second method: dual controller and third method: the control strategy proposed by the present invention. From the simulation results, we can observe that when 奂=〇.〇〇1Ω, the dual controller produces 12 1375387 The voltage chopping is smaller than the single controller method of the voltage-conducting. However, when 0.2Ω, the voltage chopping generated by the dual controller is better than the voltage-directed single-controller. The seriousness of this example shows that the traditional dual controller method does not consider the overall loss of the spool. However, the voltage chopping generated by the conventional dual controller is susceptible to the efficiency of the converter. The simulation waveform of the control strategy is as shown in Fig. i6. At this time, Α=α2Ω, Fig. 6(4) is the waveform of the negative sequence direct current/shape, and the i 6th is the waveform of the output voltage ,, Fig. 16 ( _ is to control the waveform of the direct axis and the sequence axis voltage ~KisN, VqsN of the mosquito frame. From the above simulation results, it can be seen that the control device provided by the present invention, the change of the line knows what the converter produces. The Bocoby single-controller's technical voltage (4) is close to the command value, and the money W is affected by the conversion efficiency', which is more robust than the traditional dual (four) device.
13 1375387 BRIEF DESCRIPTION OF THE DRAWINGS FIG. 1 is a control block diagram of the present invention. FIG. 2 is a control flow chart of the present invention. FIG. 3 is a power circuit architecture diagram of a three-phase AC/DC converter according to the present invention. FIG. Intersecting DC converter controller using a digital signal processor architecture diagram
5 is a circuit structure diagram of one phase of the input three-phase voltage sensor of the present invention. FIG. 6 is a circuit diagram of the output voltage sensor of the present invention. FIG. 7 is a two-phase current sensor of the present invention. FIG. 8 is a schematic diagram of an internal block of the present invention. The first block diagram of the present invention is a schematic diagram of the internal block of the 1-sequence current controller of the present invention. FIG. 10 is a signal of the positive sequence q-axis current command of the present invention. Command schematic
嶋本(4) 贞 d 轴 魏 命令 命令 峨 ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ The data graph of the controller simulation is based on the (4) reliance®, the ridiculously-sorted straight axis ^^; (b) is used to display the wheel-out voltage k(4) to show the negative sequence and negative sequence of the L and t mosquito frames. Cross-axis voltage 14 1375387 [Main component symbol description] Three-phase AC/DC converter controller 1 Positive sequence current controller 11 Negative sequence current controller 12 Positive sequence q-axis current command 13 Negative sequence d-axis current command 14 Negative sequence q-axis current Command 1 5 Voltage controller 16 Pulse width modulation module 17 Three-phase power supply 2 Input voltage sensor 31 Output voltage sensor 3 2 Current sensor 4 Input side three-phase inductor 5 Three-phase AC-DC converter 6 Regulated Capacitor 7 DC load 8 15

Claims (1)

1375387 VII. Patent application scope: 1.- A control device for input unbalanced three-phase boosting plastic AC/DC converter, mainly composed of - three-phase AC-DC converter and its controller: The pressure-type AC-DC converter controller comprises a separately operated AC/DC converter voltage controller, a pulse width modulation module and a positive sequence current controller, a negative sequence current controller, and a positive sequence q-axis current life. 7. A negative sequence d-axis current command and a negative sequence axis power eight. The AC/DC voltage control system will control the output of the cake and the output pressure. The axis current command is measured with the positive sequence q-axis current command and the current sensor: the actual positive sequence d minus the q-axis current and the voltage measured by the actual positive-sequence d-axis and q-axis voltage Output to the positive sequence current controller: the current sense ϋ4 measured actual negative sequence d-axis and q-axis current and the negative sequence d-axis current life 7, the negative sequence q-axis current command and the voltage sense The actual negative sequence d-axis and q-axis output measured by the detector are output to the negative current control ^ 'and then the red sequence The parent control (4) is added to the value generated by the step current controller J, and sent to the pulse width modulation module to generate six switching signals for driving the six switches of the AC/DC converter to Achieve the input and reduce the generation of the second wave of the transmission voltage. 2. The control device for the input unbalanced three-phase boost type AC-DC converter according to the first aspect of the patent scope, wherein the input side of the three-phase AC-DC converter is a three-phase power supply, and the output The side is a "DC load, and the one-phase AC-DC converter is connected to the three-phase AC-DC converter.
TW098105251A 2009-02-19 2009-02-19 TWI375387B (en)

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