TWI296460B - High-performance power conditioner for clean energy with low input voltage - Google Patents

High-performance power conditioner for clean energy with low input voltage Download PDF


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TWI296460B TW95101845A TW95101845A TWI296460B TW I296460 B TWI296460 B TW I296460B TW 95101845 A TW95101845 A TW 95101845A TW 95101845 A TW95101845 A TW 95101845A TW I296460 B TWI296460 B TW I296460B
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TW200729683A (en
Rong Jong Wai
Wen Hung Wang
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Univ Yuan Ze
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1296460 IX. INSTRUCTIONS OF THE INVENTION: TECHNICAL FIELD The technical field to which the present invention relates includes automatic control, power electronics, DC/DC conversion technology, DC/AC converter technology, and energy technology, although the present invention relates to It has a wide range of technologies, but it mainly uses clean energy in decentralized power generation systems to improve the current lack of clean energy for distributed power generation systems. [Prior Art] Although advances in science and technology have brought many conveniences to human life, they have also spawned many problems such as: reduced stock of fossil fuels, rising awareness of energy crisis, rising awareness of environmental protection, norms of Kyoto Protocol, and energy prices. In addition to reducing the waste of existing energy use, the development of new energy is an urgent task. Generally, new energy has little impact on the environment, and the pollution caused by air, water or waste is less significant. Clean energy such as solar energy, fuel cell and wind power are more important in new energy. [1,2], if the power conversion system uses a low-voltage power source such as solar energy or a fuel cell as an input, the DC power supply must be converted into an AC power source for use by the load via the power conditioner [3, 4], generally It includes DC input power, Power Conditioner, distribution box, transformer, battery, etc. The power regulator is mainly composed of DC/DC converter, DC/AC converter and system controller. And depending on the application and user needs. When the input voltage of the system is low, the required DC bus voltage [5, 6] is formed in series, but the bus voltage is easily affected by the load, which makes the design of the rear 1296460 converter difficult and The problem of poor power quality occurs when the DC load is supplied; in addition, if the power generation function of any module in the series module is degraded or malfunctions, the overall power generation system performance is greatly reduced. Therefore, the output of the AC power supply is generally completed by a two-stage power conversion method, and the input voltage is first stably boosted by the DC/DC converter, and then converted into an AC voltage output via the DC/AC converter. The conventional DC/DC boost circuit usually adopts a boost converter circuit composed of a single inductor. The power semiconductor switch in the circuit is subjected to high voltage, large current and reverse recovery surge current of the output diode. The power conversion efficiency is not as good as the 'boost limit' is about seven times the south. Secondly, with the transformer boost, the boost range is limited by the turns ratio. If the leakage inductance energy cannot be effectively processed, the conversion efficiency is difficult to increase. In order to improve the problem, the present invention uses the high-boost ratio conversion circuit of the coupled inductor bidirectional magnetic circuit energy transfer of reference [7] to replace the conventional circuit, which has the advantages of high step-up ratio and better conversion efficiency, and can provide system continuous flow. High-efficiency DC/DC power conversion with voltage boost ratios over thirty times higher. In order to make the clean energy power conversion system stable power supply, this paper uses microprocessor to control the converter. When solving the control problem, it often encounters parameter changes and various uncertainties. There are various types in the control field. Control theory, such as Proportional-Integral_Derivative (PID) control [8], or modern control theory using complex equations such as Computed Torque Control (Computed)

Torque Control), sliding mode control (Siiding_M〇de Control) [9,10], etc. are all designed to make the system 7 1296460's behavior conform to the design requirements of system parameters and various external disturbances. Proportional, integral, and derivative controllers are simple to use, easy to design, and low in cost, so they are widely used in the industry's. However, for systems with uncertain dynamics, proportional-integral-derivative controllers do not provide perfect performance. Computational torque control uses a nonlinear term that eliminates some or all of the nonlinear equations to obtain its linearization equation, and then designs a linear feedback controller to violate the designed closed loop control characteristics. However, since the calculated torque control is based on the idealized theory of eliminating nonlinear dynamics, its shortcoming is the lack of understanding of the system uncertainty I in the time domain, including system parameter changes and external disturbances. Control gain to achieve system robustness and system stability. Variable Structure Control or Sliding Mode. Control is one of the effective methods of nonlinear robust control [9_18], because • the dynamics of the controlled system are not subject to system non-disc and quantification Impact. The design of the sliding mode control system can be divided into two major steps. Firstly, according to the required closed loop control, the sliding flat in the state change space is selected. The surface design control law makes the system state move toward the sliding plane and keeps sliding. on flat surface. The situation before the system state trajectory touches the sliding plane is called the Reaching Phase. Once the system state trace reaches the sliding plane, the system state remains on the plane and faces the target point. This condition is called the sliding phase. (Sliding Phase). However, when the system state is in the near phase, it will still be affected by system parameter changes and external interference. Therefore, many scholars have proposed the approach phase design or the total sliding mode control (Total Sliding-Mode Control) to reduce the system uncertainty. The impact [12-15]. Gao and Hung [12] jointly studied the design of the special law 12 1296460 to determine the dynamics of the system state when the phase is approaching, but in this case the system uncertainty will still affect the system control performance. Global, sliding mode control [13-15] means that the control process does not have an impending phase mode and all states are on the sliding plane, and the whole control process is not affected by the system uncertainty. 'But it may still cause control tremor and Stimulate system instability. In the past few years, many researchers have used the Boundary Layer concept [16, 17] to eliminate the control tremor phenomenon. Unfortunately, if the inappropriate boundary layer width is chosen, it will easily cause the unstable control response of the system. There is no guarantee of stability in the boundary layer. Therefore, some scholars have introduced an adaptive algorithm that can handle uncertainty estimation [18] in order to reduce the control tremor phenomenon. The present invention uses this method to apply to the control of a full-bridge converter. In addition, the equivalent mathematical model of the traditional full-bridge converter is based on resistance and sexual load [19]. After obtaining the equivalent mathematical model, the design and stability of the system controller are analyzed, but usually in the load nature. When changing, the stability of the control system will no longer be guaranteed and the system response will be degraded. In view of this, the present invention utilizes state space averaging method and linearization technique to deduct the mathematical equivalent model and replace the traditional resistive load-based converter equivalent model in the form of unknown load, so that the system can be applied to Various loads. Remarks: References [1] S. R. Bull, "Renewable energy today and tomorrow/5 Proc. IEEE, vol· 89, no. 8, pp· 1216-1226, 2001.

[2] S. Rahman, “Green power: what is it and where can we find it?,” IEEE Power Energy Mag., vol. I, no. 1? pp. 30 — 37, 2003. 9 1296460 [3] S. Duryea, S. Islam, and W. Lawrance, "A battery management system for stand-alone photovoltaic energy systems/9 IEEE Ind Appl Mag., vol. 75 no. 3? pp. 67 — 72, 2001.

[4] K. Raiashekara, “Hybrid fuel-cell strategies for dean power generation Z, IEEE Trans. Ind. ΑρρΙ, νοΧ. 41? n〇· 3, pp. 682 — 689, 2005.

[5] T·F· Wu, CH Chang, and Y·H. Chen, “A fuzzy-logic-controlled single-stage converter for PV-powered lighting system applications^ IEEE Trans. Ind. Electron., vol. 47? No. 25 pp. 287 — 296, 2000.

[6] T. J. Liang, Y·C· Kuo, and J· F Chen, “Single-stage photovoltaic energy conversion system^ IEE Proc. Electr, Power Appl, vol. 148, no. 4, pp· 339 — 344, 2001.

[7] R. J. Wai and R. Y. Duan, “High step-up converter with coupled-inductor/5 IEEE Trans. Power Electron., vol. 20? no. 5, pp. 1025-1035, 2005.

[8] K. J. Astrom and T. Hagglund, PID Controller: Theory, Design, and Tuning. Research Triangle Park? NC: ISA? 1995.

[9] Κ·K· Shyu, Y·W· Tsai, and C·K· Lai, “Sliding mode control for mismatched uncertain systems/9 Electronic Letters, vol. 34, no. 24, pp· 2359-2360, 1998 · 10 1296460 [10] Κ· K. Shyu, Y. W. Tsai, and C· Κ· Lai, “Stability regions estimation for mismatched uncertain variable structure systems with bounded controllers/5 Electronic Letters, vol. 35, no. 16 Pp. 1388-1390, 1999.

[11] V. I. Utkin, “Sliding mode control design principles and applications to electric drives/5 IEEE Trans, Ind Electron., vol. 40, no. 1, pp· 23 — 36, 1993.

[12] W. Gao and J. C. Hung, "Variable structure control for nonlinear systems: a new approach/9 IEEE Tran. Ind. Electron^ vol. 40? no. 1, pp. 2 — 22, 1993.

[13] J. C. Hung, “Total invariant VSC for linear and nonlinear systems,” A seminar given at Harbin Institute of Technology, Harbin, China, Dec 1996; Hunan University Changsha, China, Dec. 1996.

[14] K. K. Shyu and J. C. Hung, "Totally invariant variable structure control systems/5 IEEE Conf Ind Electron. Contn Instrument., vol· 3, pp·1119—1123, 1997.

[15] K. K. Shyu, J. Y. Hung, and J. C. Hung, “Total sliding mode trajectory control of robotic manipulators/5 IEEE Conf. Ind Electron. Contr. Instrument., vol. 3? pp. 1062-1066, 1999.

[16] J. J. E. Slotine and W. Li? Applied Nonlinear Control. Englewood 1296460

Cliffs, NJ: Prentice-Hall, 1991.

[17] K. J. Astrom and B. Wittenmark, Adaptive Control. New York: Addison-Wesley, 1995.

[18] R. J. Wai, uAdaptive sliding-mode control for induction servo motor drived IEE Proc. Electr. Power Appl, vol. 147? no. 6? pp. 553-562, 2000.

[19] SL Jung and YY Tzou, "Discrete sliding-mode control of a PWM inverter for sinusoidal output waveform synthesis with optimal sliding curve/5 IEEE Trans. Power Electron., vol. 11, no. 4, pp· 567- 577, 1996· [Invention] The overall architecture of the high-performance low-input voltage clean energy power conversion system disclosed in the present invention, as shown in FIG. 1, the low input voltage clean energy is represented by a low-voltage DC power source 10, and its output voltage Γ/; ν is connected with the high step-up ratio DC/DC conversion circuit 20 to provide DC/DC voltage conversion with high step-up ratio and high conversion efficiency of the system. The high step-up ratio DC/DC conversion circuit architecture is shown in FIG. 2, and the DC input circuit 201 is The DC voltage Κ/ΛΓ, when the power semiconductor switch 2 of the primary side circuit 202 is turned on, the current is stored in the first horse winding inductor 7; the secondary side circuit 204 is coupled to the secondary side of the inductor & Winding A has a bidirectional current conducting loop, the induced voltage % (the polarity point is positive at this time), and the clamped capacitor q voltage of the regenerative passive cushioning circuit 203 is connected in series, The power semiconductor switches and the discharge diode 2 2 is the circuit for the secondary-side high-voltage capacitor circuit 204 〇2 (charging current -t). When the power 12 1296460 semiconductor switch 2 is turned off, the primary side circuit 202 current leaves the power semiconductor switch ρ, and the clamped diode Di of the regenerative passive cushion circuit 203 flows into the clamped capacitance of the circuit. The current L of the secondary side circuit 204 must use the clamp diode q and the discharge diode to be 2 freewheeling to release the energy stored in the leakage inductance of the inductor r__human side winding A, by the high voltage capacitor & In the absorption-moon ,, after releasing the secondary side winding &amplitude leakage energy, the rectifying diode of the magnetic flux 205 is turned on and the filter capacitor of the circuit is turned on, thereby obtaining a DC voltage that is not easily changed (for improving f) The DC busbar voltage of the single-stage clean energy power conversion system is susceptible to the fluctuation of the load, and is connected to the full-bridge converter 30. At the same time, the DC voltage can be regarded as a fixed value, and The design of the dynamic control system of the rear-stage converter. The movable shoulder, effectively simplifying the converter [formula derivation] Let the coupled inductor 7; the primary winding ^ and Μ, the combination coefficient 々 is defined as the human side winding & (4) k L· (1) L, Lm where 4 is the magnetizing inductance (also known as mutual inductance), % is not

Gn=^ = l±!± + £(t^Xn~l) ^in 1-D l — D Sense' By the analysis of the circuit, it can be deduced that the leakage of the side winding a is affected by Forest type (2) and equation ^^ voltage gain and open 13 (2) 1296460

'DS + 1 - D 2 (1 - D)

^IN (3) where D is the duty cycle of the switch, so that the coupling coefficient A: is equal to 1, the formula (2) and equation (3) can be rewritten as follows:

Gv\ =

Vd _2 +



Vin/(\ — D) (4)(5)

Substituting equation (5) into equation (4), the voltage value of the switch can be obtained as follows: VDS = + (6) Observe equation (6), fix the output voltage 匝 and turns ratio π, and the power semiconductor switch δ The voltage is independent of the input voltage factory and the duty cycle d, thus ensuring that the highest voltage to which the power semiconductor switching element is subjected is constant. As long as the input voltage is not higher than the withstand voltage of switch 2, the conversion circuit designed according to equation (6), in combination with the original high voltage gain ratio, will accept input voltages with high and low voltage variations. The full-bridge converter 30 is connected to the high-boost DC/DC converter circuit 20 for DC/AC conversion. The system control unit 50 includes a microprocessor 60 and a drive circuit 70. The present invention transmits feedback through the system state. The microprocessor 60 controls and outputs a driving signal by a unipolar (unipolar) voltage switching method in a sinusoidal pulse-width-modulation (SPWM) technique, and the driving circuit 70 of the converter is fully integrated. The four power crystal switches of the bridge converter 30 are controlled, and the output thereof is connected to the low pass filter 40, thereby filtering the AC voltage, 14 1296460 to know the sinusoidal output voltage v〇 of the design, and supplying power to the load 8〇 use. The decoupled system equivalent circuit is shown in Figure 3. In order to make the description simple and easy to understand that 'proper nouns are not too long, the circuit attribution figure number (such as ... circuit 忉) is omitted, directly compare the description of the schema It will be clear. In the figure, p is the DC busbar voltage of the high-boost ratio DC/DC converter circuit. The voltage of the DC busbar is two. The DC busbar I is modulated by the full-bridge converter and contains the high-frequency spectrum of the component. The component can be filtered by a low-pass filter composed of a filter inductor Zy and a filter capacitor, and further obtain an AC output voltage V〇 and provide a load & use, and a seven-wave inductor and a filter capacitor respectively. Equivalent internal resistance 'and electric "interference current caused by load deuteration. For the convenience of analysis and simplification of the derivation of the state space equation" This paper assumes that (1) the filter inductance ^ and the filter capacitor & equivalent internal resistance is small ' Therefore, it is neglected; (2) Assume that the power is turned off as an ideal component, the conduction loss and switching loss of the switch are zero; (the reaction delay time of the wall switch is turned on and off; (4) the switching frequency of the switch is much larger than the natural frequency of the system. And the modulation frequency 'because the control signal and the input/output voltage can be regarded as fixed values during the switching period of the switch. ... according to the above assumptions, the power of the unipolar sinusoidal pulse width is modulated. The switching mode is divided into positive and negative half cycles. Since the voltage polarity of the negative half cycle is opposite to that of the positive half cycle, the operation principle is similar to that of the positive half cycle. Therefore, the following detailed analysis is introduced in the positive half cycle. The switch has two in the positive half cycle switching. For different states, the equivalent circuit is shown in Figure 4. Therefore, the dynamic space equation for the whole positive half cycle can be expressed as 15 1296460 VC/ (7) (8) WC/ where the positive half cycle is deduced by the state space averaging method and linearization technique. (9) " is: cut 1 is the current of the filter inductor, filter capacitor and load, especially the period Α = ν (10) / 1 · and the bridge power level gain ί tν (10) is The sinusoidal control signal, which is a triangular wave signal, and the equations (7) to (9), the dynamic model of the I system can be changed; the private mode of the mouth (10)*, and the transformation of the τ face by the Lagrangian f〇_ can further optimize the converter The model representation is shown in Figure 5.



LfCf ' ---i

LfCf'con C/〇rC~fid (10) Select the AC output voltage νσ as the system state and %” as the control variable, then equation (10) can be rearranged as follows···^(0 ~ aPx(t) + bpu{ t) + cpz(t) + m(t) ~ (apn + ^apn)x(f) + (bpn + Abpn)u(t) + (Cpn+Acpn)Z(t) + m(t) =αρηχ (β) + bpn^(t)+Cpnz(t) + W(t) ( n ) where 4t) = v0, u(t) = vcon, af_vwc", bp=KpwM/(LfC〇, cp = -l/c, LL and %, heart and c〆 respectively represent the system parameters of α〆~ and in the normal state; △%, △心 and Ac^ represent the system parameter disturbance amount; w(〇 represents the total set uncertainty and is defined Let w(t) = Δα^χ(〇+ Abpnu(t) + h, cpnz{t) + m(t) (12) 1296460 where the boundary value of the total set uncertainty is given as shown in equation (13), Where p is a positive constant. |w(0| < P (13)

In order to make the full-bridge converter follow the voltage command effectively under the condition of uncertainty and external interference, the present invention adopts Adaptive Total Sliding-Mode Control (ATSMC) to change the current. The output voltage of the device is controlled, as shown in Figure 6, the control error is defined as -X - V〇^cmd 'the center / is the output voltage command, and the sliding plane is designed to be (0 = c(e) c(e〇) ~ j-rAedr (14) where e = [e έ]Γ, A= j 1 , homogenization and moxibustion 2 are positive constants, c(4) generation one-allow 2 - allow 1" table index function and design it as <〇 initial value 0 The adaptive global sliding mode control system can be mainly divided into three parts: • The first part is the system performance planning, which is mainly to specify the system performance expected under the normal situation and to attribute it to Baseline Model Design~; The second part is the construction of the Curing Controller wc, which eliminates the unpredictable disturbances from system parameter changes, load disturbance currents and unpatterned system dynamics. Effect Can fully meet the system performance of the basic model design; in addition, the third part is the development of adaptive algorithm (Adaptive Observation Design) ^, the upper bound of the total set of uncertainty estimates, 17 1296460 to avoid the constraint controller The control tremor caused by improper selection of the upper bound. The overall control design of the adaptive global sliding converter control system is shown in Theorem 1. In addition, if the DC/AC conversion mechanism of the system is changed in the same way, it can be performed in the same way. Derivation, and then complete the design of the converter control system. [Theorem 1] Assume that the full-bridge converter shown in equation (11) adopts adaptive global sliding mode control, and the various parts of the controller are designed as equations (15) to equations ( 17) and develop the adaptive algorithm as shown in equation (18), then the stability of the system will be guaranteed. u = ub +uc (15) ub = -bpln(apnx + cpnz - + Ι^έ + k2e) (16) uc =-p(〇^sgn(^(〇) (17) kt) = jb-pln\Sl(t)\ (18) where sgn(·) is a sign function and · is an absolute value Function, ;l is a positive constant. [proof] According to Riapuno (Lyapunov) stability theory [16,17] analysis, the stability of the converter control system will be guaranteed, because the proof of theorem 1 is roughly the same as the reference [18], so it will be omitted. [Embodiment] The present invention The disclosed high-performance low-input voltage clean energy power conversion system adopts six F-MSN-75W-R-02 solar panels produced by Motech to be connected as a low-voltage DC power supply with high boost ratio DC/DC. The conversion circuit is used, the solar panel under the standard test condition 1296460 2, the electrical specifications of the board is rated output power is Μ567Λ, the output voltage of the jaw is 1T228V, the rated output current is the conversion efficiency; the pressure is η··, and the short-circuit current is 4 · 9649Α and photoelectric switch ^ main 彳 ',, ' · 92 / °, because the high boost ratio DC / DC conversion circuit open 35I Bay * cycle D is about G · 5, will make each circuit component conduction current has = 涟The wave component's special conduction relationship is a complementary component, and its influence is more, and the 'the solar panel input voltage is close to the maximum power at around 17V—and there is a good use efficiency of #x, so the equation can be Equation (4), and the set value 疋 output voltage is 2GGV ′. The design (4) of the present invention is equal to 4, and the maximum clamp voltage of the switch is 34V by the equation (6). Even if the minimum input voltage is 1 〇V and the output voltage is 2 〇〇V, the duty cycle Z) at this time can be calculated by equation (4) as G.7 ’, which is a practically acceptable value. The invention has a high-boost ratio DC/DC conversion circuit switching frequency *1 〇〇 kHz, which is a frequency switching frequency used by the general industry, and the detailed circuit specifications are as follows:

Vd : DC 200V

Tr : L{ =9μΗ ; I2 =143μΗ ; Nx : N2=3 : 12 ; k=0.97 ; core : EE-55 Q : IRFP048N : 55V/64A ; CIN : 3300μΡ/50Υ*2 Cx : 6.8μΡ/10〇 ν ; C2 : 1μΡ/25〇ν*2 ; C〇: 47μΡ/45〇ν*2 Dx : SB2060, 60V/20A (Schottky), TO-220AC D2, D〇: SB20200CT, 200V/20A (Schottky), TO-220AB To understand the contents of the high step-up ratio DC/DC converter circuit used in the present invention, the experimental waveforms of the following embodiments, the voltage and current codes of the circuit components, please refer to FIG. 1296460 South boost ratio DC / DC conversion circuit in the output power 4 〇 w (light load) and 320 W (heavy load) real response as shown in Figure 7 and Figure 8, from the figure can be found at the voltage across the switch ~ It is clamped at about 34V, and the switching current is approximately ^ wave, which shows that the switch has better utilization and can reduce the conduction loss. View all the diode voltage and current waveforms, the reverse recovery current is lower than the on current, and in the absence of the cushioning circuit, there is no surge voltage at both ends of the diode and lower than the output voltage of 200V, indicating The diode has achieved voltage clamping and flexible switching effects. It is worth mentioning that the current leakage is discontinuous at light load, and the leakage inductance of the primary side and secondary winding of the coupled inductor will resonate with the parasitic capacitance inside other components, such as The waveform of the v melon in Fig. 7 is caused by the leakage inductance of the primary side winding and the resonance of the internal parasitic capacitance of the switch. Figure 9 is a high-boost ratio DC/DC converter circuit. When the load is changed from 8〇w遂 to 320W, the current center of the rectifying diode, the voltage v and the voltage of the switch 2 are reflected. It is found that the voltage of the diode is below 2〇〇v under different loads, and the switching!β voltage still has a good clamping effect. Figure 10 shows the conversion efficiency under different loads. The maximum conversion efficiency of the circuit exceeds 96.5%. The conversion efficiency is above 95% at light load, thereby verifying the effectiveness of the high step-up ratio DC/DC conversion circuit used in the present invention. The invention adopts the digital signal processor TMS320LF2407A produced by Texas Instruments Co., Ltd. to realize the adaptive global sliding mode control in the full bridge converter, the switching frequency of the switch is 20 kHz, and the detailed circuit rules of the converter are as follows:

Ta+Ja-Jb^tb^ : IRFP264:250V/38A 20 1296460 〇/:26.8μΡ Also. The ten system, the first wheel voltage command is 110Vrms/60Hz, and the control variable hook = 249 Z, _, sex / · 9 heart = 830, and = 1.66; Figure 11 shows the system using the basic model control in the resistance system The response of the adaptive and global sliding system is shown in Figure U(a). The system response via the basic model can be found to have response errors, while adaptive global sliding

Γ It can help the system overcome the response error caused by the uncertainty, and ®^, Harmonic Distortion (1 HD), such as 圄11 a, resistive, Kb) is shown. Fig. 12(a) and Fig. 12(b) show the actual response of the system to the load and the heavy load and the heavy load to the light load. The figure shows that the system recognizes & When the system changes, the output voltage can still follow the life, ",,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,, The actual response, from the graph load: "**13 (a) and Figure 13 (b) can be found that the system has a good control response to the resistive capacitive 丄 resistance inductive load, and in the non-linear load a year, & 2 ^Net, due to the instantaneous change of output current caused the output voltage to pay $ &# ^ at the peak point p, but the total harmonic distortion of the system output voltage is still within 5% of the harmonic control specification. [Simple description of the map]

Round 1 I 发明 Invented the overall architecture of a high performance, low input voltage clean energy power conversion system. Figure 2 jk shows the horse-boost ratio DC/DC conversion circuit architecture for high-performance, low-input, clean energy power conversion systems. "3 The high performance low input voltage clean energy power conversion system of the invention 21 1296460 equivalent circuit. Fig. 4 Two states of the full-bridge converter of the high performance low input voltage clean energy power conversion system of the present invention when switching in the positive half cycle·(a)G+ and conduction; (b)h+ and 4+ conduction or heart- And conduction. Fig. 5 is a converter equivalent model of the high performance low input voltage clean energy power conversion system of the present invention. Figure 6 is an adaptive global sliding mode converter control system for a high performance, low input voltage clean energy power conversion system of the present invention. Fig. 7 shows a high-boost ratio DC/DC conversion circuit embodiment of the high-performance low-input voltage clean energy power conversion system of the present invention, which is applied to a voltage and current waveform of each component when the solar panel is boosted to 200V and the output power is 40W. FIG. 8 is a schematic diagram of a high step-up ratio DC/DC conversion circuit of the high performance low input voltage clean energy power conversion system of the present invention, which is applied to voltage and current waveforms of various components when the solar panel is boosted to 200V and the output power is 320W. 9 is a high-boost ratio DC/DC conversion circuit embodiment of the high-performance low-input voltage clean energy power conversion system of the present invention, which is applied to a solar panel boosted to 200V, and the output power is changed from 80W to 320W, k, and ¥ Waveform. Fig. 10 is a schematic diagram of a high step-up ratio DC/DC conversion circuit of the high performance low input voltage clean energy power conversion system of the present invention, which is applied to a conversion efficiency when the solar panel is boosted to 200V and the output power is changed from 40W to 320W. 22 1296460 Figure 11. One of the embodiments of the converter control system for the high performance low input voltage clean energy power conversion system of the present invention, the system's actual response under resistive load: (a) basic model control; (b) adaptability Global sliding mode control. 12 is an embodiment of an adaptive global sliding mode converter control system of the high performance low input voltage clean energy power conversion system of the present invention, and the actual response in the case of resistive load: (a) light load to heavy load; (b ) Heavy to light load. Figure 13 is an adaptive global sliding mode converter control system of the high performance low input voltage clean energy power conversion system of the present invention that responds at different loads: (a) resistive capacitive load; (b) resistive inductive load; c) Non-linear load. [Main component symbol description] 10: Low-voltage DC power supply 20: High-boost ratio DC/DC conversion circuit 201: DC input circuit 202: - Secondary circuit 203: Regeneration passive mode circuit 204: Secondary circuit 205: Filter circuit 30 : Full-bridge converter 40: Low-pass filter 50: System control unit 60: Microprocessor 23 1296460 70: Drive circuit 80: Load: Low-voltage DC power supply Output voltage: Low-voltage DC power supply output current ^: High step-up ratio DC /DC converter circuit output voltage: full-bridge converter output voltage full-bridge converter output current 7;: transformer with high excitation current (referred to as coupled inductor) • 2: high boost ratio DC/DC converter circuit power Semiconductor switch A: coupled inductor primary winding A: coupled inductor secondary winding. 4: coupled inductor primary side magnetizing inductance 4: coupled inductor primary winding leakage inductance c/7V: DC input circuit input capacitor q: regenerative passive slow Clamping capacitor c2 of the shock circuit: high-voltage capacitor of the secondary circuit®: filter capacitor of the filter circuit A: clamped diode of the regenerative passive cushion circuit Z) 2: regenerative passive Discharging diode circuits: the filter circuit rectifier diode 24

Claims (1)

1296460 X. Patent application scope·· h—A high-performance, low-input-voltage clean energy power conversion system, including a low-voltage DC power supply: consisting of a low-voltage direct-state power supply or clean energy; DC/DC conversion circuit: converts low-voltage DC power supply into high-voltage DC energy source and outputs it to a high-voltage DC busbar; a system control unit: which includes a microprocessor and a driving circuit for system control; Bridge converter: consists of four power transistor switches connected to the 咼 直 ML hui yi row, controlled by the system control unit for DC / AC voltage conversion; a low pass filter · · A filter inductor and a filter capacitor are connected to the output end of the full bridge converter for filtering the AC voltage; the system is characterized in that the system can accept a low voltage input power source with different electrical characteristics, and provides a boost ratio and High conversion efficiency DC/DC voltage conversion, allowing system inputs to operate in parallel to avoid overall failure caused by series boost The problem 'improves the performance of the system; another, the DC bus voltage is stable, easy to change, can be regarded as a fixed value, and is dynamically decoupled from the latter converter, which has a simplified design of the moxibustion control system. At the same time, the system uses the microprocessor to control the dual-flow control strategy. In addition to effectively planning the system performance, it has the ability to compensate for the amount of deterministic and external interference, so that the system can supply stable power under various loads and reduce the total harmonics of the output voltage. The amount of distortion. 25 1296460 The high-performance low input voltage clean energy two-conversion system described in Item 1 of the source power fan park, in which the DC/DC conversion circuit package is encoded; The second circuit includes a power semiconductor switch and a coupling electrical connection; the polarity point is defined with the positive input of the DC input circuit = the passive passive circuit: a clamped diode, a discharge diode and _ Clamping capacitor; human side circuit. Contains a high voltage capacitor and a winding 'the polarity point is defined at the junction with the high voltage capacitor; ―, the wave circuit filter, wave capacitor and a rectifying diode are formed; person, circuit The power semiconductor is turned on (four) material, the current will store energy = a inductor - the sub-sector, the voltage of the secondary winding of the same inductor is positive 'the winding electric (four) regenerative passive slow-shock circuit, the voltage, the voltage Regeneration passive cushioning circuit discharge diode, Shi = South is willing to low current to charge the high-voltage capacitor of the secondary circuit; when the power is half-two open, cut-off, regenerative passive cushioning circuit clamp capacitor, through the j circuit preparation two The polar body first absorbs the surface-inductance—the leakage inductance of the secondary side can be set, and the current steering of the secondary winding of the inductor is to be engaged. The non-polarity of the winding is positive, and the primary winding of the series is combined with the excitation of the primary winding. The flow is in the non-polar! The positive voltage, the DC input voltage and the secondary side circuit high voltage, the voltage of the four voltages, the rectified diode of the Chengcheng circuit, the charging of the chopper capacitor 'to obtain a stable DC output Voltage; characterized by high boost ratio and high conversion efficiency, the voltage clamp function can be achieved by both the switch and the diode, the short-circuit current when the switch is not turned on, and the reverse high recovery current of the second 12 1249660 polar body, and The current ripple is low, and low-cost high-efficiency components suitable for the voltage range can be selected respectively. The device proves that the conversion rate and the boost ratio are not directly related, and whether the duty cycle and the switch conduct current are related to the square wave. The technical bottleneck of the conventional circuit that overcomes the higher the boost ratio and the lower the efficiency; the voltage with which the power semiconductor switch is subjected is only related to the output voltage and the ratio of the combined inductance. This feature is more suitable for the power conversion device with a wide range of DC input voltage variation. application.
= Lizhong # lawei, the high-performance low-input voltage clean energy mouse power conversion system described in item 1, where the microprocessor implements an adaptive global sliding mode strategy and has a built-in pulse width modulation output module. The wave width is output to the output module, and the pulse width modulation signal is output, and the power transistor of the full bridge converter is driven by the converter driving circuit to generate a sinusoidal voltage rotation. 4·If the scope of the patent application is 3rd, the low-input voltage clean energy conversion system, which is ## π ^ ^ ^ ^ from the treatment of the adaptive global sliding control Including a system performance planning performance; • Clearly plan the system to expect the system to obtain the second controller; eliminate the generation of parameters from the _ system, load dry to avoid I (four): the upper bound of the uncertainty is estimated 'shake Phenomenon, ·,, I system ◎ control tremor caused by improper selection of upper bounds, especially (4) process does not exist impending phase (four) and all states are 27 l29646 〇 : 广 广 广 广 广 ' ' ' ' ' The system uncertainty -^ can effectively reduce the control force tremor phenomenon, and at the same time, the unknown load = the completion of the traditional converter-based converter equivalent model, so that the system can be applied to various loads and has a lower The total amount of voltage harmonic distortion.
TW95101845A 2006-01-18 2006-01-18 High-performance power conditioner for clean energy with low input voltage TWI296460B (en)

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