KR100912831B1 - Method And System For Controlling High Intensity Discharge Lamp Using Digital Signal Processor - Google Patents

Abstract

The present invention relates to a lamp control method and system using a digital signal processing apparatus, the disclosed lamp control method and system is applied to the lamp from the power factor corrector and the input voltage and input current to generate an input voltage and an input current having the same phase An electronic ballast which generates an output voltage and an output current is characterized by being controlled by one central processing unit. According to the present invention there is an advantage that the price is much lower than the existing product and the volume of the whole product is reduced, the compatibility of the product is increased, and also capable of coping with a high capacity input and output source.

DSP, lamp, power factor compensator, electronic ballast.

Description

Method and System for Controlling High Brightness Discharge Lamp Using Digital Signal Processing System

1 is a block diagram of a lamp control system according to the present invention.

Figure 2 is a circuit diagram of the voltage source and rectifier circuit according to the present invention and a graph showing the waveform of the power supply voltage and power supply current.

3 is a circuit diagram of a power factor corrector according to the present invention.

Figure 4 is a graph showing the waveform of the current flowing through the inductor of the power factor corrector according to the present invention.

Figure 5 is a graph showing the operation waveform of the power factor corrector under the control of the controller according to the present invention.

Figure 6 is an equivalent circuit diagram according to the operation waveform of the power factor corrector according to the present invention.

7 is a graph showing a current waveform according to the control method of the power factor corrector according to the present invention.

8 is a block diagram illustrating a module for controlling a power factor corrector in a controller according to the present invention.

Figure 9 is a graph showing the waveform of the power supply current of the voltage source according to the present invention.

Figure 10 is a graph showing the waveform of the output voltage and the current flowing in the inductor of the power factor corrector according to the present invention.

11 is a basic structural diagram of a typical metal halide lamp.

12 is a graph showing the characteristic between voltage and current of gas discharge in a typical metal halide lamp.

FIG. 13 is a graph showing negative resistance characteristics of a metal halide lamp. FIG.

14 is a circuit diagram of an electronic ballast in accordance with the present invention.

15 is an equivalent circuit diagram of an electronic ballast according to the present invention.

16 is a graph showing the frequency characteristics of the electronic ballast according to the present invention.

17 is an equivalent circuit diagram of an electronic ballast according to the present invention.

18 is a graph showing the output frequency characteristics of the electronic ballast according to the starting state and the normal state of the lamp according to the present invention.

19 is an equivalent circuit diagram of an electronic ballast according to the present invention.

20 is a graph showing the movement of the operating point according to the change in frequency in the electronic ballast according to the present invention.

21 is an exemplary photograph actually implementing a lamp control system according to the present invention.

22 is a graph showing a simulation waveform of the starting voltage in the starting state in the electronic ballast according to the present invention.

23 is a graph showing the waveform of the starting voltage measured in the starting state in the electronic ballast according to the present invention.

24 is a graph showing a simulation waveform of the output voltage and the output current in the steady state in the electronic ballast according to the present invention.

25 is a graph showing waveforms of output voltage and output current measured in a steady state in an electronic ballast according to the present invention.

The present invention relates to a lamp control method and system using a digital signal processing apparatus. More specifically, the present invention relates to a lamp control method and system for allowing a power factor corrector and an electronic ballast to be controlled by a central processing unit.

High Intensity Discharge Lamps (HIDs), such as metal halide (MH) lamps, are bright and have low power consumption, which is extremely useful in terms of user satisfaction and energy saving.

However, high brightness discharge lamps require a high pulse waveform starting voltage. In addition, since the lamp is turned on by using arc discharge, a ballast circuit is needed to control the current when the lamp is turned on.

In recent years, interest in reducing harmonics and power factor correction circuits has increased due to the strengthening of various international regulations on harmonics such as the European standard IEC 1000-3-2. This is because a large amount of harmonics are generated in the input current in the power conversion system using a conventional diode rectifier at the input stage, thereby causing a lot of problems. Accordingly, the adoption of a power factor correction circuit for unit power factor has become commonplace in low and medium power converters applied to high-brightness discharge lamps.

For this purpose, the power factor correction circuit of the high intensity discharge lamp and an electronic ballast products have been developed by the semiconductor companies such as Fairchild ^{TM, ®} On Semiconductor, Texas Instrument ^TM.

However, conventional power factor correction circuits and electronic ballasts are often implemented by configuring analog circuits using dedicated integrated circuits, resulting in incompatibility, increased product volume, and increased product development period and cost. In addition, there is a problem that a lot of cost and time are consumed when adding new functions and improving performance of a product in the future.

In addition, the existing electronic ballast products developed at home and abroad has a problem that the electronic ballast products are developed only for the lamp of a low capacity of less than 300W.

In order to solve the above problems, an object of the present invention is to provide a lamp control method and system using a digital signal processing apparatus.

In particular, it is an object of the present invention to provide a lamp control method and system in which a power factor corrector and an electronic ballast are controlled by a central processing unit through pre-input software.

In order to achieve the above object, the present invention is connected to a power factor corrector and a power factor corrector for generating an input voltage and an input current having a waveform having the same phase to generate an output voltage and an output current to be applied to the lamp from the input voltage and the input current. An object of the present invention is to provide a lamp control method and system for controlling an electronic ballast in a central processing unit.

1 is a block diagram of a lamp control system according to the present invention. This will be described with respect to the lamp control system of the present invention.

As shown in FIG. 1, the lamp control system 100 according to the present invention is connected to the rectifier circuit 20 and the lamp 50. The rectifier circuit 20 is connected to the voltage source 10 and the lamp control system 100.

The lamp control system 100 includes a power factor corrector 30, an electronic ballast 40, and a controller 60. The controller 60 includes a central processing unit 61.

The voltage source 10 generally refers to an AC voltage source used in homes or the like.

The rectifier circuit 20 refers to a circuit that receives an AC voltage applied through the voltage source 10 and outputs a high voltage DC voltage. FIG. 2 is a circuit diagram including a diode rectifier circuit, which is a general rectifier circuit, and a voltage source 10 connected thereto, and a graph showing waveforms of a power supply voltage V _IN and a power supply current I _IN .

2 is a circuit diagram of a voltage source and a rectifying circuit according to the present invention and a graph showing waveforms of a power supply voltage and a power supply current. In the circuit diagram of FIG. 2, current flows to the rectifier composed of four diodes only for a short time around the maximum value of V _IN , which is the voltage supplied from the voltage source 10, which is an AC power source. As a result, I _IN supplied from the voltage source 10 becomes a current of a pulsed waveform having a large narrow peak value.

When a large number of lamps and electronic ballasts are installed and operated in the same place, these pulsed waveform currents are simultaneously applied to the electronic ballasts and lamps, causing severe effects and malfunctioning of other electronic devices. .

The power factor corrector 30 receives the power current I _IN of the pulsed waveform and outputs a sinusoidal input current. In addition, the power factor corrector 30 outputs a high voltage DC voltage, but generates an input voltage and an input current having the same phase.

3 is a circuit diagram of a power factor corrector 30 according to the present invention. The circuit diagram of FIG. 3 shows a power factor correction circuit (PFC) in which a non-isolated inductor energy storage type chopper converter of a non-isolated type is added instead of a smoothing capacitor of a passive filter. Chopper converters are a type of DC-DC converter that outputs a voltage higher than the voltage applied. In addition to the above chopper converter, various power factor correction circuits or techniques may be applied to the power factor corrector 30 of the present invention.

Figure 4 is a graph showing the waveform of the current flowing through the inductor of the power factor corrector according to the present invention. This will be described for the principle of generating an input voltage and an input current having the same phase in the power factor corrector 30 of the present invention.

When the current of the pulsed waveform rectified in the rectifier circuit 20 is applied to the power factor corrector 30, the current I _Lb flowing in the inductor Lb of FIG. 3 over the entire period at a frequency of several tens of kilohertz (kHz) as shown in FIG. Detect.

At the time when I _Lb becomes 0, the maximum Q1 of FIG. 4 is turned ON and the value of I _Lb is output from the rectifier circuit 20 to be proportional to the value of the input voltage applied to the power factor corrector 30. When the value reaches a value, switching is performed by turning off Q1 of FIG. 4.

According to the switching method of Q1, the waveform of I _Lb in the power factor corrector 30 is close to the waveform of the pure sine wave. Since I _Lb becomes in phase with the input voltage V _O at the capacitor C2 on the right side of the power factor corrector 30 of FIG. 3, the power factor becomes almost one. In addition, when Q1 is used as a switch, the power loss of Q1 itself becomes almost zero, which increases the efficiency of the entire circuit.

5 is a graph showing an operation waveform of the power factor corrector 30 according to the control of the controller according to the present invention, and FIG. 6 is an equivalent circuit diagram of the power factor corrector 30 according to the operation waveform of the power factor corrector 30.

In FIG. 5A, V _L in the first graph refers to a voltage applied to the inductor Lb of FIG. 3. Vd is a voltage applied to the power factor corrector 30 by the rectifier circuit 20 and refers to a voltage applied to the capacitor C1 on the left side of FIG. 3. Vo is an input voltage generated by the power factor corrector and refers to a voltage applied to the capacitor C2 on the right side of FIG. 3.

In FIG. 5B, Ts denotes a period for turning Q1 on and off, t _ON denotes a time for turning Q1 on, and t _OFF denotes a time for turning Q1 off. Ipic is the magnitude of the peak current which is the maximum value of the current.

FIG. 6A is an equivalent circuit diagram of the power factor corrector 30 during the time t _ON when Q1 is turned on, and FIG. 6B is a power factor corrector during the t _OFF time Q1 is turned off. 30 is an equivalent circuit diagram.

The reason why the equivalent circuit is shown in FIG. 6 is that energy is accumulated in the inductor Lb of FIG. 3 during the time of t _ON in which Q1 is on, and diode D2 is cut off, and Lb is in the time of t _OFF in which Q1 is off. This is because the accumulated energy is released to the output through diode D2.

7 is a graph illustrating a current waveform according to a control method of a power factor corrector according to the present invention. When the output of the power factor corrector 30 is increased, the peak value of the current becomes very large in the critical conduction mode, making the design of the inductor Lb difficult and the burden on the semiconductor switch Q1. Therefore, in the present invention, the power factor control method of controlling the current in the average mode as shown in FIG.

In the lamp control system 100 according to the present invention, the central processing unit 61 controls the power factor corrector 30 according to the following three modules. The three modules include a voltage control module 801, a current control module 802, and a pulse width modulation (PWM) signal generation module 803, as shown in FIG.

The voltage control module 801 receives the command voltage value V * stored in advance in the memory and outputs the command current value I *. The command voltage value V * corresponds to the voltage value Vo to be applied to the capacitor C2 on the right side of the power factor corrector of FIG. 3. That is, the basic operation of the voltage control module 801 is to control the voltage Vo between both ends of the capacitor C2 to maintain a constant value.

The principle of calculating the command current value I * from the command voltage value V * in the voltage control module 801 is as follows. The voltage control module 801 controls I * to have a positive value if dVo is positive through Equation 1, and I * to have a negative value if dV is negative.

The current control module 802 receives the command current value I * from the voltage control module 801 and calculates a duty ratio. The command current value I * corresponds to the value of I _{PIC which} is the peak value of the current I _Lb flowing through the inductor in FIG. 5 (b).

The duty ratio output from the current control module 802 refers to the ratio of the on / off time of the Q1 of FIG. 3 in the pulse width modulation signal generation module 803, and the duty ratio is one period T in FIG. _Shows the ratio of t _ON and t _OFF during _S.

The principle of calculating the duty ratio from the command current value I * received from the current control module 802 may vary for each circuit of the power factor corrector 30. In the case of one embodiment of the chopper converter, the principle is based on [Equation 2]. In Equation 2, D denotes a duty ratio, I _Lb denotes an input current output from the power factor corrector 30, and I _IN denotes a power current input to the power factor corrector 30.

The pulse width modulation signal generation module 803 receives the duty ratio from the current control module 802 and generates a pulse width modulation signal for turning on / off the switch Q1 of FIG. 3. The pulse width modulation signal generation module 803 follows a general pulse width modulation signal generation principle.

As a result, the controller 60 according to the present invention controls the power factor corrector 30 by generating a pulse width modulation signal for turning on and off the switch Q1 of FIG. 3 through the above three modules from the prestored command voltage value V *. do.

In this case, all information such as I _Lb or I _IN required for calculation in each module is measured in the circuit of the power factor corrector 30 and fed back to the controller 60.

FIG. 9 is a graph showing waveforms of power supply current I _IN of the voltage source of FIG. 2, and FIG. 10 is a graph showing waveforms of input voltage Vo and current I _Lb flowing in an inductor generated by the power factor corrector 30.

As shown in FIG. 9, the power supply current I _IN is a pulse-shaped current, but the input voltage Vo generated by the power factor corrector 30 is close to the DC voltage, and the waveform of the input current I _{Lb flowing through} the inductor is a forward sine wave. You can see that it is close to the waveform of.

11 is a basic structural diagram of a general metal halide lamp. It is preferable that the lamp applied to this invention is a high brightness discharge lamp, especially a metal halide lamp. Hereinafter, general characteristics of the metal halide lamp will be described.

Unlike fluorescent lamps or incandescent lamps, discharge lamps such as metal halide lamps have a double structure of an arc tube and an outer jacket or an outer jacket. It is filled with vacuum or nitrogen.

There are three electrodes in the discharge tube, and the actual discharge is caused by the main electrode, which is two of them, and the auxiliary electrode is made of thin tungsten next to any one of the two main electrodes.

12 is a graph showing the characteristic between voltage and current of gas discharge in a typical metal halide lamp. As shown therein, the gas discharge step includes four stages: break down, glow discharge, glow to arc transition, and arc discharge.

As shown in the graph of FIG. 12, a high voltage is required between the main electrodes in order to start the discharge lamp in the dielectric breakdown step. When the insulation in the discharge tube is broken by such a high voltage, the glow discharge starts, leading to a stable arc discharge step from the glow discharge within a few ms.

FIG. 13 is a graph illustrating negative resistance characteristics of a metal halide lamp. As the transition from glow discharge to arc discharge increases the release of hot electrons and the impedance of the lamp itself begins to decrease. As a result, in the arc discharge step, as shown in FIG. 13, a negative resistance characteristic in which the voltage of the lamp falls as the current of the lamp increases.

Therefore, the electronic ballast 40 of the present invention must supply a high output voltage to the lamp in the dielectric breakdown step to start the lamp 50. In addition, the electronic ballast 40 should limit the amount of current supplied to the lamp 50 in the arc discharge step so that excessive current does not flow to the lamp 50 in the arc discharge step by the negative resistance characteristic.

In order to enable the electronic ballast 40 to perform these functions, the central processing unit 61 of the controller 60 changes the magnitude of the frequency applied to the circuit of the electronic ballast 40 and generates it in the electronic ballast 40. Controls the output voltage and the magnitude of the output current.

14 is a circuit diagram of an electronic ballast according to the present invention. The DC power Vo on the left side of the circuit corresponds to the input voltage Vo generated by the power factor corrector 30.

As mentioned above, the electronic ballast 40 must provide the lamp 50 with a large enough starting voltage to operate the lamp 50 and continue to provide a certain amount of voltage and current during operation of the lamp 50. Should be. To this end, the electronic ballast 40 generally uses a resonant inverter circuit having a load dependent characteristic.

FIG. 15 is a simplified circuit diagram of a circuit of the electronic ballast 40 of FIG. 14 and a circuit of the lamp 50. R _L is modeled after the lamp (50). High-frequency metal halide lamps can be modeled with pure resistive components because the voltage and current appear in phase. In addition, the series capacitance C _S has a much larger value than the parallel capacitance C _P.

16 is a graph showing the frequency characteristics of the electronic ballast 40 in accordance with the present invention. As shown in FIG. 15, the resonant circuit of FIG. 15 has a frequency selective characteristic, and among them, a band pass filter (BPF).

The resonant inverter of the electronic ballast 40 has two operating states. The first state is just before starting, which is the breakdown phase, and the second state is after starting, which is the stage of glow discharge and arc discharge.

FIG. 17 is an equivalent circuit diagram of the circuit of the electronic ballast 40 of FIG. 15 for a state immediately before starting the lamp 50. Since the lamp R _L is very large in the state immediately before starting, the resonant inverter circuit of FIG. 15 is modeled as a circuit in which L _S , C _S and C _P are connected in series. Here, the switching frequency of the starting section is very high in order to obtain a high voltage.

In the circuit of FIG. 17 immediately before starting, the resonance frequency fo, the characteristic impedance Zo, and the good quality Qo can be approximated as follows.

18 is a graph illustrating output frequency characteristics of the electronic ballast according to a state immediately before starting and a normal state after starting of the lamp according to the present invention. For real circuits, the value of Q _O is designed to be greater than 20.

Therefore, the resonance characteristic of the circuit of the electronic ballast 40 in the before igniting state is very sharp curve as shown in FIG. The high output voltage required for the initial lighting of the lamp 50 is generated using the resonance between L _S and C _P.

In the circuit of FIG. 17, the resonance current i _LS flowing through the L _S gradually increases as resonance progresses, and the voltage V _CP applied to C _P is expressed as follows.

In short, in the present invention, the circuit is finally set under the condition of C _S >> C _P to obtain a high voltage pulse for starting the lamp 50. Just before starting, the circuit of the electronic ballast 40 operates only the inductor L _S and the capacitor C _P, ignoring the capacitor C _S , and starts about 1 kV at both ends of C _P near the resonance frequency of C _P and L _S. Generate a voltage.

19 is an equivalent circuit diagram of the electronic ballast 40 circuit of FIG. 15 for a post-start state of the lamp 50. As soon as the voltage V _CP reaches the ignition voltage, the lamp 50 starts up and starts emitting light. The lamp 50, which had a high value of resistance immediately before starting, rapidly lowered in resistance after starting.

Thus, C _P is, since the value is very small compared to C _S C _P is the structure of the L _S, C _S, R _L, such as the effect on the circuit is relatively small because the circuit diagram of Figure 15 a circuit diagram is 19 in the state after the start-up Is simplified.

In FIG. 19, the square wave voltage V _S is expressed by Equation 7 below. Among the components of V _S, the fundamental wave component affects the operation of the actual resonant circuit, and the effective value V _eff of the fundamental wave component is expressed by Equation (8). V _O is equal to the voltage applied on the left in the circuit diagram of FIG. 14.

The effective value of the current Ir flowing in the load R _L of the lamp 50 of the resonant circuit with respect to the fundamental wave frequency w of the voltage applied to the resonant circuit of the electronic ballast 40 is expressed as follows.

The stage after the start of the lamp 50 can be divided into a stage immediately after the start of the glow discharge stage and a steady state stage of the arc discharge stage.

In the steady state stage, the resistance of the lamp 50 becomes R _MAX , where the current I ₁ flowing in the lamp 50 is equal to the rated current In of the lamp 50 at the driving frequency w ₁ , which is represented by Equation 10 ] Appears.

In the stage immediately after starting, the current I ₂ flowing in the lamp 50 R _L is required to be 1.2 times the rated current In of the lamp 50, and the impedance R _L of the lamp 50 becomes the minimum resistance R _MIN . In this case, I ₂ is represented by Equation 11 at the driving frequency w ₂ .

20 is a graph showing the movement of the operating point according to the change in frequency in the electronic ballast according to the present invention. The graph of FIG. 20 shows the movement of the driving frequency and the change of the current flowing through the lamp when the load resistance of the lamp 50 changes.

As shown here, in the state immediately after the start of the lamp 50, the lamp 50 has a low impedance R _MIN , the output current is limited to I ₂ , and an operating point is formed at a relatively high frequency w ₂ . When the lamp 50 reaches the steady state, the impedance of the lamp 50 rises to R _MAX and the output current I ₁ is required, so an operating point is formed at a relatively low frequency w ₁ .

Based on this principle, the controller 60 of the present invention changes the driving frequency applied to the electronic ballast 40 to control the magnitude of the output voltage and the output current applied to the lamp 50. The central processing unit 61 included in the controller 60 sets the frequencies w ₁ and w ₂ applied to the electronic ballast 40 using [Equation 10] and [Equation 11] according to a program stored in advance. Decide

When the lamp 50 is driven by the electronic ballast 40, the lamp 50 reaches a steady state within several msec after the lamp 50 is started. Therefore, the controller 60 applies a constant frequency w ₂ to the electronic ballast 40 for several msec before reaching the steady state.

In the steady state stage of the lamp 50, the driving frequency w ₁ and the good quality Q ₁ of the electronic ballast 40 are expressed as follows.

In the state step immediately after the start of the lamp 50, the driving frequency w ₂ and the good quality Q ₂ of the electronic ballast 40 are expressed as follows, respectively. Provided that w ₂ > w ₁ .

21 is an exemplary photograph of a lamp control system 100 actually implemented using a single central processing unit 61 according to the present invention. The configuration of the experimental apparatus is as shown in [Table 1].

parameter value Supply voltage V _IN 110 Vac Switching frequency w _o 32 kHz Input Inductor Lb 540 uH Output capacitor Cs 1640 uF Output voltage V _RL 300 V

22 is a graph showing a simulation waveform of the voltage V _RL applied to the lamp in the state immediately after starting in the electronic ballast 40 according to the present invention. 23 is a graph showing the waveform of the voltage V _RL applied to the lamp measured in the state immediately after starting in the electronic ballast 40 according to the present invention. In the simulation and actual measurements, the voltage values were all 1 kV / div.

24 is a graph showing a simulation waveform of the output voltage and the output current in the steady state in the electronic ballast 40 according to the present invention, Figure 25 is an output measured in the steady state in the electronic ballast 40 according to the present invention It is a graph showing waveforms of voltage and output current. In the simulation and actual measurements, the suppression values were all 200 V / div and the current values were all 5 A / div.

It can be seen that the actual measurement results are in good agreement with the simulation results by the computer program in both normal and normal conditions immediately after startup.

The method of the present invention can also be embodied in computer readable code on a computer readable recording medium. The computer-readable recording medium includes all kinds of recording devices in which data that can be read by a computer system is stored. Examples of computer-readable recording media include ROM, RAM, CD-ROM, magnetic tape, floppy disk, optical data storage, and the like, which are also implemented in the form of a carrier wave (for example, transmission over the Internet). It also includes. The computer readable recording medium can also be distributed over network coupled computer systems so that the computer readable code is stored and executed in a distributed fashion.

The technical scope of the present invention described above through the embodiments is not limited to the above-described embodiments, and various modifications and changes may be made without departing from the spirit and scope of the present invention. It is evident to those who have knowledge. Therefore, such modifications or variations will have to be belong to the scope of the invention described in the claims of the present invention.

As described above, in the case of the lamp control method and system according to the present invention, unlike the conventional lamp control, it is possible to integrally control the power factor compensator and the electronic ballast using a single central processing unit. Unlike the products of the power factor correction circuit and the electronic ballast circuit implemented using each of the existing hardware integrated circuits, since the operation and control of the central processing unit is performed by software input into the memory according to the present invention, The price is much lower than the product and the volume of the whole product is reduced. In addition, since it is controlled by software, the compatibility that can be used for various existing lamps or voltage sources is increased, various modifications of the product are easy, and there is an advantage that it can cope with high-capacity input / output sources compared to existing products.

Claims (6)

A power factor corrector for generating an input voltage and an input current having the same phase according to the pulse width modulation signal; And a frequency selective resonant circuit, generating an output voltage and an output current from the input voltage and the input current based on the frequency information that changes according to the lighting step, and generating the generated output voltage and output current according to the lighting step. An electronic ballast for providing a high-brightness discharge lamp whose impedance changes; And The pulse width modulated signal is connected to the power factor corrector and the electronic ballast, and the pulse width modulated signal is supplied to the power factor corrector using the duty ratio of the command current information calculated from predetermined command voltage information. It includes a central processing unit for controlling the magnitude of the output voltage and the output current by applying a, The changing frequency information First frequency information about a startup step of the high brightness discharge lamp; Second frequency information about a glow discharge step immediately after the startup step; And And a third frequency information on the arc discharge step reaching the steady state after the glow discharge step. According to claim 1, wherein the central processing unit A voltage control module configured to receive the predetermined command voltage information and calculate the predetermined command current information; A current control module which receives the predetermined command current information and calculates a predetermined duty ratio; And A pulse width modulated signal generation module configured to receive the duty ratio and generate a pulse width modulated signal, And control the power factor corrector to generate the input voltage and the input current. a power factor correction step of generating, by the power factor corrector, an input voltage and an input current having the same phase according to a pulse width modulated signal input from the CPU; And (b) The electronic ballast generates an output voltage and an output current from the input voltage and the input current based on the frequency information input from the central processing unit, and generates the high brightness discharge lamp whose impedance varies according to the lighting stage. And an output step of providing the output voltage and the output current. Frequency information input from the CPU is First frequency information about a start-up step of the high brightness discharge lamp; Second frequency information for the glow discharge step immediately after the start-up step, And third frequency information on the arc discharge step reaching the steady state after the glow discharge step, The magnitude of the output voltage and the output current is controlled to be generated differently according to the lighting step based on the frequency information input from the central processing unit. The method of claim 3, wherein step (a) (a1) calculating, by the central processing unit, predetermined command current information from predetermined command voltage information; (a2) calculating, by the central processing unit, a predetermined duty ratio from the calculated command current information; And and (a3) the central processing unit generating the pulse width modulated signal from the calculated duty ratio. delete A recording medium which records a program for realizing the control method of the high brightness discharge lamp of any one of Claims 3-4.

Images