JPS6346619B2 - - Google Patents
Info
- Publication number
- JPS6346619B2 JPS6346619B2 JP1936479A JP1936479A JPS6346619B2 JP S6346619 B2 JPS6346619 B2 JP S6346619B2 JP 1936479 A JP1936479 A JP 1936479A JP 1936479 A JP1936479 A JP 1936479A JP S6346619 B2 JPS6346619 B2 JP S6346619B2
- Authority
- JP
- Japan
- Prior art keywords
- complex
- fourier inverse
- signal
- outputs
- circuit
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Expired
Links
- 238000012545 processing Methods 0.000 claims description 16
- 230000005540 biological transmission Effects 0.000 claims description 9
- 238000005070 sampling Methods 0.000 claims description 6
- 239000000969 carrier Substances 0.000 claims description 3
- 230000001360 synchronised effect Effects 0.000 claims description 3
- 238000000034 method Methods 0.000 claims 2
- 238000007781 pre-processing Methods 0.000 claims 2
- 238000012805 post-processing Methods 0.000 claims 1
- 229920002401 polyacrylamide Polymers 0.000 description 14
- 238000006243 chemical reaction Methods 0.000 description 1
- 230000003111 delayed effect Effects 0.000 description 1
- 238000010586 diagram Methods 0.000 description 1
- 230000008054 signal transmission Effects 0.000 description 1
- 238000001228 spectrum Methods 0.000 description 1
Classifications
-
- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
- H04L27/00—Modulated-carrier systems
- H04L27/26—Systems using multi-frequency codes
- H04L27/2601—Multicarrier modulation systems
- H04L27/2626—Arrangements specific to the transmitter only
- H04L27/2627—Modulators
- H04L27/2628—Inverse Fourier transform modulators, e.g. inverse fast Fourier transform [IFFT] or inverse discrete Fourier transform [IDFT] modulators
-
- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
- H04L27/00—Modulated-carrier systems
- H04L27/26—Systems using multi-frequency codes
- H04L27/2601—Multicarrier modulation systems
- H04L27/2626—Arrangements specific to the transmitter only
- H04L27/2627—Modulators
- H04L27/264—Pulse-shaped multi-carrier, i.e. not using rectangular window
-
- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
- H04L27/00—Modulated-carrier systems
- H04L27/26—Systems using multi-frequency codes
- H04L27/2601—Multicarrier modulation systems
- H04L27/2647—Arrangements specific to the receiver only
- H04L27/2649—Demodulators
- H04L27/26534—Pulse-shaped multi-carrier, i.e. not using rectangular window
Description
【発明の詳細な説明】
本発明は多チヤンネルパルス振幅変調(以下
PAMと略称する。)信号を直交多重することによ
り情報伝送効率を上昇せしめる直交多重信号の送
信装置に関わり、特に複数個の複素ベースバンド
PAM信号をデイジタル処理により直交振幅(以
下QAMと略称する。)変調して直交多重するデ
イジタル処理形送信装置に関する。DETAILED DESCRIPTION OF THE INVENTION The present invention provides multi-channel pulse amplitude modulation (hereinafter referred to as
It is abbreviated as PAM. ) Related to orthogonal multiplex signal transmission equipment that increases information transmission efficiency by orthogonally multiplexing signals, especially multiple complex baseband
The present invention relates to a digital processing type transmitter that performs quadrature amplitude (hereinafter abbreviated as QAM) modulation and orthogonal multiplexing of a PAM signal through digital processing.
この種の送信装置としては既に昭和52年特許願
第104609号明細書(特開昭54−37520号公報)に
より“直交多重信号のデイジタル処理形送信号装
置”が提案されている。しかしこの直交多重信号
のデイジタル処理形送信装置においては入力とし
てN/2点複素データしかないにも拘らずT/2秒
毎にN点逆フーリエ変換を行う必要があり、(た
だしTは各PAM信号のクロツク周期であり、
N/Tはサンプリング周波数である。)しかも各
所にT/2秒毎の切替制御部等を設ける必要があ
り、ハードウエア期模が複雑となる欠点を有して
いた。 As this type of transmitting device, a "digital processing type transmitting signal device for orthogonal multiplexed signals" has already been proposed in Patent Application No. 104609 of 1972 (Japanese Unexamined Patent Publication No. 54-37520). However, in this digital processing transmitter for orthogonal multiplexed signals, it is necessary to perform N-point inverse Fourier transform every T/2 seconds, even though there is only N/2-point complex data as input (where T is for each PAM is the clock period of the signal,
N/T is the sampling frequency. ) Furthermore, it is necessary to provide switching control units for every T/2 seconds at various locations, which has the disadvantage of complicating the hardware design.
本発明の目的は上記の欠点に鑑み、N/2点逆フ
ーリエ変換器の使用を可能にしT/秒毎の切替制
御部を極が減少させた直交多重信号のデイジタル
処理形送信装置を提供するものである。 SUMMARY OF THE INVENTION In view of the above-mentioned drawbacks, it is an object of the present invention to provide a digital processing type transmitting device for orthogonal multiplexed signals, which allows the use of an N/2-point inverse Fourier transformer and reduces the number of switching control units every T/second. It is something.
以下図面を用いて本発明を説明する。 The present invention will be explained below using the drawings.
第1図は直交多重QAM信号の送受信系を表わ
すブロツク図であり、10,11,……,12L-1は
クロツク周期T秒で互いに同期した2L個のPAM
信号が入力される入力端、20,21,……,2L-
1はL個のT/2秒遅延回路、30,31,……,
32L-1は2L個の送信ベースバンドフイルタ40,
41,……,42L-1は2L個の変調器、5は各変調
の出力を全て加算し伝送路に送出する多重化回
路、6は伝送路、70,71,……,72L-1は2L個
の復調器、80,81,……,82L-1は2L個の受信
ベースバンドフイルタ、90,91……,9L-1は
L個のT/2秒遅延回路、100,101,……,
10L-1はL個のT秒遅延回路、110,111,
……,112L-1は2L個のPAM信号が出力される
出力端である。 Figure 1 is a block diagram showing the transmission/reception system of orthogonal multiplexed QAM signals, where 1 0 , 1 1 , ..., 1 2L-1 are 2L PAMs synchronized with each other with a clock period of T seconds.
Input terminals where signals are input, 2 0 , 2 1 , ..., 2 L-
1 is L T/2 second delay circuits, 3 0 , 3 1 , ...,
3 2L-1 has 2L transmit baseband filters 4 0 ,
4 1 , ..., 4 2L-1 is a 2L modulator, 5 is a multiplexing circuit that adds all the outputs of each modulation and sends it to the transmission path, 6 is a transmission path, 7 0 , 7 1 , ..., 7 2L-1 is 2L demodulators, 8 0 , 8 1 , ..., 8 2L-1 is 2L reception baseband filters, 9 0 , 9 1 ..., 9 L-1 is L T /2 second delay circuit, 10 0 , 10 1 , ...,
10 L-1 are L T-second delay circuits, 11 0 , 11 1 ,
..., 11 2L-1 is an output terminal from which 2L PAM signals are output.
第1図にて第R番目の入力端(Rは0R<L
とする)1Rおよび第(L+R)番目の入力端
1L+Rに各々第R番目のPAM信号および第(L+
R)番目のPAM信号が入力されるものとする。
第R番目のPAM信号は2RにてT/2秒の遅延を
受けた後送信ベースバンドフイルタ3Rにて帯域
制限および波形成形されて変調器4Rに至る。 In Figure 1, the R-th input terminal (R is 0R<L
)1 R and (L+R)th input terminal
1 L+R respectively the Rth PAM signal and the (L+
It is assumed that the R)th PAM signal is input.
The R-th PAM signal is delayed by T/2 seconds at 2R , is band-limited and waveform-shaped at transmission baseband filter 3R , and then reaches modulator 4R .
一方第(L+R)番目のPAM信号はそのまま
送信ベースバンドフイルタ3L+Rにて帯域制限お
よび波形成形されて変調器4L+Rに至る。変調器
4Rおよび4L+Rにおいては周波数fRの同相キヤリ
アcos2πfRtおよび直交キヤリアsin2πfRtが変調
キヤリアとして入力されれ両変調出力が多重化回
路5で加算されることにより中心周波数fRなるR
番目のQAM信号が形成される。 On the other hand, the (L+R)th PAM signal is band-limited and waveform-shaped by the transmission baseband filter 3 L+R as it is, and then reaches the modulator 4 L+R . In the modulators 4 R and 4 L+R , the in-phase carrier cos2πf R t of frequency f R and the orthogonal carrier sin2πf R t of frequency f R are input as modulation carriers, and both modulation outputs are added in the multiplexing circuit 5 to obtain the center frequency f R becomes R
The second QAM signal is formed.
ここで各変調器にて使用されるキヤリアの周波
数は1RL−1なるRに対しfR−fR-1=T-1
と設定されており、変調器40,41,……,4L-
1におけるキヤリアは余弦波と正弦波とが交互に
配置されている。 Here, the frequency of the carrier used in each modulator is f R - f R-1 = T -1 for R, which is 1RL-1.
The modulators 4 0 , 4 1 , ..., 4 L-
The carrier in No. 1 has cosine waves and sine waves arranged alternately.
このような送信側の変調操作により多重化回路
5から直交多重されたQAM信号が出力されるこ
とは既によく知られている。多重化回路5から出
力された直交多重QAM信号は伝送路6を介して
受信側に伝送される。受信側では前記送信側と全
く逆の変換が行われ出力端110,111,……,
112L-1に対応する各PAM信号が得られる。こ
こで送信ベースバンドフイルタ30,31,……,
32L-1および受信ベースバンドフイルタ80,81,
……,82L-1は全て同一周波数応答G(ω)でそ
の3dB低下帯域(片側実効帯域と称す)1/2T
ヘルツの低域通過フイルタであるとし、G2(ω)
が1/2Tのヘルツで6dB低下する通常のナイキ
ストフイルタであるとすると受信側の出力端11
0,111,……,112L-1には適当なサンプリン
グ時点で符号間干渉もなくチヤンネル間干渉もな
いPAM信号が得られることが知られている。 It is already well known that an orthogonally multiplexed QAM signal is output from the multiplexing circuit 5 by such a modulation operation on the transmitting side. The orthogonal multiplexed QAM signal output from the multiplexing circuit 5 is transmitted to the receiving side via the transmission line 6. On the receiving side, a conversion completely opposite to that on the transmitting side is performed, and the output terminals 11 0 , 11 1 , . . .
11 Each PAM signal corresponding to 2L-1 is obtained. Here, the transmission baseband filters 3 0 , 3 1 , ...,
3 2L-1 and reception baseband filters 8 0 , 8 1 ,
......, 8 2L-1 all have the same frequency response G (ω) and its 3 dB lower band (referred to as one-sided effective band) 1/2T
Assume that it is a Hertzian low-pass filter, and G 2 (ω)
is a normal Nyquist filter that reduces by 6 dB at 1/2 T hertz, then the output terminal 11 on the receiving side
It is known that a PAM signal without intersymbol interference or interchannel interference can be obtained at an appropriate sampling point for 0 , 11 1 , . . . , 11 2L-1 .
第1図の入力端10,11,……,12L-1から多
重化回路5の出力までの送信部の信号処理操作を
全てデイジタル処理にて行なうことを考える。即
ち、複数個のPAM信号を各々サンプリング周波
数1/Tヘルツのサンプル値系列とし、多重化回
路5の出力に対応するサンプリング周波数fsヘル
ツのサンプル値系列を生成するものとする。この
サンプリング周波数fsは多重化後の信号スペクト
ルにおいて折返しによる干渉を生じないよう一定
程度高い周波数に設定しておかねばならない。 Let us consider that the signal processing operations of the transmitting section from the input terminals 1 0 , 1 1 , . . . , 1 2L-1 in FIG. 1 to the output of the multiplexing circuit 5 are all performed by digital processing. That is, each of the plurality of PAM signals is made into a sample value series with a sampling frequency of 1/T hertz, and a sample value series with a sampling frequency f s hertz corresponding to the output of the multiplexing circuit 5 is generated. This sampling frequency f s must be set to a certain high frequency so as not to cause interference due to aliasing in the signal spectrum after multiplexing.
更に後のデイジタル処理を容易にするためにfs
は1/Tの整数倍に選ぶ必要がある。また、第1
図の20,21,……,2L-1等におけるT/2秒
遅延差を付与するにはfsは1/Tの偶数倍である
事が必要である。 f s to further facilitate subsequent digital processing.
must be selected as an integral multiple of 1/T. Also, the first
In order to provide a delay difference of T/2 seconds at 2 0 , 2 1 , . . . , 2 L-1, etc. in the figure, f s needs to be an even multiple of 1/T.
ここでfsとして1/TのN倍の周波数を選んだ
とする。但しNは偶数であり、入力PAMチヤネ
ル数2Lより大であるとする。いま入力端1Rに
入力されるT秒毎のPAM信号サンプル値列をXR
(ZN)とする。但し、z=ej2〓f/fsである。 Here, it is assumed that a frequency N times 1/T is selected as f s . However, it is assumed that N is an even number and larger than the number of input PAM channels, 2L. The PAM signal sample value sequence every T seconds that is now input to input terminal 1 R is
( ZN ). However, z=e j2 〓 f/fs .
更に送信ベースバンドフイルタをz変換したも
のをG(z)と表わせば0RL−1なるRに
対し送信ベースバンドフイルタ3Rの出力UR(z)
および送信ベースバンドフイルタ3R+Lの出力VR
(z)は各々次式で表わされる。 Furthermore, if the transmitting baseband filter is z-transformed and expressed as G(z), the output of the transmitting baseband filter 3 R is U R (z) for R which is 0RL-1.
and the output of transmitting baseband filter 3 R+L V R
(z) are each expressed by the following equations.
UR(Z)=XR(ZN)G(Z)ZN/2 ……(1)
VR(Z)=XR+L(ZN)G(Z) ……(2)
(1)、(2)式で与えられるUR(Z)、VR(Z)はRが
偶数ならば各々cos2πfRtおよびsin2πfRtにより
変調された後加算されR番目のQAM信号を形成
し、Rが奇数ならば各々sin2πfRtおよびcos2πfR
tにより変調された後加算されR番目のQAM信
号を形成する。U R (Z)=X R (Z N )G(Z)Z N/2 ……(1) V R (Z)=X R+L (Z N )G(Z) ……(2) (1 ), U R (Z) and V R (Z) given by equation (2) are modulated by cos2πf R t and sin2πf R t, respectively, if R is an even number, and then added to form the R-th QAM signal, If R is an odd number, sin2πf R t and cos2πf R
t and then summed to form the Rth QAM signal.
従つて送信出力のサンプル値系列Y(Z)は次
の如く表わされる。 Therefore, the sample value series Y(Z) of the transmitted output is expressed as follows.
Y(Z)= 〓 〓R=0,2ゥ Y(Z)= 〓 〓 R=0,2u
Claims (1)
個(ただしLは正整数)のベースバンドデータに
て周波数f0、f1、……、fL-1なるL個の複素キヤ
リアを直交変調し、その出力を直交多重する信号
処理過程をN/Tヘルツ(ただしNは偶数であ
り、N≧2L)のサンプリング速度にて行なう際
に、前記Tと最小キヤリヤ周波数f0との積f0Tの
少数部であるパラメータγが0.5に設定された直
交多重信号デイジタル処理形送信装置において、
前期2L個のベースバンドデータに選択的にT/
2秒遅延を付加し複素化を施して複素信号群a1,
a2,……,aLを出力する前処理回路と、該複素信
号群a1,a2,……,aLおよび(N/2−L)個の
ダミー信号を入力としT/2秒毎にN/2点オフ
セツトフーリエ逆変換を行うオフセツトフーリエ
逆変換器と、該オフセツトフーリエ逆変換器に接
続され実効帯域巾が1/Tヘルツで線形位相勾配
のみが段階的に異なるN/2個の複素帯域フイル
タで構成されるポリフエーズ回路とより成り、該
ポリフエーズ回路のN/2個の実部出力を時分割
多重する事により直交多重信号を得る事を特徴と
する直交多重信号のデイジタル処理形送信装置。 2 クロツク周期T秒で互いに同期がとれた2L
個(ただしLは正整数)のベースバンドデータに
てL個の複素キヤリアを直交変調し、その出力を
直交多重する信号処理過程をN/Tヘルツ(ただ
しNは偶数であり、N≧2Lである。)のサンプリ
ング速度にてデイジタル処理する送信装置におい
て、前記2L個のベースバンドデータに選択的に
T/2秒遅延を付加し複素化を施し二組の複素信
号群a1,a2,……,aLおよびb1,b2,……,bLを
出力する前処理回路と、該複素信号群a1,a2,…
…,aLおよび(N/2−L)個のダミー信号を入
力としT/2秒毎にN/2点オフセツトフーリエ
逆変換を行う第一のオフセツトフーリエ逆変換器
と、前記複素信号群b1,b2,……,bLおよび
(N/2−L)個のダミー信号を入力とし前記第
一のオフセツトフーリエ逆変換器と同一構成の第
二のオフセツトフーリエ逆変換器と、前記第一の
オフセツトフーリエ逆変換器に接続され実効帯域
幅が1/Tヘルツで線形位相勾配のみが段階的に
異なるN/2個の複素帯域フイルタで構成される
第一のポリフエーズ回路と、前記第二のオフセツ
トフーリエ逆変換器に接続され前記第一のポリフ
エーズ回路と同一構成の第二のポリフエーズ回路
と、前記第一のポリフエーズ回路N/2個の実部
出力を実数部とし前記第二のポリフエーズ回路の
N/2個の虚部出力を虚数部とする事により得ら
れるN/2個の複素信号に対し所望の周波数オフ
セツトを施した後出力の実数部のみをとり出す後
処理回路とを含み、該後処理回路の出力として得
られるN/2個の実信号を時分割多重することに
より直交多重信号を得る事を特徴とする直交多重
信号のデイジタル処理形送信装置。[Claims] 1. 2Ls synchronized with each other with a clock cycle of T seconds
A signal processing process in which L complex carriers with frequencies f 0 , f 1 , ..., f L-1 are orthogonally modulated using baseband data (where L is a positive integer) and the outputs are orthogonally multiplexed is N. /T Hertz (where N is an even number and N≧2L), the parameter γ, which is the fractional part of the product f 0 T of the above T and the minimum carrier frequency f 0 , is set to 0.5. In the orthogonal multiplexed signal digital processing transmitter,
Selectively T/ to the first 2L baseband data
A 2-second delay is added and complexization is performed to obtain the complex signal group a 1 ,
A preprocessing circuit that outputs a 2 , ..., a L and the complex signal group a 1 , a 2 , ..., a L and (N/2-L) dummy signals are input, and the processing time is T/2 seconds. An offset Fourier inverse transformer that performs an N/2 point offset Fourier inverse transform for each N/2 point offset Fourier inverse transformer, and an N An orthogonal multiplexed signal comprising a polyphase circuit composed of /2 complex band filters, and obtaining an orthogonal multiplexed signal by time-division multiplexing N/2 real part outputs of the polyphase circuit. Digital processing type transmitter. 2 2L synchronized with each other with a clock period of T seconds
The signal processing process that orthogonally modulates L complex carriers using baseband data of 30000000000000000000000000000000000000000000000000000000000000000000000000000000000000000 form 2000 3000 30000 form orthogonal form, orthogonal multiplexed form, using baseband data of In a transmitting device that performs digital processing at a sampling rate of ..., a L and a preprocessing circuit that outputs b 1 , b 2 , ..., b L , and the complex signal group a 1 , a 2 , ...
..., a L and (N/2-L) dummy signals as input and performs N/2-point offset Fourier inverse transform every T/2 seconds, and the complex signal a second offset Fourier inverse transformer having the same configuration as the first offset Fourier inverse transformer, which inputs groups b 1 , b 2 , ..., b L and (N/2-L) dummy signals; and a first polyphase circuit connected to the first offset Fourier inverse transformer and comprising N/2 complex bandpass filters having an effective bandwidth of 1/T Hertz and differing only in linear phase gradient in steps. , a second polyphase circuit connected to the second offset Fourier inverse transformer and having the same configuration as the first polyphase circuit, and a real part output of N/2 of the first polyphase circuit as the real part. After applying a desired frequency offset to the N/2 complex signals obtained by using the N/2 imaginary part outputs of the second polyphase circuit as the imaginary part, only the real part of the output is extracted. 1. A digital processing type transmission device for orthogonal multiplexed signals, comprising a processing circuit, and obtaining an orthogonal multiplexed signal by time-division multiplexing N/2 real signals obtained as outputs of the post-processing circuit.
Priority Applications (4)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
JP1936479A JPS55112054A (en) | 1979-02-21 | 1979-02-21 | Digital process type transmitter for orthogonal multiple signal |
US06/121,943 US4300229A (en) | 1979-02-21 | 1980-02-15 | Transmitter and receiver for an othogonally multiplexed QAM signal of a sampling rate N times that of PAM signals, comprising an N/2-point offset fourier transform processor |
AU55634/80A AU527333B2 (en) | 1979-02-21 | 1980-02-18 | Multi pam signals to ortho multiplex qam converter |
CA000346089A CA1134519A (en) | 1979-02-21 | 1980-02-20 | Transmitter and receiver for an orthogonally multiplexed qam signal of a sampling rate n times that of pam signals, comprising an n/2-point offset fourier transform processor |
Applications Claiming Priority (1)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
JP1936479A JPS55112054A (en) | 1979-02-21 | 1979-02-21 | Digital process type transmitter for orthogonal multiple signal |
Publications (2)
Publication Number | Publication Date |
---|---|
JPS55112054A JPS55112054A (en) | 1980-08-29 |
JPS6346619B2 true JPS6346619B2 (en) | 1988-09-16 |
Family
ID=11997294
Family Applications (1)
Application Number | Title | Priority Date | Filing Date |
---|---|---|---|
JP1936479A Granted JPS55112054A (en) | 1979-02-21 | 1979-02-21 | Digital process type transmitter for orthogonal multiple signal |
Country Status (1)
Country | Link |
---|---|
JP (1) | JPS55112054A (en) |
-
1979
- 1979-02-21 JP JP1936479A patent/JPS55112054A/en active Granted
Also Published As
Publication number | Publication date |
---|---|
JPS55112054A (en) | 1980-08-29 |
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