JPS6216066A - Output drooping method for power converter - Google Patents

Output drooping method for power converter

Info

Publication number
JPS6216066A
JPS6216066A JP15151585A JP15151585A JPS6216066A JP S6216066 A JPS6216066 A JP S6216066A JP 15151585 A JP15151585 A JP 15151585A JP 15151585 A JP15151585 A JP 15151585A JP S6216066 A JPS6216066 A JP S6216066A
Authority
JP
Japan
Prior art keywords
output
circuit
set level
voltage
semiconductor element
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Granted
Application number
JP15151585A
Other languages
Japanese (ja)
Other versions
JP2566131B2 (en
Inventor
Yoshio Suzuki
義雄 鈴木
Yutaka Kuwata
豊 鍬田
Seiichi Muroyama
室山 誠一
Shinichiro Asami
浅見 真一郎
Ryoji Saito
斉藤 亮治
Kazuhiro Senoo
妹尾 一宏
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Origin Electric Co Ltd
Nippon Telegraph and Telephone Corp
Original Assignee
Origin Electric Co Ltd
Nippon Telegraph and Telephone Corp
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Origin Electric Co Ltd, Nippon Telegraph and Telephone Corp filed Critical Origin Electric Co Ltd
Priority to JP60151515A priority Critical patent/JP2566131B2/en
Publication of JPS6216066A publication Critical patent/JPS6216066A/en
Application granted granted Critical
Publication of JP2566131B2 publication Critical patent/JP2566131B2/en
Anticipated expiration legal-status Critical
Expired - Lifetime legal-status Critical Current

Links

Abstract

PURPOSE:To reduce a ripple component amount by lowering the reference voltage of a DC output voltage detection system in response to the magnitude of a signal corresponding to a difference between a detecting signal levelled in response to output currents and a set level when the detecting signal exceeds the set level. CONSTITUTION:An output from an AC power supply 1 is lead out as a DC output through a rectifying circuit 2, a filter circuit 3, a transformer 5 for converting power, a rectifying circuit 7 and a filter circuit 8. DC output currents rectified and levelled by the rectifying circuit 7 and the filter circuit 8 are detected by a current detecting means 19, an output from the means 19 is inputted to an operational amplifier 20, and the reference voltage of a DC output voltage detection system variable reference power supply 14 is varied by an output from the operational amplifier 20. That is, when a current detecting signal exceeds a set level, reference voltage is lowered in response to the magnitude of a signal corresponding to a difference between the current detecting signal and the set level.

Description

【発明の詳細な説明】 〔産業上の利用分野〕 本発明は、通信用電源などに適した電力変換装置の出力
垂下方法に関する。
DETAILED DESCRIPTION OF THE INVENTION [Field of Industrial Application] The present invention relates to a method for lowering the output of a power conversion device suitable for communication power sources and the like.

〔従来の技術」 先ず第5図に従って通信用電源などとして用いられてい
る電力変換装置の一例を説明する。
[Prior Art] First, an example of a power conversion device used as a communication power source will be described with reference to FIG.

第6図において、1は商用の6相交流電源、2は6相全
彼整流回路、3′は商用周波数フィルタ回路、4は電力
変換用トランス5の1次巻線N1 に直列接続されたト
ランジスタのようなスイッチング半導体素子、6はスイ
ッチング半導体素子4全介して流れる主電流を検出する
電流検出回路、7はト2/ス5の2次巻線N2 間に接
続された整流回路、8は高周波用フィルタ回路、9.1
0は直流出力端子、11は電圧分割用抵抗器、12は出
力電圧検出用抵抗器、13は抵抗器11と12との接続
点Xにおける出力検出電圧と固定基準電源14′の固定
基準電圧との偏差全増幅する演算増幅器、15はその偏
差信号を鋸歯状基準電圧と比較する比較回路、16は電
流検出回路6からの瞬時電流検出信号が設定レベル全組
えるとき出力垂下を生じさせる九めの信号を生ずる比較
回路、17はオア回路、18はスイッチング半導体素子
4に駆動信号を与える駆動回路である。
In Fig. 6, 1 is a commercial 6-phase AC power supply, 2 is a 6-phase full rectifier circuit, 3' is a commercial frequency filter circuit, and 4 is a transistor connected in series to the primary winding N1 of a power conversion transformer 5. 6 is a current detection circuit that detects the main current flowing through all of the switching semiconductor elements 4, 7 is a rectifier circuit connected between the secondary winding N2 of T2/S5, and 8 is a high frequency Filter circuit for 9.1
0 is a DC output terminal, 11 is a voltage dividing resistor, 12 is an output voltage detection resistor, and 13 is the output detection voltage at the connection point X between resistors 11 and 12 and the fixed reference voltage of the fixed reference power supply 14'. 15 is a comparator circuit that compares the deviation signal with a sawtooth reference voltage; 16 is a comparator circuit that causes output droop when the instantaneous current detection signal from current detection circuit 6 reaches the set level; 17 is an OR circuit, and 18 is a drive circuit that provides a drive signal to the switching semiconductor element 4.

次にこのような回路の動作について簡単に説明する。Next, the operation of such a circuit will be briefly explained.

通常の動作状態では、演算増@器16が抵抗11と12
との接続点Xに現出する出力電圧検出信号と固定基準電
源14′の固定基準電圧との偏差に応じた偏差信号全比
較回路に出力する。
Under normal operating conditions, the operational amplifier 16 is connected to the resistors 11 and 12.
A deviation signal corresponding to the deviation between the output voltage detection signal appearing at the connection point X and the fixed reference voltage of the fixed reference power supply 14' is output to the entire comparison circuit.

比較回路15はその偏差信号と鋸歯状基準電圧とを比較
し、偏差信号の大きさに応じてパルス幅が変化する信号
全オア回路17を介して駆動回路18に与える。従って
駆動回路18は、直流出力電圧が定電圧になるよう、ス
イッチング半導体素子4の導通幅全制御する。
The comparison circuit 15 compares the deviation signal with a sawtooth reference voltage and supplies the signal to the drive circuit 18 via a signal all-OR circuit 17 whose pulse width changes depending on the magnitude of the deviation signal. Therefore, the drive circuit 18 controls the entire conduction width of the switching semiconductor element 4 so that the DC output voltage becomes a constant voltage.

しかし出力電流が増加し、スイッ半導体牛導体素子4t
−流れる電流が急激に増大し、その電流検出信号が設定
レベルを超えると、瞬時電流検出系Aの比較回路16が
出力信号を生ずる。
However, the output current increases and the switch semiconductor conductor element 4t
- When the flowing current increases rapidly and its current detection signal exceeds a set level, the comparator circuit 16 of the instantaneous current detection system A produces an output signal.

オア回路17はこの出力信号全比較回路15からの出力
信号より誂先して駆動回路18に与え、駆動回路18は
スィッチ7グ牛導体素子の導通幅を制限するよう瞬時に
動作する。(以下、この動作全瞬時垂下という)○更に
出力iJL流をとろうとすると第4図に示すような出力
電圧の瞬時舟下が行われ、出力を流は制限されてスイッ
チング半導体素子4を過電流による損傷から保獲する。
The OR circuit 17 applies the output signal from the total comparison circuit 15 to the drive circuit 18, and the drive circuit 18 instantaneously operates to limit the conduction width of the switch 7 conductor element. (Hereinafter, this operation will be referred to as total instantaneous drooping.) ○If the output iJL current is further attempted, the output voltage will drop instantaneously as shown in Figure 4, and the output current will be limited, causing the switching semiconductor element 4 to overcurrent. Protected from damage caused by.

この過電流保循、つまり瞬時垂下が行われている場合、
前述からも分るように直流出力電圧のフィードバック系
は無効にされてしまい、駆動パルス18からの駆動パル
スはスイッチング半導体素子の電流に依存する。
If this overcurrent protection, or instantaneous droop, occurs,
As can be seen from the foregoing, the DC output voltage feedback system is disabled and the drive pulses from drive pulse 18 depend on the current of the switching semiconductor element.

〔発明が解決しようとする問題点〕[Problem that the invention seeks to solve]

最近、斯かる電力変換装置に対して小型軽量化が強く要
望されている。この要求に応えるためスイッチング半導
体素子のスイッチング周波数を高くすれば、フィルタ回
路6′を大幅に小型化でき、また電力変換用トランスも
小型@量化できる。
Recently, there has been a strong demand for such power converters to be smaller and lighter. If the switching frequency of the switching semiconductor element is increased to meet this demand, the filter circuit 6' can be significantly downsized, and the power conversion transformer can also be downsized.

フィルタ回路3′を小型化し高周波用とすると、フィル
タ回路6′の出力側に生じるリプルは1三相全波整流波
形に含まれるリプルとほぼ同様な大きな値となる。
If the filter circuit 3' is miniaturized and used for high frequencies, the ripple generated on the output side of the filter circuit 6' will have a large value almost the same as the ripple included in the 1-three-phase full-wave rectified waveform.

しかし、このリプルについては後述するが、スイッチン
グ半導体素子’k IJプル周波数よりかなジ高い周波
数で駆動することにより、直流出力側への影響全十分小
さくすることができる。
However, although this ripple will be described later, by driving at a frequency much higher than the switching semiconductor element'k IJ pull frequency, the influence on the DC output side can be sufficiently reduced.

しかし瞬時垂下に入った場合、前に説明したとおり、駆
動パルスはスイッチング半導体素子の電流に依存するの
で、スイッチング半導体素子5の導通制御による出力側
にあられれる三相全波整流にょろりプル成分(以下、三
相成分のりプルと称す)は低減されず、比較的大きな値
となる。
However, when instantaneous droop occurs, as explained earlier, the drive pulse depends on the current of the switching semiconductor element, so there is a slight pull component ( The three-phase component ripple (hereinafter referred to as three-phase component ripple) is not reduced and becomes a relatively large value.

通信用を源などでは、蓄電池の均等充電時には、出力奄
Rk定格以上必要とするので垂下状態で使用しなければ
ならない場合が多い。この場合、上記のように三相成分
のりプルが出力側にあられれると、通信品質に悪影1&
iiHを及ぼす評価雑音(周波数により実効的な妨害度
が異るため、各周波数成分に対し重みを加えて雑音を評
価するもので三相全波成分の600又は360Hzは無
視できないンが大きくなる。従って従来は、出力側のフ
ィルタ8はスイッチング周波数に対応した高周波成分に
対し、作用するものとして小型化は可能であったが、入
力側フィルタ回路6′は一次側での三相成分のり・プル
を低減するため大形のものを用いざるを得なかった。
In the case of a power source for communication, etc., when charging a storage battery evenly, the output power Rk rating or more is required, so it is often necessary to use it in a drooping state. In this case, if the three-phase component ripple occurs on the output side as described above, it will adversely affect the communication quality.
Evaluation noise that causes iiH (because the effective degree of interference varies depending on the frequency, the noise is evaluated by adding weight to each frequency component, and the three-phase full-wave component of 600 or 360 Hz becomes too large to ignore). Therefore, in the past, the output side filter 8 could be made smaller because it acted on high frequency components corresponding to the switching frequency, but the input side filter circuit 6' was designed to act on the three-phase components on the primary side. In order to reduce this, we had no choice but to use a large one.

〔問題点を解決するための手段〕[Means for solving problems]

直流出力電流に応じて平均したia電流検出信号必ずし
も平均値と一致する必要はない)が設定レベルを超える
とき、これらの差に相当する信号の大きさに応じて直流
出力電圧検出系の基準!諒電圧を低下、又は直流出力電
圧検出用抵抗器の抵抗値を増大させる。
When the IA current detection signal averaged according to the DC output current (not necessarily the same as the average value) exceeds the set level, the standard of the DC output voltage detection system is determined according to the magnitude of the signal corresponding to the difference between them! Reduce the output voltage or increase the resistance value of the DC output voltage detection resistor.

〔作 用〕[For production]

この様にしているので、@流出力電流に応じて平均化し
た電流検出信号が設定レベルを超えると、出力電圧検出
系の検出電圧と基準電圧との差をスイッチング半導体素
子の導通幅を制限する方向に大きくするので、スイッチ
/グ牛導体菓子の定電圧制?n機能を保持しながら出力
電圧の垂下を行わせることが出来る。
Since this is done, when the current detection signal averaged according to the output current exceeds the set level, the difference between the detection voltage of the output voltage detection system and the reference voltage is used to limit the conduction width of the switching semiconductor element. Since it increases in the direction, is the constant voltage system of the switch / Gugyu conductor sweets? It is possible to cause the output voltage to drop while maintaining the n function.

〔実施例〕〔Example〕

本発明の一実施例を第1図により説明する。 An embodiment of the present invention will be explained with reference to FIG.

この図において、第6図と同じ記号のものは同一部材全
示し、6は高周波用として小型化したフィルタ回路、1
9は整流回路7及びフィルタ回路@8により整流され平
均化され交直流出力電流全検出する電流検出手段、20
は演算増幅器、14は演算増@器20の出力により基準
電圧が可変される可変基準電源であり、例えば固定電圧
源と定電圧ダイオードと、この定電圧ダイオードに並列
接続されfc電圧分割用抵抗器などからなる。
In this figure, all the same parts are shown with the same symbols as in Figure 6, 6 is a filter circuit miniaturized for high frequency use, 1 is
Current detection means 9 detects all AC/DC output currents rectified and averaged by the rectifier circuit 7 and filter circuit @8; 20
14 is an operational amplifier, and 14 is a variable reference power supply whose reference voltage is varied by the output of the operational amplifier 20. For example, it includes a fixed voltage source, a constant voltage diode, and an fc voltage dividing resistor connected in parallel with the constant voltage diode. Consists of etc.

次にこの回路の動作を説明しながら、この発明に係る垂
下方法を説明する。
Next, the drooping method according to the present invention will be explained while explaining the operation of this circuit.

過*a状態でない通常の場合、瞬時it流流出出糸も平
均化電流検出系Bも駆動回路18に影響を与えるような
出力信号金主じない。このとき可変基準trJ!!、1
40基準電圧は一定のままであり、通常の定電圧制御が
行われる。従って、駆動回路18からの駆動パルスが又
流電源1の周波数に比べて十分に高い周波数(例えば2
0k)iz )であれば、少くともフィルタ8の出力に
あられれる数100Hz程度のす曽プル分に対しては十
分に応答でき、フィルタ回路6を大幅に小型化してもこ
の小型化によシ、出力側にあられれる三相成分り・グル
分の増大は出力電圧のフィードバック糸の第1」得によ
り十分に低減できる。
In the normal case where there is no over*a state, neither the instantaneous IT current nor the averaged current detection system B has any output signals that affect the drive circuit 18. At this time, variable reference trJ! ! ,1
The 40 reference voltage remains constant and normal constant voltage control is performed. Therefore, the drive pulse from the drive circuit 18 has a sufficiently high frequency (for example, 2
0k)iz), it can respond sufficiently to at least the sub-pull of several hundred Hz that is present in the output of the filter 8, and even if the filter circuit 6 is significantly miniaturized, it is possible to The increase in the three-phase component and the glue component that appears on the output side can be sufficiently reduced by the first gain of the feedback thread of the output voltage.

次に電流が瞬時的に増大することなく比較的緩やかに土
性する場合、瞬時電流検出系Aにおける′rkL流検出
流路出回路6電流検出信号が設定レベルに達する前に、
平均化電流検出系Bにおける電流検出手段Bからの電流
検出信号が設定レベルに達するよう、夫々の回路16.
20における設定レベル金選択しであるので、先ず演算
増幅器20がその設定レベルと電流検出信号との差に対
応する信号全可変基準電源14に与える0これに伴い可
変基準電源14は、演算増幅器20からの信号の大きさ
に応じてその基準電正金低下させる。従って、その低下
し次基準電圧と点XcD出力電圧検出信号との差は大き
くなり、演算増幅器16は出力電圧全低下させるような
信号を生じ、出力電圧は垂下(この場合の垂下を平均垂
下といううする。
Next, when the current increases relatively slowly without instantaneous increase, before the current detection signal of the 'rkL flow detection flow path output circuit 6 in the instantaneous current detection system A reaches the set level,
Each circuit 16.
20, the operational amplifier 20 first applies a signal corresponding to the difference between the set level and the current detection signal to the fully variable reference power supply 14. Accordingly, the variable reference power supply 14 Depending on the magnitude of the signal from that reference electrode, the positive value is lowered. Therefore, the difference between the next reference voltage and the output voltage detection signal at point I will use it.

前述から分るようにこの様な平均垂下の場合には、直流
出力電圧のフィードバック系が有効なので、スイッチン
グ半導体素子4の導通幅は制限された状態で直流出力電
圧の変動に応じて制御されている。従ってフィルタ回路
6を小型軽鎗化したことにより出力す・プル分が増えて
も、平均垂下領域ではスイッチング半導体素子4の定電
圧制御機能が確保されているので、実質的に出力り・プ
ル分は増えず、評価雑音も大きくならない。
As can be seen from the above, in the case of such an average droop, the feedback system of the DC output voltage is effective, so the conduction width of the switching semiconductor element 4 is controlled in a limited state according to fluctuations in the DC output voltage. There is. Therefore, even if the output/pull increases as a result of making the filter circuit 6 smaller and lighter, the constant voltage control function of the switching semiconductor element 4 is secured in the average droop region, so the output/pull actually increases. does not increase, and evaluation noise does not increase.

次に瞬時に電流が増大して過電流状態に至った場合には
、平均化電流検出系Bは応答が遅いため先ず瞬時電流検
出系Aにおける電流検出信号が設定レベルに達し、比較
回路16がオア回路17を介して1u動回路18に信号
を与え、瞬時垂下が行われスイッチング半導体素子を保
膿する1、そしてこの瞬時垂下が開始して僅かな時間(
例えば数Hz)の経過後、電流の瞬時的な増大は平均化
1流検出系Bにおいても検出され、電流検出信号が演算
増幅器20の設定レベル奮起えることにより、演算増幅
器20が信号全可変基準電圧源14に与えてその基準電
圧を低下させる。つ1り平均垂下が行わrしる。この平
均者下が行われると、系A、Hの設定レベルは前述の通
りであるので、第2図の鎖線で示すように、瞬時垂下a
から平均垂下すに移行する。従って瞬時垂下が行われて
いる時間は極めて短く、その間の評価雑音の増大は通信
上、実質的に支障がない。
Next, when the current instantaneously increases and an overcurrent condition occurs, the averaged current detection system B has a slow response, so the current detection signal in the instantaneous current detection system A reaches the set level first, and the comparator circuit 16 A signal is given to the 1u circuit 18 via the OR circuit 17, and instantaneous drooping is performed to protect the switching semiconductor element 1. After this instantaneous drooping starts, a short time (
For example, after several Hz), the instantaneous increase in current is also detected in the averaging first current detection system B, and the current detection signal rises to the set level of the operational amplifier 20, so that the operational amplifier 20 changes the signal fully variable standard. voltage source 14 to lower its reference voltage. An average droop is performed. When this averager lowering is performed, since the set levels of systems A and H are as described above, the instantaneous droop a
to average droop. Therefore, the time during which instantaneous drooping is performed is extremely short, and the increase in evaluation noise during that time does not substantially impede communication.

以上の実施例では、演算増幅器20の出力信号で町変基
4を源の基準電圧金町変じたが、第1図において@線で
示すように、電圧検出用抵抗12としてム〕゛変抵抗器
を用い、この可変抵抗器の抵抗値を変えてもよい。また
平均化され之出力電流の検出は、必ずしも出力側でおこ
なう必要はなく、検出器乙のように1次側にあっても良
いO 〔効 果〕 以上説明したように、本発明によれば出力電圧の垂下鎖
酸においてもスイッチング半導体素子の制御機能に確保
しているので、フィルタ回路の小型軽量化によるり・プ
ル分の増大は垂下領域においてもスイッチング半導体素
子の制御機能により十分低減でき、評価雑音を支障のな
い程度に抑止できる。従ってフィルタ回路全大幅に小型
軽量化することが可能である。
In the above embodiment, the output signal of the operational amplifier 20 is used to change the source reference voltage of the transformer 4, but as shown by the @ line in FIG. The resistance value of this variable resistor may be changed using Furthermore, the detection of the averaged output current does not necessarily have to be performed on the output side, and may be performed on the primary side like the detector B. [Effect] As explained above, according to the present invention, Even in the drooping range of the output voltage, the control function of the switching semiconductor element is secured, so the increase in the pull component can be sufficiently reduced by making the filter circuit smaller and lighter. Evaluation noise can be suppressed to an acceptable level. Therefore, the entire filter circuit can be significantly reduced in size and weight.

【図面の簡単な説明】[Brief explanation of the drawing]

第1図は本発明による出力垂下方法の一実施例を実施す
る之めの電力変換装fjXtt−示す図、第2図は本発
明を説明するための垂下特性を示す因、第6図は従来方
法を説明するための電力変換装置を示す図、第4図は従
来方法を説明するための垂下曲線を示す図である。 1・・・父流電源    2.7・・・整流回路6.8
・・・フィルタ回路 4・・・スイッチング半導体素子 5・・・電力変換用トランス 6・・・′電流検出回路 9.10・・・直流出力亀子 13.20・・・演算増幅器 15.16・・・比較回路 17・・・オア回路 18・・・駆動回路 日本電信電話株式会社 第2図    第午國
Fig. 1 is a diagram showing a power converter fjXtt for implementing an embodiment of the output drooping method according to the present invention, Fig. 2 is a diagram showing the drooping characteristics for explaining the present invention, and Fig. 6 is a diagram showing a conventional FIG. 4 is a diagram showing a power conversion device for explaining the method, and FIG. 4 is a diagram showing a drooping curve for explaining the conventional method. 1... Father current power supply 2.7... Rectifier circuit 6.8
...Filter circuit 4...Switching semiconductor element 5...Power conversion transformer 6...'Current detection circuit 9.10...DC output key 13.20...Operation amplifier 15.16...・Comparison circuit 17...OR circuit 18...Drive circuit Nippon Telegraph and Telephone Corporation Figure 2

Claims (1)

【特許請求の範囲】[Claims] 直流出力電圧の検出電圧と基準電圧との差の大きさに応
じてスイッチング半導体素子の導通幅を制御する機能、
及び前記スイッチング半導体素子を流れる電流の検出値
が設定レベルを超えるとき前記スイッチング半導体素子
の導通幅を制限して出力電圧の瞬時垂下を行わせる機能
を少くとも備えた電力変換回路において、出力電流に応
じて平均化された検出信号が前記瞬時垂下の設定レベル
とは別の設定レベルを超えるとき、前記スイッチング半
導体素子の導通幅を制限する方向に前記検出電圧と基準
電圧との差を大きくすることを特徴とする電力変換装置
の出力垂下方法。
A function that controls the conduction width of the switching semiconductor element according to the magnitude of the difference between the detection voltage of the DC output voltage and the reference voltage.
and a power conversion circuit having at least a function of limiting the conduction width of the switching semiconductor element to cause an instantaneous drop in the output voltage when the detected value of the current flowing through the switching semiconductor element exceeds a set level. When the detected signal averaged accordingly exceeds a set level different from the set level of the instantaneous droop, the difference between the detected voltage and the reference voltage is increased in a direction that limits the conduction width of the switching semiconductor element. An output drooping method for a power conversion device characterized by:
JP60151515A 1985-07-10 1985-07-10 Power converter for communication Expired - Lifetime JP2566131B2 (en)

Priority Applications (1)

Application Number Priority Date Filing Date Title
JP60151515A JP2566131B2 (en) 1985-07-10 1985-07-10 Power converter for communication

Applications Claiming Priority (1)

Application Number Priority Date Filing Date Title
JP60151515A JP2566131B2 (en) 1985-07-10 1985-07-10 Power converter for communication

Publications (2)

Publication Number Publication Date
JPS6216066A true JPS6216066A (en) 1987-01-24
JP2566131B2 JP2566131B2 (en) 1996-12-25

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ID=15520192

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JP60151515A Expired - Lifetime JP2566131B2 (en) 1985-07-10 1985-07-10 Power converter for communication

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Cited By (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JPS63164382U (en) * 1987-04-15 1988-10-26
JPH0246130A (en) * 1988-08-04 1990-02-15 Fuji Electric Co Ltd Overload protective circuit for switching regulator
JPH037678U (en) * 1989-06-09 1991-01-24
CN112448578A (en) * 2019-09-04 2021-03-05 株式会社东芝 Switching power supply circuit

Citations (2)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JPS54116627A (en) * 1978-03-01 1979-09-11 Yuasa Battery Co Ltd Switching regulator
JPS6215024A (en) * 1985-07-10 1987-01-23 Mitsubishi Electric Corp Grinding method for metal mold

Patent Citations (2)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JPS54116627A (en) * 1978-03-01 1979-09-11 Yuasa Battery Co Ltd Switching regulator
JPS6215024A (en) * 1985-07-10 1987-01-23 Mitsubishi Electric Corp Grinding method for metal mold

Cited By (7)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JPS63164382U (en) * 1987-04-15 1988-10-26
JPH0246130A (en) * 1988-08-04 1990-02-15 Fuji Electric Co Ltd Overload protective circuit for switching regulator
JP2765704B2 (en) * 1988-08-04 1998-06-18 富士電機株式会社 Overload protection circuit for switching regulator
JPH037678U (en) * 1989-06-09 1991-01-24
CN112448578A (en) * 2019-09-04 2021-03-05 株式会社东芝 Switching power supply circuit
JP2021040445A (en) * 2019-09-04 2021-03-11 株式会社東芝 Switching power supply circuit
US11594963B2 (en) 2019-09-04 2023-02-28 Kabushiki Kaisha Toshiba Switching power circuit

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