JPS6056394B2 - Motor control device - Google Patents
Motor control deviceInfo
- Publication number
- JPS6056394B2 JPS6056394B2 JP51149173A JP14917376A JPS6056394B2 JP S6056394 B2 JPS6056394 B2 JP S6056394B2 JP 51149173 A JP51149173 A JP 51149173A JP 14917376 A JP14917376 A JP 14917376A JP S6056394 B2 JPS6056394 B2 JP S6056394B2
- Authority
- JP
- Japan
- Prior art keywords
- motor
- signal
- rotational speed
- circuit
- level
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Expired
Links
Description
【発明の詳細な説明】
本発明はモータの回転速度に応じた周波数信号を形成し
、この周波数信号に応じて上記モータの回転速度を制御
するようにしたモータの制御装置に関するものであつて
、テープレコーダ、ＶＴＲ。DETAILED DESCRIPTION OF THE INVENTION The present invention relates to a motor control device that forms a frequency signal corresponding to the rotational speed of a motor and controls the rotational speed of the motor in accordance with this frequency signal. Tape recorder, VTR.
等の記録再生装置やレコードプレーヤーに用いて最適な
ものである。従来から知られているように、例えばテー
プレコーダにおいては、磁気テープを走行させるために
ブラシレス直流モータ（以下において単にモーｌ夕と称
する）が多用されている。It is most suitable for use in recording and reproducing devices such as the above, and record players. As is conventionally known, in tape recorders, for example, brushless DC motors (hereinafter simply referred to as motors) are often used to run magnetic tapes.
そしてモータの回転速度を所定の回転速度に保持するた
めに、以下に述べるように、大別して二種類の制御装置
が従来から知られている。次に従来のモータの制御装置
の第１例を第１図及び第２図にもとづき説明する。In order to maintain the rotational speed of the motor at a predetermined rotational speed, two types of control devices are conventionally known, as described below. Next, a first example of a conventional motor control device will be explained based on FIGS. 1 and 2.
第１図はモータの制御装置のブ冶ツクダイヤグラムてあ
って、モータ１と周波数発電機（以下においてＦＧと称
する）２とは連動して回転するようになつている。FIG. 1 is a block diagram of a motor control device, in which a motor 1 and a frequency generator (hereinafter referred to as FG) 2 are designed to rotate in conjunction with each other.
そしてＦＧ２からは、第２Ａ図・に示すようにモータ１
の回転速度に比例した周波数信号１８が得られ、この周
波数信号１０は次段のリミッター回路３に供給される。
次いでリミッター回路３からは、第２Ｂ図に示すような
波形整形された連続したパルス信号１１が得られる。な
おこのパルス信号１１の時間巾Ｔは、モータ１の回転速
度に比例して変化するようになつている。そしてパルス
信号１１は再トリガ出来ないモノステーブル・マルチバ
イブレータ回路（以下においてモノマルチと称する）４
に供給される。このモノマルチ４から得られるパルス信
号１２は、第２Ｃ図に示すようにパルス信号１１の立上
り位置に同期してＨレベルになり、所定の時間巾Ｔ。後
にＬレベルになるようになつている。ところで、パルス
信号１２のＨレベルの時間巾Ｔｏはモノマルチ４の時定
数によつて決定されるが、Ｌレベルの時間巾を。From FG2, motor 1 is connected as shown in Figure 2A.
A frequency signal 18 proportional to the rotation speed of is obtained, and this frequency signal 10 is supplied to the limiter circuit 3 at the next stage.
Next, from the limiter circuit 3, a continuous pulse signal 11 whose waveform has been shaped as shown in FIG. 2B is obtained. Note that the time width T of this pulse signal 11 is designed to change in proportion to the rotational speed of the motor 1. The pulse signal 11 is a monostable multivibrator circuit (hereinafter referred to as monomulti) 4 that cannot be retriggered.
supplied to The pulse signal 12 obtained from the monomulti 4 goes high in synchronization with the rising position of the pulse signal 11 for a predetermined time width T, as shown in FIG. 2C. Later on, it became L level. By the way, the time width To of the H level of the pulse signal 12 is determined by the time constant of the monomulti 4, and the time width To of the L level.
はモータ１の回転速度に応じて変化する。即ち、前述の
パルス信号１１の時間Ｔは、モータ１が低速回転になつ
たときこれに応じて広くなり、これとは逆にモータ１が
高速回転になつたとき狭くなる。一方、モノマルチ４の
時定数は一定であり、しかもパルス信号１１とパルス信
号１２との立上り位置は同期しているから、パルス信号
１２のＬレベルの時間巾ちはモータ１の回転数に比例す
ることになる。そしてパルス信号１２は次段のパルス巾
一直流電圧変換回路（以下において変換回路と称する）
５に供給される。なお変換回路５は鋸歯状波信号発生回
路（図示せず）とサンプルホールド回路（図示せず）と
を含むものてあつて、鋸歯状波信号発生回路からは、第
２Ｄ図に示すような鋸歯状波信号１３が得られる。changes depending on the rotational speed of the motor 1. That is, the time T of the pulse signal 11 described above becomes wider when the motor 1 rotates at a lower speed, and conversely becomes narrower when the motor 1 rotates at a higher speed. On the other hand, since the time constant of the monomulti 4 is constant and the rising positions of the pulse signals 11 and 12 are synchronized, the time width of the L level of the pulse signal 12 is proportional to the rotation speed of the motor 1. I will do it. Then, the pulse signal 12 is transmitted to the next stage pulse width DC voltage conversion circuit (hereinafter referred to as conversion circuit).
5. The conversion circuit 5 includes a sawtooth signal generation circuit (not shown) and a sample hold circuit (not shown), and the sawtooth signal generation circuit generates a sawtooth signal as shown in FIG. 2D. A wave signal 13 is obtained.
そして鋸歯状波信号１３の波高値■は、パルス信号１２
のＬレベルの時間巾Ｔ。に比例して変化する。これは言
い換えれば、モータ１の回転数が低下したとき波高値■
が高くなり、これとは逆に回転数が高くなつたとき波高
値Ｖが低くなることを意味する。次いで鋸歯状波信号１
３はサンプルホールド回路に供給され、この回路から第
２Ｅ図に示すようにその電圧レベルが階段状に変化する
直流信号１４が得られる。即ち、この直流信号１４の電
圧レベルは、モータ１の回転速度が低下したとき高くな
り、これとは逆に回転速度が高くなると低下する。この
直流信号１４はモータ駆動回路６の制御端子（図示せず
）に供給される。The peak value ■ of the sawtooth wave signal 13 is the same as that of the pulse signal 12.
The time width T of the L level. changes in proportion to. In other words, when the rotation speed of motor 1 decreases, the peak value ■
conversely, as the rotational speed increases, the peak value V decreases. Then sawtooth signal 1
3 is supplied to a sample and hold circuit, from which a DC signal 14 whose voltage level changes stepwise as shown in FIG. 2E is obtained. That is, the voltage level of this DC signal 14 increases when the rotational speed of the motor 1 decreases, and conversely decreases when the rotational speed increases. This DC signal 14 is supplied to a control terminal (not shown) of the motor drive circuit 6.
そしてモータ１の回転速度が低下して直流信号１４の電
圧レベルが高くなると、モータ１に供給される制御信号
が調整されて、このモータ１の回転速度が次第に高くな
る。この結果、モータ１の回転速度が所定の回転速度に
近づくにつれて、直流信号１４の電圧レベルが低くなる
。そしてモータ１が所定の回転速度になると、直流信号
１４も一定の電圧レベルになつて、モータ１は所定の回
転速度を保持する。しかし、上述の如く構成された第１
図に示すモータの制御装置に、例えば、第２Ａ図に示す
周波数信号１０に較べて２倍の周波数の第２Ｎ図に示す
ような周波数信号１０ａが供給されると、時間ｔ１の位
置て得られるトリガー信号（図示せず）はモノマルチ４
の動作中に供給されることになる。従つてモノマルチ４
はこのトリガー信号を無視することになり、このために
直流信号１４の電圧レベルも変化しない。そして時騨，
の位置で得られるトリガー信号にもとづいて、モータ１
を前述の如く制御する。このように従来のモータの制御
装置では、モータの回転速度が所定の回転速度の整数倍
になると、この回転速度をそのまま保持してしまう欠点
があつた。次に従来のモータの制御装置の第２例を第３
図及び第４図にもとづき説明する。When the rotational speed of the motor 1 decreases and the voltage level of the DC signal 14 increases, the control signal supplied to the motor 1 is adjusted, and the rotational speed of the motor 1 gradually increases. As a result, as the rotational speed of the motor 1 approaches a predetermined rotational speed, the voltage level of the DC signal 14 becomes lower. When the motor 1 reaches a predetermined rotation speed, the DC signal 14 also becomes a constant voltage level, and the motor 1 maintains the predetermined rotation speed. However, the first
For example, when a frequency signal 10a as shown in FIG. 2N having twice the frequency as the frequency signal 10 shown in FIG. 2A is supplied to the motor control device shown in FIG. Trigger signal (not shown) is mono multi 4
will be supplied during operation. Therefore, monomulti 4
will ignore this trigger signal, and therefore the voltage level of the DC signal 14 will not change. And Tokiden,
Based on the trigger signal obtained at the position of
is controlled as described above. As described above, the conventional motor control device has a drawback that when the rotational speed of the motor becomes an integral multiple of a predetermined rotational speed, this rotational speed is maintained as it is. Next, the second example of the conventional motor control device will be explained in the third example.
The explanation will be given based on the figure and FIG.
なお第１例と同様の動作をなす回路ブロックには同一の
符号を付しその説明を省略する。第３図は回路構成を示
すブロックダイヤグラムであつて、モータ１の回転にと
もないＦＧ２から第４Ａ図に示すような周波数信号１０
が得られ、次段のりミッター回路３に供給される。Note that circuit blocks that operate in the same way as in the first example are given the same reference numerals and their explanations will be omitted. FIG. 3 is a block diagram showing the circuit configuration, and as the motor 1 rotates, a frequency signal 10 as shown in FIG. 4A is generated from FG2.
is obtained and supplied to the next-stage glue limiter circuit 3.
そしてりミッター回路３から第４Ｂ図に示すようなパル
ス信号１１が得られ、次段の鋸歯状波信号発生回路７に
供給される。この鋸歯状波信号発生回路７は、パルス信
号１１の立上り位置に同期して、所定の傾斜角度の鋸歯
状波信号１３を発生する。A pulse signal 11 as shown in FIG. 4B is obtained from the limiter circuit 3 and supplied to the sawtooth wave signal generating circuit 7 at the next stage. This sawtooth wave signal generation circuit 7 generates a sawtooth wave signal 13 having a predetermined inclination angle in synchronization with the rising position of the pulse signal 11.
この鋸歯状波信号１３は次段の比較回路８の一方の入力
端子に供給されるが、他方の入力端子には基準信号発生
回路９からの電圧レベル■１の基準信号１５が供給され
ている。そして比較回路８において、第４Ｃ図に示すよ
うに、鋸歯状波信号１３と基準信号１５との電圧比較が
行われる。この結果、基準信号１５の電圧レベル■１よ
りも鋸歯状波信号１３の電圧レベルが高いとき、その時
間巾Ｔ１に応じたパル・ス巾のパルス信号１６が得られ
る。即ち、モータ１の回転速度が低くなつたとき、第４
Ｄ図に示すようにパルス信号１６のＨレベルの時間巾ｔ
１が広くなる。またモータ１の回転速度が高くなつたと
き、第４Ｄ図に示すようにパルス信号１６のＨレベルの
時間巾ちが狭くなる。次いでこのパルス信号１６はモー
タ駆動回路６に供給され、そのＨレベルの時間巾ｔ１に
もとづいてモータ１の回転速度を制御する。This sawtooth wave signal 13 is supplied to one input terminal of the next-stage comparison circuit 8, while the other input terminal is supplied with the reference signal 15 at voltage level 1 from the reference signal generation circuit 9. . Then, in the comparator circuit 8, a voltage comparison is performed between the sawtooth wave signal 13 and the reference signal 15, as shown in FIG. 4C. As a result, when the voltage level of the sawtooth wave signal 13 is higher than the voltage level 1 of the reference signal 15, a pulse signal 16 having a pulse width corresponding to the time width T1 is obtained. That is, when the rotational speed of the motor 1 becomes low, the fourth
As shown in figure D, the time width t of the H level of the pulse signal 16
1 becomes wider. Further, when the rotational speed of the motor 1 increases, the time width of the H level of the pulse signal 16 becomes narrower, as shown in FIG. 4D. This pulse signal 16 is then supplied to the motor drive circuit 6, and the rotational speed of the motor 1 is controlled based on the time width t1 of the H level.
従つてモータ１の回転速度が低下して、パルス信号１６
のＨレ・ベルの時間巾ちが広くなると、モータ１に供給
される制御信号（図示せず）の供給時間が長くなり、モ
ータ１の回転速度が次第に高くなる。これとは逆にモー
タ１の回転速度が高くなつて、パルス信号１６のＨレベ
ルの時間巾ちが狭くなると、モータ１に供給される制御
信号の供給時間が短かくなり、モータ１の回転速度が次
第に低くなる。しかし、上述の如く構成された第３図に
示すモータの制御装置では、ＦＧ２から得られる周波数
信号１０以外にモータ１の回転速度を決定するために基
準信号１５が必要である。しかも基準信号１５の電圧レ
ベルＶ１が変動すると、パルス信号１６のＨレベルの時
間巾ｔ１が変化して、モータ１の回転速度を正確に制御
することができない。このために従来は基準信号発生回
路９に温度補償回路等を別に設けて、基準信号１５の電
圧レベルＶ１が変動しないようにしていた。更に比較回
路８の回路動作も、周囲の温度変化や電源電圧の変動に
よる影響を受けやすいため、温度補償回路や定電圧回路
等を設けなければならなかつた。一方、モータ１の回転
速度を所望の回転速度に変化させる場合には、鋸歯状波
信号１３の傾斜角度を変えてパルス信号１６のＨレベル
の時間巾ｔ１を変えるようにしている。このような場合
、コンデンサ（図示せす）とこれを充電させるための定
電流電源（図示せず）とを設けて、コンデンサに供給さ
れる充電電流を制御するようにしている。従つて定電流
電源が温度変化等によつて変動すると、鋸歯状波信号１
３の傾斜角度が直線的にはならない。このため基準信号
１５との電圧比較を行つて，も、比較回路８から得られ
るパルス信号１６のＨレベルの時間巾ちは、必らずしも
モータ１の回転速度に応じたものとはならなかつた。従
つて鋸歯状波信号発生回路７には特別の温度補償回路等
を設ける必要があり、このために生産コストが高くなつ
ていた。本発明は上述の如き欠陥を是正すべく発明され
たものであつて、モータの回転速度に応じた周波数信号
を形成し、この周波数信号に応じて上記モータの回転速
度を制御するようにしたモータの制ｊ御装置において、
上記周波数信号が供給されるりミッター回路と、このり
ミッター回路の出力が供給されるリトリガラブル・モノ
ステイブル・マルチバイブレータと、このリトリガラブ
ル◆モノステイブル・マル芋バイブレータの時定数を可
変すクることによりモータの回転速度を設定する調整手
段と、上記リトリガラブル●モノステイブル◆マルチバ
イブレータの出力信号をそのパルス巾に応じた直流電圧
に変換する変換回路とを設け、上記変換回路の出力に応
じて上記モータを制御するようにしたものである。Therefore, the rotational speed of the motor 1 decreases, and the pulse signal 16
As the time width of the H level becomes wider, the supply time of the control signal (not shown) supplied to the motor 1 becomes longer, and the rotational speed of the motor 1 gradually increases. On the contrary, when the rotational speed of the motor 1 increases and the time width of the H level of the pulse signal 16 becomes narrower, the supply time of the control signal supplied to the motor 1 becomes shorter, and the rotational speed of the motor 1 becomes smaller. gradually decreases. However, in the motor control device shown in FIG. 3 configured as described above, a reference signal 15 is required to determine the rotational speed of the motor 1 in addition to the frequency signal 10 obtained from the FG2. Moreover, when the voltage level V1 of the reference signal 15 fluctuates, the time width t1 of the H level of the pulse signal 16 changes, making it impossible to accurately control the rotational speed of the motor 1. For this reason, conventionally, a temperature compensation circuit or the like has been separately provided in the reference signal generation circuit 9 to prevent the voltage level V1 of the reference signal 15 from changing. Furthermore, since the circuit operation of the comparator circuit 8 is also susceptible to changes in ambient temperature and power supply voltage, it is necessary to provide a temperature compensation circuit, a constant voltage circuit, and the like. On the other hand, when changing the rotational speed of the motor 1 to a desired rotational speed, the time width t1 of the H level of the pulse signal 16 is changed by changing the inclination angle of the sawtooth wave signal 13. In such a case, a capacitor (not shown) and a constant current power supply (not shown) for charging the capacitor are provided to control the charging current supplied to the capacitor. Therefore, when the constant current power supply fluctuates due to temperature changes, etc., the sawtooth wave signal 1
The inclination angle of No. 3 is not linear. Therefore, even when the voltage is compared with the reference signal 15, the time width of the H level of the pulse signal 16 obtained from the comparison circuit 8 does not necessarily correspond to the rotational speed of the motor 1. Nakatsuta. Therefore, it is necessary to provide a special temperature compensation circuit or the like to the sawtooth wave signal generating circuit 7, which increases the production cost. The present invention was invented to correct the above-mentioned defects, and provides a motor which forms a frequency signal corresponding to the rotational speed of the motor and controls the rotational speed of the motor according to this frequency signal. In the control device of
A retriggerable monostable multivibrator to which the above frequency signal is supplied, a retriggerable monostable multivibrator to which the output of the remitter circuit is supplied, and a motor by varying the time constant of the retriggerable monostable marimo vibrator. and a conversion circuit that converts the output signal of the retriggerable monostable multivibrator into a DC voltage according to its pulse width, and the motor is controlled according to the output of the conversion circuit. It was designed to be controlled.
このように構成されたモータの制御装置によれば、モー
タの回転速度が大巾に、例えば整数倍に変化しても、こ
れを検出して所定の回転速度になるように制御すること
が可能になる。次に本発明の一実施列を第５図及び第６
図にもとづき説明する。According to the motor control device configured in this way, even if the rotational speed of the motor changes widely, for example, by an integral multiple, it is possible to detect this and control the motor to a predetermined rotational speed. become. Next, one embodiment of the present invention is shown in FIGS. 5 and 6.
This will be explained based on the diagram.
なお第１図及び第３図に示す従来例と同様の回路動作を
なす回路ブロックには同Ｌ−の符号を付しその説明を省
略する。第５図は回路構成を示すブロックダイヤグラム
であつて、１はモータ、２はＦＧｌ３はりミッター回路
である。Note that circuit blocks that perform the same circuit operations as those of the conventional example shown in FIGS. 1 and 3 are given the same reference numerals L-, and their explanations will be omitted. FIG. 5 is a block diagram showing the circuit configuration, where 1 is a motor and 2 is an FG13 beam transmitter circuit.
そしてりミッター回路３からは第６Ｂ図に示すようなパ
ルス信号３１が得られるようになつている。２０は微分
回路であつて、これに供給されるパルス信号３１の立上
り位置に同期して、第６Ｃ図に示すようなトリガー信号
３２が得られるようになつている。A pulse signal 31 as shown in FIG. 6B is obtained from the limiter circuit 3. Reference numeral 20 denotes a differentiating circuit, which is designed to generate a trigger signal 32 as shown in FIG. 6C in synchronization with the rising position of a pulse signal 31 supplied thereto.
２１はリトリガラブル・モノステイブル●マルチバイブ
レータ（以下において再トリガモノマルチと称する）で
あつて、トリガー信号３２に同期して第６Ｄ図に示よう
なパルス信号３３が得られるようになつている。Reference numeral 21 denotes a retriggerable monostable multivibrator (hereinafter referred to as a retriggerable monostable multivibrator), which is designed to generate a pulse signal 33 as shown in FIG. 6D in synchronization with a trigger signal 32.
そして再トリガモノマルチ２１の時定数、即ちパルス信
号３３のＨレベルの時間巾ＴｌＯは、可変抵抗２１ａを
調整することによつて変化するようになつている。また
再トリガモノマルチ２１は、これが動作中に引きつづい
てトリガー信号３２が供給されると、最後のトリガー信
号が供給された時点から時定数に対応した時間巾ＴｌＯ
だけ動作時間が延長されるようになつている。従つて再
トリガモノマルチ２１の時定数よりもトリガー信号３２
の時間巾が短かい場合には、パルス信号３３のＨレベル
の時間巾が延長される。また５は変換回路、６はモータ
駆動回路であつて、それぞれの回路構成及び回路動作は
前述の従来例の場合と同様である。The time constant of the retrigger monomulti 21, that is, the time width TlO of the H level of the pulse signal 33, is changed by adjusting the variable resistor 21a. In addition, when the re-trigger mono multi 21 is continuously supplied with the trigger signal 32 while it is in operation, the time width TlO corresponding to the time constant starts from the time when the last trigger signal is supplied.
However, the operating time has been extended. Therefore, the trigger signal 32 is smaller than the time constant of the retrigger monomulti 21.
If the time width is short, the time width of the H level of the pulse signal 33 is extended. Further, 5 is a conversion circuit, and 6 is a motor drive circuit, and the circuit configuration and circuit operation of each are the same as in the conventional example described above.
次に上述の如く構成された第５図に示すモータの制御装
置の回路動作を説明する。Next, the circuit operation of the motor control device shown in FIG. 5 constructed as described above will be explained.
モータ１が回転すると、その回転速度に応じて、ＦＧ２
から第６Ａ図に示すような周波数信号３０が得られる。When motor 1 rotates, FG2
From this, a frequency signal 30 as shown in FIG. 6A is obtained.
次いでりミッター回路３によつて第６Ｂ図に示すような
パルス信号３１が得られ、これにもとづき微分回路２０
からトリガー信号３２が得られる。そしてトリガー信号
３２にもとづき、再トリガモノマルチ２１から第６Ｄ図
に示すようなパルス信号３３が得られる。ところで、モ
ータ１の回転周期が再トリガモノマルチ２１の時定数よ
りも大きい時には、パルス信号３３のＨレベルの時間巾
ＴｌＯは再トリガモノマルチ２１の時定数によつて決定
され、またＬレベルの時間巾ＴｌＯはモータ１の回転速
度に応じて変化する。Next, a pulse signal 31 as shown in FIG. 6B is obtained by the remitter circuit 3.
A trigger signal 32 is obtained from. Based on the trigger signal 32, a pulse signal 33 as shown in FIG. 6D is obtained from the retrigger monomulti 21. By the way, when the rotation period of the motor 1 is larger than the time constant of the retrigger monomulti 21, the time width TlO of the H level of the pulse signal 33 is determined by the time constant of the retrigger monomulti 21, and the time width TlO of the L level is determined by the time constant of the retrigger monomulti 21. The time width TlO changes depending on the rotational speed of the motor 1.
いま仮りに、モータ１の回転速度が次第に低下すれば、
パルス信号３３のＬレベルの時間巾Ｔ，Ｏが次第に広く
なる。従つて変換回路５内の鋸歯状波発生回路から、前
述したＬレベルの時間巾ＴｌＯに応じた波高値Ｖ。の鋸
歯状波信号３４ａが得られる。この結果、サンプルホー
ルド回路から得られる直流信号３５の電圧レベルは、第
６Ｆ図の点線のレベルＥ１から実線で示すレベルＥ２に
変化する。そしてモータ駆動回路６からモータ１に供給
される制御信号のレベルも高くなつて、モータ１の回転
速度は次第に高くなる。故に第６Ａ図の時間Ｔ２〜Ｔ３
に示すように、周波数信号３０の周期も短かくなる。従
つてパルス信号３３のＬレベルの時間巾ＴｌＯも短かく
なり、鋸歯状波信号３４ｂの波高値Ｖ。も低レベルにな
る。このため直流信号３５の電圧レベルも、電圧レベル
Ｅ２からＥ３に低下する。このときの直流信号３５の電
圧レベルの変化は、鋸歯状波信号３４ａ，３４ｂの波高
値■。の変化に比例する。このように直流信号３５の電
圧レベルが低下すると、モータ１の回転速度も低くなる
はづであるが、モータ１の慣性等によつてその回転速度
が急激に低下することはない。Now, if the rotational speed of motor 1 gradually decreases,
The time widths T and O of the L level of the pulse signal 33 gradually become wider. Therefore, from the sawtooth wave generation circuit in the conversion circuit 5, the peak value V is generated according to the above-mentioned L level time width TlO. A sawtooth wave signal 34a is obtained. As a result, the voltage level of the DC signal 35 obtained from the sample and hold circuit changes from the level E1 shown by the dotted line in FIG. 6F to the level E2 shown by the solid line. The level of the control signal supplied from the motor drive circuit 6 to the motor 1 also increases, and the rotational speed of the motor 1 gradually increases. Therefore, time T2-T3 in FIG. 6A
As shown in , the period of the frequency signal 30 also becomes shorter. Therefore, the L level time width TlO of the pulse signal 33 also becomes shorter, and the peak value V of the sawtooth wave signal 34b. will also be at a low level. Therefore, the voltage level of the DC signal 35 also decreases from voltage level E2 to E3. The change in the voltage level of the DC signal 35 at this time is the peak value ■ of the sawtooth wave signals 34a and 34b. is proportional to the change in When the voltage level of the DC signal 35 decreases in this way, the rotational speed of the motor 1 should also decrease, but due to the inertia of the motor 1, etc., the rotational speed does not decrease suddenly.
従つてＦＧ２から得られる周波数信号３０の周期は、第
６Ａ図の時間Ｔ３〜ζに示すように狭くなる。そしてト
リガー信号３２ａ，３２ｂ間の周期も狭くなるから、再
トリガモノマルチ４がトリガー信号３２ａによつて動作
している間に、次のトリガー信号３２ｂが供給される。
このため、再トリガモノマルチ２１はトリガー信号３２
ｂが供給された時腓，から、更に時間巾ＴｌＯだけ動作
する。故に鋸歯状波信号３４の、時間ζに対応する位置
には鋸歯状波が表われず、従つて直流信号３５の電圧レ
ベルＥ３も変化しない。このようにして、直流信号３５
の電圧レベルＥ３が一定のま）であれば、モータ１の回
転速度は次第に低下する。Therefore, the period of the frequency signal 30 obtained from FG2 becomes narrower as shown from time T3 to ζ in FIG. 6A. Since the cycle between the trigger signals 32a and 32b also becomes narrower, the next trigger signal 32b is supplied while the retrigger monomulti 4 is operating in response to the trigger signal 32a.
For this reason, the retrigger monomulti 21 uses the trigger signal 32
After b is supplied, the operation continues for a time width TlO. Therefore, the sawtooth wave does not appear at the position corresponding to time ζ of the sawtooth wave signal 34, and therefore the voltage level E3 of the DC signal 35 does not change. In this way, the DC signal 35
If the voltage level E3 remains constant, the rotational speed of the motor 1 gradually decreases.
従つて周波数信号３０の周期も第６Ａ図の時間ζ〜Ｔ５
に示すように広くなる。故にパルス信号３３のＬレベル
の時間巾ＴｌＯは、時間らに対応する位置まて延長され
ることになり、従つて鋸歯状波信号３４には鋸歯状波３
４ｃが表われることとなる。このため直流信号３５は電
圧レベルＥ３からＥ４に変化するので、モータ１の回転
速度は次第に高速回転になる。このように、モータ１の
回転速度が高くなると、再トリガモノマルチ２１の動作
中に次のトリガー信号３２が供給されるので、この間直
流信号３５の電圧レベルが変化しない。Therefore, the period of the frequency signal 30 is also the time ζ~T5 in FIG. 6A.
It becomes wider as shown in . Therefore, the L level time width TlO of the pulse signal 33 is extended to the position corresponding to the time, and therefore the sawtooth wave signal 34 has the sawtooth wave 3.
4c will appear. For this reason, the DC signal 35 changes from voltage level E3 to E4, so that the rotational speed of the motor 1 gradually increases. In this way, when the rotational speed of the motor 1 increases, the next trigger signal 32 is supplied while the retrigger monomulti 21 is operating, so the voltage level of the DC signal 35 does not change during this time.
従つてモータ１の回転速度が次第に高くなつて、所定の
回転速度の整数倍の回転速度になるようなこともなく、
またこの整数倍の回転速度をそのま）保持するようなこ
ともない。一方、再トリガモノマルチ２１の時定数は、
可変抵抗２１ａを調整することによつて変化させること
が出来るので、この時定数を選択してモータ１の回転速
度を所望の回転速度に変えることが出来る。次に再トリ
ガモノマルチ２１の時定数を変化させたときの制御装置
の回路動作を説明する。Therefore, the rotational speed of the motor 1 does not gradually increase to a rotational speed that is an integral multiple of the predetermined rotational speed.
Furthermore, there is no possibility of maintaining a rotational speed that is an integral multiple of this value. On the other hand, the time constant of the retrigger monomulti 21 is
Since it can be changed by adjusting the variable resistor 21a, the rotational speed of the motor 1 can be changed to a desired rotational speed by selecting this time constant. Next, the circuit operation of the control device when the time constant of the retrigger monomulti 21 is changed will be explained.
可変抵抗２１ａを調整して再トリガモノマルチ２１の時
定数か変化すると、この時定数を基準としてモータ１の
回転速度が制御される。即ち、再トリガモノマルチ２１
の時定数を小さくすると、パルス信号３３のＨレベルの
時間巾ＴｌＯが狭くなる。従つてパルス信号３３のＬレ
ベルの時間巾ＴｌＯが広くなり、以下前述のように鋸歯
状波信号３４の波高値Ｖ。及び直流信号３５の電圧レベ
ルが高くなる。このためモータ１の回転速度は次第に高
速回転となり、これに応じてＦＧ２から得られる周波数
信号３０の周期が次第に短かくなる。When the time constant of the retrigger monomulti 21 is changed by adjusting the variable resistor 21a, the rotational speed of the motor 1 is controlled based on this time constant. That is, the retrigger monomulti 21
When the time constant of is made smaller, the time width TlO of the H level of the pulse signal 33 becomes narrower. Therefore, the time width TlO of the L level of the pulse signal 33 becomes wider, and the peak value V of the sawtooth wave signal 34 increases as described above. And the voltage level of the DC signal 35 becomes high. Therefore, the rotational speed of the motor 1 gradually increases, and the period of the frequency signal 30 obtained from the FG 2 gradually becomes shorter accordingly.
そしてパル・ス信号３３のＨレベルの時間巾ＴｌＯより
も、周波数信号３０の周期が短かくなつたとき、前述の
ように直流信号３５の電圧レベルが低下する。従つてモ
ータ１の回転速度も、直流信号３５の電圧レベルに応じ
て低くなる。以後、モータ１の回転速ノ度は前述のよう
にして制御され、パルス信号３３のＨレベルの時間巾Ｔ
ｌＯを基準に高速回転を続ける。一方、可変抵抗２１ａ
を調整して再トリガモノマルチ２１の時定数が変化する
と、この時定数を基準としてモータ１の回転速度が制御
される。即ち、再トリガモノマルチ２１の時定数を大き
くすると、パルス信号３３のＨレベルの時間巾ＴｌＯが
広くなる。従つてパルス信号３３のＬレベルの時間巾Ｔ
ｌＯが狭くなり、以下前述のように鋸歯状波信号３４の
波高値Ｖ。及び直流信号３５の電圧レベルが低くなる。
このため、モータ１の回転速度は次第に低速回転となり
、これに応じてＦＧ２から得られる周波数信号３０の周
期が次第に広くなる。When the period of the frequency signal 30 becomes shorter than the H level time width TlO of the pulse signal 33, the voltage level of the DC signal 35 decreases as described above. Therefore, the rotational speed of the motor 1 also decreases in accordance with the voltage level of the DC signal 35. Thereafter, the rotational speed of the motor 1 is controlled as described above, and the time width T of the H level of the pulse signal 33 is controlled.
Continue high speed rotation based on lO. On the other hand, variable resistor 21a
When the time constant of the re-trigger monomulti 21 changes by adjusting , the rotational speed of the motor 1 is controlled based on this time constant. That is, when the time constant of the retrigger monomulti 21 is increased, the time width TlO of the H level of the pulse signal 33 becomes wider. Therefore, the time width T of the L level of the pulse signal 33
lO becomes narrower, and the peak value V of the sawtooth wave signal 34 becomes smaller as described above. And the voltage level of the DC signal 35 becomes low.
For this reason, the rotational speed of the motor 1 gradually decreases, and the period of the frequency signal 30 obtained from the FG 2 gradually increases accordingly.
そしてパルス信号３３のＨレベルの時間巾ＴｌＯよりも
、周波数信号３０の周期が広くなつたとき、前述のよう
に直流信号３５の電圧レベルが高くなる。従つてモータ
１の回転速度も、直流信号３５の電圧レベルに応じて高
くなる。以後、モータ１の回転速度は前述のように制御
され、パルス信号３３のＨレベルの時間巾ＴｌＯを基準
に低速回転を続ける。このように、再トリガモノマルチ
２１の時定数を調整すれば、パルス信号３３のＨレベル
の時間巾ＴｌＯが変化するので、これを基準にして極め
て容易にモータ１の回転速度を変えることが可能である
。従つて従来のこの種の制御装置のように、モータ１の
回転速度を決定するために基準信号発生回路等を設ける
必要がなく、また制御装置全体の回路構成を簡単にする
ことが出来る。本発明は上述の如く、モータの回転速度
に応じた周波数信号が供給されるりミッター回路と、こ
のりミッター回路の出力が供給されるリトリガラブル◆
モノステイブル●マルチバイブレータと、このリトリガ
ラブル・モノステイブル・マルチバイブレータの時定数
を可変することによりモータの回転速度を設定する調整
手段と、上記リトリガラブル●モノステイブル●マルチ
バイブレータの出力信号をそのパルス巾に応じた直流電
圧に変換する変換回路とを設け、上記変換回路の出力に
応じて上記モータを制御するようにしたものである。When the period of the frequency signal 30 becomes wider than the H level time width TlO of the pulse signal 33, the voltage level of the DC signal 35 becomes higher as described above. Therefore, the rotational speed of the motor 1 also increases according to the voltage level of the DC signal 35. Thereafter, the rotational speed of the motor 1 is controlled as described above, and the motor 1 continues to rotate at a low speed based on the H level time width TlO of the pulse signal 33. In this way, by adjusting the time constant of the retrigger monomulti 21, the time width TlO of the H level of the pulse signal 33 changes, so it is possible to change the rotational speed of the motor 1 very easily based on this. It is. Therefore, there is no need to provide a reference signal generation circuit or the like for determining the rotational speed of the motor 1, unlike the conventional control device of this type, and the circuit configuration of the entire control device can be simplified. As described above, the present invention provides a retriggerable circuit that is supplied with a frequency signal corresponding to the rotational speed of the motor, and a retriggerable circuit that is supplied with the output of this miter circuit.
A monostable multivibrator, an adjusting means for setting the rotational speed of the motor by varying the time constant of this retriggerable monostable multivibrator, and an adjustment means that sets the output signal of the retriggerable monostable multivibrator to its pulse width. A conversion circuit for converting the DC voltage into a corresponding DC voltage is provided, and the motor is controlled according to the output of the conversion circuit.
このように構成されたモータの制御装置によれば、リト
リガラブル●モノステイブル●マルチバイブレータの時
定数よりも、モータの回転速度に応じた周波数信号の周
期が小さい場合でも、モータを正常に制御することが出
来、従つてモータの回転速度を所定の回転速度よりも大
巾に変動することがないようになし得られる。上記時定
数を調整手段により可変することによつてモータの回転
速度を任意に設定することが出来るので、上記設定が極
めて容易で面倒な調整作業は不要であり、このために生
産コストを低減させることが可能てある。According to the motor control device configured in this way, the motor can be controlled normally even when the period of the frequency signal according to the rotational speed of the motor is smaller than the time constant of the retriggerable monostable multivibrator. Therefore, it is possible to prevent the rotational speed of the motor from fluctuating more than a predetermined rotational speed. By varying the above-mentioned time constant using an adjustment means, the rotational speed of the motor can be arbitrarily set, so the above-mentioned setting is extremely easy and there is no need for troublesome adjustment work, which reduces production costs. It is possible.
第１図及び第２図は従来のモータの制御装置の第１例を
示すものてあつて、第１図は回路構成を示すブ七ツクダ
イヤグラム、第２図は第１図に示す回路の各部の波形図
てある。1 and 2 show a first example of a conventional motor control device. FIG. 1 is a block diagram showing the circuit configuration, and FIG. 2 is a block diagram showing each part of the circuit shown in FIG. 1. The waveform diagram is shown.
Claims (1)
の周波数信号に応じて上記モータの回転速度を制御する
ようにしたモータの制御装置において、上記周波数信号
が供給されるリミッター回路と、このリミッター回路の
出力が供給されるリトリガラブル・モノステイブル・マ
ルチバイブレータと、このリトリガラブル・モノステイ
ブル・マルチバイブレータの時定数を可変することによ
りモータの回転速度を設定する調整手段と、上記リトリ
ガラブル・モノステイブル・マルチバイブレータの出力
信号をそのパルス巾に応じた直流電圧に変換する変換回
路とを設け、上記変換回路の出力に応じて上記モータを
制御するようにしたモータの制御装置。1. A motor control device that forms a frequency signal corresponding to the rotational speed of a motor and controls the rotational speed of the motor according to this frequency signal, comprising: a limiter circuit to which the frequency signal is supplied; a retriggerable monostable multivibrator to which the output of the circuit is supplied; an adjusting means for setting the rotational speed of the motor by varying the time constant of the retriggerable monostable multivibrator; A motor control device comprising: a conversion circuit that converts an output signal of a vibrator into a DC voltage according to a pulse width thereof, and controls the motor according to an output of the conversion circuit.
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP51149173A JPS6056394B2 (en) | 1976-12-10 | 1976-12-10 | Motor control device |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP51149173A JPS6056394B2 (en) | 1976-12-10 | 1976-12-10 | Motor control device |
Publications (2)
| Publication Number | Publication Date |
|---|---|
| JPS5373315A JPS5373315A (en) | 1978-06-29 |
| JPS6056394B2 true JPS6056394B2 (en) | 1985-12-10 |
Family
ID=15469386
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| JP51149173A Expired JPS6056394B2 (en) | 1976-12-10 | 1976-12-10 | Motor control device |
Country Status (1)
| Country | Link |
|---|---|
| JP (1) | JPS6056394B2 (en) |
Families Citing this family (118)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| JPS55167794U (en) * | 1979-05-18 | 1980-12-02 | ||
| JPS55155588A (en) * | 1979-05-18 | 1980-12-03 | Matsushita Electric Ind Co Ltd | Speed controller for motor |
| JPS59165975A (en) * | 1983-03-10 | 1984-09-19 | Fuji Xerox Co Ltd | Failure detector of encoder |
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| US11589865B2 (en) | 2018-03-28 | 2023-02-28 | Cilag Gmbh International | Methods for controlling a powered surgical stapler that has separate rotary closure and firing systems |
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| US11096688B2 (en) | 2018-03-28 | 2021-08-24 | Cilag Gmbh International | Rotary driven firing members with different anvil and channel engagement features |
| US11278280B2 (en) | 2018-03-28 | 2022-03-22 | Cilag Gmbh International | Surgical instrument comprising a jaw closure lockout |
| US11090047B2 (en) | 2018-03-28 | 2021-08-17 | Cilag Gmbh International | Surgical instrument comprising an adaptive control system |
| US11369377B2 (en) | 2019-02-19 | 2022-06-28 | Cilag Gmbh International | Surgical stapling assembly with cartridge based retainer configured to unlock a firing lockout |
| US11357503B2 (en) | 2019-02-19 | 2022-06-14 | Cilag Gmbh International | Staple cartridge retainers with frangible retention features and methods of using same |
| US11751872B2 (en) | 2019-02-19 | 2023-09-12 | Cilag Gmbh International | Insertable deactivator element for surgical stapler lockouts |
| US11331100B2 (en) | 2019-02-19 | 2022-05-17 | Cilag Gmbh International | Staple cartridge retainer system with authentication keys |
| US11317915B2 (en) | 2019-02-19 | 2022-05-03 | Cilag Gmbh International | Universal cartridge based key feature that unlocks multiple lockout arrangements in different surgical staplers |
| USD950728S1 (en) | 2019-06-25 | 2022-05-03 | Cilag Gmbh International | Surgical staple cartridge |
| USD952144S1 (en) | 2019-06-25 | 2022-05-17 | Cilag Gmbh International | Surgical staple cartridge retainer with firing system authentication key |
-
1976
- 1976-12-10 JP JP51149173A patent/JPS6056394B2/en not_active Expired
Also Published As
| Publication number | Publication date |
|---|---|
| JPS5373315A (en) | 1978-06-29 |
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