JPS6028471B2 - Ferro-resonant power supply for deflection and high voltage circuits - Google Patents

Description

DETAILED DESCRIPTION OF THE INVENTION The present invention relates to a high frequency iron-resonant power supply for a deflection/high voltage circuit.

In a deflection and high voltage power supply for a television receiver, the B+ supply voltage and the high voltage ultor acceleration potential for the deflection circuit are generally obtained in two different ways.

That is, the B+ voltage is derived from the AC mains and rectified flyback pulses, whereas the ultor acceleration potential is derived from the rectified flyback pulses obtained from the horizontal output transformer or Raffiback transformer. Such a configuration requires the use of two independent and expensive power supplies.
The high voltage can be regulated either directly by regulating the high voltage itself, or by regulating the B+ voltage, typically with a relatively complex electronic series switch or shunt regulator, but such circuits are relatively expensive and This often causes accidents that require the addition of a protection circuit to shut off the television receiver when the high voltage rises abnormally.

Many television receivers include circuitry that maintains a constant raster width even as the ulta beam current changes.

This is achieved by changing the B+ raster voltage so that the B+ raster voltage follows the fluctuation of the ultor voltage, and the raster width and therefore the screen size are kept constant even if the ultor voltage changes. Part of the modification involves connecting a series resistor to the primary winding of the flyback transformer, which senses changes in the beam current and changes the B+ pressure accordingly.
This is done by adding a regulator control circuit. The former method has the drawback that power is unnecessarily dissipated in its series resistance, while the latter method has the drawback of unavoidable follow-up circuit complexity and expense. 60Hz for some B+ voltage regulators
The regulated B1 voltage is obtained using a 60Hz AC mains voltage regulating transformer such as a ferro-resonant transformer, but due to the low frequency operation of 60Hz, it is necessary to use a relatively large and heavy transformer. be.

Additionally, the high voltage is independently provided by a relatively large flyback transformer designed to accommodate relatively high power. In other prior art television receiver voltage regulation circuits, high voltages are regulated by providing a flyback transformer which itself operates in a fero-resonant manner.

A flyback pulse is applied to the primary winding of this flyback transformer to tune the ultor voltage winding to the desired frequency. Since the B+ voltage is drawn from another power source such as an AC main line, it is necessary to provide an adjustment circuit if this B+ voltage also needs to be adjusted. Also, if the B+ voltage is not adjusted, other circuitry may be required to keep the raster width constant. In conventional flyback extraction type high voltage circuits, the peak voltage of the high voltage is often substantially lower than the required ultor potential in order to reduce the required turns of the high voltage winding, and then the peak voltage of the high voltage is substantially lower than the required ultor potential. The voltage is boosted to the required level.

Since the design of voltage multipliers often requires the use of both polarities of an alternating voltage, it is desirable that the multiplier be driven by an alternating voltage that has portions of both positive and negative polarities that are close in size. . If one polarity is smaller than the other, the capacitors and diodes acting in this polarity will provide very little voltage. This is the state when a flyback pulse is used as a power source for the voltage increase circuit. To make the voltage multiplier perform a three-fold increase when a flyback pulse with a low shock coefficient is applied to the voltage multiplier, 6
A sextupler using six diodes and six capacitors is required. According to a preferred embodiment of the invention, the ferro-resonant power supply for a deflection and high voltage circuit for a television receiver includes an alternating current voltage source.

A ferro-resonant transformer includes a magnetic core, a first winding coupled to its alternating current voltage source, and a high-voltage winding wound around the saturable portion of the core and coupled to high-voltage terminals to produce a high voltage. We are prepared. A second winding is wound around the saturable portion of the core and coupled to the scan power supply voltage terminal to generate the scan power supply voltage. winding the saturable portion of the core with sufficient capacitance to generate a circulating current that saturates the saturable portion of the core under the high voltage winding and the second winding during each cycle of the alternating voltage; Means are provided for providing at least one of the windings with a regulated high voltage and a regulated scanning supply voltage. A deflection switch is coupled to the deflection winding to generate a scan period and a retrace period for each deflection cycle. A scanning voltage source is also coupled to the deflection winding for generating a scanning current. By the first means, the regulated scanning power supply voltage is applied to the scanning voltage source and the ultor acceleration potential is supplied from the ultor terminal. High voltage means for generating this ultor acceleration potential from a regulated high voltage is coupled to the high voltage terminal and the ultor terminal. Next, embodiments of the present invention will be described with reference to the accompanying drawings.

For example, the AC mains voltage of 120V60HZ is connected to terminals 21 and 2.
2 to input terminals 23 and 24 of a full-wave bridge rectifier 25. A current limiting resistor 30 is provided between the terminals 21 and 23. A DC voltage of, for example, 1150 V is generated at the terminal 26, and is applied to a capacitor 27 provided between the terminals 26 and 28. Terminal 28 is a common ground current return terminal that is not isolated from the AC mains current. 1150
A resistor 29 is coupled to the V power supply terminal 26, and this resistor 29
The cathode of the Jenner diode 33 (terminal 32
) is formed with a low DC voltage power supply of, for example, 120V.
A high frequency square power oscillator 35 is provided which includes a sine wave oscillator 36, a push-pull square Illi stage 37 and a power output stage 38.

The sine wave oscillator 36 is a self-oscillating type, and its transistor 39
The collector electrode of is coupled to a resonant LC tank circuit 45 that includes a winding 41a of a coupling transformer 41 and a capacitor 40. The collector voltage of transistor 39 is derived from a twelve power source coupled through resistor 42 to tap terminal 48 of winding 41a. A bypass capacitor 4 is connected to the tap terminal 48.
3 are combined. Resistor 42 drops the 20V to 17V and capacitor 43 helps remove the IJ pull from the rectified 60Hz input voltage. To keep oscillator 36 in self-oscillation mode, AC feedback is provided by capacitor 44 coupled between the base electrode of transistor 49 and tank circuit 45.
DC bias to the base of transistor 39 is provided by voltage divider resistors 46, 47 coupled to resistor 42.
An oscillator 36 provided by generates a high frequency sinusoidal voltage on winding 41a.

The resonant frequency of the tank circuit 45 is selected, for example, in the vicinity of the horizontal deflection frequency 1/TH of 15.7 HZ. Horizontal female pulse 6 obtained from a practical horizontal flyback transformer 68
7 is applied to the synchronous input terminal 69 of the oscillator 36, and a retrace pulse is AC coupled from this terminal 69 to the emitter of the transistor 39 via the capacitor 70 and the resistor 71 of the voltage dividing resistors 71, 72. . Female wire pulse 67 shuts off transistor 39 during horizontal retrace to synchronize the frequency of oscillator 36 to the horizontal deflection frequency. Winding 41 of oscillator 36
The high frequency sinusoidal voltage formed at a is applied to the winding 4 of the transformer 41.
1b is applied to the bases of push transistors 49 and 50 via low resistors 51 and 52, respectively.

The center tap of the winding 41b is rounded. Square wave stage 37 converts the sinusoidal voltage generated by oscillator 36 into a square wave voltage of the same frequency. This square wave voltage is more suitable for driving power output stage 38 than a sine wave. Square stage 37
The high frequency square wave voltage generated by is passed from winding 53a of coupling transformer 53 to push-pull power transistors 54, 5 via its winding 53b and resistors 56, 67, respectively.
Applied to the base of 5. A parallel circuit of a resistor 58 and a capacitor 59 is inserted between the center tap of the winding 53b and the common connection point of each emitter of the transistors 54 and 55. The resistor 58 and capacitor 56 act to apply a negative bias voltage to the base of the power transistor. A diode 60 is coupled in parallel with the collector-emitter circuit of the transistor 54 with its cathode on the collector side, and similarly, a diode 61 is coupled in parallel with the collector-emitter circuit of the transistor 55 with its cathode on the collector side. There is.

These diodes 60, 61 serve to limit the peak values of undesirable impulse voltages that could destroy these transistors. Power output stage 38 has an output terminal 62 coupled to each collector electrode of transistors 54 and 55.
, 63 generate a high frequency AC square wave voltage 64.

This voltage 64 serves as an unregulated energy filter or excitation voltage for a high frequency ferro-resonant transformer 65. The input winding of the transformer 62, ie, the primary winding 65a, is coupled between the output terminals 62 and 63 of the power output stage 38, and the wire of the terminal 26 is coupled to the center tap 66 of the primary winding 65a. Adjusted DC+
The power supply voltage of the power output stage 38 is obtained from 150V. The high-frequency iron-resonant transformer 65 includes a primary winding 65a, a low-voltage secondary winding 65b, a high-voltage secondary winding 65c, and a magnetic core 165.

As shown in FIG.
It consists of 5a and 165b. Core portion 165a is formed as a C-shaped section, and core portion 165b is formed as a relatively thin rectangular plate of magnetic material having a relatively high surface area to volume ratio. As shown in FIG. 2, the primary winding 65a is wound around the center of the C-shaped magnetic core portion 165a, and
The secondary winding 65b is wound around the plate-like central portion 166b, and the high voltage secondary winding 65c is coaxially wound around the low voltage secondary winding 65b.

The secondary windings 65b and 65c are cylindrical coil bobbins 265.
b, 265c, or other suitable winding configurations may be used, such as winding the high voltage winding 65c directly on the low voltage winding 65b.

It is also possible to use split pi-type windings for the low voltage winding and the high voltage winding, and furthermore, as shown in FIG.
5 can also be constructed by having one leg 765a, 865a have a cross-sectional area of J*, and the two legs of two C-shaped magnetic cores 765, 865 are brought into contact with each other at their end faces. Although the low voltage winding 65b and the high voltage winding 65c are not shown in FIG. 4, they are wound coaxially with the legs 765a and 865a as shown in FIG. Wrap it around your legs as shown in Figure 2. As shown in FIG. 1, one end of low voltage secondary winding 65b is coupled to terminal 101 and one tap conductor is coupled to ground current return reference terminal 102.

Terminal 102 is electrically isolated from the AC mains power supply. This terminal 102 can also be at ground potential. Low voltage secondary winding 65b is coupled to scan power supply voltage terminal 301 via half wave rectifier 401. The high-frequency AC voltage formed between the terminals 101 and 102 by the low voltage winding 65M is half-wave rectified by the rectifier 401, and the capacitor 5
Reverberated by 01. A DC B+scanning power supply voltage of, for example, 1120 V is generated at the scanning power supply voltage terminal 301. Another tap conductor is drawn out from the low voltage secondary winding 65b,
terminal 3 via rectifiers 403, 404, 405, respectively.
03, 304, and 305 to generate low DC voltages of +30V, +72V, and +210V at these terminals, respectively. Rectifier (diode) 403, 404, 40
Furnace wave capacitors 503 and 504 are connected to each cathode of 5.
, 506 are combined. Horizontal deflection circuit 73 includes a conventional oscillation drive circuit 74, a deflection scan capacitor 79 including a damper diode 77 and a horizontal output transistor 78, and a series coupled horizontal deflection winding 80 and scan capacitor 81.

The voltage yt across the scanning capacitor 81 serves as the scanning power supply voltage for the horizontal deflection winding 80. During each horizontal scan period, the scan switch 76 conducts and transfers the scan voltage Vt to the horizontal deflection winding 8.
01 is applied to generate the required horizontal sawtooth scanning current in this winding. Scan capacitor 81 is coupled to B+ scan power supply voltage profile 301 via primary transformer 68a of flyback transformer 68 to obtain scan voltage yt.

Therefore, the average value, that is, the DC value of the scanning voltage Vt is substantially equal to B+scanning power supply voltage 1120 V'. During the horizontal retrace period, the scan switch 76 is cut off and the horizontal deflection winding 8
0 and horizontal female wire capacitor 79 resonate for half a cycle of oscillation.

The horizontal pulse generated in the primary winding 68a of the practical flyback transformer 68 is generated in the flyback secondary windings 68b, 68.
terminals 82 and 83 of the secondary winding 68b.
A retrace pulse is supplied to circuits such as an eraser circuit and a horizontal synchronization circuit. The secondary winding 68c is a high frequency square wave power oscillator 3
5 serves as a signal source for the retrace pulse 67 used to synchronize the oscillator 36 of 5.

In the power supply circuit of a normal television receiver, the ultor acceleration potential is often extracted from the rectified retrace pulse, but in the circuit shown in Figure 1, the ultor voltage is generated by the high voltage secondary winding 65c. It is a high frequency AC high voltage generated by. This alternating voltage generated between terminals 106 and lo7 is connected to three diodes 85, 86, 87 and three capacitors 88.
, 89 and 90, the voltage is rectified and multiplied. The cathode of diode 87 is coupled to ultor terminal U;
A DC ultor acceleration potential of, for example, 127 KV is formed at this terminal. The intermediate high DC voltage developed at the cathode of diode 85 can also serve as a collector voltage for the collector electrode of a cathode ray tube of a television receiver. Ferro-resonant transformer 6
5 generates a high voltage in its high voltage winding 65c and a low voltage in its low voltage winding 65b, so that the Alter accelerating potential and the B scan can be adjusted without the need for a relatively complex and failure-prone electronic adjustment circuit. Both the power supply voltage and the power supply voltage are adjusted.

In order to adjust the voltage of the secondary windings 65b, 65c, a resonant capacitor is connected to the terminal 101 of the low voltage secondary winding 65b or to the winding wound around the other thin plate-shaped magnetic core portion 165b, as shown in FIG. 91 can also be combined.

The value of this capacitor 91 is this and the low voltage secondary winding 65b.
and the vicinity of its excitation power supply frequency, that is, high frequency AC voltage 6
4 so that it resonates near the frequency 15.7 HZ. Under certain conditions as described below, capacitor 91
It is also possible to omit this to reduce the cost. For example, if the high voltage secondary winding has sufficient winding capacitance, no additional capacitors are needed.

The circulating resonant current flowing in winding 65b and capacitor 91 helps magnetically saturate the core portions under low voltage winding 65b and high voltage winding 65c during a half cycle of circulating current oscillation.

By saturating the magnetic core in this manner, the voltages induced in the two windings 65b and 65c are adjusted. As shown in FIG. 5a, the voltage V6 appearing at the primary winding 65a of the high frequency iron resonant transformer 65 has a period of TH=6
It is a symmetrical square wave voltage with a frequency of 15.7Hz with a duration of 3.5 seconds.

The high voltage appearing at the secondary winding 65c is also a voltage V65c that is close to a relatively symmetrical square wave, as shown in FIG. 5b.

The square wave generated between the terminals 101 and 102 by the low voltage winding 65b is transmitted through the rectifier 40 as shown in FIG. 5c.
It has a flat portion at the top that occurs during conduction of I. As shown in FIG. 5d, the input current i65a of the secondary winding 65a (from the diagram 26) corresponds to a portion near the switching moment of the transistors 54 and 55 near the front and rear ends of the waveform V653 in FIG. 5a. except that the current is relatively constant.

Low voltage winding 65 between terminals 101 and 102 shown in Figure 5e
b and the resonant current or circulating current ic flowing through the capacitor 91, the high voltage secondary winding 65c and the low voltage secondary winding 65
b helps to magnetically saturate the magnetic core portion 165b below.

This saturation occurs near the peak portions 94, 95 of the circulating current waveform ic. In order to keep the central portion 165a below the primary winding 65a unsaturated and to saturate the central portion 165b, the cross-sectional area of the plate member 165b in FIG.
It is 4 cm smaller than the cross-sectional area of 5a.

As shown in FIG. 3 as a cross-sectional view taken along line 3-3 in FIG. 165a cross section type A=w
・It is much smaller than f, that is, the product of the two sides w and f. The values in the table below give an a/A ratio equal to approximately 0.19. After energization of the circuit of FIG. 1, it is desirable to limit the temperature rise in the saturated core portion 165b under the low voltage secondary winding 65b and the high voltage secondary winding 65c.

The saturation magnetic flux density Bsa of the magnetic core material decreases as the temperature rises, but in the iron-resonant transformer, the voltage generated in the secondary winding 65b is a function of the B skin, so there is a large difference between the secondary winding and the magnetic core body. It is desirable to limit temperature rise by providing cooling capacity. This temperature increase can be caused by increased iron loss in high frequency operation and relatively large PR losses due to relatively large high frequency saturation circulating currents and the like. As shown in FIGS. 2 and 3, the magnetic core portion 165b consists of a thin plate-like member having a thickness t, a width w, and a length 1, and according to typical values shown in the table below, the surface area of the core portion 165b is The volume ratio has a relatively large value, for example 4:1, which facilitates cooling of the sheet.

Furthermore, the inner diameter 〇 of the cylindrical coil bobbin 265b is larger than the thickness t of the plate-like member 165b, so a relatively large gap is created between the coil bobbin 265b and the magnetic core, and the windings 65b and 65c are loosely attached to the central portion 165b of the plate-like member. It can be rolled.

Convective cooling of the magnetic core is therefore promoted. A magnetic core with such a configuration is 197g as disclosed in US Patent No. 00781 dated January 30th.
It is described in Specification No. 4. If the temperature rise of the core is relatively not a problem, a normal magnetic core shape such as a square or circular cross section is used for the core D portion 165b, and the winding 6 is attached to this.
5b and 65c can also be wound more tightly.

As shown in FIG. 5b, the high voltage V6 heat generated in the high voltage winding 65c is a relatively symmetrical square wave with a positive portion 9
The magnitude of 2 is approximately equal to the magnitude of the negative portion 93.

If the peak-to-peak voltage amplitude of this V voltage is, for example, 1 ship V, the first
The high voltage multiplier circuit 84 shown requires only three rectifiers and a few capacitors. Diode 85, 87
rectifies the positive portion of V65c, and diode 86 rectifies the negative portion. Therefore, the ultor voltage V is approximately equal to twice the positive amplitude of the storm plus the negative amplitude. Capacitor 90 may be omitted if the conductive coating of the picture tube provides sufficient furnace wave capacitance. In the case of a normal high-voltage power supply that rectifies a positive retrace pulse of the same magnitude as the positive part in Figure 5b, the multiplier requires 5 to 6 diodes and their accessories to obtain the same ultor voltage. Requires capacitor. The above-described high-frequency iron-resonant transformer scheme for implementing the invention has a regulated scanning power supply voltage and thus a regulated scanning voltage V
t and also provides a regulated high voltage.
Such a configuration considerably eases the design conditions for the horizontal deflection circuit 73. For example, flyback transformer 6
8, since only a relatively small load current flows through this transformer since it is no longer necessary to transfer load energy to the transformer, the size of this transformer can be reduced considerably.
Furthermore, since the direct current flowing through the horizontal output transistor 78 is reduced, the dimensions, current rating, voltage rating, and heat dissipation conditions of this transistor can be reduced.
Appropriate changes in the circuit design allow for the use of a low impedance deflection winding 80, which allows for example 200V to be used instead of the relatively high horizontal retrace pulse of, for example 1,000V, which is commonly used. A much lower voltage peak would be sufficient. This high frequency iron-resonant transformer 65 supplies the B-scan power supply voltage as well as the ulta high voltage.
According to the invention, relatively good screen width stability is obtained without the use of pin-like control circuits or individual series resistors.

As the peak loading of the ultor terminal U increases, the ultor acceleration potential decreases. The rise in the DC portion of the load current flowing through high voltage winding 65c slightly demagnetizes core portion 165b, shifting the operating point of that core portion from a greater saturation point to a bending point in the transformer's B-day hysteresis loop. By moving it slightly in the opposite direction, it has the effect of lowering the high voltage by a small amount. However, since the low-voltage winding 65b and the high-voltage winding 65c share a common saturated magnetic core, as the load current flowing through the winding 65c increases, the B+ scan voltage also decreases, resulting in a substantial increase in the raster width. adjustments will be made. As another explanation, the leakage inductance present in transformer 65 causes an increase in voltage drop with increased image beam loading, causing both the high voltage and the B+ voltage to drop.

The raster width is adjusted by adjusting the leakage inductance between the high voltage secondary winding 65c and the low voltage secondary winding 65b, and the degree and position of saturation of the magnetic core. A relatively large number of windings are required to generate a relatively high voltage in the high voltage secondary winding 65c.

By appropriate selection of factors such as winding configuration, interlayer separation, conductor dimensions, etc., the stray capacitance or distributed capacitance between the windings can be reduced by the resonance of the high voltage winding 65c and the magnetic core portion 1.
65b and can be large enough to be able to adjust the voltages of the high and low voltage secondary windings. Although such distributed resonant capacitance is represented in FIG. 1 by capacitor 665 coupled in parallel to high voltage winding 65c, in reality the entire capacitance is distributed along the turns of the winding. Distributed capacitance 665 and high voltage winding 65c providing circulating current to saturate core portion 165b eliminates capacitor 91 and eliminates aging or failure of individual components that could cause high voltage build-up.

Furthermore, changes in the capacitance value of the winding inductance or resonant capacitance generally result in losses in the ferro-resonant operation and a drop in the winding voltage, so the use of ferro-resonant transformers for the supply of high voltages provides inherent high-voltage protection. ability is obtained. The ferro-resonant transformer 65, which supplies both the high voltage and the B-scan power supply voltage, allows a relatively large increase in temperature to occur after circuit start-up without substantially affecting the raster width.

Furthermore, since the high voltage secondary winding 65c and the low voltage winding 65b are wound around the common magnetic part 165b, both the ultor voltage and the B+ voltage are , which results in a significant raster width adjustment. Typical values of the high frequency iron resonant transformer 65 using a distributed capacitance 665 associated with the high voltage winding 65c as shown in FIGS. 1 to 3 are listed below.

Magnetic core 165 C-shaped central portion 165a Sectional mirror 2.32 Length of outer leg 5.1 Length of central portion 7.1 Plate-shaped magnetic core portion 165b Thickness t 2.79 Snout width w
15.5 skin length 1
7.1 Cross-sectional area 43.2 Fence material: ferrite, 25qo, B side is approximately 4000 gauss, for example, Ferroxkeuf Co., Ltd.
rp. )'s Femoxcuup (Femoxcu is)
Group 2A type or RCA Corp. RCA54 top type primary winding 6
5a30/40 Lio nylon coated insulated enamelled copper wire, 4 layer winding, center tapped, 2 windings, total number of turns 200 times, no insulation layer between winding layers, winding length 3.94 feet .

Low voltage winding 65b Cylindrical coil bobbin 265b Inner diameter ○ 18.2 Rib outer diameter 21.6 Side length 42.55 Rib winding 65b
25'28 Lit Nylon coated insulated enamelled steel wire, 2 turns, 4 layers of approximately 48 turns per layer, total number of turns 190 turns.

Approximately from the 5th layer of 4 turns 6.3V 9 dish hA picture tube filament Take out the voltage.

Winding length 42.55 side high voltage winding 6
5c Cylindrical coil bobbin 265c Inner diameter 29.21 Rib thickness 1.52 Skin length
26.67 Rib winding 65c Enamelled copper wire with 3 wood flea (0.1007 ribs), 32 layer windings, 147 turns in the first 31 layers, 43 turns in the last layer, 0.000 in thickness between each layer. 05~1.10 Insulated with lylar film,
The total number of turns is 4,600 times, and the length of the turns is 19 o.

[Brief explanation of the drawing]

FIG. 1 is an electric circuit diagram of a high-frequency iron-resonant power supply for a deflection and high-voltage circuit embodying the present invention, and FIG. 2 is a diagram showing the magnetic core and winding structure of a high-frequency iron-resonant transformer used in the circuit of FIG. , FIG. 3 is a cross-sectional view of the transformer along line 3--3 in FIG.
Figure 4 is a diagram showing another magnetic core mechanism of the transformer in Figure 2;
The figure is a diagram showing waveforms related to the circuit of FIG. 1. 37, 38... AC voltage source, 65...
Ferro-resonant transformer, 65a... First winding of transformer 65, 65b... Second winding of transformer 65, 6
5c... High voltage winding of transformer 65, 68...
...Horizontal flyback transformer, 68a... Winding of transformer 68, 78... Deflection switch (transistor), 80... Deflection winding, 81... Scanning voltage source (capacitor), 84... High voltage means,
91... Capacitor, 106... High voltage terminal, 165... Magnetic core of transformer 65, 165
b... Part of the magnetic core 165, 301...
- Scanning power supply voltage terminal, 665...Distributed capacitance, U.・・・． ...Alternative terminal. Figure 2 Figure 3 Figure 4 Figure Ship Figure 5

Claims (1)

[Claims] 1 an alternating current voltage source, a ferro-resonant transformer, a deflection winding, an eccentric switch coupled to the deflection winding to generate a scan period and a retrace period for each deflection cycle, and an eccentric switch coupled to the deflection winding; a scanning voltage source for supplying a scanning current to the deflection winding, a first means for applying a regulated scanning power supply voltage to the scanning voltage source, an ultor terminal for generating an ultor acceleration potential, and a high voltage terminal. and high voltage means coupled to the ultor terminal for generating an ultor accelerating potential from the regulated high voltage, the ferro-resonant transformer comprising a magnetic core and a first winding coupled to the alternating current voltage source. a high voltage winding wound around the saturable portion of the magnetic core and coupled to the high voltage terminal to generate a high voltage; and a high voltage winding wound around the saturable portion of the magnetic core and coupled to the scanning power supply voltage terminal. a second winding that generates a scanning power supply voltage; and at least one of the windings wound around the saturable portion of the magnetic core. means for providing sufficient capacitance to saturate the saturable portion of the core under winding 2 to generate a circulating current for producing the regulated high voltage and the regulated scanning supply voltage; Ferro-resonant power supply for deflection and high voltage circuits of television receivers including.