JPS6025306A - Oscillator - Google Patents

Oscillator

Info

Publication number
JPS6025306A
JPS6025306A JP13396183A JP13396183A JPS6025306A JP S6025306 A JPS6025306 A JP S6025306A JP 13396183 A JP13396183 A JP 13396183A JP 13396183 A JP13396183 A JP 13396183A JP S6025306 A JPS6025306 A JP S6025306A
Authority
JP
Japan
Prior art keywords
transistor
circuit
differential amplifier
emitter
output
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Pending
Application number
JP13396183A
Other languages
Japanese (ja)
Inventor
Hironori Murakami
弘規 村上
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Panasonic Holdings Corp
Original Assignee
Matsushita Electric Industrial Co Ltd
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Matsushita Electric Industrial Co Ltd filed Critical Matsushita Electric Industrial Co Ltd
Priority to JP13396183A priority Critical patent/JPS6025306A/en
Publication of JPS6025306A publication Critical patent/JPS6025306A/en
Pending legal-status Critical Current

Links

Classifications

    • HELECTRICITY
    • H03ELECTRONIC CIRCUITRY
    • H03BGENERATION OF OSCILLATIONS, DIRECTLY OR BY FREQUENCY-CHANGING, BY CIRCUITS EMPLOYING ACTIVE ELEMENTS WHICH OPERATE IN A NON-SWITCHING MANNER; GENERATION OF NOISE BY SUCH CIRCUITS
    • H03B5/00Generation of oscillations using amplifier with regenerative feedback from output to input
    • H03B5/30Generation of oscillations using amplifier with regenerative feedback from output to input with frequency-determining element being electromechanical resonator
    • H03B5/32Generation of oscillations using amplifier with regenerative feedback from output to input with frequency-determining element being electromechanical resonator being a piezoelectric resonator
    • H03B5/36Generation of oscillations using amplifier with regenerative feedback from output to input with frequency-determining element being electromechanical resonator being a piezoelectric resonator active element in amplifier being semiconductor device

Abstract

PURPOSE:To prevent amplitude shift of each oscillating output by providing a compensating circuit against variation in hFE to an oscillating circuit where plural outputs of different phase shift are extracted by using a resonance circuit, a phase shift circuit and a differential amplifier circuit. CONSTITUTION:The oscillating circuit is constituted by the resonance circuit 1, the phase shift circuit 2 and the differential amplifier circuit 3. The phase shift circuit 2 shifts the phase of an output signal from the resonance circuit 1, gives an oscillated output having different phase to transistors (TR) 16, 17 of the 1st differential amplifier circuit and TRs 23, 24 of the 2nd differential amplifier circuit via the 1st-3rd emitter followers 12, 19 and 26 and extracts an oscillated output having different phase from output terminals 4-7. The 3rd differential amplifier circuit consisting of the 5th and 6th TRs 35, 36 are operated so as to make the emitter current of the 1st-3rd emitter followers 12, 19 and 26 equal, then a DC voltage of each output terminal of the 1st and 2nd differential amplifier circuit is made relatively equal even if the hFE of the TRs 16, 17, 23 and 24 is fluctuated and the amplitude of oscillated outputs 4-7 is made equal.

Description

【発明の詳細な説明】 産業上の利用分野 本発明は集積回路化に適した発振装置に関する。[Detailed description of the invention] Industrial applications The present invention relates to an oscillation device suitable for integration into an integrated circuit.

従来例の構成とその問題点 近年、回路の集積回路化が進んでいく中で当然のことな
がら、この集積回路化に適した発振装ばかめられている
。第1図は従来の発振装置の基本ブロック図で、共振回
路(1)の発振出力は移相同* (2)と差動増幅回路
(3)に加えられる。差動増幅回路(3)では共振回路
(1)の発振出力と移相回路(2)の出力を入力々して
出力端子(4) (5) (6) (7)に異なる位相
の発振出力を得る。この発振出力は共振回路(1)に帰
産される。第2図はL記移相回路(2)と差動増幅回路
(3)の具体的回路例を示す。ここで、(8)は電源端
子、(9ンは直流バイアスが与えられる入力端子、00
QOすUηQ罎(イ)(ハ)(4)はNPN )ラシジ
スタ、Uυu4Q脣μQ四しV(4)(イ)(7)(4
)…は抵抗、明(4)は定電流源、のりはコンデンサ、
(2)は+jIJ記共振回路(1)の出力端子からの発
振出力か加わる入力端子である。入力端子6))に共振
回路(υから45°の位相の発振出力電圧が加えられる
と、この発振出力Vlf圧は抵抗(2)と工三ツタフオ
Dアを構成するトランジスタ@を介してトランジスタ(
至)のベースに加えられる。また、移相回路(2)の抵
抗(7)、コンデンサCυのそれぞれの値をIZ、C。
Conventional Structures and Their Problems In recent years, as circuits have become more integrated, as a matter of course, oscillation devices suitable for integrated circuits have been attracting attention. FIG. 1 is a basic block diagram of a conventional oscillation device, in which the oscillation output of a resonant circuit (1) is applied to a phase-shifted phase shift* (2) and a differential amplifier circuit (3). The differential amplifier circuit (3) inputs the oscillation output of the resonant circuit (1) and the output of the phase shift circuit (2), and outputs oscillation outputs with different phases to the output terminals (4), (5), (6), and (7). get. This oscillation output is returned to the resonant circuit (1). FIG. 2 shows a specific circuit example of the L phase shift circuit (2) and the differential amplifier circuit (3). Here, (8) is a power supply terminal, (9) is an input terminal to which DC bias is applied, and 00
QOsu UηQ (a) (c) (4) is NPN)
)... is a resistor, light (4) is a constant current source, glue is a capacitor,
(2) is an input terminal to which the oscillation output from the output terminal of +jIJ resonant circuit (1) is applied. When an oscillation output voltage with a phase of 45° from υ is applied to the resonant circuit (input terminal 6)), this oscillation output Vlf voltage is applied to the transistor (
(to) is added to the base of Also, the respective values of the resistor (7) and capacitor Cυ of the phase shift circuit (2) are IZ and C.

発振出力電圧の角周波数をωとし、RとCを−45゜1 =tan (ω・R−C)を満足するように選ぶと、発
振出力電圧は1三ツタフォロアを形成するトランジスタ
tJ、Iを介して位相0°の発振出力電圧がトランジス
タαηに)のベースに加えられる。その振幅Vけ、発振
出力電圧の振幅をViとするとgfI記の条件よりω・
C−R=1 、ヨッテ、V=ViX(1/mc)/ R
”+(1/a+c)”=Vi/iである。従って、トラ
ンジスタ(ト)弼、定電流源(至)、負荷の抵抗(財)
に)で形成される差動増幅器の出力端子(6) (7)
にはそれぞれ+90°、−90°の位相の発振出力が得
られるoトランジスタIJHη、定電流源θ均、負荷抵
抗QΦOQで形成される差動増幅器の出力端子(4)(
5)にはそれぞれ0°、180°の位相をもつ発振出力
が得られる。すべてのトランジスタのhFg (電流増
幅率)が等しいものとし、抵抗0))C;fJw(至)
の抵抗値をそれぞれ、R11+R28,R29,R80
とすると、抵抗Oυ(ト)(至)にはそれぞれトランジ
スタu4(至)四のベース電流が、抵抗(ハ)Kはトラ
ンジスタ(11とトランジスタ(イ)の2つのベース電
流の相か流れていることから、R1x=2Rgs+Rg
i+*Rg9=Rsoの関係式を満足するようにすると
、トランジスタ四すI(イ)のベースには入力端子(9
)からトランジスタQlを介して等しい直流バイアス車
圧がかかる。ここで、抵抗μ5CIQv)のそれぞれの
抵抗値ならびに定電流源(1119と(2)の電流値か
等しい場合、トランジスタ@(イ)はそれぞれトランジ
スタaiCAにベース電流を供給しているが、トランジ
スタQすはトランジスタαη−の2つにベース電流を供
給しており、トランジスタ@−に比ベトランジスタQ値
のエミッタ電流が大きく、これに伴いベース・工三ツタ
聞電圧(以” VBFtと称す)も大きくなる。トラン
ジスタ(6)り呻(イ)のベースは等しくバイアスされ
ているので、このvBEの差がトランジスタ07)tn
のベース電位をトランジスタ韓■のベース′電位より低
くし、出力端子の直流電圧の差として出る。
If the angular frequency of the oscillation output voltage is ω, and R and C are selected to satisfy -45°1 = tan (ω・R−C), then the oscillation output voltage will be the same as the angular frequency of the transistors tJ and I forming the 1-triangle follower. An oscillating output voltage with a phase of 0° is applied to the base of the transistor αη). If the amplitude is V, and the amplitude of the oscillation output voltage is Vi, then from the conditions in gfI, ω・
C-R=1, Yotte, V=ViX(1/mc)/R
“+(1/a+c)”=Vi/i. Therefore, the transistor (g), the constant current source (t), and the load resistance (t)
output terminals (6) (7) of the differential amplifier formed by
are the output terminals (4) of a differential amplifier formed by an o transistor IJHη, a constant current source θ, and a load resistor QΦOQ, which provide oscillation outputs with phases of +90° and −90°, respectively.
5), oscillation outputs with phases of 0° and 180° are obtained, respectively. Assume that hFg (current amplification factor) of all transistors is equal, resistance 0))C; fJw (to)
The resistance values of R11+R28, R29, R80 respectively
Then, the base current of transistor U4 (to) flows through the resistors Oυ(G) and (to), and the base current of the two transistors (11 and A) flows through the resistors (C) and K, respectively. Therefore, R1x=2Rgs+Rg
If the relational expression i+*Rg9=Rso is satisfied, the input terminal (9
) is applied an equal DC bias vehicle pressure via transistor Ql. Here, if the resistance values of the resistors μ5CIQv) and the current values of the constant current sources (1119 and (2) are equal), the transistors @(A) each supply base current to the transistor aiCA, but the transistor Q supplies the base current to two transistors αη−, and the emitter current of the Q value of the transistor is larger than that of the transistor @−, and accordingly, the base-to-power voltage (hereinafter referred to as “VBFt”) is also large. Since the bases of transistors (6) and (a) are equally biased, this difference in vBE is the difference between transistors (07) and tn.
The base potential of the transistor K is lower than the base potential of the transistor K, and it appears as a difference in the DC voltage at the output terminal.

第3図は、第2図の各出力端子(4) (5) (6)
 (7)と直流′車圧との関係を示したグラフであり、
横軸は各出力端子番号、縦軸は直流電圧である。同図の
a、b、CはそれぞれhFllcが小、中、大の場合を
示しており、特にhFKが小の場合、すなわち特性aで
は出力端子間の直流電圧の差が大きくなっている。これ
は発振出力の位相ずれ振幅の差となってくるという問題
点を有していた。
Figure 3 shows each output terminal (4) (5) (6) in Figure 2.
It is a graph showing the relationship between (7) and DC' vehicle pressure,
The horizontal axis represents each output terminal number, and the vertical axis represents DC voltage. In the same figure, a, b, and C show cases where hFllc is small, medium, and large, respectively. In particular, when hFK is small, that is, in characteristic a, the difference in DC voltage between the output terminals is large. This has the problem that it results in a difference in phase shift amplitude of the oscillation output.

発明の目的 本発明はhFKの変!WJに対しての出力端子間の直流
電圧の差が小さく、発振出力の位相ずれ、振幅の差の小
さい、hF):の変動に対して安定な発振装置を提供す
ることを目的とする。
Purpose of the Invention The present invention is based on the modification of hFK! It is an object of the present invention to provide an oscillation device in which the difference in DC voltage between output terminals with respect to WJ is small, the phase shift of the oscillation output, and the difference in amplitude are small, and which is stable against fluctuations in hF):.

発明の構成 本発明の発振装置は、第1の差動増幅器を形成する第1
.第2のトランジスタと、第2の差動増幅器を形成する
第3.第4のトランジスタと、第3の差動増幅器を形成
する第5.第6のトランジスタと、共振回路とを設け、
かつ自fI記第1のトランジスタのベースに直流電圧源
より第1の抵抗を介して駆動される第1の1三ツタフオ
0アを接続し、前記共振回路を前記直流電圧源に第2の
抵抗?介して接続し、11J記第2.第3のトランジス
タのベースに前記共振回路より第3の抵抗を介して1枢
!Iのされる′!i’、 2の1三ツタフォロアを接続
し、前記第4のトランジスタのベースに前記共振回路よ
り第4の抵抗を介して駆1明される第3の工三ツタフ1
oアを接続し、第5のトランジスタのベースを+jfJ
記第1のトランジスタのベースに接続し、第6の1〜ラ
ンジスタのベースをiff記第4のトランジスタのベー
スに接続すると共に、1ift記第1.第2、第3のエ
ミッタフォロアの1三ツタ電流が等しくなるよう構成し
てhおの変動に対しても安定な!iの作を犬現したこと
を特徴さする。
Structure of the Invention The oscillation device of the present invention includes a first differential amplifier forming a first differential amplifier.
.. a second transistor, and a third transistor forming a second differential amplifier. a fourth transistor, and a fifth transistor forming a third differential amplifier. a sixth transistor and a resonant circuit are provided;
and a first transistor driven by a DC voltage source via a first resistor is connected to the base of the first transistor, and the resonant circuit is connected to the DC voltage source through a second resistor. ? 11J No. 2. 1 point from the resonant circuit to the base of the third transistor via the third resistor! I'll be done'! i', 2 is connected to a third transistor follower, and a third transistor is driven from the resonant circuit through a fourth resistor to the base of the fourth transistor.
Connect oa and connect the base of the fifth transistor to +jfJ
1 is connected to the base of the first transistor; The second and third emitter followers are configured so that their currents are equal, making it stable even against fluctuations. It is characterized by the fact that it is a version of the work of i.

実施例の説1夕] 第4図は木発+31の一実施例における発振装置の差励
増I面回路の回路図で、鵠2図の従来例の回路にトラン
ジスタ(至)砂9轡、了電流源(功、抵抗に)に)。
Embodiment 1] Fig. 4 is a circuit diagram of the differentially pumped I-plane circuit of the oscillator in an embodiment of the Kihatsu +31. end current source (to the resistor).

コンデンサ0」)□ならびに水晶訣動子四を付は加えた
ものである。なお、共振回路(1ンは抵抗−と]ンヂン
サいυ(財)および水晶振動子(6)とから構成されて
(2) おり、移相回路、は抵抗(至)とコンデンサOυとで構
成法に第4図の構成を動作と共に詳しく説明する。
Capacitor 0") □ and crystal trigger 4 are added. The resonant circuit (1 is a resistor) is composed of a capacitor (2) and a crystal oscillator (6), and the phase shift circuit (2) is composed of a resistor (1) and a capacitor (0). The structure shown in FIG. 4 will be explained in detail along with its operation.

入力端子c3)に45°の位相をもつ発振出力を加える
An oscillation output having a phase of 45° is applied to the input terminal c3).

この発振出力電圧は抵抗に)、エミッタフォロアを構成
するトランジスタ(イ)を介して1−ランジスタ弼のベ
ースに加えられる。移相回路(2)の抵抗艶、コンデン
サOJ)のそれぞれの値は従来と同様に選ばれているた
め、発振出力電圧はエミッタフォロアを形成するトラン
ジスタ四を介して位相O0の発振出力がトランジスタ割
脅のベースに加えられる。その振幅Vけ発振出力電圧の
振幅Viとすると、前記条件よりV=Vi/ J 2で
ある。よって、トランジスタに)■、定電流源に)、負
荷抵抗G!])に)で形成される差動増幅器の出力端子
(6) (7)には、+90°、−90°の位相を持つ
発振出力が得られる。トランジスタueui、定屯流源
(ト)、負荷抵抗01は形成される差動増幅器の出力端
子(4戸5)には、θ°、180uの位相をもつ発振出
力が得られる。すべてのトランジスタの1171が等し
いものとし、抵抗σI−一の抵抗値を従来例と同様に選
ぶと、トランジスタ0か烏竣のベースには入力端子(9
)からトランジスタ0(夛を介して等しい直流バイアス
重圧がかかる。従来例ではトランジスタ(11がトラン
ジスタ(Iηと@の2つ分のベース電流を供給している
のに対し、トランジスタ@(ホ)はそれぞれトランジス
タ(1ゆ(財)の1つ分のベース電流を供給していたか
、第4図ではトランジスタに)(至)および定電流源1
1段等しい電流値を持つ定電流源(ロ)を加えることに
より、トランジスタ@(ハ)もトランジスタ01と同様
にそれぞれトランジスタ(11(至)、トランジスター
に)の2つ分のベース電流を供給することになり、抵抗
Q1す1@の抵抗値は等しいことからトランジスタ@財
争い金のエミッタ電流は等しい。
This oscillation output voltage is applied to the base of the transistor (1) via the resistor (a) and the transistor (a) that constitutes the emitter follower. Since the respective values of the resistor and capacitor OJ of the phase shift circuit (2) are selected in the same way as before, the oscillation output voltage is determined by the oscillation output of phase O0 being divided by the transistor 4 through transistor 4 forming an emitter follower. Added to the threat base. If the amplitude V is equal to the amplitude Vi of the oscillation output voltage, then from the above condition, V=Vi/J2. Therefore, for the transistor)■, for the constant current source), and the load resistance G! Oscillation outputs having phases of +90° and -90° are obtained at the output terminals (6) and (7) of the differential amplifier formed by ). An oscillation output having a phase of θ° and 180u is obtained at the output terminals (4 doors 5) of the differential amplifier formed by the transistor ueui, the constant current source (g), and the load resistor 01. Assuming that 1171 of all transistors are equal and the resistance value of resistor σI-1 is selected as in the conventional example, the input terminal (9
An equal DC bias load is applied from transistor 0 () through transistor 0. In the conventional example, transistor (11) supplies the base current for two transistors (Iη and Each of them supplies the base current for one transistor (in Figure 4, the transistor) and constant current source 1.
By adding a constant current source (b) with the same current value in one stage, the transistor @ (c) also supplies the base current of two transistors (11 (to), to the transistor), similarly to transistor 01. Therefore, since the resistance values of the resistors Q1 and 1@ are equal, the emitter currents of the transistors are equal.

よって、トランジスタ1.lシー(至)のエミッタ電流
が等しくなり、トランジスタθ″HI(イ)のVBEは
等しくなる。よってトランジスタQQQη(23弼のベ
ース電位を等しくすることができ、出力端子C4)(5
) (6J (7)の直流電圧を等しくすることができ
る。なお、ここで出力端子(5)の出力′電圧はトラン
ジスタ(至)と抵抗に)で構成されるエミッタフォロア
により共振回路C1)に帰還されている。
Therefore, transistor 1. The emitter currents of the transistors QQQη (23) become equal, and the VBE of the transistors θ''HI (A) become equal. Therefore, the base potentials of the transistors QQQη (23) can be made equal, and the output terminal C4) (5
) (6J (7) can be made equal to the DC voltage. Here, the output voltage of the output terminal (5) is connected to the resonant circuit C1) by the emitter follower composed of a transistor (to) and a resistor). He has been returned.

第5図は第4図の発振装置における各出力端子(4) 
(5) (6) (7)とその直流電圧との関係を示す
。同図のd、e、fはそれぞれhF□が小、中、犬の場
合を示しており、hFEの変動に対して、各出力端子間
の直流電圧は、等しく安定になっていることがわかる。
Figure 5 shows each output terminal (4) in the oscillator shown in Figure 4.
(5) (6) The relationship between (7) and its DC voltage is shown. d, e, and f in the same figure show cases where hF□ is small, medium, and dog, respectively, and it can be seen that the DC voltage between each output terminal is equally stable despite fluctuations in hFE. .

また、第4図の実施例においてはトランジスタ(IQ(
17)■■(至)く均が請求の範囲の第1〜第6のトラ
ンジスタで、抵抗αυ(ハ)(至)が請求の範囲の第1
〜第3の抵抗、トランジスタa陣四(ハ)が請求の範囲
の第1〜第3のエミッタフォロアに相当する。
In addition, in the embodiment shown in FIG. 4, a transistor (IQ(
17)■■(to) the first to sixth transistors in the claimed range, and the resistance αυ(c)(to) the first to sixth transistor in the claimed range.
~The third resistor and the transistor A group 4 (c) correspond to the first to third emitter followers in the claims.

L記実流側においては、1三ツタフォロアを構成するト
ランジスタ@μI(Jの1三ツタ電流を等しくするため
に抵抗時(ホ)(ロ)の伯を等しくしたが、これはトラ
ンジスタ(lluηのエミッタをそれぞれ抵抗を介して
定電流源O印に接続し、トランジスタ脅(財)のエミッ
タをそれぞれ抵抗を介して定電流源に)に接続し、抵抗
u3(イ)(ロ)をそれに流れる電流に等しい定電流源
に置きかえても、同様に各出力端子間の自流電圧を等し
く安定にできるということは浦うまでもない。また、E
記実流側では各出力端子に90°の位相差をもり発振出
力を収り出しているが、移相回路(2)の構成値を変え
ることによって位相差90°以外の発振出力を収り出す
ことができる。
On the L actual current side, in order to equalize the 13-point current of the transistor @μI (J) that constitutes the 13-point follower, the ratios of (E) and (B) at the time of resistance were made equal; The emitters of the transistors are connected to the constant current source O mark through the resistors, the emitters of the transistors are connected to the constant current source through the resistors, and the current flowing through the resistors U3 (A) and (B) is It goes without saying that if you replace it with a constant current source equal to E, you can equally stabilize the free current voltage between each output terminal.
On the recording flow side, each output terminal has a phase difference of 90° to accommodate the oscillation output, but by changing the configuration values of the phase shift circuit (2), the oscillation output with a phase difference other than 90° can be accommodated. I can put it out.

発明の詳細 な説明のように木売り]の発振装置によると、従来の発
振回路の差動増幅回路に、第5.第6のトランジスタで
形成される第8の差動増幅器を設け、第i 、第2 +
 ’43の工三ツタフオ0アの1三ツタ電流を等しくし
たため、前記差動増幅回路の各出力端子の直流電圧を第
1−第4のトランジスタのhFK7”変動しても相対的
に等しく安定Jることができる。これにより各発振出力
の位相差振幅も等しくすることができ)1 p Hの変
動に対して安定な発振出力を得ることができ、次段へ回
路を接続する場合に、特に相対精度がよく、集積回路化
において極めて有効なものである。
As described in the detailed description of the invention, according to the oscillation device of ``Kokusei'', a fifth. an eighth differential amplifier formed by a sixth transistor;
Since the 13 currents of the 13 currents of the 13 currents of the 1st to 4th transistors of the differential amplifier circuit are made equal, even if the DC voltage of each output terminal of the differential amplifier circuit fluctuates by 7" of the first to fourth transistors, the currents are relatively equal and stable. (This makes it possible to equalize the phase difference amplitude of each oscillation output.) It is possible to obtain a stable oscillation output against fluctuations of 1 pH, especially when connecting the circuit to the next stage. It has good relative accuracy and is extremely effective in integrated circuits.

【図面の簡単な説明】[Brief explanation of the drawing]

第1図は従来の発振装置の基本構成図、第2図は第1図
における差uノ増幅回路と移相回路の構成図、第3図は
第2図の差動増幅回路の出力特性図、第4図は本発明の
発振装置の一実施例の回路図、第5図は第4図の差動増
幅回路の出力特性図である。 (1)・・−共振回路、(2)・・・移相回路、、 (
3J・・・差!1lIJ増幅回路、(4) (5) (
6) (7)・・・出力端子、@Q旧[・・トランジス
タ〔第1〜第3の1!ツタフオ0ア] 、 01)(ハ
)■・・・抵抗〔第1〜第3の抵抗〕、頭Qη・・・ト
ランジスタ部1、第2のトランジスタ]、@@・・・ト
ランジスタ(第3.第4のトランジスタ] 、mB5−
1−ランジスタ〔第5.第6のトランジスタ] 代理人 森 木 義 弘 第1図 第2図 刃−
Figure 1 is a basic configuration diagram of a conventional oscillation device, Figure 2 is a configuration diagram of the difference u amplifier circuit and phase shift circuit in Figure 1, and Figure 3 is an output characteristic diagram of the differential amplifier circuit in Figure 2. , FIG. 4 is a circuit diagram of an embodiment of the oscillation device of the present invention, and FIG. 5 is an output characteristic diagram of the differential amplifier circuit of FIG. 4. (1)...-resonant circuit, (2)...phase shift circuit, (
3J... difference! 1lIJ amplifier circuit, (4) (5) (
6) (7)... Output terminal, @Q old [...transistor [1st to 3rd 1! 01) (c) ■... Resistor [first to third resistor], Head Qη... Transistor section 1, second transistor], @@... Transistor (third... fourth transistor], mB5−
1-Rangister [5th. 6th transistor] Agent Yoshihiro Moriki Figure 1 Figure 2 Blade -

Claims (1)

【特許請求の範囲】 1、第1の差動増幅器を形成する第1.第2のトランジ
スタと、第2の差動増幅器を形成する第3.第4のトラ
ンジスタと、第3の差動増幅器を形成する第5.第6の
トランジスタと、共振回路とを設け、かつ前記第1のト
ランジスタのベースに直流電圧源より第1の抵抗を介し
て駆動される第°1のエミッタフォロアを接続し、前記
共振回路を前記直流電圧源に第2の抵抗を介して接続し
、前記第2.第3のトランジスタのベースに前記共振回
路より第3の抵抗を介して駆動される第2のエミッタフ
ォロアを接続し、前記第4のトランジスタのベースに前
記共振回路より第4の抵抗を介して駆動される第3の1
ミツタフオ0アを接続し、第5のトランジスタのベース
を前記fJ’1のトランジスタのベースに接続し、第 
;6のトランジスタのベースを前記第4のトランジスタ
のベースに接続すると共に、前記第i、 第2.第3の
エミッタフォロアのエミッタ抵抗が等しくなるよう構成
した発振装置。 2° 第1j第2.第8のエミッタフォロアのエミッタ
抵抗を等しく設定して、第1.第2゜第8のエミッタフ
ォロアのエミッタ電流を等しくしたことを特徴とする特
許請求の範囲第1項記載の発振装置。 8、 第1.第2のトランジスタのエミッタをそれぞれ
抵抗を介して第1の定電流源に接続し、第8.第4のト
ランジスタの1三ツタをそれぞれ抵抗を介して第2の定
電流源に接続し、第1.第2.第3のエミッタフォロア
のl:ツタ抵抗をそれに流れる電流に等しい電流源に置
き代えて、第1.第2.fE8のエミッタフォロアのエ
ミッタ電流を等しくシ、たことを特徴とする特許請求の
範囲第1項記載の発振装置。
[Claims] 1. A first differential amplifier forming a first differential amplifier. a second transistor, and a third transistor forming a second differential amplifier. a fourth transistor, and a fifth transistor forming a third differential amplifier. A sixth transistor and a resonant circuit are provided, and a first emitter follower driven by a DC voltage source via a first resistor is connected to the base of the first transistor, and the resonant circuit is connected to the resonant circuit. connected to a DC voltage source via a second resistor; A second emitter follower driven by the resonant circuit through a third resistor is connected to the base of the third transistor, and a second emitter follower driven by the resonant circuit through the fourth resistor is connected to the base of the fourth transistor. 3rd 1 to be done
The base of the fifth transistor is connected to the base of the transistor fJ'1, and the
; the base of the sixth transistor is connected to the base of the fourth transistor, and the i-th, second . An oscillation device configured such that the emitter resistances of the third emitter followers are equal. 2° 1jth 2nd. The emitter resistances of the eighth emitter follower are set equal, and the emitter resistance of the eighth emitter follower is set equal to that of the first emitter follower. 2. The oscillation device according to claim 1, wherein the emitter currents of the second and eighth emitter followers are made equal. 8. 1st. The emitters of the second transistors are each connected to the first constant current source via a resistor, and the eighth. One of the fourth transistors is connected to the second constant current source via a resistor, respectively, and the first... Second. l of the third emitter follower: replacing the vine resistor with a current source equal to the current flowing through it, the first. Second. 2. The oscillation device according to claim 1, wherein the emitter currents of the fE8 emitter followers are set equally.
JP13396183A 1983-07-21 1983-07-21 Oscillator Pending JPS6025306A (en)

Priority Applications (1)

Application Number Priority Date Filing Date Title
JP13396183A JPS6025306A (en) 1983-07-21 1983-07-21 Oscillator

Applications Claiming Priority (1)

Application Number Priority Date Filing Date Title
JP13396183A JPS6025306A (en) 1983-07-21 1983-07-21 Oscillator

Publications (1)

Publication Number Publication Date
JPS6025306A true JPS6025306A (en) 1985-02-08

Family

ID=15117122

Family Applications (1)

Application Number Title Priority Date Filing Date
JP13396183A Pending JPS6025306A (en) 1983-07-21 1983-07-21 Oscillator

Country Status (1)

Country Link
JP (1) JPS6025306A (en)

Cited By (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JPS63501208A (en) * 1985-10-29 1988-05-12 イギリス国 articulated car

Cited By (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JPS63501208A (en) * 1985-10-29 1988-05-12 イギリス国 articulated car

Similar Documents

Publication Publication Date Title
US4760353A (en) Integrated gyrator oscillator
JPH08250941A (en) Low-distortion differential amplifier circuit
KR900005552B1 (en) Current mirror circuit
US5245298A (en) Voltage controlled oscillator having cascoded output
JPS6025306A (en) Oscillator
JPH0479166B2 (en)
KR100412002B1 (en) Fm signal oscillation circuit and modulation level correcting method
KR0161364B1 (en) A high-input impedance circuit and semiconductor device
JP2896029B2 (en) Voltage-current converter
JPH0519321B2 (en)
JPS62290204A (en) Electronic circuit including cascade circuit
JPS58147211A (en) Differential amplifier capable of being integrated
JPH0720960A (en) Current generating device
JPH0685536A (en) Voltage controlled oscillator
JPH06120747A (en) Differential amplifier
JP2600479B2 (en) Voltage controlled oscillator
JPH0258911A (en) Power amplifier circuit
JPH11120273A (en) Low voltage transformer linear circuit
JPH08222968A (en) Amplifier
JP2602313B2 (en) Oscillation circuit
JPS6221310A (en) Current constant multiple circuit
JP2007173971A (en) Analog frequency divider
JPH0449288B2 (en)
JPS6145882B2 (en)
JP2600648B2 (en) Differential amplifier circuit