JPS58120301A - Band pass filter - Google Patents
Band pass filterInfo
- Publication number
- JPS58120301A JPS58120301A JP298682A JP298682A JPS58120301A JP S58120301 A JPS58120301 A JP S58120301A JP 298682 A JP298682 A JP 298682A JP 298682 A JP298682 A JP 298682A JP S58120301 A JPS58120301 A JP S58120301A
- Authority
- JP
- Japan
- Prior art keywords
- resonator
- line
- transmission line
- resonators
- pass band
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Pending
Links
Classifications
-
- H—ELECTRICITY
- H01—ELECTRIC ELEMENTS
- H01P—WAVEGUIDES; RESONATORS, LINES, OR OTHER DEVICES OF THE WAVEGUIDE TYPE
- H01P1/00—Auxiliary devices
- H01P1/20—Frequency-selective devices, e.g. filters
- H01P1/201—Filters for transverse electromagnetic waves
- H01P1/203—Strip line filters
- H01P1/20309—Strip line filters with dielectric resonator
Abstract
Description
【発明の詳細な説明】
本発明は例えば誘電体共振器を用いた帯域通過フィルタ
に関する。DETAILED DESCRIPTION OF THE INVENTION The present invention relates to a bandpass filter using, for example, a dielectric resonator.
帯域通過フィルタにおいては一般に、通過帯域の外では
挿入損失が1徽に増大するような特性が望まれる。その
場合に一つの共振器を用いた帯域通過フィルタでは、挿
入損失の増大の急峻さkは、共振器の無負荷Q値によっ
て決まる限界があるので、それ以上の急峻さを実現しよ
うとするkは。Generally, it is desirable for a bandpass filter to have a characteristic in which the insertion loss increases by one degree outside the passband. In this case, in a bandpass filter using one resonator, the steepness of the increase in insertion loss k has a limit determined by the unloaded Q value of the resonator, so it is necessary to try to achieve a steeper increase k. teeth.
複数個の共振器を組合せてフィルタを構成する方法がと
られる。A method is used in which a filter is constructed by combining a plurality of resonators.
第1図はそのような装置の一例を示す。図におい″cI
l電体基坂(1)の裏面の全面にわたって接地導体(2
)が設けられる。また基[(11の表面側に1入力端子
となるマイク四ストリップツイン(3)、誘電体共振器
(4) * (5) * (6)、出力端子となる!イ
ク璽ストリップライン(7)が設けられる。FIG. 1 shows an example of such a device. In the figure “cI”
l A ground conductor (2
) is provided. In addition, on the front side of 11, there is a microphone 4 strip twin (3) that serves as an input terminal, a dielectric resonator (4) * (5) * (6), and a strip line that serves as an output terminal (7). is provided.
そしてこの装置kThいて、入力信号がライン(3)K
供給されると、このライン(3)と共振器(4)とが結
合され、この共振器(4)と共振器(5)とが結合され
、この共振器(5)と共振器(6)とが結合され、この
共振器(6)とライン(7)とが結合されてこのツイン
(7)から出力信号が職り出される。And this device kTh has an input signal on line (3) K
When supplied, this line (3) and resonator (4) are coupled, this resonator (4) and resonator (5) are coupled, and this resonator (5) and resonator (6) are coupled. The resonator (6) and the line (7) are coupled to produce an output signal from the twin (7).
しかしながら、この装置において共振器間の結合が十分
に強くとれない場合や、スゲリアスモードの共振器間結
合が強いような場合には、こりように共振器を直接結合
させる方法は適切でない。However, in this device, if the coupling between the resonators is not strong enough, or if the coupling between the resonators in Sgelius mode is strong, this method of directly coupling the resonators is not appropriate.
そこでこのような鳩舎において、共振器と共振器との間
を伝送allで結んで、被数個の共振器を用いた帯域通
過フィルタを形成することが提案された。Therefore, in such a pigeon house, it has been proposed to connect the resonators with a transmission all to form a band-pass filter using a number of resonators.
本発明はこのような帯域通過フィルタにおいて通過帯域
の外での挿入損失の増大をさらに急峻にできるよ5Kし
たものである。以下に図面を参照しながら本発明の一実
施例について説明しよ5゜第2図において、基板(1)
の!!藺儒に、入力端子となるマイク−ストリップティ
ン住υ、誘電体共振器az、as、a4、これらの共振
器の間をつなぐマイク四ストリップツインα9、ae、
出力端子となるマイク−ストリップ2インαηが設けら
れる。The present invention provides such a bandpass filter with 5K so that the increase in insertion loss outside the passband can be made even steeper. An embodiment of the present invention will be described below with reference to the drawings. 5. In Figure 2, a substrate (1)
of! ! In a conventional manner, the input terminals are microphone-strip tin housings, dielectric resonators az, as, and a4, and the microphone four-strip twin α9, ae, which connects these resonators.
A microphone strip 2-in αη serving as an output terminal is provided.
そしてこの装置において、入力信号を第1の伝送線路と
しての2インIに供給し、このツインaυを第1の共振
器UKM合させ、この共振器Iを第2の伝送−路として
のツイン(15に結合させ、このライン四を第2の共振
器a3に結合させると共k。In this device, an input signal is supplied to the 2-in I as the first transmission line, this twin aυ is coupled to the first resonator UKM, and this resonator I is connected to the twin ( 15 and this line 4 is coupled to the second resonator a3 as well as k.
ラインα9の共振器aり、儲とのそれぞれ結合点の間の
奇数倍に等しくシ、共振器峙をラインα$及び共振器I
と等しい構成(ツインa19及び共振器a4)を介して
第3の伝送線路としてのツインaηに結合させ、このツ
イン鰭から出力信号を取り出す。Resonator a of line α9 is equal to the odd number times between the coupling points of line α and resonator I.
It is coupled to the twin aη as the third transmission line via a configuration (twin a19 and resonator a4) equal to the above, and an output signal is extracted from this twin fin.
この装置において、ラインαs、aeのそれぞれ共振器
0、aJ及びas、a4との結合点の間の距離を通過帯
域の中心周波数の一波長の奇数倍に等しくしたことによ
り、通過帯域外の挿入損失の増大を最も急峻にすること
ができる。以下にこの等親を行なう。In this device, the distance between the coupling points of the lines αs and ae with the resonators 0, aJ and as, a4, respectively, is made equal to an odd multiple of one wavelength of the center frequency of the passband. The increase in loss can be made the steepest. We perform this equality below.
いま簡単のために、共振器の数が2個の帯域通過フィル
タを考え、2つの共振器は同一であると仮定する。この
とき、帯域通過フィルター価回踏は第3図のように表わ
される。For simplicity, consider a bandpass filter with two resonators, and assume that the two resonators are the same. At this time, the bandpass filter value is expressed as shown in FIG.
この等価回路から、端子AB間の2端子■賂綱の8マト
リツクス〔S〕、端子CD間の2端子閣路網のS−vト
リックス〔Sりの各要素は以下のよ5に求まる。From this equivalent circuit, each element of the 8 matrix [S] of the 2-terminal network between terminals AB and the S-v matrix [S] of the 2-terminal network between terminals CD is determined as shown in 5 below.
・・・・・(1)
・・・・・(2)
ここで端子AD間全全体2端子回路網の8 Y)リツク
スを(8)とすると、〔S〕は[8]を用いて以下のよ
うに!!わされる。・・・・・・(1) ・・・・・・(2) Here, if the 8Y) ricks of the entire two-terminal circuit network between terminals AD is (8), then [S] is as follows using [8]. like! ! I will be forgotten.
・・・・・(3)
この帯域通過フィルタの挿入損失の値は、−10怠og
151g”l”となるから、181!tl”Kついて
吟味し・・・・・(4)
この(4)式にある81!あるいは81mは、(1)ま
たは(2)式より第4図のよ5な変化を示す、これから
、8xs8xt’は第5図のように変化する。またg
t 雪B ue″j 5iは81!81!を時計方向に
2g1/λラジアン回転しただけであるから、同一周波
数における1stmu’e″j!1ψ−の値は変化しな
い、即ち(4)式の分子は、露の値に依らず同一周波数
において同じ値をとる。一方、(4)式中の82!ある
いは8tt’は、(1)または(2)式より第6図のよ
うな変化を示す、これから、8z*8ss’は!7図の
ような変化をすル* t ?:、 8u8x/e−j”
’/’は8xs8xt’を時計方向に4πVλラジアン
回転したものであるから、ト1λ/4(fi−1tR*
・・・)のとき、ちょうど原点に対して第7図の反対側
k〈るよ5にな9、第8図のような変化を示す。...(3) The insertion loss value of this bandpass filter is -10log
Since it is 151g "l", it is 181! tl''K...(4) 81! or 81m in equation (4) indicates a change of 5 as shown in Figure 4 from equation (1) or (2).From this, 8xs8xt ' changes as shown in Figure 5. Also, g
t Snow B ue''j 5i is just rotating 81!81! clockwise by 2g1/λ radians, so 1st mu'e''j at the same frequency! The value of 1ψ- does not change, that is, the numerator of equation (4) takes the same value at the same frequency regardless of the dew value. On the other hand, 82! in equation (4)! Alternatively, 8tt' shows a change as shown in Figure 6 from equation (1) or (2). From this, 8z*8ss'! 7. Do you want to change as shown in Figure 7? :, 8u8x/e-j”
'/' is 8xs8xt' rotated clockwise by 4πVλ radians, so t1λ/4(fi-1tR*
...), the opposite side of Fig. 7 with respect to the origin, k〈Y5 to 9, shows a change as shown in Fig. 8.
t −j鶴Vλ
さらK 11−&511e l f)値ハ、複素
平面上s −j4πVλ
での1の点と82ffi8oe の点との距離で
あるから、−がω0から遠ざかったとき、すなわちL+
nλ/4t −j4πVλ
に選んだ場合に最も1l−8uSoelの値が大きくな
るようKなり、<4>tの18s意1は小さくなる。t −j TsuruVλ SaraK 11−&511e l f) Value C is the distance between the point 1 and the point 82ffi8oe on the complex plane s −j4πVλ, so when − moves away from ω0, that is, L+
When nλ/4t −j4πVλ is selected, K is set such that the value of 1l−8uSoel becomes the largest, and 18s of <4>t becomes smaller.
一方、6に610のときkは、1l−8t雪8t 7e
−j4d/λ1の値はiK依らずほとんど一定している
ことが解り、+81!+のω二ω0でのl依存性は小さ
い。On the other hand, when 6 is 610, k is 1l-8t snow 8t 7e
It turns out that the value of -j4d/λ1 is almost constant regardless of iK, and it is +81! The l dependence of + on ω2ω0 is small.
以上のことから明らかなよ5 K m −nλ/4(n
=1*3・・・)に選んだ時、通過帯域外の挿入損失の
増大は最つとも急峻になる。It is clear from the above that 5 K m −nλ/4(n
=1*3...), the increase in insertion loss outside the passband becomes the steepest.
こうして帯域通過フィルタが形成されるわけであるが、
本発明によれば、共振器の間をつなぐツインのそれぞれ
共振器との結合点の間の距離を通過帯域の中心周波数の
7波長の奇数倍に等しくしたことKより、通過帯域外の
挿入損失の増大を最も急峻にすることができる。In this way, a bandpass filter is formed.
According to the present invention, since the distance between the coupling points of the twin resonators connecting the resonators is equal to an odd multiple of 7 wavelengths of the center frequency of the passband, the insertion loss outside the passband is can be made to have the steepest increase.
さらに第9図は、1つの共振器を用いた時の挿入損失の
シs−ル−ジョン結果である。また第10図は、2個の
共振器を用いて1−OX選んだ場合の挿入損失である。Further, FIG. 9 shows the insertion loss sieving results when one resonator is used. Moreover, FIG. 10 shows the insertion loss when 1-OX is selected using two resonators.
これらの図において1つの共振器を用いた場合に比べ幾
分帯域外の挿入損失の増大は急になっていることが解る
。これに対して第11図は2個の共振器を用いて1−λ
/4に選んだ場合の挿入損失である。この図においてg
−6の場合よりも更に帯域外の挿入損失の増大は急峻に
なっている。It can be seen from these figures that the out-of-band insertion loss increases somewhat more rapidly than when one resonator is used. On the other hand, in Fig. 11, two resonators are used to generate 1-λ
This is the insertion loss when selecting /4. In this figure, g
The increase in out-of-band insertion loss is even steeper than in the case of −6.
このように本発明によれば通過帯域外の挿入損失の増大
を極めて急峻にすることができる。As described above, according to the present invention, the increase in insertion loss outside the passband can be made extremely steep.
なお、本発明において複数個の共振器のm波数は必ずし
も一致しなくても良く、はぼ近くの共振周波数tもつ複
数個の共振器の場合にも同じ効果がある。また共振器と
し【は上述の誘電体共振器に限らず平面回路、空胴共振
器、フェリ磁性共振器などあらゆる共振器に対して有効
である。さらに共振器間を結ぶ伝送線路としては、!イ
クpストリップライン以外にも、導波管、同−纏絡、ス
トリップラインなどあらゆる伝送線路に対して有効であ
る・Note that in the present invention, the m-wavenumbers of a plurality of resonators do not necessarily have to match, and the same effect can be obtained even in the case of a plurality of resonators having a resonant frequency t near the center. Furthermore, the resonator is effective not only for the above-mentioned dielectric resonator but also for all types of resonators such as planar circuits, cavity resonators, and ferrimagnetic resonators. Furthermore, as a transmission line connecting the resonators,! In addition to IkuP strip lines, it is effective for all kinds of transmission lines such as waveguides, parallel lines, and strip lines.
第1図は従来の装置の構成図、第2図は本発明の一例の
構成図、第3図〜第11図はその説明のための図である
。
01)eQ5*(lfi*(17))lv(りOX )
IJ yフ94y、Q3 * (+31 * Q4)
は共振器である。
第2図
身FIG. 1 is a block diagram of a conventional device, FIG. 2 is a block diagram of an example of the present invention, and FIGS. 3 to 11 are diagrams for explaining the same. 01) eQ5*(lfi*(17))lv(riOX)
IJ yfu94y, Q3 * (+31 * Q4)
is a resonator. 2nd figure
Claims (1)
路を第1の共11i@に結合させ、との@1の共振器を
第2の伝送線路に結合させ、この第2の伝送線路を第2
の共振器に結合させると共に1上記第2の伝送線路の上
記第1及び第2の共振器とのそれぞれ結合点の間の距離
を通過帯域の中心周波数の7波長の奇数倍に等しくシ、
上記第8の共振器を直接または1組以上の上記第2の伝
送線路及び第2の共振器と等しい構成を介してjIsの
伝送線路に結合させ、この第3の伝送線路から出力信号
を取り出すようにした帯域通過フィルタ。An input signal is provided to a first transmission line, a transmission line of sl of and is coupled to a first common 11i@, a resonator of @1 of is coupled to a second transmission line of this second 2nd transmission line
resonator, and the distance between the coupling points of the second transmission line and the first and second resonators is equal to an odd multiple of seven wavelengths of the center frequency of the passband,
The eighth resonator is coupled to the jIs transmission line directly or through one or more sets of the second transmission line and the second resonator, and the output signal is extracted from the third transmission line. Bandpass filter.
Priority Applications (1)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
JP298682A JPS58120301A (en) | 1982-01-12 | 1982-01-12 | Band pass filter |
Applications Claiming Priority (1)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
JP298682A JPS58120301A (en) | 1982-01-12 | 1982-01-12 | Band pass filter |
Publications (1)
Publication Number | Publication Date |
---|---|
JPS58120301A true JPS58120301A (en) | 1983-07-18 |
Family
ID=11544688
Family Applications (1)
Application Number | Title | Priority Date | Filing Date |
---|---|---|---|
JP298682A Pending JPS58120301A (en) | 1982-01-12 | 1982-01-12 | Band pass filter |
Country Status (1)
Country | Link |
---|---|
JP (1) | JPS58120301A (en) |
Cited By (4)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
JPS60145704A (en) * | 1984-01-10 | 1985-08-01 | Fujitsu Ltd | Dielectric filter |
US5525945A (en) * | 1994-01-27 | 1996-06-11 | Martin Marietta Corp. | Dielectric resonator notch filter with a quadrature directional coupler |
WO2014009069A3 (en) * | 2012-07-10 | 2014-03-20 | Endress+Hauser Gmbh+Co. Kg | Printed circuit board equipped with a radio-frequency assembly emitting interference waves |
CN104466308A (en) * | 2014-11-28 | 2015-03-25 | 南通大学 | Balanced dielectric filter and manufacturing method thereof |
Citations (1)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
JPS5081043A (en) * | 1973-11-08 | 1975-07-01 |
-
1982
- 1982-01-12 JP JP298682A patent/JPS58120301A/en active Pending
Patent Citations (1)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
JPS5081043A (en) * | 1973-11-08 | 1975-07-01 |
Cited By (6)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
JPS60145704A (en) * | 1984-01-10 | 1985-08-01 | Fujitsu Ltd | Dielectric filter |
US5525945A (en) * | 1994-01-27 | 1996-06-11 | Martin Marietta Corp. | Dielectric resonator notch filter with a quadrature directional coupler |
WO2014009069A3 (en) * | 2012-07-10 | 2014-03-20 | Endress+Hauser Gmbh+Co. Kg | Printed circuit board equipped with a radio-frequency assembly emitting interference waves |
US9801268B2 (en) | 2012-07-10 | 2017-10-24 | Endress + Hauser Gmbh + Co. Kg | Circuit board equipped with a high-frequency component emitting interference waves |
CN104466308A (en) * | 2014-11-28 | 2015-03-25 | 南通大学 | Balanced dielectric filter and manufacturing method thereof |
CN104466308B (en) * | 2014-11-28 | 2017-10-31 | 南通大学 | A kind of balanced type dielectric filter and preparation method thereof |
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