JPH09223930A - Colpitts oscillation circuit - Google Patents

Colpitts oscillation circuit

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Publication number
JPH09223930A
JPH09223930A JP5101796A JP5101796A JPH09223930A JP H09223930 A JPH09223930 A JP H09223930A JP 5101796 A JP5101796 A JP 5101796A JP 5101796 A JP5101796 A JP 5101796A JP H09223930 A JPH09223930 A JP H09223930A
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circuit
oscillation circuit
colpitts
capacitor
oscillation
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JP3322791B2 (en
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Yasuo Tsuzuki
泰雄 都築
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Toyo Commun Equip Co Ltd
東洋通信機株式会社
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Abstract

PROBLEM TO BE SOLVED: To provide a Colpitts oscillation circuit with stable oscillation activation characteristics without delaying the rise of an oscillation level at the time of supplying power.
SOLUTION: In this Colpitts oscillation circuit composed of a piezoelectric vibrator, an amplification element and a capacitor to be a part of load capacity, etc., one end of the piezoelectric vibrator is grounded through a power supply line. The capacitor CA is inserted between the base and emitter of a transistor, the capacitor CB and a resistor RE are inserted between the emitter and ground, a crystal resonator is inserted between the base and the power supply line and a required bias voltage is supplied to the transistor.
COPYRIGHT: (C)1997,JPO

Description

【発明の詳細な説明】 DETAILED DESCRIPTION OF THE INVENTION

【0001】 [0001]

【発明の属する技術分野】本発明はコルピッツ発振回路、特に電源投入時の発振起動を確実にしたコルピッツ発振回路に関する。 The present invention relates to the Colpitts oscillation circuit, a Colpitts oscillation circuit to ensure oscillation start at particular power-on.

【0002】 [0002]

【従来の技術】マイクロプロセッサ等のデジタル機器或いは水晶時計、及び移動体通信には安定なデジタルクロック信号が必要であるが、近年そのための発振回路としてトランジスタを増幅素子とし、圧電振動子として水晶振動子を利用したコルピッツ発振回路が一般的である。 BACKGROUND ART microprocessor such as a digital device or quartz watch, and the mobile communication is necessary stable digital clock signal, in recent years the transistors and the amplifying element as an oscillation circuit for the crystal oscillation as a piezoelectric vibrator Colpitts oscillator circuit using a child is common.
その基本的な回路を示せば図7の通りであって、トランジスタのベースとエミッタ間にコンデンサC Aを、エミッタと接地間にコンデンサC B及び抵抗R Eを、ベースと接地間に抵抗R B及び水晶振動子X A 、さらに必要に応じて周波数調整用として可変コンデンサC Sを挿入したものである。 Be as in FIG. 7 if Shimese the basic circuit, the capacitor C A between the base and emitter of the transistor, the capacitor C B and a resistor R E between the emitter and the ground, the resistance R B between the base and the ground and crystal oscillator X a, is obtained by inserting a variable capacitor C S for the frequency adjustment if necessary. 端子V CCは直流電源を加える端子である。 Terminal V CC is a terminal to apply the DC power supply.

【0003】 [0003]

【発明が解決しようとする課題】しかしながら、前述のコルピッツ発振回路では電源投入時直後の発振出力の立ち上がりが遅れたり、或いは周波数の安定に時間を要する等の問題があった。 [SUMMARY OF THE INVENTION However, there are problems such as requiring or delay the rise of the oscillation output immediately after power-on in the Colpitts oscillation circuit of the above, or the stable time of the frequency. 更に著しい場合には、発振が正常に起動せず、不発に終わることがあった。 If more pronounced, the oscillation may not start properly, it was sometimes end up unexploded. 本発明は上述した如き発振回路が有する欠点を除去する為になされたものであって、電源投入時の発振レベルの立ち上がりが遅れることがなく、安定した発振起動特性を持ったコルピッツ発振回路を提供することを目的とする。 The present invention was made in order to eliminate the drawbacks possessed by as mentioned above oscillation circuit, without rising is delayed oscillation level at power-on, providing a Colpitts oscillation circuit having a stable oscillation startup characteristics an object of the present invention is to.

【0004】 [0004]

【課題を解決する為の手段】上述の目的を達成するため本発明に係わる発振回路は、圧電振動子と増幅素子と負荷容量の一部となるコンデンサ等からなるコルピッツ発振回路において、圧電振動子の一方端を電源ラインを介して接地したことによって電源投入時の立ち上がりを速く且つ確実にしたものである。 Oscillator circuit according to the present invention to achieve the above object, according to an aspect of, in Colpitts oscillation circuit composed of a capacitor or the like to be a part of the amplifier element and the load capacitance and the piezoelectric vibrator, the piezoelectric vibrator by one to an end is grounded through a power supply line of the is obtained by the fast and reliably the rise of the power-on.

【0005】 [0005]

【発明の実施の形態】以下、本発明を実施例を示す図面に基づいて詳細に説明する。 BEST MODE FOR CARRYING OUT THE INVENTION Hereinafter, will be described in detail based on the drawings illustrating the present invention embodiment. 図1は本発明の一実施例を示す回路図であって、この回路図が前記従来の回路図と異なる点は水晶振動子の一端を電源ラインを介して接地するよう構成したものである。 Figure 1 is a circuit diagram showing an embodiment of the present invention in that the circuit diagram is different from the circuit diagram of the prior art is that configured to ground through one end of the power line of the quartz oscillator. 基本的な回路は同図に示すように、トランジスタのベースとエミッタ間にコンデンサC Aを、エミッタと接地間にコンデンサC Bと抵抗R Eを、ベースと接地間に抵抗R B 、必要に応じて可変コンデンサC Sを挿入し、水晶振動子X Aの一端を電源ラインに一端をトランジスタのベースに接続したものである。 As the basic circuit shown in the figure, the capacitor C A between the base and emitter of the transistor, the capacitor C B and a resistor R E between the emitter and ground, the base and the resistor R B and the ground, if necessary insert the variable capacitor C S Te, in which one end of the one end of the crystal resonator X a to the power supply line is connected to the base of the transistor. 従来のコルピッツ発振回路で端子V CCに直流電圧を加えた後の動作は、トランジスタが動作状態になるまで、起動時間全体では無視できる程度の短時間の領域で、振動子はほぼ一定振幅で振動する。 Conventional operation after adding a DC voltage to the terminal V CC Colpitts oscillation circuit, until the transistor is operational, a short region of negligible throughout startup time, the vibrator is substantially constant amplitude vibrations to. 電源投入直後の動作は図2に示す等価回路で考えることができ、電源投入直後にはR C 、トランジスタのベースコレクタ間容量C BC 、2つの容量C A 、C Bの直列回路に充電電流が流れ、その時定数は小さいのでベース側には次式で決まる小振幅のステップ電圧Vtが生じる。 Operation immediately after power-on can be considered the equivalent circuit shown in FIG. 2, R is immediately after power C, between the base and the collector of the transistor capacitance C BC, 2 one capacity C A, the charging current to the series circuit of C B flow, small amplitude step voltage Vt determined by the following equation occurs in the base side since the time constant is small.

【0006】Vt=(C BC /(C BC +Ct))V CCただし、CtはC AとC Bの直列容量 Ct=C AB /(C A +C B ) であり、振動子の影響は無視してある。 [0006] Vt = (C BC / (C BC + Ct)) V CC However, Ct is the / C A and C B of the series capacitance Ct = C A C B (C A + C B), the influence of the vibrator It is ignored. このステップ電圧により振動子が励振され、振動子等価回路のL 1 、C Vibrator This step voltage is excited, L 1, C oscillator equivalent circuit
1 、R 1の直列共振片を流れる高周波電流(振動子の振動振幅に比例する。以下、共振電流と呼ぶ。)の初期振幅は、 1 0 =√(C 1 /L 1 )×Vt と示すことができる。 1, the high-frequency current flowing through the series resonant piece of R 1 (proportional to the vibration amplitude of the vibrator. Hereinafter referred to as a resonance current.) The initial amplitude indicates the 1 0 = √ (C 1 / L 1) × Vt be able to.

【0007】前述のように、電源投入直後の振動子電流は振動子に加わる電圧に比例するので、本発明のように構成すれば振動子には電源電圧とほぼ同じ大きさ、即ち、最大のステップ電圧が加わることとなるので、振動子は最も高い振動レベルで始動することとなり、コルピッツ発振回路の起動時間の短縮となる。 [0007] As described above, since the vibrator current immediately after power is proportional to the voltage applied to the vibrator, the power supply voltage to the vibrator be configured as in the present invention substantially the same size, i.e., maximum because so that the step voltage is applied, the vibrator becomes possible to start at the highest vibration level, a shorter startup time Colpitts oscillation circuit. また、水晶振動子は、振動子電流即ち振動子励振レベルが変動しても等価直列抵抗が変化しないことが望ましいが、低励振レベルとなると抵抗値が数10%も増加するような振動子が少なからずある。 Further, the crystal oscillator, the oscillator as also the equivalent series resistance transducer current or oscillator drive level is varied. However it is desirable not to change, and the resistance value becomes the low excitation levels also increases the number by 10% not a little there. 前記振動子の低励振レベルにおける等価抵抗が大幅に大きい場合は、発振回路が不発となってしまう恐れがある。 Wherein when the equivalent resistance at low excitation level of the vibrator is much larger, there is a possibility that the oscillation circuit becomes a dud.

【0008】しかし、振動子では励振レベルを低くすると等価抵抗は増加する傾向を持っている。 However, the vibrator has a tendency to increase the equivalent resistance A low excitation levels. 従って発振回路の不発を減少させるためには高い励振レベルで振動子を始動させればよく、前述のように振動子の接続を変更することによって最大のステップ電圧が加わることとなるので、振動子は最も高い振動レベルで始動することとなり、不発となることのない発振回路を実現するという効果を有する。 Thus in order to reduce the unexploded oscillation circuit it is sufficient to start the vibrator at a high excitation level, because so that the maximum step voltage is applied by changing the connection of the oscillator as mentioned above, the transducer an effect that becomes possible to start at the highest vibration level, to achieve a free oscillation circuit be a misfire. 本願発明は前述した回路のみならず、図3に示すようなカスコード型のコルピッツ回路に適用することができる。 The present invention is not only the circuit described above can be applied to the cascode type Colpitts circuit as shown in FIG. カスコード型コルピッツ発振回路は携帯電話等に多用されており、頻繁に発振器の電源のON Cascoded Colpitts oscillation circuit is widely used in cellular phones or the like, of frequent oscillator power ON of
―OFFを繰り返す場合に特に有効であろう。 It would be particularly effective in the case of repeating the -OFF.

【0009】前記カスコード形コルピッツ発振回路は、 [0009] The cascode type Colpitts oscillator circuit,
ふたつのトランジスタが直列に接続しており、バッファとしてカスコード接続されたベース接地回路にはベースと接地間に大容量のコンデンサが接続されているため、 Since the two transistors are connected in series, a large capacitance of the capacitor is connected between ground and the base is the cascoded common base circuit as a buffer,
電源投入直後の振動子の起動レベルは通常のコルピッツ回路より大幅に低くなり、起動時間も長くなる。 Start Level oscillator immediately after power is much lower than normal Colpitts circuit, the startup time becomes longer. しかし圧電振動子の一端を電源を介して接地すれば、通常のコルピッツ回路を変形した場合と同一のレベルで始動することになり、起動時間短縮の効果は一段と著しいこととなる。 But if the ground one end of the piezoelectric vibrator via the power, would be started at the same level as in the case obtained by modifying the conventional Colpitts circuit, the effect of activation time reduction becomes possible more significant.

【0010】前述のカスコード形発振回路を、コンピュータ解析により起動時間短縮の効果を検証した。 [0010] The cascade-type oscillation circuit of the above-mentioned, was to verify the effect of start-up time shortened by computer analysis. 発振回路の条件は、発振周波数:10MHz, 電源電圧:5 Conditions of the oscillation circuit, the oscillation frequency: 10MHz, the power supply voltage: 5
V, 振動子電流:1mA,振動子の負荷容量:30p V, the oscillator current: 1mA, the transducer of the load capacitance: 30p
F, 負性抵抗余裕:振動子等価抵抗の3倍 振動子の等価回路定数値は、L 1 =18.7mH, C F, negative resistance margin: equivalent circuit constant values of the triple resonator oscillator equivalent resistance, L 1 = 18.7mH, C
1 =0.0135pF, R 1 =11.9Ω,C 0 1 = 0.0135pF, R 1 = 11.9Ω , C 0 =
2.75pF, fs=10.0MHz Re=14.2Ω(負荷容量30pFのときの等価抵抗) とし、以上に基づき図3の回路定数を次のように定めた。 2.75pF, fs = 10.0MHz Re = a 14.2Omu (equivalent resistance when the load capacitance 30 pF), the circuit constants of the basis Figure 3 above was determined as follows. (トランジスタは2SC1359) R A =68KΩ, R B =62KΩ, R C =1.8K (Transistor 2SC1359) R A = 68KΩ, R B = 62KΩ, R C = 1.8K
Ω,R D =47KΩ, R E =5.1KΩ, C A =1 Ω, R D = 47KΩ, R E = 5.1KΩ, C A = 1
80pF,C B =220pF, C D =10nF,C S 80pF, C B = 220pF, C D = 10nF, C S
=42.3pF,(能動回路側の等価容量を30pFにする値) なお、図3の回路の出力端には、負荷インピーダンスとして10KΩと10pFの並列回路を付加してあり、負荷側に電流が分流するために始動レベルはさらに低下する。 = 42.3pF, (a value to the equivalent capacitance of the active circuitry side 30 pF) Note that the output end of the circuit of Figure 3, Yes by adding a parallel circuit of 10KΩ and 10pF as a load impedance, the current on the load side starting levels to divert further reduced. 従来のカスコード形コルピッツ発振回路、および振動子を電源側に接続変更した発振回路について、電源投入後の0〜0.3μs(10MHzでは3周期)の間の振動子電圧と共振電流とを解析して得られた結果を表1 Conventional cascode type Colpitts oscillation circuit, and the oscillation circuit connected changed vibrator on the power supply side, it analyzes the transducer voltage and the resonant current during 0~0.3μs after power (in 10 MHz 3 cycles) Table 1 the results obtained Te
に示す。 To show.

【0011】 [0011]

【表1】 [Table 1] 従来の発振回路では電源投入直後にパルス状の微小電圧が振動子に加わり、振動子は極めて低レベルの0.1n Pulsed minute voltage immediately after the power is turned on in the conventional oscillation circuit is applied to the vibrator, the vibrator is of very low levels 0.1n
Aで始動するが、接続を変更した回路では振動子には電源電圧の5ボルトの変化がほぼそのまま加わり、従来の回路より約4万倍の4μAで振動子は始動する。 Starting at A, but in the circuit to change the connection joined as substantially change the 5 volt supply voltage to the vibrator, the vibrator is about 40,000 times that of 4μA than traditional circuit starts. 前述の始動電流の式、 I 0 =√(C 1 /L 1 )×V t・・・・(1) でV tを4.8ボルトとするとI Oは4.1μAとなり、表1の値とよく一致している。 The preceding formulas of the starting current, I 0 = √ (C 1 / L 1) × V t ···· (1) When the V t and 4.8 volts I O is 4.1μA, and the Table 1 values and it is in good agreement. 前述と異なる評価方法として、共振電流が90%に達するまでの時間、及び発振周波数の周波数許容偏差が1ppmとなる起動時間について解析した。 As a different evaluation method described above, the time until the resonant current reaches 90%, and frequency tolerance of the oscillation frequency is analyzed start time satisfying 1 ppm. 振動子を接続変更した回路の場合は短縮量14.6msを差し引いて表2の結果を得た。 For circuit connected changed vibrator give the results shown in Table 2 by subtracting the amount of shortening 14.6Ms.

【0012】なお起動時間の短縮量とは、振動子始動電流の増大比がわかっている場合、線形LCR回路についての周知の解析結果から簡単に算出でき、振動子の等価直列インダクタンスL1に直列になる抵抗分は振動子の等価直列抵抗R1と振動子並列容量C Oを含めた発振回路側の小信号負性抵抗−R LO 'の和(R1−R LO ')であり、R LO 'は振動子接続端子から見た発振回路側の小信号負性抵抗−R LO 'から次式で求められる。 [0012] Note that the amount of shortening startup time, if the increase ratio of the oscillator starting current is known, can easily be calculated from known analysis results for the linear LCR circuit, in series with the equivalent series inductance L1 of the vibrator It becomes resistive component is the 'sum of (R1-R LO' small signal negative resistance -R LO of the oscillation circuit side, including the equivalent series resistance R1 of the vibrator to the vibrator parallel capacitance C O), R LO 'is from small signal negative resistance -R LO 'of the oscillation circuit side as viewed from the transducer connection terminal is determined by the following equation. LO '≒R LO /(1+C0/CL)・・・・(2) ただしCLは振動子の負荷容量である。 R LO '≒ R LO / ( 1 + C0 / CL) ···· (2) provided that CL is the load capacitance of the oscillator. 損失の小さい線形LCR回路における交流振幅Iの変化は、周知のように次式になる。 Change of AC amplitude I in small linear LCR circuit loss becomes the following equation as is well known. I=I 0 exp{(−P/2L)t}・・・・(3) 共振電流の初期振幅がI 0からI 1に増大する起動時間の短縮量t Sは、上式がI 1になるまでの時間であるから次式で求められる。 I = I 0 exp {(- P / 2L) t} ···· (3) reducing the amount t S of start time initial amplitude of the resonant current is increased from I 0 to I 1, the above equation to I 1 since the time of until given by the following equation.

【0013】 t s ={2L 1 /(R LO '−R1)}In・(I 1 /I 0 )・・・・(4) 表1の結果から従来の発振回路と本発明による発振回路の共振電流の比4.1×10 4を式(4)に代入すると起動時間の短縮量は14.6msとなる。 [0013] t s = {2L 1 / ( R LO '-R1)} In · (I 1 / I 0) ···· (4) Table 1 Results of the conventional oscillation circuit and an oscillation circuit according to the invention amount of shortening of the ratio 4.1 × 10 4 of the resonant current to be substituted into the equation (4) start time is 14.6ms.

【0014】 [0014]

【表2】 [Table 2] 定義によって相違はあるが、起動時間は約1/2から約1/3にまで大幅に短縮される。 Although differences by definition, activation time is greatly reduced from about 1/2 to about 1/3. なお、カスコード回路の場合はベース接地回路のベース接地用コンデンサC D The capacitor C D for the base ground of the base circuit in the case of cascode circuit
の容量が大きいため発振用トランジスタが動作状態になるまでに時間が長いが(時定数約0.4ms)、その前記コンデンサによる遅れ時間の影響は解析を簡易化するために無視してある。 While the oscillation transistor for large capacity of a long time until the operation state (time constant of about 0.4 ms), the influence of the delay time due to the said capacitor are ignored in order to simplify the analysis. さらに本願発明は、振動子の基本振動を利用する回路だけでなく、図4に示すような3次振動、5次振動などのオーバートーン振動を利用する回路にも適用できる。 Furthermore the present invention, not only circuit utilizing the fundamental vibration of the vibrator, primary 3 as shown in FIG. 4 vibration can also be applied to a circuit utilizing overtone vibrations of a fifth order vibration. Eは交流の短絡用、L BとC Bの並列回路は振動子の基本波周波数では誘導性リアクタンスとなりオーバートーン周波数では容量性リアクタンスとなる回路であって、動作原理は通常のコルピッツ回路と同じである。 C E For short circuit AC, a parallel circuit of L B and C B is a circuit comprising a capacitive reactance in the overtone frequency becomes inductive reactance at the fundamental frequency of the oscillator, the operating principle is the usual Colpitts circuit it is the same. この回路も、振動子の一端を電源に接続して接地することにより、起動の安定したオーバートーン発振回路となる。 This circuit also by grounding by connecting one end of the vibrator to the power supply, a stable overtone oscillation circuit startup. 尚、以上本発明の発振回路の増幅素子をトランジスタとして構成したものを例として説明したが、本発明はこれに限定されるものではなく、図5、 The above is the amplifying element of the oscillation circuit of the present invention has been described as an example those configured as a transistor, the present invention is not limited to this, Figure 5,
図6に示すような、増幅素子を接合型FET、或いはM As shown in FIG. 6, the amplifier element junction FET, or M
OS型FETに変更して構成したコルピッツ発振回路においても、振動子の一端を電源ラインを介して接地する回路構成であってもよく、同様の効果を得ることは当業者にとって周知事項である。 Also in the Colpitts oscillation circuit configured to change the OS type FET, may be a circuit configuration for grounding the one end of the vibrator via the power line, to obtain the same effects it is well known matter to those skilled in the art.

【0015】 [0015]

【発明の効果】本発明は以上説明した如く圧電振動子の一方端を電源ラインを介して接地するよう構成するものであるから、起動の安定したコルピッツ発振回路を得る上で著しい効果を発揮する。 Since the present invention is to configured to ground through the power line to one end of the piezoelectric vibrator as described above, it exhibits a remarkable effect in obtaining a stable Colpitts oscillation circuit of the boot .

【図面の簡単な説明】 BRIEF DESCRIPTION OF THE DRAWINGS

【図1】本発明に係わるコルピッツ発振回路を示す回路図。 Circuit diagram showing a Colpitts oscillation circuit according to the present invention; FIG.

【図2】コルピッツ発振回路の起動状態を示す回路図。 2 is a circuit diagram showing the activation status of the Colpitts oscillation circuit.

【図3】本発明をカスコード形コルピッツ発振回路に適用した回路図。 Circuit diagram applied to the cascode type Colpitts oscillation circuit to the invention, FIG.

【図4】本発明をオーバートーン発振回路に適用した回路図。 Circuit diagram applied to overtone oscillation circuit to the invention; FIG.

【図5】本発明に係わる増幅素子を接合型FETに適用した回路図。 Circuit diagram including a amplifying element junction FET according to the present invention; FIG.

【図6】本発明に係わる増幅素子をMOS型FETに適用した回路図。 Circuit diagram including a amplifier element in a MOS FET according to the present invention; FIG.

【図7】従来のコルピッツ発振回路を示す回路図。 Figure 7 is a circuit diagram showing a conventional Colpitts oscillation circuit.

【符号の説明】 DESCRIPTION OF SYMBOLS

A 、C B 、C C 、C D ……コンデンサ C S ……可変コンデンサ R A 、R B 、R C 、R E ……抵抗 X A ……振動子 V CC ……電源端子 C A, C B, C C , C D ...... capacitor C S ...... variable capacitor R A, R B, R C , R E ...... resistance X A ...... vibrator V CC ...... supply terminal

Claims (4)

    【特許請求の範囲】 [The claims]
  1. 【請求項1】 圧電振動子と増幅素子と負荷容量の一部となるコンデンサ等からなるコルピッツ発振回路において、圧電振動子の一方端を電源ラインを介して接地したことを特徴とするコルピッツ発振回路。 1. A Colpitts oscillation circuit composed of a capacitor or the like to be a part of the piezoelectric vibrator and the amplifying element load capacitance, Colpitts oscillation circuit, characterized in that one end of the piezoelectric vibrator is grounded via the power line .
  2. 【請求項2】 トランジスタのベースとエミッタ間にコンデンサC Aを、エミッタと接地間にコンデンサC Bと抵抗R Eを、ベースと電源ライン間に水晶振動子を挿入すると共に、トランジスタに所要のバイアス電圧を与えるよう構成したことを特徴とする請求項1記載のコルピッツ発振回路。 2. A capacitor C A between the base and emitter of the transistor, the capacitor C B and a resistor R E between the emitter and the ground, is inserted a crystal oscillator between the base and the power supply line, the required bias to the transistor Colpitts oscillation circuit according to claim 1, characterized by being configured to provide a voltage.
  3. 【請求項3】 接合型FETのゲートとソース間にコンデンサC Aを、ソースと接地間にコンデンサC Bと抵抗R Sを、ゲートと電源ライン間に水晶振動子を挿入すると共に、接合型FETに所要のバイアス電圧を与えるよう構成したことを特徴とする請求項1記載のコルピッツ発振回路。 The capacitor C A between the gate and source of 3. A junction FET, a capacitor C B and a resistor R S between ground and the source, is inserted a crystal oscillator between the gate and the power supply line, junction FET Colpitts oscillation circuit according to claim 1, characterized by being configured to provide a required bias voltage.
  4. 【請求項4】 MOS型FETのゲートとソース間にコンデンサC Aを、ソースと接地間にコンデンサC Bと抵抗R Sを、ゲートと電源ライン間に水晶振動子を挿入すると共に、MOS型FETに所要のバイアス電圧を与えるよう構成したことを特徴とする請求項1記載のコルピッツ発振回路。 The capacitor C A between the gate and source of the 4. A MOS-type FET, a capacitor C B and a resistor R S between ground and the source, is inserted a crystal oscillator between the gate and the power supply line, the MOS FET Colpitts oscillation circuit according to claim 1, characterized by being configured to provide a required bias voltage.
JP05101796A 1996-02-14 1996-02-14 Colpitts oscillator circuit Expired - Lifetime JP3322791B2 (en)

Priority Applications (1)

Application Number Priority Date Filing Date Title
JP05101796A JP3322791B2 (en) 1996-02-14 1996-02-14 Colpitts oscillator circuit

Applications Claiming Priority (1)

Application Number Priority Date Filing Date Title
JP05101796A JP3322791B2 (en) 1996-02-14 1996-02-14 Colpitts oscillator circuit

Publications (2)

Publication Number Publication Date
JPH09223930A true JPH09223930A (en) 1997-08-26
JP3322791B2 JP3322791B2 (en) 2002-09-09

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JP05101796A Expired - Lifetime JP3322791B2 (en) 1996-02-14 1996-02-14 Colpitts oscillator circuit

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Cited By (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
WO1999049566A1 (en) * 1998-03-25 1999-09-30 Rohm Co., Ltd. Oscillation circuit
US6496695B1 (en) 1998-07-27 2002-12-17 Hitchi, Ltd. Resource-saving event-driven monitoring system and method
WO2004042914A1 (en) * 2002-11-07 2004-05-21 Niigata Seimitsu Co., Ltd. Crystal oscillator and semiconductor device
CN1312844C (en) * 2003-02-18 2007-04-25 株式会社村田制作所 Oscillator and high-frequency superposing module for driving laser diode

Cited By (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
WO1999049566A1 (en) * 1998-03-25 1999-09-30 Rohm Co., Ltd. Oscillation circuit
US6496695B1 (en) 1998-07-27 2002-12-17 Hitchi, Ltd. Resource-saving event-driven monitoring system and method
WO2004042914A1 (en) * 2002-11-07 2004-05-21 Niigata Seimitsu Co., Ltd. Crystal oscillator and semiconductor device
CN1312844C (en) * 2003-02-18 2007-04-25 株式会社村田制作所 Oscillator and high-frequency superposing module for driving laser diode

Also Published As

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