JPH02275993A - Device and method for musical sound waveform generation - Google Patents

Abstract

PURPOSE:To compose various musical sounds by setting a carrier signal so that a musical sound wave is a single-frequency sine or cosine wave when a mixing control means controls the mixing rate of a modulated signal to the carrier signal to 0. CONSTITUTION:The characteristics of the carrier signal from a carrier signal generation part 101 are set so that when the mixing control part 104 controls the mixing rate of the modulated signal to 0, the musical sound waveform generated by a waveform output part 106 is the single-frequency sine or cosine wave. Consequently, the mixing control part 104 sets the mixing rate of the modulated signal to 0 in advance and then the musical sound waveform consisting of only the single-frequency sine or cosine wave can be generated and a complicate musical sound waveform can be generated with the simple circuit constitution.

Description

[Detailed Description of the Invention] [Industrial Application Field] The present invention relates to a musical sound waveform generator for an electronic musical instrument,
More specifically, the present invention relates to a musical sound waveform generating device and a musical sound waveform generating method that performs modulation to generate a musical sound waveform containing many high-order overtone components.

In addition, the present invention relates to a tone waveform generation device and a tone waveform generation method that control the characteristics of a tone waveform based on performance information generated in response to a performance operation.

The present invention also relates to a musical sound waveform generating device and a musical sound waveform generating method that generate a modulated waveform signal in multiple stages and generate musical sound waveforms using arbitrary connection combinations.

Furthermore, the present invention relates to a musical sound waveform generation method and a musical sound waveform generating method for generating a musical sound waveform containing many high-order overtone components in stereo by performing modulation.

[Prior art and problems to be solved by the invention] The first conventional example of an electronic musical instrument capable of digitally generating musical sound waveforms with various types of complex characteristics was disclosed in Japanese Patent Publication No. 54-3352.
There are electronic musical instruments based on the FM system described in Japanese Patent Application Laid-Open No. 50-126406 and the like.

This method basically uses the waveform output e obtained by the following calculation formula as a musical sound waveform, and the carrier wave frequency ω. and the modulation wave frequency ω for modulating it are selected in an appropriate ratio, a modulation depth function 1(t) that can change over time is set, and an amplitude coefficient A that can also change over time is set. By setting , it is possible to synthesize musical tones that have complex overtone characteristics and whose overtone characteristics can change over time. In addition to synthesizing musical tones that are close to the musical tones of actual instruments, it is also possible to synthesize musical tones that have complex overtone characteristics and whose overtone characteristics can change over time. It is also possible to obtain unique synthesized sounds.

Furthermore, as a second conventional system that is an improvement on the FM system, there is an electronic musical instrument described in Japanese Patent Publication No. 12279/1983. This method uses triangular wave operation instead of the sine operation in equation (1), and e=A−T (α+I(t) T (θ) )
. . . The waveform output e obtained by the arithmetic expression (2) is used as a musical sound waveform. Here, T(θ) is a triangular wave function generated by the modulated wave phase angle θ.

Then, by advancing the carrier wave phase angle α and the modulating wave phase angle θ at an appropriate speed ratio, and setting the modulation depth function r(t) and amplitude coefficient A in the same way as in the first conventional example, musical tones can be produced. Waveforms can be synthesized.

Here, in addition to the fundamental wave component based on the pinch frequency, the musical tone of an actual musical instrument such as a piano includes overtone components of a plurality of frequencies that are integral multiples of the fundamental wave component, and even considerably high-order overtone components exist. Furthermore, overtone components of non-integer multiples may be included. These overtone components generate rich musical tones. In addition, in the musical sound of an actual musical instrument, in the process of the musical sound gradually attenuating after it starts to sound,
The amplitude of the harmonic components decreases in order from higher order harmonics, and eventually only a single sine tonnage component corresponding to the pinch frequency may remain. Furthermore, there are musical tones that originally contain only a single sine wave component.

Since the first conventional example is based on modulation using a sine wave, by making the value of the modulation depth function Bt in equation (1) approach 0 with time, as in the case of the actual musical tone, It is possible to realize the process in which a musical tone is attenuated into only a single sine wave component, or the generation of a musical tone consisting only of a single sine wave component. However, the frequency components of the musical tones generated in (1) 2 are concentrated in low-order (low-frequency) overtone components, and even if the modulation depth function 1 (t) is set to a large value and deeply modulated, High-order (high-frequency) harmonic components do not appear well. Therefore, the first conventional example has a problem in that it is not possible to generate musical tones with a rich quality similar to actual musical tones, and the quality of musical tones that can be generated is limited.

On the other hand, the second conventional example based on equation (2) above is based on modulation using a triangular wave that originally contains many harmonics, so it is easy to easily reproduce musical tones that clearly have high-order harmonic components as frequency components. It is possible to generate However, on the other hand, because Equation (2) does not include the term for a single sine wave component, the process in which a musical tone attenuates into only a single sine wave component, as in an actual musical tone, or The problem is that it is not possible to generate a musical tone consisting of only a single sine wave component.

On the other hand, in general, with acoustic instruments such as pianos, if you press the keys quickly, you can generate a hard sound that contains many high-order harmonic components, whereas if you press the keys very slowly, the sounds contain almost only a single sine wave component. It is possible to generate soft and mysterious musical tones.

However, when attempting to realize a keyboard instrument having the above effects using the first conventional example, as described above, the above (1)
) High-order harmonic components do not appear well in the musical tones generated by the formula. As a result, even if the value of the modulation depth function 1 (t) is controlled to be a large value during fast key presses, there is a limit to the level of high-order harmonic components that can be generated, and the The problem is that it is not possible to generate musical tones rich in high-order overtones.

On the other hand, if an attempt was made to realize a keyboard instrument having the above-mentioned effect using the second conventional example, it would be impossible to produce a musical tone consisting only of a single sine wave component. At the time of key operation, the modulation depth function 1 (t,
) is controlled to a small value (for example, 0), it cannot be controlled so that only a single sine wave component is generated, and only a single sine wave component is generated in response to the playing operation. The problem is that it is not possible to generate a soft musical tone consisting of.

Furthermore, in the first or second conventional example, the above (1)
It may not be possible to obtain a waveform with sufficient frequency characteristics by performing calculations such as the expression or (2) once to obtain the waveform output e. For this reason, these calculations are executed multiple times with predetermined connection combinations, and the equation (1) or the equation (2)
I (t) sin ωml, or I (t) in the formula
There is a conventional technique in which a musical sound waveform with a more complex overtone structure can be synthesized by inputting the waveform output e obtained in the previous calculation instead of T (θ). For example, there is an electronic musical instrument described in Japanese Unexamined Patent Publication No. 58-211789.

However, when the first conventional example is applied to the above-mentioned conventional technique in which waveform output calculation based on modulation is executed multiple times using a predetermined connection combination, a fairly complicated connection combination is required to obtain sufficient overtone components. I need. As mentioned above, this is
This is because the first conventional example is difficult to generate high-order overtone components. Therefore, for example, when applied to a low-priced electronic musical instrument where the above connection combinations are limited, it is not possible to generate rich musical tones like actual musical tones, and the sound quality of the musical tones that can be generated is limited. This has the problem that it may be lost.

On the other hand, when the second conventional example is applied to the above-mentioned conventional technique in which waveform output calculation based on modulation is executed multiple times using a predetermined connection combination, even a relatively simple connection combination is sufficient. There is an advantage that overtone components can be obtained. However, on the other hand, it is not possible to obtain a sine wave synthesized sound such as the musical tone of a Hammond organ, in which a waveform output of only a single sine wave component or a plurality of waveform outputs of single sine wave components with different frequencies are mixed in parallel. First, there is still a problem in that the quality of musical tones that can be generated is limited.

As described above, in the conventional technology in which a waveform output calculation based on modulation is executed multiple times using a predetermined connection combination, the modulation method is not particularly limited, and as a result, the first musical waveform generation method is simply applied. It is easy to synthesize musical tones such as a single sine wave component, but it is not possible to obtain sufficient overtone components with simple connection combinations. However, although sufficient overtone components can be obtained, it is difficult to synthesize musical tones such as single sine wave components.

As a result, when musical tones are generated based on the above combination technique without particularly limiting the modulation method, for example, immediately after the start of sound generation, it contains abundant harmonic components, but as time passes, it gradually changes to include only single sine wave components. The problem is that musical sound waveforms that can be synthesized cannot be obtained by simple connection combinations, and the quality of musical sounds that can be synthesized, for example, in low-cost electronic musical instruments is limited.

Further, since the frequency composition of each higher-order overtone often differs depending on the type of musical instrument, it is desirable to be able to generate musical tones with various overtone compositions. However, in the first conventional example,
Since the sine wave is driven by a sine wave, it is only possible to generate musical tones with harmonic characteristics that can be generated as a combination of these waves.Moreover, as mentioned above, it is difficult to generate high-order harmonics in the first place, so the tones that can be supported are limited. There is a problem with this. On the other hand, in the second conventional example, since the triangular wave is used to drive the triangular wave, it is possible to generate only musical tones with harmonic characteristics that can be generated as a combination of the triangular waves, and the types of musical tones that can be generated are limited. It has points.

Apart from the various problems mentioned above, in order to produce a stereo effect in the modulation type musical waveform generator as described above, conventionally, the musical sound signal is delayed using a delay element such as a BBD or RAM, and the delay time is By controlling each stereo channel independently, stereo musical sound signals for the left channel and right channel are generated to obtain a stereo effect.

However, the conventional example described above has a problem in that a delay device is required in addition to the normal musical tone generating device in order to obtain a stereo effect, which increases the cost of the entire device.

An object of the present invention is to make it possible to generate musical tones that include even high-order harmonic components, and to also enable the synthesis of various musical tones consisting only of a single sine wave component or a single cosine wave component. .

Another object of the present invention is to make it possible to control the characteristics of musical tones at that time based on performance information generated in response to performance operations.

Furthermore, when generating musical waveforms by performing waveform output calculations based on modulation multiple times with a predetermined connection combination, even a simple connection combination can generate a single sound from a musical tone that is rich in high-order harmonic components. To easily synthesize musical tones containing only sine wave components or cosine wave components to musical tones in which a plurality of single sine wave components or cosine wave components having different frequencies are mixed.

In addition, it is possible to easily obtain a stereo effect in musical tone synthesis based on modulation type.

[Means and effects for solving the problem] According to the first aspect of the present invention, a musical sound waveform generating device that generates a musical sound waveform based on a mixed signal obtained by mixing a modulation signal with a carrier signal has the following features. It has a configuration.

First, it has a carrier signal generating section that generates a carrier signal. The generator is a circuit that receives as input a carrier wave phase angle signal in which the phase angle repeats an operation in which the phase angle linearly increases sequentially over time, for example, and converts it according to a certain function and outputs it as a carrier signal. Yes, it is composed of a ROM or the like that receives a carrier wave phase angle signal as an address input. Note that the characteristics of the output carrier signal will be described later.

Next, it has a modulation signal generation section that generates a modulation signal. The generator receives as input a modulated wave phase angle signal in which the phase angle repeats an operation in which the phase angle sequentially increases linearly over time, for example, and converts it according to a certain function to generate a sine wave, a rectangular wave, This is a circuit that outputs a modulated signal such as a sawtooth wave, for example, an R circuit that uses a modulated wave phase angle signal as an address input.
It is composed of OM etc.

Further, the modulated signal is mixed with a carrier signal generated from a carrier signal generator to output a mixed signal, and the mixing ratio of the modulated signal to the carrier signal in this case is controlled between 0 and an arbitrary mixing ratio. It has a mixing control section. The control unit includes, for example, a multiplier that multiplies the modulation signal output from the modulation signal generation unit by a modulation depth value whose value can vary between 0 and 1 according to a predetermined modulation depth function; This is an adder that adds the output signal of the device and the carrier signal generated from the carrier signal generator and outputs the result as a mixed signal.

Note that a mixing rate control section may be included that controls the mixing rate so that it can change over time after the start of the tone waveform. In this case, for example, for the modulation depth value to be multiplied by the multiplier, a different modulation depth value is calculated from a predetermined modulation depth function every time that elapses after the start of sound generation of the musical waveform, and is multiplied by the multiplier.

Furthermore, it has a waveform output section whose input and output have a predetermined functional relationship and outputs a musical waveform by inputting the mixed signal output from the mixing control section. The output section is, for example, a decoder that converts the mixed signal according to a predetermined functional relationship and outputs it as a musical sound waveform.

Alternatively, it is a ROM etc. that uses a mixed signal as an address input.

In the above configuration, the predetermined functional relationship in the waveform output section is neither a sine function nor a cosine function, and the carrier signal generated from the carrier signal generation section is controlled by the mixing ratio of the modulated signal in the mixing control section. This is a signal that is set so that when the waveform output section is controlled so that the waveform output section has a sine wave or a cosine wave, the musical waveform generated from the waveform output section becomes a sine wave or a cosine wave of a single frequency.

Specifically, the carrier signal generator generates a carrier wave phase angle ω that increases at a constant angular velocity over time. For example, with t [rad) as input, the carrier signal Wc(rad) shown in the following equation
Output.

Here, π indicates pi and sin indicates sine wave calculation.

In this case, the waveform output section receives the mixed signal X as input and outputs a musical sound waveform based on the following equation.

In the above-described first aspect, it is possible to include an amplitude envelope control section that temporally changes the amplitude envelope characteristic of the musical tone waveform output from the waveform output section.

For example, the control section multiplies the musical sound waveform output from the waveform output section by an amplitude coefficient whose value can change over time, for example between 0 and 1, according to a predetermined amplitude envelope function after the musical sound waveform starts producing sound. It is a multiplier that performs

Further, the carrier signal generation section, modulation signal generation section, mixing control section, and waveform output section perform processing on a plurality of sound generation channels in a time-division manner, and generate a plurality of musical sound waveforms assigned corresponding to each sound generation channel. may be output polyphonically.

According to the above-described first aspect, the musical waveform output from the waveform output section basically has characteristics obtained by converting the carrier signal output from the carrier signal generation section according to a predetermined functional relationship, and further, By mixing the modulation signal with the carrier signal in the mixing control section, a characteristic that the musical sound waveform is modulated by the modulation signal is added.

As a result, harmonic components can be added as frequency characteristics of the musical sound waveform, and musical tones that are close to the musical tones of an actual musical instrument can be synthesized, as well as unique synthesized tones etc. can be obtained.

In particular, by setting a functional relationship other than the sine function and cosine function as the predetermined functional relationship in the waveform output section,
It is possible to include more high-order overtone components in the output musical sound waveform.

Furthermore, by allowing the mixing control section to arbitrarily change the mixing ratio of the modulation signal to the carrier signal, musical sound waveforms having various frequency characteristics can be generated.

In this case, by not only setting the mixing ratio before the start of the performance, but also changing it over time after the start of sound generation of the musical sound waveform, it is possible to gradually change the frequency characteristics of the musical sound waveform immediately after the start of sound generation.

In particular, in the present invention, when the characteristics of the carrier signal from the carrier signal generating section are controlled by the mixing control section so that the mixing rate of the modulated signal becomes 0, the musical waveform generated from the waveform output section has a single frequency. Set it so that it becomes a sine wave or cosine wave. This allows the mixing control section to set the mixing rate of the modulation signal to 0 in advance.
If set to , it is possible to generate a musical sound waveform consisting only of a sine wave or a cosine wave of a single frequency. Alternatively, during a performance, for example, by setting the mixing ratio to a high value immediately after the start of a musical tone, and then increasing the mixing ratio to O as time passes, the single sine wave component can be changed from a state containing many high-order harmonics to a single sine wave component. Alternatively, the frequency characteristics of the musical sound waveform can be gradually controlled so that it contains only a single cosine wave component. In this way, it is possible to realize a process similar to the musical tones of an actual musical instrument (after the start of sound generation, the amplitude of high-order harmonic components gradually decreases until only a single sine wave component remains). .

In addition to the above operation, the amplitude envelope characteristic of the musical waveform output from the waveform output section is also controlled by the amplitude envelope control section so as to attenuate over time, so that sound generation starts like the musical tone of an actual musical instrument. Thereafter, it is possible to realize a process in which the musical sound waveform gradually attenuates.

As described above, in the first aspect of the present invention, both a state containing many high-order harmonics and a state containing only a single sine wave component or a single cosine wave component can be easily generated. ,
This can be achieved using only a combination of ordinary ROMs, decoders, adders, multipliers, etc., making it possible to realize complex musical waveforms with a simple circuit configuration, resulting in improved quality. It becomes possible to provide high-quality electronic musical instruments and the like at a low cost.

Note that the predetermined functional relationship in the waveform output means is such that when the mixing ratio is a predetermined value and the waveform shapes of the carrier signal and the modulation signal are specific shapes, a sine wave or cosine wave of a single frequency is generated by the waveform output means. may be determined to be generated from.

Next, a second aspect of the present invention will be explained. This aspect is based on a tone waveform generator of a modulation type similar to that of the first aspect, and of a type that controls the characteristics of a tone waveform based on performance information generated in response to a performance operation. For example, in the case of a keyboard instrument, the performance information in this case includes pitch information indicating which key was pressed, herosity information indicating the speed at which the key was pressed, and aftertouch information indicating the key pressure after the key was pressed. Alternatively, it is key range information indicating which key range of the keyboard was pressed.

The second embodiment has a carrier signal generating section and a modulating signal generating section similar to those in the first aspect, but these generating sections each generate a carrier signal or a modulating signal in accordance with performance information. in this case,
For example, the period of the carrier wave phase angle signal is determined to correspond to, for example, pitch information, and the period of the modulated wave phase angle signal has a predetermined ratio to the carrier wave phase angle signal generated based on, for example, the pitch information. It is determined as follows.

Further, the mixing control section is also the same as in the first aspect, but the mixing ratio in this case is also controlled to change according to the mixing characteristics corresponding to the performance information. In this case, similar to the first aspect, the modulation depth value of the modulation depth function and its degree of change over time are controlled in accordance with the performance information.

Furthermore, it has a waveform output section similar to the first aspect.

The second aspect described above can be configured to have the same amplitude envelope control section as the first aspect, and in this case, for example, the same amplitude coefficient and the degree of change over time as in the first aspect, City II according to the above performance information? Wholesale.

Further, similar to the first aspect, it can be configured to output polyphonic musical sound waveforms.

According to the second aspect of Section 2, in addition to the features of the first aspect, the mixing characteristics in the mixing control section are not only set before the start of the performance, but also performance information such as velocity information or key range information, etc. By changing the frequency characteristics in accordance with the performance operation, it is possible to change the frequency characteristics of the musical sound waveform in accordance with the performance operation. In particular, by controlling the mixing characteristics, it is possible to control each amplitude value of the overtone component determined by the carrier signal and the modulation signal.

As a result, during a performance, for example, if the mixing ratio is set to a high value when the key is pressed strongly, and conversely, when the mixing ratio is set to be close to 0 when the key is pressed weakly, the high-order States containing many overtones and states containing only a single sine wave component or a single cosine wave component can be arbitrarily generated. It is also possible to control the frequency characteristics of a musical sound waveform to change over time by changing the mixing ratio over time, and also control the degree of change over time of the mixing ratio according to performance information. Then, the temporal change characteristics of the frequency characteristics of the musical sound waveform can also be varied in accordance with the performance operation.

As described above, in the second aspect of the present invention, it is possible to easily generate both a state containing many high-order harmonics and a state containing only a single sine wave component or a single cosine wave component, and
The state can be arbitrarily varied according to the performance operation.

Next, a third aspect of the present invention will be explained. This aspect assumes a modulation type musical waveform generator similar to the first aspect.

In the third aspect, first, a carrier signal generating section that generates a carrier signal, a mixed signal output section that mixes a modulation signal with the carrier signal and outputs a mixed signal, and inputs and outputs have a predetermined functional relationship. and an amplitude envelope characteristic control section that controls temporal amplitude envelope characteristics of the waveform signal output from the waveform output section that receives the mixed signal outputted by the mixed signal output section as input and outputs a waveform signal. It has at least one basic processing unit as a basic configuration.

Here, the carrier signal generation section and the modulation signal generation section are the same as those in the first embodiment, and when there is no modulation signal input to the mixed signal output section (when the value is O), the carrier signal generation section and the modulation signal generation section are The predetermined functional relationship is the same as in the case where the mixing ratio in the mixing control section of the first aspect is set to 0. Therefore,
The above-mentioned basic processing unit is a single unit, and similarly to the first aspect,
It is possible to easily generate musical sound waveforms ranging from a musical sound waveform consisting only of a sine wave or cosine wave of a single frequency to a musical sound waveform containing many high-order harmonic components.

In a third aspect, based on the basic processing unit, a first connection inputs a modulated signal having a value of 0 or a value near 0 to one basic processing unit, or converts another waveform signal into a new modulated signal. A second connection that is input to one basic processing unit as an input, or a new waveform signal is generated by mixing the waveform signal obtained by one basic processing unit with each waveform signal obtained by at least one other basic processing unit. It has a waveform input/output control section that connects the basic processing section by combining the obtained third connections based on a preset connection combination and outputs the waveform signal output from the final stage as a musical sound waveform.

Thereby, by making the first connection, a waveform signal consisting only of a single sine wave or a cosine wave can be generated. Furthermore, if the second connection is made, the modulated waveform signal is used as the next modulated waveform, so it is possible to generate a very deeply modulated waveform signal. Furthermore, by performing the third connection, a waveform signal in which waveform signals containing different overtone components are mixed can be obtained. By combining these connections to finally obtain a tone waveform, it is possible to generate a tone waveform with extremely complex characteristics.

In particular, in the present invention, sufficient overtone components can be obtained even with simple connection combinations, and musical waveforms of only a single sine wave component or a single cosine wave component can also be easily obtained.

In the third aspect described above, instead of the configuration in which a plurality of basic processing units are connected, a configuration in which one basic processing unit is operated in a time-sharing manner may be adopted.

In this case, instead of the above-mentioned waveform input/output control section, multiple processing timings are set as one calculation period, and the modulation signal input is set to the value O or a value near 0 for each processing timing within the calculation period, and basic processing is performed. The basic processing section is operated to obtain a new waveform signal by using the waveform signal obtained at a processing timing earlier than the current processing timing as a new modulation signal input. second operation,
or a third operation of performing an operation similar to the first or second operation to obtain a waveform signal and mixing it with each waveform signal obtained at at least one processing timing before the current processing timing, It has a waveform input/output control section that performs execution based on a preset connection combination and generates a waveform signal obtained at the last processing timing in each calculation cycle as a musical sound waveform for that calculation cycle. The control unit includes, for example, first and second accumulating units and a first accumulating unit that selectively inputs the waveform signal output from the basic processing unit to the first or second accumulating unit.
a second switch unit that selectively inputs the value O or a value near 0 or the output of the second accumulation unit as a modulation signal to the basic processing unit; And for each processing timing within each calculation cycle,
By controlling the accumulation operation in the first and second accumulation sections and the selection operation of the first and second switch sections based on a preset connection combination, a multistage operation control unit that operates the processing unit in multiple stages;
and a tone waveform output section that outputs the output of the first accumulation section as a tone waveform of the operation cycle at the end of each operation cycle. Note that the calculation period corresponds to, for example, the sampling period.

With the above configuration, it is possible to obtain the same effects as in the above case using one basic processing unit, reduce the circuit scale, and realize a configuration with a high degree of freedom in connection combinations.

Next, a fourth aspect of the present invention will be explained. The basic configuration of this aspect is the same as that of the third aspect, and further includes the following configuration.

First, in the third aspect, a setting section is provided for allowing the user to set a connection combination that should be set in advance. The setting unit may, for example, tell the user the input/output relationship in the waveform output unit between each processing timing in the third aspect.
The above-mentioned connection combinations are set by setting using symbolic arithmetic expressions.

Next, it has a display section that displays the connection combinations set by the setting section. The display section displays the connection combinations set by the setting section, for example, by displaying a symbolic arithmetic expression similar to the above-described setting section. Alternatively, the display section may group the basic processing sections for each processing timing into one unit, and display the connection combination set by the setting section as the connection relationship between the units.

According to the fourth aspect described above, the user (performer) can efficiently set connection combinations in the musical sound waveform generator of the third aspect, and can display this in an easy-to-understand format. Therefore, it is possible to realize a musical sound waveform generator with very good operability.

Next, a fifth aspect of the present invention will be explained.

The basic configuration of this aspect is the same as that of the third aspect, but the waveform input/output control section operates in a slightly different manner.

That is, the waveform input/output control section performs the first, second, or third calculation in the third aspect on a preset connection combination that changes over time after the start of sound generation of each musical sound waveform. This generates a musical sound waveform.

According to the fifth aspect described above, for example, the sound can be changed from a connection combination that can generate a musical sound waveform containing a large number of high-order harmonic components to a connection combination that can generate a musical sound waveform that contains only a single sine wave or cosine wave component. Since it can be automatically changed midway through, it is possible to perform a very wide range of pronunciation operations.

Next, a sixth aspect of the present invention will be explained. The basic configuration of this aspect is also the same as that of the third aspect, but in the sixth aspect, the waveform input/output control section performs processing on a plurality of sound generation channels in a time-sharing manner, and corresponds to each sound generation channel. Outputs multiple musical waveforms assigned as polyphonic.

According to the sixth aspect described above, the operation based on the third aspect can be realized polyphonically.

Next, a seventh aspect of the present invention will be explained. This aspect assumes a modulation type musical waveform generator similar to the first aspect.

The seventh aspect first has a basic processing section similar to the third aspect. That is, the processing unit includes a carrier signal generating unit that generates a carrier signal, a carrier signal generating unit that mixes a modulated signal with the carrier signal, outputs a mixed signal, and adjusts the mixing ratio of the modulated signal to the carrier signal from 0 to an arbitrary mixing ratio. a basic processing unit that includes a mixing control unit that controls between the above and , the basic configuration is multiple lines.

Here, the carrier signal generation section and the modulation signal generation section are the same as those in the first embodiment, and the predetermined functional relationship with the carrier signal when the mixing rate of the modulation signal in the mixing control section is 0. , is the same as in the first aspect. Therefore, just like the first aspect, the above-mentioned basic processing section can easily produce musical sound waves ranging from a musical sound wave consisting of only a sine wave or a cosine wave of a single frequency to a musical sound wave including many high-order harmonic components. can be generated.

In a seventh aspect, based on the basic processing unit, the first connection inputs a modulated signal having a value of 0 or a value near 0 to one basic processing unit, or converts another waveform signal into a new modulated signal. A second connection that is input to one basic processing unit as an input, or a new waveform signal is generated by mixing the waveform signal obtained by one basic processing unit with each waveform signal obtained by at least one other basic processing unit. or a fourth connection in which the modulated signal input to one basic processing unit is a signal obtained by feeding back the waveform signal obtained by the basic processing unit, based on a preset connection combination. By combining a plurality of basic processing sections, a waveform input/output control section is provided which connects a plurality of basic processing sections and outputs the waveform signal output from the final stage as a musical sound waveform.

The seventh aspect described above differs from the third aspect described above in the following points:
This point includes a fourth connection in which the modulation signal input to the two basic processing sections is a signal obtained by feed-packing the waveform signal obtained by the basic processing section. By including such a connection, the amplitude envelope characteristics of the overtone components of the musical tone waveform can be made unique, and a characteristic musical tone waveform can be generated.

In particular, as in the present invention, it is possible to obtain sufficient overtone components even with a simple connection combination, while also being applied to a configuration in which a musical sound waveform of only a single sine wave component or a single cosine wave component can be easily obtained. In this case, a great effect can be obtained.

Next, the eighth aspect of the present invention will be explained. In this aspect, the same basic processing unit as in the seventh aspect is executed in multiple lines.

In the eighth aspect, based on the basic processing unit, a connection is continuously made in multiple stages for inputting the waveform signal obtained in the previous basic processing unit to the current basic processing unit as a new modulation signal input, It has a waveform input/output control section that outputs the waveform signal obtained by the final stage basic processing section as a musical sound waveform and feeds it back as a modulation signal input to the first stage basic processing section.

The eighth aspect described above is different from the seventh aspect described above in that the basic processing unit that feeds and hacks the waveform signal to the modulation signal is
The point is that it is not the own basic processing unit, but the basic processing unit from some time ago. By including such a connection, the amplitude envelope characteristics of the harmonic components of the musical tone waveform can be made unique and different from the seventh aspect, and a characteristic musical tone waveform can be generated.

Next, a ninth aspect of the present invention will be explained. This aspect assumes a modulation type musical waveform generator similar to the first aspect.

First, it has a carrier signal generating section similar to the first aspect.

Next, it has a modulation signal generation section that selectively generates a plurality of types of modulation signals. This embodiment differs from the first embodiment in that a plurality of types of modulation signals can be generated. The generating section includes a storage section such as a ROM that stores in advance a plurality of types of modulation functions, and a selection section such as an addressing circuit that selects one of the plurality of types of modulation functions stored in the storage section. , a modulated wave phase angle signal in which the phase angle inputted from the outside repeats an operation in which the phase angle sequentially increases linearly with the passage of time during one cycle is converted by a modulation function selected by the selection section to obtain a modulated wave correction phase angle. The output section generates a signal and converts the modulated wave correction phase angle signal based on a triangular wave function to output a modulated signal such as a sine wave, a rectangular wave, or a sawtooth wave.

Next, the selectively generated modulated signal is mixed with the carrier signal generated from the carrier signal generator to output a mixed signal, and the mixing ratio of the modulated signal to the carrier signal is set from 0 to an arbitrary mixing ratio. It has a mixing control section that controls the mixing ratio. This configuration is similar to the first aspect.

It also has a waveform output section similar to that of the first embodiment.

The ninth aspect described above can be configured to have an amplitude envelope control section similar to the first aspect, and can also be configured to output polyphonic musical sound waveforms as in the first aspect.

In the above-described ninth aspect, since the modulation signal generation section can selectively generate a plurality of types of modulation signals, the mixing control section can vary the characteristics of the modulation signal mixed with the carrier signal. As a result, it becomes possible to output many types of musical sound waveforms having various overtone characteristics from the waveform output section.

Next, a tenth aspect of the present invention will be explained.

This aspect is a modulation type as shown in the first aspect,
A tone waveform generator that generates stereo tone waveforms is assumed.

That is, for example, a carrier signal generator similar to the first aspect,
It has a modulation signal generator. In addition, for example, a mixing section that mixes a modulated signal with a carrier signal generated from a carrier signal generating section and outputs a mixed signal, and a mixing ratio of the modulated signal to the carrier signal by the mixing section from 0 to an arbitrary mixing ratio. and a mixing ratio control section that changes the mixing ratio over time. □The combination of this mixing section and the mixing rate control section is the mixing control section in the first embodiment. Furthermore, it has a waveform output section similar to, for example, the first aspect.

In addition to the above configuration, in the tenth aspect, at least one of the carrier signal generation section, the modulation signal generation section, or the mixing rate control section
These are time-divisionally controlled so that different values are generated between each stereo channel, and based on this, the mixed signal for each stereo channel output from the mixer at each time-division timing is input to the waveform output section. Accordingly, it has a time division control section that outputs each musical sound waveform that is independently modulated for each stereo channel.

The tenth aspect described above can also be configured to include an amplitude envelope control section similar to the first aspect.

In this case, for example, the amplitude envelope characteristics of each musical sound waveform independently outputted from the waveform output section for each stereo channel are controlled so as to vary over time with mutually different characteristics between the stereo channels.

In addition, the carrier signal generation section, modulation signal generation section, mixing section, mixing rate control section, waveform output section, and time division control section time-divide each stereo channel into a plurality of sound generation channels and process them. It is also possible to configure a plurality of tone waveforms assigned to each sound generation channel to be output in stereo and polyphonically.

Currently, in a tone waveform generator using a modulation method that generates a tone waveform by converting a signal that is a mixture of a carrier signal and a modulation signal according to a predetermined functional relationship, it is possible to obtain a tone waveform with different characteristics by changing the modulation state. I can do it. In particular, a chorus effect can be added by converting the modulation signal into a low sine waveform of several Hz to several tens of Hz and mixing it with the carrier signal, and then performing function conversion based on the resulting mixed signal. A stereo effect can be obtained by obtaining a plurality of mixed signals with different mixing ratios, and simultaneously generating a plurality of musical sound waveforms generated based on the different mixed signals.

Therefore, in the above-mentioned tenth aspect, first, for example, the modulation signal, mixing rate, etc. are controlled independently for each stereo channel so that they are different from each other, and the carrier signal is made common, and each stereo By generating mixed signals for each channel and performing modulation based on these independently generated mixed signals, musical sound waveforms for each stereo channel can be easily obtained.

In addition, by arbitrarily setting the mixing ratio of the modulated signal to the carrier signal in the mixing ratio control section between 0 and other values in advance or over time, it is possible to change the mixing ratio from a state containing many high-order harmonics to a simple one. It is possible to freely control the generation up to a state that includes only one sine wave component or a single cosine wave component, and by doing so, it is possible to obtain musical sounds close to the musical sounds of actual musical instruments or unique synthesized sounds in stereo. be able to.

Next, an eleventh aspect of the present invention will be explained.

This aspect is based on a tone waveform generator of a modulation type similar to that of the first aspect, and of a type that controls the characteristics of a tone waveform based on performance information generated in response to a performance operation.

In addition to the first aspect, at least one of the carrier signal generated by the carrier signal generation section, the modulation signal generated by the modulation signal generation section, or the mixing ratio controlled by the mixing control section changes randomly. The random control section includes a random control section that controls the content of the random component to contain the component.

In this case, in particular, a great effect can be obtained by controlling the signal to include components that randomly change in a predetermined time interval after the start of the tone generation. Here, the predetermined time interval is, for example, an attack part, a decay part,
Either the steen section or the release section.

In the above eleventh aspect, the amplitude envelope random control means is configured to control the amplitude envelope characteristic of the musical sound waveform outputted from the waveform output means to include a component that changes randomly in a predetermined time interval after the start of sound generation of the musical tone. It may be configured to include.

In the above-mentioned eleventh aspect, it is possible to continuously generate musical sound waves having only a single sine wave or cosine wave component, which is a feature of the present invention, to musical tones having many overtone components, and at the same time,
Natural fluctuations can be added to the pitch, timbre, volume, etc. of the musical tones being produced. This makes it possible to achieve characteristics similar to the fluctuations of natural musical instruments.

Finally, the twelfth aspect of the present invention will be explained.

Similar to the second aspect, this aspect is based on a modulation type musical sound waveform generator that controls the characteristics of musical sound waveforms based on performance information generated in response to performance operations.

Further, it has a carrier signal generation section, a modulation signal generation section, a mixing control section, and a waveform output section similar to those of the first aspect or the second aspect.

The twelfth aspect differs from the second aspect in that instead of controlling the mixing ratio in the mixing control section based on performance information, the frequency ratio control section controls the frequency ratio of the carrier signal and the modulation signal. It is a point. The control section controls the frequency ratio, for example, using the tone of the musical waveform that is generated. Alternatively, if the performance operation is a key press operation on a keyboard, the frequency ratio control section controls the frequency ratio in accordance with at least one of the speed of the key press operation and the range of the pressed key.

According to the twelfth aspect, as in the second aspect, it is possible to change the frequency characteristics of the musical sound waveform according to the set tone, the key press operation, or the key range of the pressed key. especially,
By controlling the frequency ratio of the carrier signal and modulating signal,
It becomes possible to control the frequency structure of the harmonic components themselves. As a result, it becomes possible to add unique characteristics different from the second aspect to the musical sound waveform.

〔Example〕

Hereinafter, the present invention will be described in detail with reference to the drawings.

1 of 1 First, a first embodiment of the present invention will be described.

First, the principle of the first embodiment will be explained.

FIG. 1 shows the principle of the first embodiment.

The carrier wave phase angle ω, whose value sequentially increases linearly between O and 2π (rad), is used as the address of the carrier wave ROM10I to read out the carrier signal WC.

Here, the carrier wave phase angle ωct is the angular velocity ω. (rad/s
ec ) multiplied by time t (sec),
From now on, unless otherwise specified, 'ctJ will be collectively represented by a subscript.

Also, the modulated wave phase angle ω□, whose value sequentially increases linearly between O and 2π (rad), is the modulated wave ROM 102
The modulation signal read out is then multiplied by a modulation depth function r(t) [rad] that can change over time in a multiplier (hereinafter referred to as MUL) 103, so that A modulated signal WM is obtained. This modulated wave phase angle ω1 also has an angular velocity ω.

1: rad/sec ) multiplied by the time t [sec ]; unless otherwise specified, [, nLJ
are collectively represented by a subscript.

The modulated signal WM and the carrier signal WC are added by an adder (hereinafter referred to as ADD) 104, and the added waveform W
(+W, (rad) is further decoded by a decoder 105 to obtain a decoded output.

Then, it is multiplied by the amplitude coefficient A at the decode output terminal MUL 106 to obtain the final waveform output e.

In the musical sound waveform generator having the above configuration, first, the carrier wave R
The function waveform shown in FIG. 2 is stored in OMl0I. Now, let π be pi, and the carrier wave phase angle ω in each region I, ■, and ■ in the same figure. [rad] and carrier signal Wc[rad
], respectively, Wc = (π/2) si
n ωct... (Area ■: 0≦ω0.≦π/2) Wc
=rc-(π/2)sin ωct... (Area ■:
π/2≦ωct≦3π/2) Wc =2 π+ (π/
2) sin ωct... (area ■: 3π/2≦ωc
t≦2π) (3).

On the other hand, the modulated wave ROM 102 stores a normal sine function waveform. Therefore, the relationship between the modulated wave phase angle ωmt (rad) and the modulated signal W, (rad) after passing through the MUL 103 is WM = I (t) sin ωmt
H+ + (4).

The carrier signal Wc and the modulation signal WM calculated by the above equations (3) and (4) are added and input to the decoder 105, so that the decoder 105 outputs a decoded output, and furthermore, the M U L The waveform output e after being multiplied by the amplitude coefficient A in step 106 is e=A-TRI
((π/2) sin ωct··(5) where TRI(X) is defined as a triangular wave function.

Here, first, when the value of the modulation depth function J(t) is O1, that is, no modulation, the input waveform to the decoder 105 is (
3) The carrier signal W determined by the formula is itself. That is, e = A-TRI (Wc)...
- (6). Note that the carrier signal W and the carrier phase angle ω
From equation (3) above or from FIG. 2, cL is determined by the relationship A in FIG. 3.
It is indicated by.

On the other hand, the triangular wave function D calculated in the decoder 105
=TRI(X) (where X is the input) is the above (3
) is the carrier wave phase angle ω, which is the input in the equation.

Since the input X in the equation (7) always takes a value in the same interval, the equations (3), (6), and (7) can be combined in the same interval. That is, the above (3
) and (7) into the above equation (6), we get...
・(7) This is a function defined by the following and shown in relation B in FIG.

As can be seen from relationship A and relationship B in FIG.
The triangular wave function D=TRI(x) calculated in 05 is a monotonically increasing function in each region (■, ■, and ■) defined by the above formula (3) or (7), and is a monotonically increasing function.
(8) becomes. That is, when there is no modulation, the carrier phase angle ω. ,
A single sine wave A-sinωCL containing no high-order overtones is output for any region.

That is, for example, if the amplitude coefficient A=1, the relationship between the carrier wave phase angle ωct and the waveform output e when no modulation is performed becomes a single sine wave as shown in the relationship C in FIG. 3.

From the above relationship, in order to realize the process in which a musical tone attenuates into only a single sine wave component, or the generation of a musical tone consisting only of a single sine wave component, the modulation depth function must be calculated using equation (5) above. It can be seen that the value of I (t) should be brought closer to 0 with time.

Next, consider changes in the waveform output e when the value of the modulation depth function I(t) is increased. Modulation depth function I
When (L) is gradually increased from the value O, the addition waveform WC+WM output from ADD 104 in FIG.
, the modulation signal W? gradually changes from the carrier signal Wc only component.
As the component of I is superimposed, the waveform output e gradually becomes distorted on the time axis from a single sine wave, and changes to include many high-order overtone components on the frequency axis.

FIGS. 4(a) to (i) show the carrier wave phase angle ω. , −modulated wave phase angle ω, and under that condition the modulation depth function + (1)
A waveform diagram of the waveform output e when the value of is changed from 0 to 2π (rad) is shown. In addition, FIGS. 5(a) to (i) show the frequency characteristics (
power spectrum). In addition, in the same figure, hl indicates the fundamental frequency (pitch frequency), and h2, h3, h, I,
... is twice, three times, four times the fundamental frequency component, etc.
Indicates the higher harmonic frequency of.

As can be seen from FIGS. 4(a) to (i), as the value of the modulation depth function r(t) increases, sharp edges appear in the waveform output e. That is, it is expected that the waveform output e will include even considerably high-order overtone components.

This is clear from FIGS. 5(a) to 5(i). That is, it can be seen that as the value of the modulation depth function 1(t) increases, higher-order harmonic components of the 10th harmonic or higher appear. Moreover, the power of low-order harmonic components is not simply increased or decreased, but it is possible to obtain complex harmonic changes according to changes in I(t).

FIGS. 6(a) and (b) show the above (5) according to this embodiment.
and the above (by the FM method which is the first conventional example)
Using equation 1), a histogram (frequency distribution) of the frequency characteristics of each waveform output e synthesized under the same conditions is shown. From the figure, it can be seen that although the FM method cannot express high-order harmonic components of the 11th harmonic or higher, in this example, it is possible to express high-order harmonic components up to around the 30th harmonic. .

Based on the above facts, by changing the value of the modulation depth function 1 (t) between about O and 2π [rad] in the musical sound waveform generator shown in FIG. 1, as in the case of actual musical tones,
The process in which a musical tone attenuates into only a single sine wave component,
Alternatively, it is possible to generate a musical tone consisting only of a single sine wave component, and it is also possible to easily generate a musical tone in which even high-order overtone components clearly exist as frequency components. In particular, when synthesizing a musical tone with a low pitch, that is, when synthesizing a musical tone whose fundamental frequency (pitch frequency) h+ is low and may include many high-order harmonics in the audible frequency range, musical waveform generation according to this embodiment is useful. The device is very effective.

FIG. 7(a) shows the angular velocity ω of the carrier wave phase angle ω. The ratio of the modulating wave phase angle ω, to the angular velocity ω□ is ω. :ω.

-1:0.5, the change in the waveform output e when changing the value of the modulation depth function 1 (t) is also shown in the same figure (b).
,ωC:ω. = 1:16, the modulation depth function 1(t
) shows the waveform output e when the value is set to 0 and when it is set to an appropriate value. The conditions in (a) of the same figure are effective for synthesizing musical tones that include thick subharmonics (0,5 overtones) such as plus tones, and the conditions in (b) of the same figure are effective for synthesizing musical tones such as plus notes that contain thick subharmonics (0,5 harmonics), and conditions in (b) of the same figure are effective for synthesizing musical tones such as positive notes that contain thick subharmonics (0,5 harmonics). This is particularly effective when it is desired to output musical tone components in high-order harmonics such as 16th harmonics.

Also, by slightly shifting the ratio of ω0 and ω from the integer ratio (
By detuning) to obtain a chorus effect, or by setting the modulating wave phase angle ω, to a low frequency of several Hz to several tens of Hz, a similar chorus can be obtained by adding phase modulation to the carrier wave phase angle ωcl. effect or carrier phase angle ω
. , and the modulated wave phase angle ω1 to be a perfect non-integer ratio, it is also possible to simulate musical sounds such as chime sounds and drum sounds that include non-integer overtones.

In the principle configuration of the musical sound waveform generator described above, the above-mentioned (
For the decoder 105 having the characteristics shown in equation 7) or relationship B in FIG. 3, the waveform output e is a sine wave as shown in equation (3) or relationship A in FIG. By storing the carrier signal WC in the carrier wave ROM 101, it is possible to generate a single sine wave. However, the invention is not limited to this, and the decoder 105 may be used to calculate a function other than a single sine wave that originally contains harmonic components, and a function whose decoded output is a sine wave. A similar effect can also be obtained by storing it in the carrier wave ROM10I. (a) to (d) in Figure 8
The function and carrier wave ROM calculated by the decoder 105 are
An example of a combination of functions stored in 101 is shown.

In the figure, a function that relates the carrier wave phase angle ωct and the carrier signal WC is stored in the carrier wave ROMl0I, and the input
The decoder 105 is a function that relates the decoded output and
It is calculated by Further, the characteristics corresponding to FIGS. 8(a) to 8(d) are shown below.

First, corresponding to FIG. 8(a), the decoder 105 of FIG.
The function to be calculated is as follows.

D=1 (x/4□8-3 x/4)
D−−(4/π)x+4 ... (3π/4≦X≦5π/4) D″′″−' , , , (5, (/4s:) (<
□774) D-(4/π)X-8 ・ ・ ・ (7π/4≦X≦2π) ・ ・ ・ (9) Also, corresponding to FIG.
The functions stored in 01 are as follows.

WC= (π/4) sinωct... (0≦ωct≦π/2) WC=-(π/4) sinωct+π... (π/2≦ωct≦3π/2) WC= (π/
4) sinωct+2π... (3π/2≦ωct≦
2π) ...00) Next, corresponding to FIG. 8(b), the decoder 105 of FIG.
The function to be calculated is as follows.

0-1"2x ,...X < K / 4
) Also, corresponding to FIG. 8(C), the carrier wave ROM of FIG.
The functions stored in 101 are as follows.

Also, corresponding to FIG. 8(b), the carrier wave ROM1 in FIG.
The functions stored in 01 are as follows.

・ ・ ・04) Then, corresponding to FIG. 8(d), the decoder 10 of FIG.
The function calculated in 5 is as follows.

・ ・ ・θ2) Furthermore, corresponding to FIG. 8(C), the decoder 105 in FIG.
The function to be calculated is as follows.

・ ・ ・05) Also, corresponding to FIG. 8(d), the carrier wave ROM1 in FIG.
The functions stored in 01 are as follows.

Wc = (π/2) sin ωct+
2π・ ・ (3π/2≦ωct≦2π) ・ ・ ・00 or more, equations (9) and 00), equations (11) and 02), θ
By combining equation 3) and equation θ4, and equation θ and equation 06), the modulation depth function I(t
) is set to 0, by inputting the carrier signal Wc output from the carrier wave ROM10I as the input X to the decoder 105, a single sine wave can be output as the waveform output e. Also, Fig. 8(a) to (d)
With the function of the decoder 105 as shown in FIG. 1, if the value of the modulation depth function (1) is set to a value other than O, it is possible to obtain a waveform output e containing many high-order harmonics.

In addition, in each aspect regarding the principle configuration of the first embodiment, a sine function is stored in the modulated wave ROM 102 of FIG. However, it is not limited to this. For example, by storing waveforms containing high-order harmonics such as sawtooth waves and square waves as shown in FIGS. 9(a) to (C) and inputting these to the decoder 105, higher-order It is possible to synthesize musical sound waveforms containing many overtones. In addition, the modulated wave R
Instead of reading out the various waveforms mentioned above from the OM 102 to generate a modulated wave, it has a built-in logic circuit that directly generates a waveform containing high-order harmonics, or something similar to the decoder 105 in FIG. 1, and a ROM, etc. The circuit may be configured to generate a modulation signal containing higher-order harmonics by inputting various phase angle waveforms stored in the .

Furthermore, although the amplitude coefficient A multiplied by the MUL 106 in FIG. It is possible to add envelope characteristics.

Next, a specific configuration of the first embodiment based on the principle configuration of the first embodiment described above will be explained. This embodiment is an example in which the musical sound waveform generator according to the present invention is applied to an electronic musical instrument.

First, FIG. 10 is an overall configuration diagram of an electronic musical instrument according to a first embodiment. Since this embodiment is based on the basic configuration of the first embodiment shown in FIG. 1, the following explanation will be made with reference to FIG. 1 and the like from time to time.

The controller 1001 sets the carrier frequency CF, modulator frequency MF, and envelope information ED (each rate value of the envelope,
It is a means to generate and output level values, etc.).

The adder 1002 or 1004 connects each output to the addend terminal B.
The carrier frequency C is fed back to the addition terminal A.
By inputting F or modulator frequency MF, each I increases sequentially by the step width of each frequency.
Carrier phase angle ω for O bits.

0~ωct10 or modulated wave phase angle ω□0~ω,,,t1
It is an accumulator for generating 0. Here, the carrier wave phase angle ωCtO ~ ωCt10 and the modulation wave phase angle ω□tO ~ ω
110 are carrier wave phase angles ω in FIG. 1, respectively. , and the modulated wave phase angle ω1. Further, the carrier frequency CF is the angular velocity ωゎ of the carrier wave phase angle ωcl, and the modulator frequency MF is the angular velocity ω of the modulated wave phase angle ωI.

corresponds to

The carrier wave phase angle ωctO to ωct10 and the modulated wave phase angle ωmtO to ω, t10 are the carrier wave generation circuit 10, respectively.
03 and modulated wave generation circuit 1005 as each address signal. Note that the carrier wave generation circuit 1003 and the modulated wave generation circuit 1005 each correspond to the carrier wave ROM 10 in FIG.
1 and the modulated wave ROM 102.

On the other hand, based on the envelope information ED from the controller 1001, the enherobe generator 1006 generates a two-channel modulation depth function IO~110 of 11 bits and 10 bits and an amplitude coefficient AMPO~A from the terminals C and M.
Output MPIO. Note that these correspond to the modulation depth function r(t,) and the amplitude coefficient A of FIG. 1, respectively, and both can change over time.

The modulation depth functions IO to IIO take values of 1 or less, are input to terminal B of multiplier 1007, and are multiplied by the output from modulated wave generation circuit 1005 input to terminal A to produce 11-bit modulation signals WMO to W. Output M10.

Here, the multiplier 1007 and the modulation signal WMO~WM1
0 correspond to M U L 103 and modulation signal WM in FIG. 1, respectively.

Carrier signals WcO to Wc10 and modulation signals WMO to WM10 outputted from the carrier generation circuit 1003 and the multiplier 1007 are input to terminals A and B of an adder 1008, respectively, and added, resulting in an 11-bit summed waveform. 00
~010 is output. Note that the adder 1008 and addition waveforms 00 to 010 are respectively ADD 104 in FIG.
and corresponds to the summed waveform Wc +WM.

The above addition waveforms 00 to 010 are triangular wave decoder 1009
address signal, and 10-bit decode output MA
Output O-MA9. Here, the triangular wave decoder 10
09 and decode outputs MAO to MA9 correspond to the decoder 105 and decode outputs of FIG. 1, respectively.

The above decoded output MA O-MA 9 is further supplied to the multiplier 1
Amplitude coefficient A input to terminal A of 010 and input to terminal B
It is multiplied by MPO-AMP9 and amplitude modulated. In addition,
The amplitude coefficient AMPO-AMP9 takes a value of 1 or less.

The digital musical tone signal generated in this way is a D/A
The signal is converted into an analog musical tone signal by an i-converter 1011 and a low-pass filter 1012, and then emitted from a sound system (not shown).

With the above configuration, the carrier frequency CF output from the controller 1001 in response to the performance operation by the performer
, by controlling the modulator frequency MF and envelope information ED, the musical tone whose pitch, volume, timbre, etc. are controlled based on the performance operation is D/A converted in exactly the same way as the musical sound waveform generator shown in FIG. converter 1011 and low-pass filter 1012 into an analog musical tone signal,
In particular, the sound is emitted from a not-shown sound system.

With the above configuration, the carrier frequency CF output from the controller 1001 in response to the musical performance by the performer.
, by controlling the modulator frequency MF and envelope information ED, outputs a musical tone whose pitch, volume, tone color, etc. are controlled based on the performance operation in exactly the same manner as the musical waveform generator shown in FIG. 1, It can be made to emit sound.

Next, FIG. 11 shows a first circuit example of the carrier wave generation circuit 1003 of FIG. 10.

#0 to #9 exclusive OR circuit (hereinafter referred to as EOR)
Each first input terminal of 1102 has an adder 10 shown in FIG.
The carrier phase angle ω of the most significant bit from 02. .

10 is input, and O to 9 bit carrier wave phase angles ωCLO to ωct9 are input to each second input terminal.

#0 to #9 E OR1102 output AO-A9 is A
It is input as each address signal of the carrier wave ROM 1101.

The ROM outputs DO to D9 of the η wave carrier wave ROMIIOI are:
Each is input to the first input terminal of the EOR 1103 #0 to #9. Also, the second of E OR1103 of #0 to #9
The carrier wave phase angle ωct10 of the most significant bit is input to the input terminal of
enters.

Each output of the E OR1103 of #0 to #9 and the carrier wave phase angle ωct10 of the most significant bit are the carrier signals WCO to W
c10 is output to the adder 1008 in FIG.

The operation of the first circuit example will be explained based on the operation diagram of FIG. 12.

First, the (7)% illuminated transmission wave ROM 1101 in FIG.
Of the carrier signal WC explained in FIG. 2 or equation (3) above, a waveform corresponding to two cycles (0 to π [rad]) is stored. That is, from the above equation (3), if Yl is the value determined by the output DO to D9 of the D% wave carrier wave ROMll0I in FIG. The carrier wave phase angle ωct is a value determined by ωctO to ωct9.

On the other hand, the carrier wave phase angle ωゎ, 0 to ωct10 output from the adder 1002 in FIG. 10 is the most significant bit ωCt10.
When the most significant bit ωct10 is in the logic 1 state, a phase angle of 0 to π (rad) can be specified by the full range of the lower 10 bits ωCtO to ωct9. Furthermore, when the most significant bit ωct10 is in the logic 1 state, the full range of the lower 10 bits ωCtO to ωct9 can be specified. can specify a phase angle between π and 2π (rad).

Therefore, now in the adder 1002 of FIG. 10, the carrier phase angle ω
The time when the full range of cLO to ωct10 is specified is T
Then, first, from time 0 to T/2, Fig. 12 (b
), the carrier wave phase angle ωct10 of the most significant bit is logical 0, and the full range of the carrier wave phase angles ωctO to ωct9 of the lower 10 bits is specified as shown in FIG. And at this time, E OR110 of #0 to #9
Since the carrier wave phase angle ωct10 of the most significant bit of logic 0 is input to the first input terminal of 2, the time 0 to T/
2, the carrier wave phase angle of the lower 10 bits ωcLO~ωct9
By sequentially increasing the value of , address signals AO to A9 are obtained that sequentially increase in exactly the same relationship as shown in FIG. 12(C). As a result, the outputs DO to D9 of the two carrier waves R○M1101 in FIG.
), O~π(rad) based on the above formula 07)
The waveforms within the range are sequentially read out. Then, this waveform is input to the first input terminal of the E OR 1103 of #0 to #9, or the carrier wave phase angle ω of the most significant bit of logic O is input to the second input terminal of the E OR 1103. Since tlo is input, the carrier signal W of the lower 10 pins of its output is
c O to Wc9 are as shown in FIG. 12(e),
) is output with a waveform exactly the same as the output Do-D9. Furthermore, since the carrier signal W c 10 of the most significant bit is equal to the carrier phase angle ωcdO of the most significant bit and is logical 0, it ends up being as shown from time 0 to T/2 in Fig. 12). , waveforms exactly the same as the output DO-D9 in FIG. 3(d) are output as carrier signals WcO to Wc1O.

Next, from time T/2 to T, as shown in FIG. 12(b),
The carrier wave phase angle ωCt10 of the most significant bit is logical 1, and the full range of the carrier wave phase angles ωCtO to ωct9 of the lower 10 bits is specified as shown in FIG. 2(a). At this time, the carrier wave phase angle ωc of the most significant bit of logic 1 is input to the first input terminal of the E OR 1102 of #0 to #9.
Since t10 is input, the lower 1 at time T/, 2 to T
0 bit carrier phase angle ω. , 0 to ωct9 sequentially increase, address signals AO to A9 which sequentially decrease in a completely opposite relationship are obtained as shown in FIG. 12(C). As a result, as shown in FIG.
As shown in FIG. 12(d), the outputs D0 to D9 of OMIIOI are read out in the reverse direction as waveforms in the range of 0 to π (rad) based on the equation 07). This waveform is input to the first input terminal of the EOR 1103 #0 to #9, but the carrier wave phase angle ωcdO of the most significant bit of logic 1 is input to the second input terminal of the EOR 1103. , its output is the carrier signal W of the lower 10 bits.
c O to Wc9 are as shown in FIG. 12(e),
) A waveform whose increase/decrease relationship is inverted with respect to the output DO-D9 is output. In addition to this, the most significant bit carrier signal W
Since CIO is logic 1, which is equal to the carrier wave phase angle ωct10 of the most significant bits 1 to 1, an offset of π (rad) corresponding to the full range of the carrier wave phase angles ωCtO to ωcL9 of the lower 10 bits is superimposed on the above output, and as a result, 1st
The waveform shown from time T/2 to T in Figure 2) is the carrier signal W.
CO~W, output as 10.

As can be seen from the above operation, the waveform output in the range of time 0-T is exactly the same as the carrier signal Wc explained in FIG. 2 or equation (3) above. In the case of this first circuit example, the two carrier waves ROMll in FIG.
Since it is sufficient to store two periods of the waveform in 0I instead of the one period waveform shown in Fig. 2, the memory capacity is reduced to 2 compared to when simply storing one period of the waveform. be able to.

FIG. 13 shows the second carrier signal generation circuit 1003 of FIG.
The configuration of an example circuit is shown below.

The carrier wave phase angle ω of the 10th bit from the adder 1002 in FIG. 10 is input to each first input terminal of the EOR 1302 #0 to #8. , 9 are input, and 0 is input to each second input terminal.
~8-bit carrier wave phase angle ωctO~ω. , 8 input.

#0 to #8 E OR1302 outputs AO to A8 are Z
It is input as each address signal of the carrier wave ROM 1301.

The ROM outputs DO to D8 of the 2-carried wave ROM 1301 are:
Each of them is input to the first input terminal of the E OR 1303 of #0 to #8. Further, the 10th bit carrier wave phase angle ω is input to the second input terminal of the EOR 1303 of #0 to #8. ,9
enters.

Each output of the E OR 1103 of #0 to #8, the carrier wave phase angle ωct9 of the 10th bit, and the carrier wave phase angle ω of the most significant bits 1 to 1. tlo is output to the adder 100B in FIG. 10 as carrier signals WCO to W010.

The operation of the second circuit example will be explained based on the operation diagram of FIG. 14.

First, the X carrier wave ROM 1301 in FIG. 13 contains the Z carrier signal WC explained in FIG.
A waveform corresponding to a period (0 to π/2 (rad)) is stored. That is, from the above equation (3), the output from the X carrier wave ROM 1301 in FIG.

If the value determined by ~D8 is Y2, then the following waveform is stored: Y2#(π/2) sin ωct (0≦ωct≦π/2) 08). Note that the carrier wave phase angle ωcl here is ω. , 0 to ωct8.

On the other hand, the carrier wave phase angles ωCtO to ωCtlO outputted from the adder 1002 in FIG. 10 are the highest bit angles ω. , 10
and the logical combination of the 10th bit ωct9 (ω0,1
0, ω. , 9), if (Olo), the lower 9 bits
0 to π depending on the full range of throat ωCOO to ωct8
/2 (rad) phase angle can be specified, (0,■)
In the case of
A phase angle of (rad) can be specified, and in the case of (1, 1), a phase angle of 3π/2 to 2π (rad) can be specified as well. Each of the above four cases will be explained below.

Now, in the adder 1002 of FIG. 10, the carrier phase angle ωctO~
If the time when the full range of ωct10 is specified is T, then (ωct10, ω0,9)−
(0,0) corresponds to time 0 to T/4 as shown in FIGS. 14(b) and (C). In this time range, the first input terminal of the EOR 1302 of #0 to #8 has the carrier wave phase angle ω of the 10th bit of logic 0. ,
9 is input, the values of the carrier wave phase angles ωctO to ωct8 of the lower 9 bits increase sequentially from time 0 to T/4, resulting in the same relationship as shown in FIG. 14(d). Sequentially increasing address signals AO to A8 are obtained. As a result, the z carrier wave ROM 1301 in FIG.
(7) For the outputs DO to D8, as shown in FIG. 14(e), waveforms in the range of 0 to π/2 (rad) based on 08) 2 are sequentially read out. And this waveform is #0~#
E of 8 is input to the first input terminal of OR1303,
The second input terminal of the above E OR1303 has a logic 0 of 1.
Since the carrier wave phase angle ωct9 of the 0th bit is input, the carrier signal of the lower 9 bits of the output is
As shown in FIG. 14(f), c8 outputs a waveform completely similar to the outputs DO to D8 in FIG. 14(e). Furthermore, 1
Carrier signals Wc9 and Wc of the 0th bit and the most significant bit
1O is the carrier phase angle ω of the 10th bit and the most significant bit. , 9 and ωct10 are both logic O, so as shown from time 0 to T/4 in FIG. 14(2), the waveform is exactly the same as the output Do-D8 in FIG. 14(e). , are output as carrier signals WcO to Wc1O.

Next, as the second case, (ωct 10, ωo, 9)
-(0,1), Figure 14(b) and (C)
This corresponds to the time T/4 to T/2. In this time range, the first input terminal of the E OR 1302 of #0 to #8 has the carrier wave phase angle ω of the 10th bit of logic 1.
Since ct9 is input, the values of the carrier wave phase angles ωctO to ωct8 of the lower 9 bits increase sequentially from time T/4 to T/2, and as a result, as shown in FIG. 14(d), Decreasing address signals AO-A8 are obtained. As a result, the illuminated transmission wave ROM2S shown in FIG.
As shown in FIG. 14(e), O4(7) outputs DO to D8 are 0 to π/2 [:rad
) is read out in the opposite direction. This waveform is input to the first input terminal of the EOR 1303 #0 to #8, but the logic 1010th bit (general transmission wave phase angle ω., 9 is input, so its output, the carrier signal W of the lower 9 bits,
As shown in FIG. 14(f), CO to Wc8 have waveforms whose increase/decrease relationship is inverted with respect to the output DO-DB in FIG. 14(e).

In addition, since the carrier signals W c 9 and W c 10 of the 10th bit and the most significant bit are equal to the carrier wave phase angles ωct9 and ωct10 of the 10th bit and the most significant bit, and their logical values are 1 and O, respectively, Lower 1 in the above output
An offset of π/2 (rad) corresponding to the full range of the 0-bit carrier wave phase angle ωCtO to ωct9 is superimposed, and as a result, the time T//1 to T/2 in FIG. 14(g) is
The waveform shown in is the carrier signal WCO~Wc10
is output as

Next, as the third case, (ωct10, ωct9)
If = (1, 0), then Figure 14 (b) and (C)
As in, it corresponds to time T/2 to 3T/4. In this time range, the 10th bit carrier phase angle ωct9
Since the logic of is 0, the operation in E OR 1302, 2 carrier wave ROM 1301 and E OR 1303 is as follows.
This is exactly the same as the first case. Therefore, E OR1
The carrier signal WcO of the lower 9 bits which is the output of 303
〜W c 8 is as shown in FIG. 14(f), and as shown in FIG. 14(e)
A waveform completely similar to the outputs DO to D8 is output.

In addition, since the carrier signals Wc9 and Wc1O of the 10th bit and the most significant bit are equal to the carrier wave phase angles ωcL9 and ωct10 of the 10th bit and the most significant bit, and their respective logics are 0 and 1, the lower An offset of π (rad), which is twice the full range of the 9-bit carrier phase angle ωCtO to ωcL8, is superimposed, resulting in a waveform as shown at time T/4 to T/2 in FIG. 14(g). It is output as carrier signals W c O to W c 10.

Finally, as the fourth case, (ωCt10, ωcL9)
- (1, 1), Figure 14 (b) and (C)
This corresponds to the time 3T/4 to T. In this time range, the logic of the 10th bit carrier wave phase angle ωct9 is 1.
Therefore, E OR1302, Z carrier wave ROM 1
The operations in 301 and E OR 1303 are the same as those in the second
This is exactly the same as in the case of . Therefore, the lower 9-bit carrier signals WCO to WC8, which are the outputs of the EOR1303, have waveforms whose increase/decrease relationship is inverted with respect to the outputs DO to D8 in Fig. 14(e), as shown in Fig. 14. be done. In addition to this, the carrier signal W of the 10th bit and the most significant bit,
9 and Wc1O are both logic 1 equal to the carrier wave phase angles ωct9 and ωcL10 of the 10th focus and the most significant bit.
Therefore, the carrier phase angle ω of the lower 9 bits is added to the above output.
3π/ which is three times the full range of ctO~ωct8
2 (rad) offsets are superimposed, and eventually the first
The waveform shown from time 3T/4 to T in FIG. 4(g) is output as carrier signals WcO to Wc1O.

As can be seen from the above operation, the waveform output in the range of time 0 to T is exactly the same as the carrier signal Wc explained in FIG. 2 or equation (3) above. In the case of this second circuit example, the two-carried wave ROM 13 in FIG.
01, it is sufficient to store the waveform for X periods in contrast to the waveform for one period in FIG.
Compared to the circuit example shown in FIG.

Next, FIG. 15 shows a circuit example of the triangular wave decoder 1009 shown in FIG. 10.

Each of the two input terminals of #9 has an adder 1008 in FIG.
The addition waveforms 09 and 010 of the 10th bit and the most significant bit are input, and this output is the E OR1 of #0 to #8.
501 to each first input terminal.

Additionally, O to 8-bit addition waveforms 00 to 08 are input to each second input terminal of the E OR 1501 #0 to #8.

The respective outputs of the E OR1501 in #O to #8 above are sent to the multiplier 1010 in FIG. 10 as the decoded outputs MAO to MA8, and the addition waveform 010 of the most significant bit is sent as the decoded output MA9 of the most significant bit representing the sign bit. Output.

The operation of the triangular wave decoder having the above configuration will be explained below.

Now, assuming that the value Z determined by the addition waveforms 00 to 010 increases sequentially in direct proportion to the passage of time, the addition waveforms 00 to 010
One period in the full range of O~2π (rad)
Suppose that we can specify the phase angle of . First, in the first case, the logical combination (010,09) of the most significant bit 010 and the 10th bit 09 of the addition waveform becomes (0,0).
In this case, the value indicated by the addition waveform 00 to 010 is from O to one-fourth of the full range, that is, π/2 (rad)
This is a case where it changes up to. In this range, the output of #9 E OR1501 is logic 0, so #0 to #
As the addition waveforms 00 to 08 input to the EOR 1501 of 8 increase sequentially with the passage of time, waveforms exactly similar to the addition waveforms 00 to 08 input to the EOR 1501 of 8 appear as decoded outputs MAO to MA8 of the lower 9 bits. Furthermore, the decoded output MA9 of the most significant bit, which is the sign bit, is equal to the addition waveform 010 of the most significant bit, which is logic 0, and therefore generates a positive decoded output in the above range. Expressing this in a formula, if the value determined by the decoded outputs MAO to MA9 is W, then the following is obtained.

In the second case, when (010,09) - (0, ■), the value indicated by the addition waveforms 00 to 010 is π/2
This is a case where the value changes up to π (rad). In this range, the output of the E OR1501 of #9 becomes logic 1, so as the addition waveforms OO to 08 input to the E OR1501 of #0 to #8 increase sequentially with the passage of time, the output of the E OR1501 of #9 becomes logic 1. Waveforms that decrease sequentially are output as decoded outputs MAO to MA8 of the lower 9 bits. Furthermore, the decoded output M of the most significant bit which is the sign bit
A9 is logic O equal to the most significant bit addition waveform 010.
Therefore, in the above range, a positive decode output is generated.

Expressing this in the formula, becomes.

In the third case, if (010,09) - (1,0), the value indicated by the addition waveforms 00 to 010 is π-3
This is a case where it changes up to π/2Crad).

In this range, the output of #9's E OR1501 becomes logic 1 as in the second case, so #0 to #8
The state of E OR1501 is also the same as in the second case,
As the input addition waveforms 00-08 sequentially increase over time, waveforms that sequentially decrease in a completely opposite relationship are output as the lower 9 bits of decoded outputs MAO-MA8. On the other hand, the decoded output MA9 of the most significant bit, which is the sign bit, generates a negative decoded output in the above range because the addition waveform 010 of the most significant bit has changed to logic 1. Expressing this in a formula, W--Z+π However, (π≦Z≦3π/2) (21).

In the fourth case, when (010,09) - (1,1), the value indicated by the addition waveforms 00 to 010 is 3π/
This is a case where it changes from 2 to 2π (rad).

In this range, the output of #9's E OR1501 becomes logic 0 as in the first case, so #0 to #8
The state of E OR1501 is also the same as in the first case,
As the input addition waveforms 00 to 08 increase sequentially with the passage of time, a waveform exactly the same as the input addition waveforms 00 to 08 is outputted as the decoded output MAO-MA8 of the lower 9 bits. On the other hand, the decoded output MA of the most significant bit which is the sign bit
9 generates a negative decoded output in the above range because the addition waveform 010 of the highest bit node is logic 1. Expressing this in a formula, W=Z-2π However, (3π/2≦Z≦2π) (22).

(19) to (22) corresponding to the first to fourth cases above
To summarize the formula, we get: ・ ・ ・(23)

Here, if the equation (7) already shown as the characteristic of the decoder 105 in FIG. 1 is modified, it becomes: (24). Comparing Equation (24) 2 and Equation (23) above, the relationship between input and output is essentially the same, with only a difference of 2/π in the overall gain, and therefore, as shown in Figure 15. The triangular wave decoder 1°09 in FIG.
It can be seen that the decoder 105 operates in exactly the same way as the decoder 105 of FIG. 1 shown by the characteristics of equation 7).

Above, specific circuit examples have been shown for the carrier signal generation circuit 1003 and the triangular wave decoder 1009 in FIG. 10, but in addition, the modulation signal generation circuit 1005 in FIG. Similar to FIG. 11 or 13, it can be realized as a ROM memory that generates a waveform for one cycle. Also, adder 1002.100
5.1008 or multipliers 1007, 1010, etc., can be realized by known circuits, and the envelope generator 1006 can also be realized by using known circuits for electronic musical instruments.

Although the first embodiment shown in FIG. 10 has been described as a circuit for outputting a single musical sound waveform, the same adder 100
2. Carrier signal generation circuit 1003, adder 1004, modulation signal generation circuit 1005, envelope generator 10
06, the multiplier 1007, the adder 1008, the triangular wave decoder 1009, and the multiplier 1010 are configured to operate in time division, and the musical tones of each time division channel are input at the input stage of the D/A converter 1011 at each sampling period. By accumulating them, it becomes possible to generate a plurality of tone waveforms in parallel.

Strategy 1 ■ Disaster garden charcoal summer theory group Next, a second embodiment of the present invention will be described.

First, the basic principle of the second embodiment is as shown in Figs. 1 to 9.
The principle configuration and operation are the same as those of the first embodiment described above with reference to the drawings.

The specific configuration of the second embodiment is shown in FIG. This embodiment is an example in which the musical sound waveform generator according to the present invention is applied to an electronic keyboard instrument. In this embodiment, depending on the speed (strength) of pressing the keys on the keyboard, the generated musical tones can be controlled in a wide range from a state in which many high-order harmonics are included to a state in which only a single sine wave is included. It is characterized by being able to

In FIG. 16, circuits, signals, etc. with the same numbers and symbols as in the first embodiment of FIG. 10 have the same functions as in the case of FIG. 10.

The second embodiment shown in FIG. 16 differs from the first embodiment shown in FIG.
001), a keyboard section 1601 is connected. Then, the controller 1602 sets the carrier frequency CF, according to the setting state in the parameter setting section (not shown) and the key code 1'' KC and velocity VL input from the keyboard section 1601.
It generates and outputs a modulator frequency MF and envelope information ED and FA, which will be detailed later.

Adder 1002 or 1004 each has a carrier wave phase angle of 10 bits ωctO to ωct10 as in the case of FIG.
Alternatively, the carrier frequency CF is determined to be the frequency corresponding to the key code KC from the keyboard section 1601, and the modulator frequency MF is determined to be the frequency corresponding to the key code KC from the keyboard section 1601, for example. By determining the ratio to the frequency CF set in advance by the performer, a musical sound waveform of a pitch corresponding to the keyboard operated by the keyboard section 1601 is generated.

Carrier signal generation circuit 1003 and modulation signal generation circuit 100
The function of 5 is the same as that of FIG.

On the other hand, the envelope generator 1603 generates 11-bit and 10-bit two-channel modulation depth functions IO to IIO and amplitude coefficients AMPO to AMP 10 from terminals C and M based on address data FA and setting data ED from the controller 1602. Output. Note that these correspond to the modulation depth function T (t) and amplitude coefficient A in FIG. 1, and both can change over time based on the values of the key code KC and velocity VL from the keyboard section 1601. This point differs from the first embodiment shown in FIG.

Multiplier 1007, adder 1008, triangular wave decoder 10
09, the functions of the multiplier 1010, the D/A converter 1011, and the low-pass filter 1012 are the same as in the case of FIG.

Next, a specific circuit example of the carrier signal generation circuit 1003 in FIG. 16 is shown in FIG. 11 or 13, as in the case of the first embodiment, and the operation thereof is shown in FIG. 1st
This is as explained in Figure 4.

Further, a specific circuit example of the triangular wave decoder 1009 in FIG. 16 is shown in FIG. 15 as in the case of the first embodiment described above, and its operation is also as described above.

Further, as a specific circuit of the modulation signal generation circuit 1005 in FIG. 16, as described above in the first embodiment, the sine waveform for A or two cycles is stored in the ROM, and the circuit shown in FIG. 11 or 13 is Similarly, it can be realized as a circuit that generates a waveform for one period.

Next, the operation of envelope generator 1603 in FIG. 16 will be explained. Envelope generator 16
The configuration of the envelope generator 1603 is the same as that of an envelope generator circuit used in a normal electronic musical instrument, except that it can output enclosing waveforms for two channels, so the details will be omitted. Starting from 1602, a characteristic operation is performed when setting each rose makeup. The operation will be explained below.

First, channel C of the envelope generator 1603
Modulation depth function IO~1 output as hi and Ch2
10 or amplitude coefficient AMPO-AMP9 characteristics as the first example.
It is shown in Figure 7. In the same figure, ON is the keyboard section 1601 in FIG.
Indicates the timing to start pressing any key in
F indicates the timing of key release. And channel Chi
Alternatively, the output value of channel ch2 reaches the initial level IL at the attack time AT from the key press, reaches the sustain level S L at the decay time DT, maintains that level until the key is released, and then reaches the sustain level IL at the decay time DT. After that, the time for release quim RT goes to O level and the sound is muted.

By setting address data FA from the controller 1602 in FIG. 16 to the address input terminal A of the envelope generator 1603 and giving setting data ED to the data input terminal, channel Ch1 and channel Ch of the envelope generator 1603 in FIG.
2 output waveforms can be set. FIG. 18 shows the relationship between the address value of the address input terminal A and the type of data at the data input terminal in this case. In this manner, by applying each value shown in the figure to the address input terminal A using the address data FA, various types of data shown in the figure can be set to the data input terminal using the setting data ED. In FIG. 18, the same type of parameters are set for both channels Chi and Ch2, but the types may of course be different.

Next, FIGS. 19 to 25 do not show the operation flowchart 1 of the controller 1602 when a player operates the keyboard section 1601 of FIG. 16 to perform a performance. Note that each variable processed within the controller 1602 is shown in FIG. In the figure, detune data DTUNE for the carrier wave of the modulated wave is data indicating which (shifted) frequency of the modulated wave phase angle ω0 to ω, t10 is set relative to the frequency of the carrier wave phase angle ωctO to ωct10. and
This makes it possible to vary the composition of higher-order harmonics of the generated musical sound waveform.

Further, each data corresponding to channel Chi and channel Ch2 in FIG. 26 corresponds to each data shown in FIG. 18 set in the envelope generator 1603 in FIG. 16.

First, FIG. 19 is a main operation flowchart of the controller 1602.

In the figure, in repeating the processing of Sl and 37, the controller 1602 monitors whether any key in the keyboard section 1601 is pressed or released.

When any key is pressed, the process advances from 31 to 32. S2
Now, the carrier frequency CF is determined by the adder 1002 in FIG.
Processing is performed to set the value to . FIG. 20 shows the operation flowchart.

First, in S9, the pressed key code KC is obtained from the keyboard section 1601.

Next, the SIO adds values such as vendor, transpose, etc. (not shown) to the key code KC to calculate the carrier frequency CF. Here, the bender is controller data that allows the performer to arbitrarily change the pitch of the musical tone being sounded during performance. Further, transpose refers to setting data for performing transposition, octave change, etc. on the keyboard section 1601.

Subsequently, at Sll in FIG. 20, the carrier frequency CF calculated as described above is output to the adder 1002.

As a result, the carrier wave phase angle ω corresponds to the pressed key from the adder 1002 in FIG. , 0 to ω0°10 are output.

After the above operation, the process returns to the main operation flowchart of FIG. 19 and proceeds from S2 to S33. In S3, processing is performed to set the modulator frequency MF in the adder 1004 in FIG. 16. FIG. 21 shows the operation flowchart.

First, in Si2, the detune data DTUNE (see FIG. 26) set in advance by the performer is added to the carrier frequency CF set in the process of S2 (FIG. 20) to calculate the modulator frequency MF.

Then, the modulator frequency MF determined in this manner is output to the adder 1004. As a result, the 16th
Carrier phase angle ωCt output from adder 1002 in the figure
O~ω. , 10, modulated wave phase angles ωmtO to ωmt 10 are output from the adder 1004.

After the above operation, the process returns to the main operation flowchart of FIG. 19 and proceeds from S3 to S34. In S4, processing is performed to set each parameter of the channel Chi of the envelope generator 1603 in FIG. 16. FIG. 22 shows the operation flowchart.

First, in S14, the velocity VL of the pressed key is obtained from the keyboard section 1601 in FIG. Note that this value ranges from 0 to
It can take values between 1.

Next, in S15, the attack time MAT, decay time MDT, and release time MRT (see FIG. 26) of channel Chi are set in the envelope generator 1603 of FIG. 16 as timbre data. For this set, as shown in FIG. 18, the value to be applied to the address input terminal A of the envelope generator 1603 is determined by the address data FA, and each variable value corresponding to the data input terminal is outputted as the setting data ED.

Subsequently, in S16, the initial level MrL of channel Chi, which is timbre data, is multiplied by the value of velocity VL and set in the envelope generator 1603. This set is also similar to the case of S15.

Furthermore, in S17, the channel Ch, which is also timbre data, is
Multiply the sustain level MSL of i by the value of velocity VL, and generate the envelope generator 1603 in the same way as above.
Set to .

After the above operation, the process returns to the main operation flowchart of FIG. 19 and proceeds to S4 to S35. In S5, processing for setting each parameter of channel Ch2 of envelope generator 1603 in FIG. 16 is performed. FIG. 23 shows the operation flowchart.

That is, in S18, the channel Ch
2 attack time CAT, initial level CIL,
Decay time CDT, sustain level C3L and release time CRT (see FIG. 26) are set in envelope generator 1603 in FIG. This set can also be performed in exactly the same manner as in the case of channel Ch1.

Through the above processing, the carrier frequency CF, modulator frequency MF and envelope generator 1 shown in FIG.
When the input of each parameter to 603 has been completed, the program returns to the main operation flowchart 1 to 1 in FIG. 19, proceeds from S5 to 86, and performs an on process for generating musical tones in S6. FIG. 24 shows the operation flowchart.

First, in S19, a command is issued to the envelope generator 1603 in FIG. 16 to turn on channel Chi. As shown in FIG. 18, this process is executed by setting the value 0 as address data FA from the controller 1602 in FIG. 16 and outputting appropriate command data as setting data ED.

Next, in S20, a command is issued to the envelope generator 1603 to turn on channel Ch2. As in the case of channel Chi, this process is performed by transmitting address data FA from the controller 1602 in FIG. 16 as shown in FIG.
The command is executed by setting the value 7 as the setting data ED and outputting appropriate command data as the setting data ED.

As a result, the ON process shown in FIG. 19 is completed.

On the other hand, if the key being pressed on the keyboard section 1601 in FIG. 16 is released, the process proceeds to steps 37 to 38 in FIG. 19, and in S8 an off process is performed to mute the musical tone being sounded. 25th
The figure shows the operation flowchart.

First, in S21, a command is issued to the envelope generator 1603 in FIG. 16 to turn off channel Ch1. As shown in FIG. 18, this process is executed by setting (!1) as address data FA from the controller 1602 in FIG. 16 and outputting appropriate command data as setting data ED.

Next, in S22, a command is issued to the envelope generator 1603 to turn off channel Ch2. As in the case of channel Chi, this process is performed by transmitting address data FA from the controller 1602 in FIG. 16 as shown in FIG.
This is executed by setting a value of 8 as 8 and outputting appropriate command data as setting data ED.

As a result, the ON process shown in FIG. 19 is completed.

Through the above processing, the modulation depth functions IO to IIO and amplitude coefficients AMPO to AMP9 corresponding to the channel Chi are obtained from the envelope generator 1603 in FIG.
The output has characteristics as shown in FIG. 7, and based on this, each circuit in FIG. 16 operates as described above to generate a musical tone waveform.

In this case, the modulation depth function 10 corresponding to channel Chi
The characteristic of -110 is determined by the velocity VL value indicating the strength of the key pressed on the keyboard section 1601 in FIG.
Changes as shown in the figure. That is, 316 in FIG.
As shown in S17, the initial level IL and the sustain level SL become larger as the value of the velocity VL becomes larger.

Therefore, when a key is pressed strongly, the value of velocity VL becomes large, and the modulation depth functions 10 to 110 become large values as a whole. As a result, the modulated wave phase angle ωmtO to ω at the adder 1008 in FIG. □, carrier phase angle ω of 10. ,
The mixing ratio for 0 to ωct10 is increased, and the generated musical tone can include many high-order overtones.

Conversely, when the key is pressed weakly, the value of velocity VL becomes small, and the modulation depth function 10~IIO becomes a small value overall, resulting in the modulated wave phase angle ωmtO~ at adder 1008 in FIG. Carrier phase angle ωCtO of ωmt1o
The mixing ratio for ~ωCdO becomes smaller, and the generated musical tone can be made closer to a single sine wave.

As described above, a major feature of this embodiment is that the generated musical tone can be controlled over a wide range from a state in which it contains many high-order harmonics to a state in which it contains only a single sine wave, depending on the strength with which the keys are pressed.

In the above embodiment, the channels C and hl of the envelope generator 1603 in FIG.
The envelope characteristics of channel Ch2, that is, the amplitude coefficients AMPO to AMP9, can be changed by the velocity L, and the volume of the musical tone can be adjusted according to the strength of the key press. may be made variable.

In addition, the envelope characteristics of the modulation depth function ■0 to 110 are varied by the velocity VL.
It is also possible to perform control based on which key range of the keyboard section 1601 in FIG. 16 is pressed instead of L. That is, for example, when a key in the low range is pressed, the modulation depth function IO
By decreasing the value of ~110 and increasing it when a key in the high range is pressed, it is possible to perform an operation suitable for simulating a tone that contains many high-order harmonics in the low range, such as a piano sound. It is possible.

Although the embodiment shown in FIG. 16 has been described as a circuit for outputting a single musical sound waveform, as in the case of the first embodiment described above, the adder 1002 and the carrier signal generation circuit 1003 shown in FIG. , adder 1004, modulation signal generation circuit 10
05, envelope generator 1603, multiplier 10
07, the adder 1008, the triangular wave decoder 1009, and the multiplier 1010 are configured to operate in time division, and the D/
If the input stage of the A converter 1011 accumulates the musical tones of each time-division channel at each sampling period, it becomes possible to generate a plurality of musical sound waveforms in parallel.

First, since this embodiment uses the concept of a basic module for calculating basic waveform outputs, the basic structure of the basic module will be explained first. FIG. 28 is a diagram showing the principle configuration of the basic module 2801.

This module differs from the principle configuration of the first embodiment shown in FIG.
102 through the MUL 103, the configuration is such that the output of the basic module at the previous stage is manually input, as will be described later. The basic operation per module is almost the same as that shown in FIG.

That is, in the basic module 2801, first, the function waveform shown in FIG. 2 described above is stored in the carrier wave ROM10I. Therefore, the carrier wave phase angle ω in each region I, ■, and ■ in the figure. , (rad) and carrier signal WC(r
ad ] is the same as the above-mentioned equation (3).

Then, the carrier signal Wc calculated by the above equation (3)
and external modulation signal W1. I is added and input to the decoder 105. As a result, a decoded output is output from the decoder 105, and the MUL 106
is multiplied by the amplitude coefficient A. The waveform output e obtained by this is e = A TRI ((rl/2) sin ω
ct+WM1... (0≦ω,≦π/2). However, TRI(X) is defined as a triangular wave function.

Here, first, when the modulated signal WM is O, that is, unmodulated, the input waveform to the decoder 105 becomes the carrier signal WC itself determined by the above equation (3). This corresponds to the case where the value of the modulation depth function 1 (t) is 0 in FIG. 1, and therefore, the waveform output e is the same as the above equation (6). Also,
The carrier signal Wc and the carrier wave phase angle ω are shown by the relationship A in FIG. 3, as in the first case. On the other hand, decoder 105
The triangular wave function D=TRI(x) (where X is an input) calculated in is defined by the above equation (7) as in the case of FIG. 1, and is a function shown in relation B in FIG. 3. Therefore,
As in the case of FIG. 1, the waveform output e is transformed as shown in equation (8) above, and becomes a single sine wave A-sinωゎ. That is, for example, if the amplitude coefficient A = 1, the relationship between the carrier wave phase angle ωゎ in the non-modulated state and the waveform output C will be as shown in the relationship C in Figure 3, as in the case of Figure 1. .

From the above relationship, in order to realize the process in which a musical tone is attenuated to only a single sine wave component, or a musical tone consisting only of a single sine wave component, the modulation signal WM input from the outside must be It can be seen that it is better to approach O with time.

Next, consider changes in the waveform output e when the mixing ratio of the modulated signal WM mixed into the carrier signal Wc in ADD 104 is increased. In this case, the same effect as in the case of increasing the value of the modulation depth function 1 (t) in FIG. 1 can be obtained. That is, if the mixing ratio of the modulation signal WM is gradually increased from the value O,
Addition waveform Wc +WM output from D D 104
, the modulation signal WM gradually changes from the carrier signal Wc only component.
As the components are superimposed, the waveform output e gradually becomes distorted on the time axis from a single sine wave, and changes to include many high-order harmonic components on the frequency axis. In this case, since the conversion function in the decoder 105 is originally a triangular wave shown in (7) 2 or FIG. , it is now possible to obtain more complex overtone characteristics.

In the above basic module 2801, for the decoder 105 having the characteristic shown in the equation (7) or the relationship B in FIG.
A single sine wave can be generated by storing a carrier signal WC as shown in the equation or relationship A in FIG. 2 or 3 in the carrier wave ROM10I. However, the present invention is not limited to this, and as in the case of FIG. 1, the same effects can be obtained by combining as shown in FIGS. 8(a) to 8(d). These relationships are explained in (9) above.
It is as shown in formula 00 from formula.

Furthermore, in the basic module 2801 of FIG.
Although the amplitude coefficient A multiplied by L106 is assumed to be a constant value in the explanation, it can actually change over time, as in the case of Fig. 1, so that the waveform output e is amplitude modulated. It is possible to add enclosing properties.

Next, a specific configuration of a third embodiment based on the basic module configuration shown in FIG. 28 will be described.

First, FIG. 29 is an overall configuration diagram of an electronic musical instrument according to a third embodiment. Since this embodiment is based on the configuration of the basic module shown in FIG. 28, the following description will be made with reference to FIG. 28 and the like from time to time.

The controller 2906 controls each one according to the setting state of the formation (described later) in a parameter setting section (not shown) and the pitch specification operation of the keyboard section, etc.
1-bit and 10-bit carrier wave phase angles ωCtO~ω.

tlO and amplitude coefficients AMPO to AMP9, formation information FO1F1, F2 and F3.2 phase clock CK
I and CK2 generate ECLK. In this case, data for the number of basic modules combined for each formation, which will be described later, is output in a time-sharing manner. This will be detailed later. Here, the carrier phase supplies. , 0~ωct10 and amplitude coefficient AMPO~
AMP9 is the carrier phase angle ω in FIG. , and the amplitude coefficient A.

The above carrier wave phase angle ω. , 0~ωゎ, 10 and amplitude coefficient A
MPO to AMP9 are input to the basic module 2901.

The basic module 2901 corresponds to the basic module 2801 in FIG. 28, and includes a carrier signal generation circuit 2902 corresponding to the carrier wave ROM10I in FIG. It is composed of a multiplier 2905 corresponding to MUL 106.

Then, the carrier wave phase angle ωc from the controller 2906
tO to ωctlO and amplitude coefficients AMPO to AMP9 are input to the carrier generation circuit 2902 and the multiplier 29o5, respectively.

In the basic module 290I, the carrier signal generation circuit 2
11-bit carrier signal W c O output from 902
~Wc1O corresponds to the carrier signal WC in FIG.
10 corresponds to the addition waveform Wc +WM in FIG. The 11-bit waveform output eO-elO corresponds to the waveform output e in FIG.

Waveform output eO~e that is the output of the basic module 2901
lO is connected to the terminal so or Sl depending on whether the formation information FO from the controller 2906 is logic 0 or logic 1.
It is selectively output to accumulator 2908 or 2907 via switch SW2913 connected and controlled by .

The accumulator 2907 receives the formation information F2 input from the controller 2906 to the clear terminal CLR and the two-phase clocks CKI and CK2 from the controller 2906.
, the waveform outputs eO to elO of the basic module 2901 input from the terminal S1 of the switch 5W2913 are accumulated. This configuration will be explained in detail later in FIG. 30.

The output of the accumulator 2907 is output to the terminal S1 of the switch SW29]4. Further, the terminal SO of the switch SW2914 is fixed at a logic 0 level. switch 5W
2914 connects the terminal SO or SL to the adder 2903 of the basic module 2901 depending on whether the formation information F3 from the controller 2906 is logic 0 or logic 1, and supplies the 11-bit modulation signal WHO to W M 10.

Note that the terminal SO of the switch SW2914 is not limited to the logic 0 level, but may have a value near 0 that does not affect the modulation of the carrier signal.

On the other hand, the accumulator 2908 outputs the terminal SO of the switch SW2913 under the control of the image information F1 input from the controller 2906 to the clear terminal CLR and the two-phase clocks CK1 and CK2 from the controller 2906.
The waveform output eO of the basic module 2901 input from
Accumulate elO. This configuration will be described in detail later with reference to FIG. 31.

The output of the accumulator 2908 is latched by a flip-flop (hereinafter referred to as F/F) 2909 in accordance with the latch clock ECLK from the controller 2906, and becomes a digital musical tone signal.

The digital musical tone signal generated in this way is a D/A
Converter 2910 and low pass filter (LPF) 291
1, the signal is converted into an analog musical tone signal, and the sound system 2912 outputs the sound.

Next, a specific circuit example of the carrier signal generation circuit 2902 in the basic module 2901 in FIG. 29 is shown in FIG. 11 or FIG. is as explained in FIG. 12 or 14.

Further, a specific circuit example of the triangular wave decoder 2904 in FIG. 29 is shown in FIG. 15, as in the case of the first embodiment described above, and its operation is also as described above.

Next, FIG. 30 shows the circuit configuration of accumulator 2907 of FIG. 29.

The 11-bit waveform outputs eO to elO from the basic module 2901, which are input from the terminal S1 of the switch 5W2913 in FIG. 1 from AND circuits 3003-1 to 3003-10
It is added to the input of 1 bin 1~.

The output of pin 11 from the adder output terminals A and B of the adder 3001 is F at the timing of the rising edge of the clock CKI output from the controller 2906 in FIG.
/F Set to 3002.

The above data set in the F/F 3002 is read out at the rising timing of the clock CK2 output from the controller 2906 in FIG. 29, and is sent from the output terminal OUT to the terminal S of the switch 5W 2914 in FIG.
1 and is output to AND circuits 3003-1 to 30
Adder input terminal I of adder 3001 via 03-10
It is fed back to B and selectively accumulated.

AND circuits 3003-1 to 3003-10 include the 29th
Formation information F2 from the controller 2906 in the figure is inverted and inputted to the inverter 3004 to control opening and closing of the circuit.

Next, FIG. 31 shows the circuit configuration of accumulator 2908 of FIG. 29.

The 11-bit waveform outputs eO to e10 from the basic module 2901 inputted from the terminal SO of the switch SW2913 in FIG. 29 are inputted from the input terminal IN to the addition input terminal IA of the adder 3101. Below, adder 3101,
F/F 3102, AND circuit 3103-1 to 31
The configurations of 03-10 and inverter 3104 are the same as accumulator 2907 in FIG.

However, if the output from the adder output terminal A+B of the adder 3101 is connected to the output terminal OUT, and the output terminal FF0UT of the F/F 3102 is connected to the output terminal FF0UT of the F/F 3102, the output from the AND circuit 31031 is
~3103-10. In addition, the AND circuit 310
31 to 3103-10, the controller 2 in FIG.
Formation information F1 from 906 is sent to inverter 3
The signal is inverted and inputted at 104 to control the opening and closing of the circuit.

Regarding the overall operation of the electronic musical instrument shown in FIG.
8. Switch SW2913, SW2914 and F
/F2909 will be mainly explained.

FIGS. 33(a) to 33(6) are diagrams showing examples of formations of an electronic musical instrument according to the third embodiment. This formation can be selectively set by the performer via a parameter setting section (not shown). This allows the performer to control the pronunciation of musical tones with various overtone compositions.

In the figure, M1 to M4 are the basic modules 290 in FIG.
1 shows the unit of operation executed. Each calculation unit has a sampling period of four processing periods (hereinafter, each of these is M
Each time-divided processing period is assigned to the processing period (referred to as 1 processing period to M4 processing period).

Below, we will explain the actions in Figure 32 (a), etc., corresponding to each formation example from Figure 33 (a) to (barrel) in Figure 29, etc.
Each operation timing chart of (g) will be sequentially explained. In addition, in the following explanation, formation information F
0~F3, clock CKI, CK2 and latch clock ECLK are simply FO~F3, CKI, CK2 and EC
It will be abbreviated as LK.

First, the operation in the formation example of FIG. 33(a) will be explained based on the operation timing chart of FIG. 32(a).

First, in the Ml processing cycle, timing 1+ (hereinafter simply referred to as tl) when CK2 becomes logic 1.

The same applies to t2 to t8. ), F3 becomes logic O and the value 0 is supplied as the modulation signal WMO-WMIO. As a result, in the basic module 2901 of FIG. 29, the waveform output eO−e from the basic module is expressed as the equation (8) in the explanation of FIG. 28 or the relationship C in FIG.
As lO, a single frequency sine wave multiplied by amplitude coefficients AMPO to AMP9 is output. This output is e(Ml
). At the same time, since FO becomes logic 1 at tl as shown in FIG. 32(a), the above e(Ml) is
907. In the accumulator 2907 of FIG. 30, since F2 is logic 1 as shown in FIG. enters and adder 3001
e(Ml) is output from 10B to the addition output terminal of .

This e (Ml) is F at tl when CKI becomes logic 1.
/F Set to 3002.

Subsequently, in the M2 processing cycle, at t3 when CK2 becomes logic 1, the e(Ml) is outputted to the output terminal OUT of the accumulator 2907 in FIG. And at t3, the 32nd
As shown in Figure (a), <F3 becomes logic 1, so e(Ml) is input as the modulation signal W HO" W Mlo to the basic module 2901 in FIG. 29 via the switch SW2914. As a result, the basic module In 2901, the second
Based on (25) 2 in the explanation of Figure 8, e(M
Waveform outputs eo to elO modulated by l) are output. Let this output be e (M2).

At the same time, as in the case of the M1 processing cycle, the third
As shown in Fig. 2(a), since FO is logic 1, e(M2) is input to the accumulator 2907, and at t3, F becomes logic 1 as shown in Fig. 32(a).
2 is logic 1 and the augend input terminal IB of the adder 3001 in FIG.
is set to F/F 3002 at F4, which becomes logic 1.

The operation in the next M3 processing cycle is the same as the M2 processing cycle. That is, at t5 when CK2 becomes logic 1, the third
Connect e (M2
) is output, and at the same time, since F3 is logic 1, the basic module 2901 in FIG. 29 outputs waveform outputs eO to elO modulated based on e(M2). This is e(M
3). Then, at F5, FO becomes e(M3
) is input to the accumulator 2907, and at the same time F2 is logic 1 and the augend input terminal IB of the adder 3001 in FIG. and CKI becomes logic 1 at t6
is set to F/F 3002.

Then, in the M4 processing cycle, as in the M2 or M3 processing cycle, CK2 becomes logic 1, and the accumulator 2 in FIG.
Since e(M3) is output to the output terminal OUT of 907 and F3 is logic 1 at the same time, the basic module 2901 in FIG. 29 outputs waveform outputs eO to elo modulated based on e(M3). Ru. Let this be e(M4). Then, at tl, FO becomes logical O, so e(M4
) is input to accumulator 2908. Accumulator 29 in Figure 31
In 08, as shown in FIG. 32(a) at tl, since Fl is logic 1, the AND circuits 3103-1 to 3103-10 are turned off, and all O's are input to the augend input terminal IB.
Adder 3101 addition output terminal A+B to output terminal OU
e (M4) is output to T. And this e(M
4) is F8 in FIG. 29 where ECLK becomes logic 1.
/F latched to 2909.

By the operation in the M1 to M4 processing cycles, the basic module 2901 in FIG. 29 outputs one sample of the musical sound waveform e (M4) modulated in series in three steps in the M2 to M4 processing cycles, and the above operation is repeated. Accordingly, the corresponding modulated musical tone can be emitted from the sound system 2912 via the D/A converter 2910 and the LPF 2911.

As described above, in the formation example shown in FIG. 33(a), since the modulation is applied very deeply, a musical sound waveform with extremely rich overtone components is obtained.

Next, the operation in the formation example of FIG. 33(b) will be explained based on the operation timing chart of FIG. 32(b).

First, the operation in the M1 processing cycle is similar to the operation in the M1 processing cycle in the formation example shown in FIG.
The basic module 2901 in FIG. 29 outputs a waveform output e(Ml) which is an unmodulated single sine wave. At the same time, at , FO becomes logic 1 as shown in Figure 32 ([)), e (Ml) is input to the accumulator 2907, and at tl, F2 becomes logic 1 as shown in Figure 32 (b). Since the logic 1 causes the addend input terminal IB of the adder 3001 in FIG. 30 to become all 0,
e (Ml) from addition output terminal A+B of adder 3001
is output and CKI becomes logic 1 at t2, F/F
Sera 1~ is done in 3002.

The operation in the next M2 processing cycle is the same as that in the M2 processing cycle in the formation example shown in FIG. 33(a).

That is, at t3 when CK2 becomes logic 1, (,!(Ml) is output to the output terminal OUT of the accumulator 2907 in FIG. 30, and at the same time F3 becomes logic 1, the basic module in FIG. 29 At 2901, a waveform output e(M2) modulated based on e(Ml) is output.Then, t3
Since FO is logic 1, e(M2) is input to the accumulator 2907, and at the same time, F2 is logic 1 and the addend input terminals IB of the adder 3001 in FIG. 30 are all O.
01's addition output terminal A 10B outputs e (M2), and at tl where CKI becomes logic 1, F / F 300
Set to 2.

In the continuation<M3 processing cycle, similar to the M2 processing cycle, e (M2) is output to the output terminal OUT of the accumulator 2907 in FIG. 30 at F5 where CK2 becomes logic 1, and at the same time, F3 becomes logic 1, In the basic module 2901 of FIG.
A waveform output e(M3) modulated based on (M2) is output. Then, at t5, FO becomes logic 0, so e (M3) is input to the accumulator 2908, as in the case of the M4 processing cycle of the formation example in FIG. Since the addend input terminals IB of the adder 3101 in Figure 31 are all O, the adder 310
e(M3) is output from 10B to the addition output terminal of 1. Then, this e (M3) is sent to the F/F 3102 at t6 when CKI becomes logic 1.

In the M4 processing cycle, as in the case of the M1 processing cycle, F3 becomes logic 0 at tl when CK2 becomes logic 1, and the basic module 2901 in FIG. 29 outputs a waveform e which is an unmodulated single sine wave. (M4) is output. At the same time, as in the case of the M3 processing cycle, FIG.
), e(M4) is the accumulator 290 since FO is logic 0.
Enter 8. In the accumulator 2908 of FIG. 31, CK2
At tl when becomes logic 1, e(M3) set in F/F 3102 is output to terminal FF0UT, and at the same time Fl becomes logic 0 as shown in FIG. 32(b), so AND circuit 3103-1 ~3103-10 is turned on, the above e (M3) is input to the augend input terminal IB, and the output terminal OUT is output from the addition output terminal A+B of the adder 3101.
, e(M3) and e(M4) are output. Then, this e (M3) + e (M4) is E CL , K is logic 1, and F / F 2909 in Fig. 29
latched to.

Due to the operation in the M1 to M4 processing cycles described above, the basic module 2901 in FIG. Tone waveform l to which e(M4) is added
By outputting the sample and repeating the above operation, the corresponding modulated musical tone can be emitted from the sound system 2912 via the D/A converter 291o and the LPF 2911.

As described above, in the formation example shown in FIG. 33(b), a musical sound waveform is obtained in which a strongly modulated component and one type of sine wave component are mixed.

Next, the operation in the formation example of FIG. 33(C) will be described based on the operation timing chart of FIG. 32(C).

First, the operation in the M1 processing cycle is similar to the operation in the M1 processing cycle in the formation example shown in FIG. 33(a) or FIG. 33(I)), and F3 is The logic becomes O, and the basic module 290 in FIG.
1, a waveform output e(Ml) which is an unmodulated single sine wave is output. At the same time, FO becomes logic 1 at t as shown in FIG.
, and at t, F2 becomes logic I as shown in Figure 32(C).
Since the addend input terminals IB of the adder 3001 in FIG. F/F is set to 3002.

In the next M2 processing cycle, as in the M2 processing cycle of the formation example in FIG. 33(a), at F3 where CH2 becomes logic 1, e( Since F3 becomes logic 1 at the same time, the basic module 2901 in FIG. 29 outputs a waveform e (M2) modulated based on e(Ml).
is output. Then, in F3, FO becomes logic O, so e (M2) is input to the accumulator 2908, as in the case of the M4 processing cycle in the formation example of FIG. Adder 310 in Figure 31
Since the addend input terminal IB of 1 becomes all 0, e (M2
) is output.

Then, this e (M2) is F where CKI becomes logic 1.
4 to F/F 3102 cents.

The operation in the M3 processing cycle is exactly the same as the operation in the M1 processing cycle. That is, at F5 where CH2 becomes logic I, F3 becomes logic O, and in the basic module 2901 of FIG. 29, the waveform output e(M
3) is output. At the same time, use F5 to
), FO becomes logic 1 and e(M3) is the accumulator 29
07, F2 is logic 1 as shown in FIG. 32 (C) at F5, and the addend input terminal IB of the adder 3001 in FIG.
is all O, so e (M3) is output from addition output terminal A+B of adder 3001, and CKI becomes logic I.
It is set to F/F3002 at F6.

In the M4 processing cycle, at F7 where CH2 becomes logic 1, the third
e(M3) is output to the output terminal OUT of the accumulator 2907 in Figure 0, and at the same time F3 becomes logic 1, so that the second
The basic module 2901 in FIG. 9 outputs a waveform output e(M4) modulated based on e(M3)4. Then, at F7, FO becomes logic 0, so FIG. 33 (a)
) As in the case of the M4 processing cycle of the formation example,
e(M4) is input to accumulator 2908. In the accumulator 2908 of FIG. 31, at F7 where CH2 becomes logic 1, F/
e (M2) set in F 3102 is terminal F
is output to F0UT, and at the same time F is output as shown in Figure 32 (C).
Since l is logic 0, AND circuits 3103-1 to 3103
-10 is turned on and the augend input terminal IB has the above e(
M2) is input, and the addition output terminal A+B of the adder 3101
From e (M2) to output terminal OUT, e (M4
) is output. And this e (M2) 10e (
M4) is latched into F/F 2909 in FIG. 29 at F8 where ECLK is a logic one.

By the operation in the M1 to M4 processing cycles described above, the waveform output e (M2) modulated in the M2 processing cycle and the waveform output e (M4) modulated in the M4 processing cycle in the basic module 2901 in FIG. One sample of the added musical waveform is output, and by repeating the operations described in section 2, the D/A converters 2910.1. , PF 2911, the corresponding modulated musical tone can be emitted from the sound system 2912.

As described above, in the formation example shown in FIG. 33(C), a musical sound waveform in which two types of modulated components are mixed is obtained.

Next, the operation in the formation example of FIG. 33(d) will be explained based on the operation timing chart of FIG. 32(d).

First, the operation in the M1 processing cycle is t when CH2 becomes logic 1.
F3 becomes logic 0 at l, and basic module 2 in Figure 29
901 has a waveform output e (Ml
) is output. Then, at t, since FO is logic 0 as shown in FIG. 32(d), e(Ml) is input to the accumulator 2908, and at the same time, Fl becomes logic 1 and adder 3 in FIG.
Since the addend input terminal IB of the adder 3101 becomes all 0, e(Ml) is output from the addition output terminal A+B of the adder 3101, and F/F3 is output at F2 where CKI becomes logic 1.
Set to 102.

In the next M2 processing cycle, CH2 becomes logic 1 at F3.
Since 3 is a logical 0, the basic module 29 in FIG.
01, the waveform output e (M2
) is output. At the same time, e (M2) is input to the accumulator 2908 since FO is logic O, as shown in FIG. 32(d). In the accumulator 2908 of FIG. 31, e(Ml) set in the F/F 3102 at F3 where CK2 becomes logic 1 is output to the terminal FF0UT, and at the same time, the third
As Fl becomes logic 0 as shown in FIG.
From the addition output terminal A+B of 01 to the output terminal OUT, e
(Ml) 10e (M2) is output and set in F/F 3102 at F4 where CKI becomes logic 1.

The operation in the continuation<M3 processing cycle is the same as the above M2 processing cycle. That is, at t5 when CK2 becomes logic I, F3 becomes logic O, so the basic module 2901 in FIG. 29 outputs a waveform output e(M3) which is an unmodulated single sine wave. At the same time, as shown in FIG. 32(d), if FO exceeds logic 0 by e(M3), it is input to the accumulator 2908. Third
In the accumulator 2908 of FIG. 1, t5 when CK2 becomes logic 1
e (Ml
)+e (M2) is output to the terminal FF0UT, and at the same time, as shown in FIG. The above e(Ml)+e(M2) is input, and from the addition output terminal A+B of the adder 3101 to the output terminal OUT, e(Ml)+e(M2)
) is output and CKI becomes logic 1 at t6, F/F
Set to 3102.

In the M4 processing cycle, as in the M4 processing cycle of the formation example in FIG. 33(b), F3 becomes logic 0 at t7 when CK2 becomes logic 1. A waveform output e (M4), which is a single sine wave, is output.

Then, in F7, since FO is logic O, e(M4) is input to the accumulator 2908. In accumulator 2908 of FIG. 31, at t7 when CK2 becomes logic 1, F/F 310
e set to 2 (Ml)+e (M2)+e
(M3) is output to the terminal FF0UT, and at the same time, as Fl is logic O as shown in FIG. 32(d), the AND circuit 310
3-1 to 3103-10 are turned on, and the augend input terminal IB receives the above e (M 1 ) +e (M2) +e.
(M3) is input, addition output terminal A of adder 3101
From +B to the output terminal OUT, e (Ml) + e (
M2)+e (M3)+e (M4) is output. This output then becomes the second output at t8 when ECLK becomes logic 1.
It is latched to F/F 2909 in Figure 9.

Through the operations in the M1 to M4 processing cycles described above, one sample of musical sound waveforms in which the four types of sine waveforms generated by the basic module 2901 in FIG. 29 are added is output, and by repeating the above operations, the D/A converter 2910,
Sound System 291 via L P F2911
2, the corresponding musical tone can be emitted.

As described above, in the formation example shown in FIG. 33(d), a musical sound waveform is obtained by the sine wave synthesis method in which so-called four types of sine wave components are mixed.

Next, the operation in the formation example of FIG. 33(e) will be explained based on the operation timing chart of FIG. 32(e).

First, in the Ml processing cycle, when CK2 becomes logic 1, F3 becomes logic 0, and the basic module 290 in FIG.
1, a waveform output e(Ml) which is an unmodulated single sine wave is output. At the same time, FO becomes logic 1 at t as shown in FIG.
, and at t, F2 becomes logic 1 as shown in Figure 32(e).
Then, the addend input terminal IB of the adder 3001 in FIG.
is all 0, so e(Ml) is output from the addition output terminal A+B of the adder 3001, and is set in the F/F 3002 at t2 when CKI becomes logic 1.

In the case of the next M2 processing cycle, first, as in the case of the M1 processing cycle, at t3 when CK2 becomes logic 1, F3 becomes logic 0, and in the basic module 2901 of FIG. 29, it is an unmodulated single sine wave. A waveform output e (M2) is output. At the same time, e(Ml) is input to the accumulator 2907 because FO is logic 1 as shown in FIG. 32(e) at t3. Third
In the accumulator 2907 in Figure 0, t3 when CK2 becomes logic 1
e(Ml) set in F/F 3002 in
is output to the output terminal OUT side. At the same time, the 32nd
Since F2 becomes logic 0 as shown in FIG.
From addition output terminal A+B of 1, e (Ml)+e (M
2) is output and CKI becomes logic 1 at F4.
F 3002 is set.

The operation in the continuation<M3 processing cycle is the same as the above M2 processing cycle. That is, since CK2 is logic 1 at F5 and F3 is logic 0, the basic module 2901 in FIG. 29 outputs a waveform output e (M3) which is an unmodulated single sine wave. At the same time, since FO is logic 1 at F5 as shown in FIG. 32(e), e(Ml) is input to the accumulator 2907. In the accumulator 2907 of FIG. 30, CK2 is a logic 1.
At F5, e (Ml)+c (M2) set in F/F 3002 is output to the output terminal OUT side. At the same time, F as in No. 3211D (e)
Since 2 is logic O, AND circuits 30031 to 300.3
-10 is turned on, and the augend input terminal TB has the above e.
(Ml) 10e (M2) is input, and e(Ml) 10e (M2) is input from addition output terminal A+B of adder 3001.
+e (M3) is output and CKI becomes logic 1 at F6
is set to F/F 3002.

Then, in the M4 processing cycle, as in the M4 processing cycle of the formation example in FIG.
Since e (Ml) 10e (M2) 10e (M3) is output and at the same time F3 becomes logic 1, the basic module 2901 in FIG.
2) Waveform output e modulated based on 10e (M3)
(M4) is output. And in tl, FO is logic O
Therefore, e(M4) is input to the accumulator 2908. In the accumulator 2908 of FIG. 31, since Fl is logic 1 at tl as shown in FIG. 32(e), AND circuits 3103-1 to
3103-10 is turned off, all 0s are input to the addend input terminal TB, and the addition output terminal A+B of the adder 3101
e(M4) is output from the output terminal OUT. Then, this e (M4) is F8 where ECLK becomes logic 1.
It is latched by F/F 2909 in FIG.

Due to the operation in the M1 to M4 processing cycles described above, the musical sound waveform e is modulated by the mixed waveform of three types of sine waves obtained in the M1 to M3 processing cycles by the basic module 2901 in FIG.
(M4) is output, and by repeating the above operation, the D/A converter 2910, L P F29
11, a corresponding modulated musical tone can be emitted from the Zaunt system 2912.

Furthermore, IJJ in the formation example in Figure 33(f)
The operation will be explained based on the operation timing chart shown in Fig. 32.

First, the operation in the M1 processing cycle is similar to the operation in the M1 processing cycle in the formation example of FIG. 33(a), and at tl when CK2 becomes logic 1, F3 becomes logic 0,
The basic module 2901 in FIG. 29 outputs a waveform output e(Ml) which is an unmodulated single sine wave. At the same time, FO becomes logic 1 at L, as shown in FIG. 32(f), and e(Ml) is input to the accumulator 2907,
As shown in Figure 2), F2 becomes logic 1 and the addend input terminal IB of the adder 3001 in Figure 30 becomes all 0.
Adder 3001 addition output terminals A and B to e (Ml)
is output and CK1 becomes logic 1 F/F at F2
Set to 3002.

In the next M2 processing cycle, e(Ml) is sent to the output terminal OUT of the accumulator 2907 in FIG. 30 at F3 where CK2 becomes logic 1.
is output and F3 becomes logic 1 at the same time, so the second
The basic module 2901 in FIG. 9 outputs a waveform output e (M2) modulated based on e (Ml). Then, in F3, FO becomes logic 0, so e (M2) is input to the accumulator 2908, and at the same time, Fl becomes logic 1, and the addend input terminal IB of the adder 3101 in FIG. 31 becomes all 0, so the adder From addition output terminals A and B of 3101, e
(M2) is output.

Then, this e (M2) is F where CKI becomes logic 1.
4 is set to F/F 3102. On the other hand, at t3, FO is logic O, so switch S in FIG.
Terminal S1 of W2913 is not connected. Now switch 5
If the unconnected terminal in W2913 is grounded to logic 0, then in the accumulator 2907 in FIG.
All 0s are input to the addition input terminal TA of the adder 3001 in the figure. Further, since F2 is logic O in F3, the AND circuits 3003-1 to 3003-10 are turned on, and e(Ml) outputted to the output terminal OUT is inputted to the augend input terminal IB. Therefore, the above e(Ml) is output to the addition output terminals A and B of the adder 3001. This e(
Ml), then F/F3 at F4 where CKI becomes logic 1
Set to 002.

In the continuation<M3 processing cycle, e(Ml) is sent to the output terminal OUT of the accumulator 2907 in FIG. 30 at F5 where CK2 becomes logic 1.
At the same time, since F3 is logic 1, the basic module 2901 in FIG. 29 outputs a waveform output e (M3) modulated based on e(Ml). Then, since FO is logic O, c (M3) is input to the accumulator 2908. In the accumulator 2908 of FIG. 31, CK2 is set to F/F 3102 at F5 where it becomes logic 1
(M2) is output to the terminal F F OUT, and at the same time the third
Since Fl becomes logic O as shown in Figure 2), the AND circuits 3103-1 to 3103-10 are turned on, and the above c (M2) is input to the augend input terminal IB, and the adder 31
e (M2)-f-c (M3) is output from the addition output terminal A-1-B of 01 to the output terminal OUT, and CK
It is set in F/F 3102 at F4 where I becomes logic 1. On the other hand, as in the case of the M2 processing cycle, since FO is logic 0 in the L5, the switch SW291 in FIG.
The third terminal S1 is not connected and the third
The addition input terminal IA of the adder 3001 in Figure 0 is all O.
enters. Further, since F2 is logic 0 at F5, the AND circuits 3003-1 to 3003-10 are turned on, and e(Ml) outputted to the output terminal OUT is inputted to the augend input terminal IB.

Therefore, the above e(Ml) is output to the addition output terminal A+B of the adder 3001. This e(Ml) is set in F/F 3002 at F6 when CKI becomes logic 1.

And in the M4 processing cycle, as in the M3 processing cycle,
Accumulator 2907 in FIG. 30 at F7 where CK2 becomes logic 1.
e (Ml) is output to the output j terminal OUT, and at the same time F
3 is logic 1, the basic module 2901 in FIG. 29 has a waveform output e(M4) modulated based on e(Ml).
is output. And in F7, since FO is logic 0, e
(M4) is input to accumulator 2908. In the accumulator 2908 of FIG. 31, at F7 where CK2 becomes logic 1, F/
e (Ml) +e set in F 3102
(M2) is output to the terminal FF0UT, and at the same time the 32nd
As shown in Figure (f), since Fl is logic 0, the AND circuits 3103-1 to 3103-10 are turned on, and ``e(Ml)+e(M2)'' is input to the augend input terminal IB. , from the addition output terminals A and B of the adder 3101 to the output terminal OUT, e (M2) and e (M3) + e (M4)
is output. And this output shows that ECLK is logic 1
is latched by F/F 2909 in FIG.

By the operation in the above M1 to M4 processing cycles, each e(Ml
) are modulated by three types of waveform output e (M2),
One sample of musical sound waveform that is a mixture of e (M3) and e (M4) is output, and by repeating the above operation,
Via the D/A converter 2910 and LPF2911,
A corresponding musical tone can be emitted from the sound system 2912.

Finally, the operation in the formation example of FIG. 33 ((2)) will be explained based on the operation timing chart of FIG. 32 (Oi).

First, the operation in the M1 processing cycle is as shown in FIG. 33(e).
This is the same as the processing cycle. That is, when CK2 becomes logic 1, F3 becomes logic 0, and the basic module 2901 in FIG. 29 outputs a waveform e which is an unmodulated single sine wave.
(Ml) is output. At the same time, at tl, FO becomes logic 1 as shown in FIG.
2 becomes logic 1 and the addend input terminal TB of the adder 3001 in FIG. 30 becomes all 0, so e(Ml) is output from the addition output terminal A-1-B of the adder 3001,
Set in F/F 3002 at F2 when CKI becomes logic 1.

The operation in the next M2 processing cycle is similar to that in the M2 processing cycle shown in FIG. 33(e). That is, since F3 is logic 0 at F3 where CK2 is logic 1, the basic module 2901 in FIG. 29 outputs a waveform e (
M2) is output. At the same time, F3 is shown in Figure 32 (
Since FO is logic 1 as in g), e(Ml) is input to the accumulator 2907. In the accumulator 2907 of FIG. 30, e(Ml) set in the F/F 3002 at F3 where CK2 becomes logic 1 is output to the output terminal OUT side. At the same time, F2 becomes logic 0 as shown in FIG. 32(g), so the ant circuits 3003-1 to 3003-
10 is turned on, the augend input terminal IB receives the above e(M
l) is input, and the addition output terminal A + of the adder 3001
B outputs e (Ml) + e (M2), and C
It is set in F/F 3002 at F4 when KI becomes logic 1.

The operation in the M3 processing cycle is the same as in the M2 processing cycle in Figure 33). That is, F where CR2 becomes logic 1
5 to the output terminal OUT of the accumulator 2907 in FIG.
(Ml) 10e (M2) is output and F3 becomes logic 1 at the same time, so the basic module 290 in FIG.
1, a waveform output e (M3) modulated based on e (Ml ) +e (M2) is output. And F
5, FO becomes logic O, so e(M3) is the accumulator 29.
08, and at the same time, Fl is logic 1 and the augend input terminal IB of the adder 3101 in FIG. 31 becomes all O.
e (M3
) is output. Then, this e(M3) is set in the F/F 3102 when CKI becomes logic 1 and becomes 6. On the other hand, in L5, since FO becomes logic 0, the second
The terminal S1 of the switch 5W2913 in FIG. 9 is not connected and is grounded to logic 0, and in the accumulator 2907, all 0s are input to the addition input terminal IA of the adder 3001 in FIG. Also, since F2 is logic 0 in F5, the AND circuit 30
03-1 to 3003-10 are turned on, and the output terminal OU
e (Ml)+e (M2) output to T is input to the augend input terminal IB. Therefore, the above e (Ml)+e (M2
) is output. This output is F when CKI is logic 1.
6 is set to F/F 3002.

The operation in the M4 processing cycle is as shown in FIG. 33(f).
This is the same as the processing cycle. That is, at F7 where CR2 becomes logic 1, e(Ml) - e(M2) is output to the output terminal OUT of the accumulator 2907 in FIG. 30, and at the same time, F3 becomes logic 1 and the basic module in FIG. e in 2901
(M1) A waveform output e (M4) modulated based on (M2) is output. Since FO is a logic 0 at F7, e (M4) is input to the accumulator 2908.

In the accumulator 2908 of FIG. 31, e (
M3) is output to the terminal FF0UT, and at the same time, the signal shown in Fig. 32 (
Since Fl becomes logic 0 as in g), the AND circuit 31
03-1 to 3103-10 are turned on, the above e (M3) is input to the augend input terminal IB, and e (M
3) +e (M4) is output. Then, this output is F/F in Fig. 29 at F8 where ECLK becomes logic 1.
2909 is latched.

By the operation in the above M1 to M4 processing cycles, each e (M
l)+e (M2) modulated by two types of waveform outputs e (M3) and e (M4), one sample of musical sound waveform is output, and by repeating the above operation,
Corresponding musical tones can be emitted from the sound system 2912 via the D/A converter 2910, 2, and the PF 2911.

In each of the formation examples shown in FIGS. 33(a) to 33(g) explained above, if the formation example is as shown in FIG. 33(C), for example, the sine wave obtained in the M1 processing period in the M2 processing period The waveform output e (M2) modulated by one step is obtained by , and the same waveform output e (M4) is obtained in the M3 processing period and the M4 processing period, but it is The waveform output obtained by modulating a triangular wave originally containing many harmonic waveforms in the triangular wave decoder 2914 of the basic module 2901 in FIG. 29 results in each waveform output containing abundant harmonic components. can get. Compared to the case where the method of modulating a sine wave explained in the "Background Technology" section is applied to the basic module, a musical sound waveform containing richer overtone components can be obtained with only one step of modulation. It is shown that.

Further, in the M1 processing cycle or the M3 processing cycle in FIG. 33(C), the values of amplitude coefficients AMPO to AMP9 given to the basic module 2901 in FIG. 29 are decreased from 1 to O as time passes after the start of sound generation. Accordingly, each waveform output e obtained in the M2 processing cycle jlJl or the M4 processing cycle
It is possible to gradually change the characteristics of (M2) or e(M4) from a state containing abundant harmonic components to a state containing only a single sine wave. This is an example of an operation that cannot be achieved when the method of simply modulating a triangular wave described in the "Prior Art" section is applied to the basic module.

In addition, in this embodiment, four types of waveform output e, each of which is a single sine wave component, are generated by the formation example shown in FIG. 33(d).
(Ml) ~e (M4) in parallel Y'IN
Although a musical sound waveform similar to a Hammond sound can be obtained, this cannot be achieved in the conventional example described above.

As described above, in this example, although sufficient overtone components can be obtained even with a simple formation, for example, the waveform output of only a single sine wave component or the waveform output of multiple single sine wave components with different frequencies may be mixed in parallel. It is also easy to obtain a sine wave synthesized sound such as a Hammond sound. Furthermore, by changing the time-varying characteristics of the values of the amplitude coefficients AMPO to AMP9 in each processing cycle, for example, immediately after the start of sound production, the sound contains abundant harmonic components, but as time passes, it gradually contains only a single sine wave component. It becomes possible to obtain changing musical sound waveforms through simple connection combinations. That is, in this example,
It becomes possible to arbitrarily and continuously control the generation of a musical sound waveform containing abundant overtone components, which could not be easily realized in the past, to the generation of a musical sound waveform containing only a single sine wave.

4.1.H Next, a fourth embodiment of the present invention will be described.

In addition to the configuration of the third embodiment described above, this embodiment includes a formation setting section 3401 that allows the user to set a formation, and a formation display section 3404 that displays the set formation. FIG. 34 shows the configuration of the fourth embodiment. In this figure, the configuration other than the controller 2906 is the same as that in FIG. 29.

In FIG. 34, a formation setting section 3401 and a formation display section 3404 are connected to a controller 2906.

As shown in the figure, the formation setting section 3401 includes a manufacturer preset section 3402 and a user set section 3403.
It consists of

The manufacturer preset section 3402 is a section that allows the user to specify a formation that has been set in advance by the manufacturer. On the manufacturer side, for example, the above-mentioned figure 33 (a
) to ((2) are preset, and the user can, for example, form "a" to 'gJ
By pressing any of the keys in Fig. 33 (a
) to (g) can be arbitrarily selected. Correspondingly, the controller 2906 outputs formation information FO-F3, etc. as shown in the operation timing charts of FIG. Execute.

On the other hand, the user set section 3403 is a section that allows the user to arbitrarily set a formation other than the formation preset by the manufacturer. The user can set any formation using the setting keys shown in 3403 of the same figure. Note that each key operation will be described later. Controller 2906,
According to the settings in the user center part 3403, formation information FO to F3 is created according to a certain logic.
etc., and execute the corresponding processing.

Next, in the formation display section 3404, the contents of the formation set in the formation setting section 3401 are displayed. The formation display section 3404 includes an image display section 3405 and a symbol display section 3.
406 and an arithmetic expression display section 3407.

The image display section 3405 is, for example, a liquid crystal display panel, and the connection relationships of formations similar to those shown in FIGS. 33(a) to 33(a) are displayed on this display section.

The symbol display section 3406 displays symbols for each formation. In the case of a formation preset by the manufacturer, for example, FIGS.
Symbols ``a'' to ``gJ'' corresponding to each of the formations in ) are displayed. On the other hand, in the case of a formation set by the user, for example, a "U" symbol is displayed.

The calculation formula display section 3407 displays what kind of calculation will be performed in the set formation.

M1 to M4 are each processing cycle described above in the third embodiment. The operator r MOD is, for example, MIMODM2
In this case, it is shown that the output obtained in the M1 processing cycle is used as the modulation input in the M2 processing cycle. Operator “+
" indicates that, for example, in the case of M1+M2, the output obtained in the M1 processing cycle and the output obtained in the M2 processing cycle are mixed. Therefore, e −(MI NOD
M2) 10M3+M4 indicates that the waveform output e can be obtained by mixing the output in the M2 processing period, the output in the M3 processing period, and the output in the M4 processing period obtained by MIMODM2 calculation. ing.

From the above relationship, each operator r M[:lD
Setting keys corresponding to J'+j, etc. are provided.

In addition, "x" in the user sensor 1 part 3403 in Figure 34
Although the key is not shown in the third embodiment, for example, M1
This is used when setting an operation to multiply each output of the processing cycle and the M2 processing cycle, and in this case, "M1 x M2" is displayed.

As described above, by providing the formation setting section 3401 and the formation display section 3404 as shown in FIG. 34, the user can efficiently set the formation.

5-1 tongue゛■ Next, a fifth embodiment of the present invention will be described.

The principle configuration and specific configuration of this embodiment are the same as those shown in FIGS. 28 and 29 to 31 regarding the third embodiment. In this embodiment, the operation of the controller 2906 in FIG. 29 is different from that in the third embodiment.

In the third embodiment, when the performer selects any one of the formations shown in FIGS. 33(a) to (6), the controller 2906 shown in FIG. , CK2 and latch O tsuku E CI-K in Fig. 32(a) to (g
). As a result, as described above, musical tones are generated using an algorithm corresponding to the selected formation. In this case, each formation is fixedly set by the performer's switch operation.

In contrast, in this embodiment, each time the performer plays a key press on a keyboard section (not shown) to produce each musical tone, the formation is automatically performed at a preset timing after the start of each musical tone. can be switched.

That is, the performer changes the formation during the sound production operation from the formation shown in FIG. 33(b) to the formation shown in FIG. 33(e), as shown in FIG. 35, through a parameter setting section (not shown). You can make settings that change.

In this case, the performer can also set in advance the time it takes for the formation to change as shown in FIG. 35 after the start of each musical tone.

As a result, the controller 2906 in FIG. 29 controls the formation information FO to F3.2 phase clock CKI, CK2 at the timing shown in A1 in FIG. and generates a latch clock ECLK.

The timing of this operation is the same as that shown in FIG. 32(b) described above, so that the sound generation operation is performed according to the algorithm corresponding to the formation shown in FIG. 33(b). Then, when the set time has elapsed, the controller 29
06 generates the formation information FO to F3.2 phase clocks CKI and CK2 and the latch clock ECLK at the timing shown in 36A2. The timing of this operation is the same as that shown in FIG. 32(e) described above, so that the sound generation operation is performed in accordance with the algorithm corresponding to the formation shown in FIG. 33(e).

In this case, the controller 2906 determines the start point of each musical tone as the timing when the performer operates a performance operation section such as a keyboard section (not shown).

Furthermore, the controller 1-roller 2906 has an internal timer (not shown) that is started at the start of each musical tone, and measures whether or not a set time has elapsed.

In this way, by changing the formation after the start of sound generation, it is possible to generate musical tones having a more diverse overtone structure than when the formation is fixed after the start of sound generation.

Note that the number of combinations of formations that change after the start of sound generation is not limited to two, but may be three or more. In this case, two or more times are set for the formation to change.

Chapter ■■ Tips and Tricks ■ Departing from Kai Next, a sixth embodiment of the present invention will be described.

The principle configuration and specific configuration of this embodiment are also the same as those shown in FIGS. 28 and 29 to 31 relating to the third embodiment. In the third embodiment, the number of musical tones that can be produced at the same time is only one, but in this embodiment, it is possible to produce musical tones using eight-tone polyphony. Therefore, the operation of the controller 2906 in FIG. 29 differs slightly from that in the third embodiment.

First, the first aspect of this embodiment will be explained.

In the first aspect of this embodiment, as shown in FIG. 37(a), each sampling period is divided into eight channel times CHI to CH8 corresponding to the sound generation timing of each tone of the eight-note polyphonic tone. Furthermore, each channel time is time-divided into M1 processing cycles to M4 processing cycles similar to the third embodiment.

Then, at each channel time one sample of each note of the eight note polyphonic is generated, and at the end of each sampling period, the accumulator 2908 of FIG.
is accumulated. Therefore, for each sampling period, the second
A musical tone in which 8 tones are added is output from the F/F 2909 in FIG. 9 via the D/A 2910, and the 8 tones are aurally produced simultaneously from the sound system 2912.

Below, specific processing for realizing the above operation will be explained using FIG. 37(a).

FIG. 37(a) is an operation timing chart when musical tones based on the formation shown in FIG. 33(a) described above are produced in eight-tone polyphony in the configurations shown in FIGS. 29 to 31. In the same figure, each channel time CH
Each operation timing in I to CH8 is based on the third
The operation timing is almost the same as that shown in FIG. 2(a). however,
The difference in FIG. 37(a) is that the formation information F1 becomes logic 1 only in the M1 processing cycle of channel time C)I1, and becomes logic 0 otherwise. Another difference is that the latch clock ECL K becomes logic 1 only in the M4 processing cycle jlJl of channel time CH8.

Initially, in the M1 processing period of channel time CHI, which is the beginning of each sampling period, the accumulator 2908 is cleared by a logic 1 on Fl.

Then, as described above with reference to FIG. 32(a), the processing operations in the M1 to M4 processing cycles of channel time CH1 are executed, and the first musical tone data based on the formation of FIG. 33(a) is generated. Ru. This musical sound data is CHI
At the timing when the clock CK1 becomes logic 1 in the M4 processing cycle, it is set in the F/F 3102 through the adder 3101 of the accumulator 2908 in FIG. Note that, unlike the case in FIG. 32(a), the latch clock E CL
Since K is logic O, F/F2909 (Figure 29)
No latch operation is performed.

Next, M1 to M of channel time CH2 in FIG. 37(a)
Processing operations are performed in four processing cycles, and second musical tone data is generated based on the formation shown in FIG. 33(a). This musical tone data is input to the addition input terminal IA of the adder 3101 of the accumulator 2908 in FIG.
Enter. In the accumulator 2908 of FIG. 31, the F
/F The first musical tone data set in 3102 is output to terminal FF0UT. At the same time, Figure 37 (
As in a), since Fl is logic O, the AND circuit 310
3-1 to 3103-10 are turned on. Therefore, the first tone data is input to the addend input terminal IB of the adder 3101. As a result, data obtained by adding the first and second musical tone data is output from the addition input terminal 80B of the adder 3101, and is set to the F/F 3102 at the timing when CKI becomes logic 1. .

Thereafter, the same process is executed from channel time CH3 to CH8 in FIG. 37(a), and musical tone data for eight tones are added.

Then, at the same time that the clock CKI of the M4 processing cycle of channel time CH8 in FIG. F in the diagram
/F latched to 2909.

As described above, by the operation in the channel times CHI to CH8 of FIG. 37(a), one sample of data obtained by adding eight tones of musical tones generated based on the formation of FIG. 33(a) is output, By repeating this process,
Eight-note polyphonic musical tone data is emitted from the Zound system 2912 via the D/A converter 2910 and LPF 2911 shown in FIG.

Above, based on the operation timing chart I in FIG. 37(a), we have explained the case where musical tones based on the formation shown in FIG. (b) to Figure 33 (
The polyphonic sounding operation corresponding to g) can also be realized in a similar manner.

Next, a second aspect of the sixth embodiment will be explained. In this case, as in the case of the first embodiment, musical tones are produced using 8-tone polyphony, but the accumulator 2907 of FIG.
This embodiment differs from the first embodiment in that the F/F 3002 is configured with a shift register capable of processing eight tones, thereby performing time-sharing processing for each of the eight tones in each processing cycle of M1 to M4.

That is, in the second aspect of this embodiment, FIG. 37(b)
As shown in , each sampling period is time-divided into four sections from M1 processing period to M4 processing period, and each processing period is further time-divided into channel times CHI to CH8.

As mentioned above, the F of accumulator 2907 in FIG.
By configuring the /F 3002 with an 8-stage shift register, M1 processing period to M4 is processed for each channel time.
Processing operations in processing cycles can be performed in parallel. That is, when looking at one channel time, for example, CH1, each processing operation from the M1 processing cycle to the M4 processing cycle is executed almost in the same way as in the case of FIG. 32(a) described above.

Note that the formation information F1 becomes logic 1 only during channel time CH1 of the M1 processing cycle, and becomes logic 0 at other times.

Furthermore, the latch clock ECLK becomes logic 1 only at channel time CH8 of the M4 processing cycle.

Then, in the channel times CHI to CH8 of the M4 processing cycle, the formation information FO becomes logical 0, so that the first to eighth musical tone data output from the basic module 2901 in FIG. Sequential input to accumulator 2908. Furthermore, since the formation information Fl becomes logical 0, the accumulator 2 in FIG.
In 908, F/F 3102 and AND circuit 3103
-1 to 3103-10, the adder 3101 sequentially accumulates the musical tone data for the eight tones. Then, at the same time that the clock CKI of channel time CH8 in the M4 processing cycle in FIG. Pull is F/F 290 in Fig. 29
It is latched to 9.

As described above, as in the case of the first embodiment, it is possible to generate musical tone data of eight-tone polyphonic.

In the case of the second aspect, only the polyphonic sounding operation corresponding to FIG. 33(a) is shown, but the third aspect described above
Polyphonic sounding operations corresponding to FIGS. 3(b) to 3(2) can also be realized in a similar manner.

In the above-mentioned sixth embodiment, the case of eight-tone polyphonic was explained, but it is naturally possible to realize other polyphonic numbers by changing the number of time-sharing processes.

Fudeyu■implementation ± of course Next, a seventh embodiment of the present invention will be described.

In this embodiment, the concept of a basic module is used, as in the third embodiment described above. In the third embodiment, the basic module 2801 having the configuration shown in FIG.
By operating based on the formations exemplified in ) to (g), musical tones having various overtone structures can be produced. In contrast, the present embodiment further has a function of feeding back the output of the basic module to the input of its own basic module, thereby making it possible to generate musical tones having a more complex overtone structure.

FIG. 38 shows the configuration of a basic module 3801 in this embodiment. In the basic module 2801 in FIG. 28, the output side, that is, the amplitude of the decoded output from the decoder 105 is controlled by the MUL 106. On the other hand, in the basic module 3801 in FIG. 38, the decoded output from the decoder 105 is directly output from the output terminal 011T, and the modulated signal W input from the MUD IN terminal
The amplitude of M is controlled by MUL 103. In this case, in both embodiments, the output of the basic module is used as the modulation input of the other basic module, so the operation of the basic module 3801 in FIG. 38 is almost the same as that of the basic module 2801 in FIG. 28 described above. It is.

FIGS. 39(a) to 39(d) show examples of formations using a plurality of basic modules 3801 shown in FIG. 28.

Although not specifically shown, in this embodiment, as in the case of the third embodiment, a configuration example in which one basic module is operated by time-sharing processing as shown in FIG. 29 can also be used.

FIG. 39(a) is an example of the first formation. In this example, the basic module 3801 has a configuration in which the waveform output e from the output terminal OUT is output as a musical tone signal and is fed directly to the basic module 3801 itself.

According to the above configuration, the waveform output e of the basic module 3801 itself is used as the modulation input of the basic module 3801.
will be used.

In this case, if the value of the modulation depth function I (t) input to the MUL 103 (Fig. 38) is set to 0, for example, the waveform output e will be the same as when the modulation signal WM is 0 in equation (25). , a single sine wave is output as described in the third embodiment. This is an example of an operation that cannot be achieved when the method of simply modulating a triangular wave described in the "Background Art" section is applied to the basic module, and unique effects can be obtained.

On the other hand, when the value of modulation depth function 1 (t) is increased,
As in the case of the third embodiment, many harmonic components are included, but in this embodiment, especially the waveform output e is modulated.
By feeding back to the IN terminal, a more complex overtone structure can be realized. Furthermore, compared to the case where the method of modulating a sine wave described in the "Background Art" section is applied to the basic module, a more complex overtone structure can be realized with only about one stage of feedback.

Therefore, by continuously increasing the modulation depth function r(t) from O or decreasing it continuously from a large value, we can continuously obtain waveforms ranging from a single sine wave to a very complex modulated waveform. becomes possible.

Next, FIG. 39(b) is an example of the second formation in the seventh embodiment. In this example, in Figure 39 (a
) The output of the first basic module 3801 (No, 1) is further input to the MUD TN terminal of the second basic module 3801 (No, 2), which has the same feedback loop as the basic module 3801 (No, 2).
The waveform output e is output as a musical tone signal.

In this case, M of basic module 3801 (No. 2)
Modulation depth function 1 input to U Li2S (Figure 38)
If the value of (t) is set to 0, for example, a single sine wave is output as the waveform output e, as in the case of FIG. 39(a).

On the other hand, by increasing the value of the modulation depth function (2), it is possible to emphasize overtone components, and moreover, it is possible to obtain a different overtone structure from that in the case of FIG. 39(a).

In the case of FIG. 39(b), the modulation depth function r (t
) can be controlled, making it possible to perform wider control than in the case of FIG. 39(a). Note that by changing the frequency ratio of the carrier wave phase angle ω of both basic modules 3801, it is possible to obtain a musical tone signal having an even more varied overtone structure.

Next, as an example of the third formation, see Figure 39 (
C), in addition to the configuration of FIG. 39(b), a multiplier (MU) is added to the output of the basic module 3801 (No. 1).
L) The signal multiplied by the modulation depth function I'(t) in 3901 is the N of basic module 3801 (No, 2)
It can also be configured such that it is input to the OD IN terminal. As a result, the modulation depth function ■'(L) is added as a parameter that can control overtones, so as shown in Fig. 39(b)
It becomes possible to perform a wider range of overtone control than in the case of .

FIG. 39(d) is an example of the fourth formation. In this example, n basic modules 3801 having a feed pack loop similar to that shown in FIG. 39(a) are arranged in parallel. Basic module 3801 (No. 1)
The output of ~3801 (No, n) is the adder (ADD) 39
02, and the added signal is further input to the NOD IN terminal of another basic module 3801 (No, n+1). Then, the basic module 3801 (No,
The waveform output e of n+1) is output as a musical tone signal. With this configuration, it is possible to realize overtone control different from that shown in FIGS. 39(a) to 39(C).

14th grade 1st grade Next, an eighth embodiment of the present invention will be described.

In this embodiment, a basic module (FIG. 38) which is completely the same as that in the seventh embodiment described above is used.

The seventh embodiment has a configuration in which the waveform output e from the basic module 3801 is fed to the MUD IN terminal of its own basic module. On the other hand, in this embodiment, the waveform output e is from the basic module 3801 several steps earlier.
It has a configuration that feeds back to the MOD IN terminal of.

FIG. 40 shows an example of the formation of this embodiment. In the figure, the first stage basic module 3801 (N
o, 1) output is the second stage basic module 3801
(No, 2) is input to the MOD IN terminal, and the following are similarly connected in cascade, and the waveform output e of the n-th stage basic module 3801 (No, n), which is the final stage, is output as a musical tone signal. It also has a configuration in which it is input to the MOD IN terminal of the first stage basic module 3801 (No. 1). With this configuration example, overtone control different from that of the seventh embodiment can be realized, and unique effects can be obtained.

79 words ゛■ Next, a ninth embodiment of the present invention will be described.

First, the principle of the ninth embodiment will be explained. FIG. 41 shows the principle configuration of the ninth embodiment.

The feature of the principle configuration in the figure is that the modulation signal WM is not a simple sine wave generated by the modulation ROM 102 as shown in FIG.
02, which are signals having various characteristics.

First, the carrier wave ROM10I stores the function waveform shown in FIG. 2 described above. Therefore, the relationship between the carrier wave phase angle ωct (rad) and the carrier signal W ((rad) in each of the regions (■) and (■) in FIG. 1 is the same as the above-mentioned equation (3).

On the other hand, the modulated wave phase angle ω in the modulated wave phase angle ROM 4101
+nt (rad) and modulated wave correction phase angle ω, ・[rad
] is ω,・-ding (ω,,L)...
It is expressed as (26). However, f is defined as a modulation function.

Furthermore, the relationship between the modulated wave correction phase angle ω1·(rad) in the triangular wave decoder 4102 and the modulated signal WM [:rad) after passing through the MUL 103 is WM
-1(t) TRI (ω,・) ...(2
7). However, TRI (χ) is defined as a triangular wave function.

Therefore, the relationship between the modulated wave phase angle ωmt (rad) and the modulated signal Wi (rad) can be expressed as follows by substituting the above equation (26) into the above equation (27): WM = I (t) TRI (f (ωmt )
) ...(28).

A carrier signal W calculated by the above equation (3) and the above equation (28). and modulated signal WM are added, and the decoder 10
5, the decoder 105 outputs a decoded output. And to this output M U L
The waveform output e after being multiplied by the amplitude coefficient A in step 106 is as follows.

Here, first, when the value of the modulation depth function r (t) is O1, that is, no modulation, the input waveform to the decoder 105 becomes the carrier signal WC itself determined by the above equation (3). This corresponds to the case where the value of the modulation depth function r(t) is O in FIG. 1, and therefore, the waveform output e is similar to the above equation (6). Also, the carrier signal W and the carrier phase angle ω. ,teeth,
As in the case of FIG. 1, this is shown by relationship A in FIG. On the other hand, the triangular wave function D=T calculated in the decoder 105
RI(X) (where X is the input) is defined by the above equation (7) as in the case of FIG. 1, and is a function shown in relation B in FIG. 3. Therefore, as in the case of Fig. 1, the waveform output e is
Transformed as in equation (8) above, a single sine wave A-sin
ω.

becomes. That is, for example, if the amplitude coefficient A=1, the carrier wave phase angle ω when no modulation is performed. The relationship between , and the waveform output e is,
The relationship becomes as shown in relationship C in FIG.

From the above relationship, in order to realize the process in which a musical tone attenuates into only a single sine wave component, or the generation of a musical tone consisting only of a single sine wave component, the modulation depth function must be calculated using the equation (27) above. It can be seen that the value of I(t) should be brought closer to 0 with time.

Next, consider the change in the waveform output e when the value of the modulation depth function 1(t) is increased. In this case, the same effect as in FIG. 1 when the value of the modulation depth function T (t) is increased will be obtained. That is, when the value of the modulation depth function T (t,) is increased, A D in FIG.
The addition waveform WC+WM output from D104 has the following:
Since the components of the modulation signal WM are superimposed on the components of the first-den transmission signal WC, the waveform output e is not a single sine wave but a distorted waveform on the time axis, and has a frequency characteristic that includes many high-order harmonic components. become.

In this case, the modulated wave phase angle ROM 4101 in FIG. 41 has a plurality of modulation functions f as shown in FIGS.
is memorized. Then, a modulation signal WM finally output from the MUL 103 corresponding to each of these modulation functions f
By setting, for example, r(t, )-1 in the equation (28), the characteristics of
It is determined as a) to (C).

In this embodiment, the modulated wave phase angle ROM 4101 shown in FIG.
By making each of the modulation functions f selectable, the modulation signal WM can be arbitrarily selected from sawtooth waves, rectangular waves, pulse waves, etc. as shown in FIGS. 42(a) to (C). It is possible to output. These waveforms themselves contain many overtone components, and by superimposing such waveforms on the first hall transmission signal Wc,
As the waveform output e, a waveform containing more overtone components can be output, and by selecting the waveform of the modulation signal WM, it is possible to change how the overtone components are included in the waveform output e.

Now, although it is not shown in Figures 42(a) to (C),
For example, if the modulated wave phase angle ROM 4101 shown in FIG. 1 is stored with the same contents as the carrier wave ROM 101 shown in FIG. 2 or (3) 2 above, and the triangular wave decoder 4102 shown in FIG. , Figure 3 or the above (
As explained in equation 8), a single sine wave can be output for each modulation signal W. That is, the above (28)
The formula is the same as (4) 2 in the case of FIG. and,
Such a single sine wave modulation signal WM is expressed as A in FIG.
DD 104 superimposes it on the carrier signal WC, and decoder 1
The waveform output e obtained by inputting it to 05 is the same as the equation (5) in the case of FIG.

Therefore, the histogram (frequency distribution) of the frequency characteristics of the waveform output e obtained by making the modulation signal WM a single sine wave and increasing the value of the modulation depth function 1 (t) over time as described above is, therefore, As shown in FIG. 6(a). As can be seen from the figure, when the modulation depth function r (t) is changed, the overtone structure changes in a complicated manner, and the overtone structure tends to be biased toward a specific frequency. In other words, the lower harmonic is I
(t) decreases as r(t) increases, but high-order overtones increase on the contrary, and as r(t) increases, the overtone structure tends to shift from low-order to high-order.

On the other hand, the modulated wave phase angle ROM 4101 in FIG. 41 stores, for example, the one shown in FIG. 42(a), and the triangular wave decoder 4102 in FIG. 41 is thereby driven.
A sawtooth wave modulation signal WM as shown in FIG. 42(a) can be generated. Then, convert this signal to ADD in Fig. 41.
By superimposing it on the carrier signal Wc at 104 and inputting it to the decoder 105, a waveform output e is obtained based on the equation (29). In this case, FIG. 43 shows a histogram of the frequency characteristics of the waveform output e obtained by temporally increasing the value of the modulation depth function 1(t). In this case, even fairly high-order harmonic components can be included without increasing the value of the modulation depth function 1 (t), and I(
Even if +, ) is changed, the power of the overtone component has relatively little unevenness.

As described above, as shown in FIG. 6(a) or FIG. 43, in this embodiment, by selecting the waveform of the modulation signal WM, it is possible to generate waveform outputs e having various overtone characteristics. In this case, for example, the characteristics shown in FIG. 6(a) are effective for generating sound waveforms for string-striking instruments such as pianos where the overtone distribution is biased.
For example, the characteristics shown in FIG. 43 are effective for generating a string or positive musical sound waveform with a uniform harmonic composition and even considerably high-order harmonics.

In addition to the above features, in the principle configuration of FIG. 41, the value of the modulation depth function I(t) is set from 0 to 2π(
rad], it is possible to generate a process in which a musical tone is attenuated into only a single sine wave component, or a musical tone consisting only of a single sine wave component, and also to generate a musical tone that consists of only a single sine wave component. It becomes possible to easily generate musical tones that clearly exist up to the next overtone component.

In the above principle configuration, the equation (7) or the relationship B in FIG.
For the decoder 105 having the characteristics shown in FIG. By storing it, it is possible to generate a single sine wave. However, the present invention is not limited to this, and as in the case of FIG. 1, similar effects can be obtained by using combinations as shown in FIGS. 8(a) to 8(d). These relationships are as shown in equations (9) 2 to 06 above.

Also, the amplitude coefficient A multiplied by MUL106 in FIG.
has been described as a constant value, but in reality it can change over time, and as a result, it is possible to add amplitude-modulated envelope characteristics to musical tones.

Next, a specific configuration of the ninth embodiment based on the principle configuration of the ninth embodiment described above will be explained.

First, the overall configuration of the ninth embodiment is shown in FIG.
This is the same as the embodiment. Further, specific circuit examples such as the carrier signal generation circuit 1003 and the triangular wave decoder 1009 in FIG. 10 are also shown in FIG. 11, FIG. 13, FIG. 15, etc., as in the case of the first embodiment described above. .

The ninth embodiment differs from the first embodiment described above in the configuration of a modulation signal generation circuit 1005. The configuration of the modulated signal generation circuit 1005 basically consists of the configuration of the modulated wave phase angle ROM 4101 and the triangular wave decoder old 02 shown in FIG.

First, the configuration of the modulated wave phase angle ROM 4101 is shown in FIG. This ROM has a 14-bit address input of AO-A13, and first, the upper 3 bits of the address
~A13 as waveform number select signal WNo, 0
By inputting a value of ~7 (decimal), the address area in which up to eight types of modulation functions f shown in Figures 42 (a) to (C) or Figure 2 are stored, for example. Any one can be specified. Note that this designation can be made arbitrarily by the performer using a selection switch (not shown), and the controller 100I in FIG. Signal generation circuit 1
005.

In this way, after selecting the modulation function f, AO~
Adder 1004 in Figure 10 is added to the lower 11 bits of AIO.
By inputting the modulated wave phase angle ωmtO~ω, t10 from
The modulated wave correction phase angle ω, · (see FIG. 41) corresponding to o to ωmt10 can be obtained from the output terminal.

The modulated wave correction phase angle ω, · is determined by the triangular wave decoder 4102 in FIG. 41 in the modulated signal generation circuit 1005 in FIG.
This triangular wave decoder can be realized with the same configuration as the triangular wave decoder 1009 in FIG. 15, which has already been described. As a result, modulation signals WMO to WMlo corresponding to the modulation function f selected by the waveform number selection signal WNo can be outputted via the modulation signal generation circuit 1005 and multiplier 1007 in FIG.

In this way, in this embodiment, by making it possible to select a plurality of modulation functions f in the modulated wave phase angle ROM (FIG. 44) in the modulation signal generation circuit 1005 in FIG.
It is possible to selectively output a plurality of types of modulation signals WMO to W M 10, and therefore, the decoded outputs MAO to MA9 from the triangular wave decoder 1009 in FIG.
It becomes possible to generate musical sound waveforms with various overtone characteristics.

10, 10's Next, a tenth embodiment of the present invention will be described.

First, the basic principle of the tenth embodiment is the same as the principle configuration and operation of the first embodiment described above using FIGS. 1 to 9.

The specific configuration of the tenth embodiment is shown in FIG. 45. In this embodiment, time-division processing is performed for each of the left and right channels, allowing musical tones to be produced in stereo. In this case, the modulated wave phase angle ωmtO to ωmtlO and the modulation depth function 10 to 110 can be set for each channel, and it is possible to obtain a stereo output with slightly different modulation performed on each left and right channel. It has the characteristic that

In FIG. 45, circuits, signals, etc. with the same numbers and symbols as in the first embodiment of FIG. 10 have the same functions as in the case of FIG. 10.

The controller 4501 is the controller 10 in FIG.
Similar to 01, this is a means for generating and outputting carrier frequency CF, modulator frequency MF, and envelope information ED (each rate value, level value, etc. of the envelope). In this case, the controller 4501 independently sets each of the above parameters corresponding to each of the left and right channels, as will be described in detail later. This point corresponds to the controller 10 in FIG.
Different from 01.

The accumulator 4502 or 4503 is the adder 10 in FIG.
Similar to 02 or 1004, carrier phase angle ω. , 0~ωc
t10 or modulated wave phase angle ω□, 0 to ω, t10 is generated. In this case, the accumulator 4502 or 4503 differs from the adder 1002 or 1004 in FIG. 10 in that it generates each phase angle independently for the left and right channels.

Carrier signal generation circuit 1003 and modulation signal generation circuit 100
The basic function of 5 is the same as that of Fig. 10, but
Furthermore, it has a function of performing time division processing corresponding to each of the left and right channels.

On the other hand, envelope generator 4504, like envelope generator 1006 in FIG.
Output IO. In this case, the modulation depth function IO~110
This differs from the envelope generator 1006 in FIG. 10 in that the left and right channels are generated independently.

Next, a specific circuit example of the carrier signal generation circuit 1003 in FIG. 45 is shown in FIG. 11 or FIG. 1st
This is as explained in Figure 4.

Further, a specific circuit example of the triangular wave decoder 1009 in FIG. 45 is shown in FIG. 15 as in the case of the first embodiment described above, and its operation is also as described above.

Further, as a specific circuit of the modulation signal generation circuit 1005 in FIG. 45, as described above in the first embodiment, a sine waveform for two or two cycles is stored in the ROM, and the circuit shown in FIG. Similarly, it can be realized as a circuit that generates a waveform for one period.

The basic functions of the multiplier 1007, adder 1008, and multiplier 1010 are the same as in the case of FIG. 10, but they also have a function of performing time division processing corresponding to each of the left and right channels.

The digital musical tone signal outputted via the multiplier 1010 is converted into an analog signal by the D/A converter 1011, and then converted into an analog signal separately for the left and right time-sharing channels.
After passing through 4507 (L) and 4507 (L), the signal is input to sample and hold circuits 4505 (R) and 4505 (L), where it is sampled and held. The signals of each of these channels are further filtered through a low pass filter (hereinafter referred to as LPF) 4506 (
R) and 4506(1,) into analog musical tone signals, and the left and right channels are emitted separately from a sound system (not shown). Here, gate 4507 (R
) and 4507 (L) are controlled to open and close by sample and hold signals S/H (R) and S/11 (L), respectively. In addition, sample and hold circuits 4505 (R) and 4
Each of 505 (L) is composed of a capacitor for holding each channel signal, a buffer amplifier, etc., as schematically shown in FIG.

Next, accumulators 4502 and 4503 and envelope generator 4 for realizing the stereo operation of this embodiment are provided.
504 is shown.

FIG. 46 shows the structure of accumulator 4503 of FIG. 45.

In the figure, each signal MF(R), MF(L) is the fourth
Corresponding to the modulation frequency MF in Figure 5, RCLK,...
LCLK, , R3ET, LSET, RCLR.

Although omitted in FIG. 45, LCLR is a control signal supplied from each controller 4501.

Also, the circuits with '(R)J added to the number are for the right channel, and the ones added with '(L)J are for the left channel.

First, the circuit configuration for the right channel will be explained.

The right channel modulator frequency M F (R) from the controller 4501 is a flip-flop (hereinafter referred to as F
/F) 4601 (R) and is set according to the right channel set signal R3ET input from the controller 4501 to the clock terminal CLK.

The output of F/F 4601 (R) is Adder 460
Input as input A of 2(R). Adder 4602 (R
) output A+B is fed back as input B via F/F 4603 (R). With this configuration, the right channel modulator frequency M F (R) input via the F/F 4601 (R) is sequentially accumulated.

Here, the operation of clearing the accumulated results is performed by the controller 450.
Clear signal RCLR for right channel from 1 is F/F
This is executed by clearing 4603(R).

In addition, in F/F 4603 (R), the output A+ of adder 4602 (R) is synchronized with the falling edge of the right channel clock RCLK input to its clock terminal CLK.
B is set, and the set contents are output in synchronization with the rising edge of the same clock.

Accumulation operations are performed sequentially via this flip-flop.

In the above configuration, the output A and B of the adder 4602(R)
The cumulative result for the right channel obtained as
At the time division timing of the right channel when 604 (R) turns on, the AND circuit 4604 (R) to the OR circuit 46
05, the modulated wave phase angle ω, tO~ω□L in Fig. 45
It is output to modulation signal generation circuit 1005 as IO.

Next, the F/F 4601 (L), adder 4602 (L), F/F 4603 (1,) and AND circuit 4604 (1,) for the left channel are connected to the F/F 4 for the right channel.
601(R), Adder 4602(R), F/F46
03 (R) and AND circuit 4604 (R). Each circuit is connected to a controller 450
Modulator frequency MF(L) for the left channel from 1,
Left channel clock L CL, K, left channel set signal LSET and left channel clear signal LCLR
operate on the basis of Then, the accumulation result for the left channel, which is the output A and B of the adder 4602 (L), is the time division result of the left channel when the left channel clock L CLK becomes high level and the AND circuit 4604 (L) is turned on. At the timing, the modulated wave phase angle ωmto~ω from the AND circuit 4604 (L) passes through the OR circuit 4605 in FIG.
-tlO is output to modulation signal generation circuit 1005.

Next, FIG. 47 shows the configuration of accumulator 4502 of FIG. 45.

F/F 4701, adder 4702, F/F
4703 is for the right channel]”/F4601(R
), Adder 4602 (R), F/F 4603
It operates exactly the same as (R). Each circuit receives the carrier frequency CF from the controller 4501, the right channel clock RCLK, and the right channel set signal R3.
It operates based on ET and the right channel clear signal RCLR. The cumulative result, which is the output A+B of the adder 4702, is the carrier phase angle ωci[) common to each left and right channel.
~ωCt10, the carrier signal generation circuit 10 in FIG.
It is output on 03.

Further, FIG. 48 shows the configuration of envelope generator 4504 of FIG. 45.

In the figure, each signal ED(R), ED(L), E
D (A) corresponds to the setting data ED in Fig. 45, and RC
Although not shown in FIG. 45, LK and LCLK are control signals supplied from the controller 4501, respectively.

The right channel modulation depth function envelope data generation circuit 4801 (R) generates right channel modulation depth function setting data E D that is set in advance from the controller 1 to the roller 450.
(R), envelope data for the modulation depth function of the right channel is generated in synchronization with the rising edge of the right channel clock RCLK. Since this circuit can be directly applied to a known envelope generator used in ordinary electronic musical instruments, the details will be omitted.

The output of the right channel modulation depth function envelope data generation circuit 4801 (R) is output from the AND circuit 4802 (R) when the right channel clock RCLK becomes high level.
) is turned on at the time division timing of the right channel, it passes from the AND circuit 4802 (R) to the OR circuit 4803 and is output as the modulation depth function IO~110 to the multiplier 100 in FIG.
7 is output.

The left channel modulation depth function envelope data generation circuit 4801 (L), like the right channel modulation depth function envelope data generation circuit 4801 (R), uses the left channel modulation depth function setting data E D (which is set in advance by the controller 4501). Envelope data for the modulation depth function of the left channel is generated based on L) in synchronization with the rising edge of the left channel clock L CL K.

The output of the left channel modulation depth function envelope data generation circuit 4801 (L) is the left channel clock L.
CLK becomes high level and AND circuit 4802 (L)
At the time division timing of the left channel when is turned on, it passes from the AND circuit 4802 (L) to the OR circuit 4803 and is converted to the multiplier 1007 in FIG. 45 as the modulation depth function IO~110.
is output to.

The envelope data generation circuit 4804 for amplitude coefficient is also the envelope data generation circuit 48 for right channel modulation depth function.
01 (R), etc., envelope data for the amplitude coefficient is generated in synchronization with the rising edge of the right channel clock RCLK based on the amplitude coefficient setting data E D (A) set in advance by the controller 4501.

The output of the amplitude coefficient envelope data generation circuit 4804 is outputted to the multiplier 1010 in FIG. 45 as amplitude coefficients AMPO to AMP9.

The operation of the entire circuit shown in FIG. 45, centering on the accumulators 4502, 4503 and envelope generator 4504 shown above, will be explained according to the operation timing chart shown in FIG. 49.

First, the performer sets the envelope of the musical tone that he wants to output from the right channel using a setting section (not shown). As a result, the controller 4501 in FIG. 45 uses the right channel modulation depth function setting data E D (R) in FIG.
As such, parameters are set in the right channel modulation depth function envelope data generation circuit 4801(R). Next, the performer similarly sets the envelope of the musical tone he wishes to output from the left channel. As a result, left channel modulation depth function envelope data generation circuit 4801 (L) is used as left channel modulation depth function setting data E D (L).
) parameters are set. Furthermore, the player similarly sets the output amplitude envelope common to each of the left and right channels. As a result, the amplitude coefficient setting data ED (A
), the amplitude coefficient envelope data generation circuit 48
Parameters are set in 04.

After the above-mentioned setting operation, a performance operation is started, and when the performer specifies a pitch by pressing a key on a keyboard section (not shown), the controller 4501 in FIG. 45 selects a carrier frequency corresponding to the pitch information. CF to F/F in Figure 47
Set to 4701. Along with this, the right channel modulator frequency M F (R), which has a specific relationship with the carrier frequency CF, is F 7 F in FIG.
4601 (R), and the left channel modulation frequency M, which is slightly separated from the right channel.
F (L) is set to F/F 4601 (L).

Next, F/F4603(R) and 4603 in Fig. 46
(L) and F/F 4703 in FIG. 47 are each cleared by each clear signal RCLRXLCLR. Thereafter, an accumulation operation is performed sequentially according to the right channel clocks PCI, K and the left channel clock LCLK.

In this case, in the accumulator 4503 of FIG. 45, the accumulator 4503 of FIG.
The AND circuit 4604 (R) in FIG. 46 is turned on at the time division timing of the right channel when the right channel clock RCLK becomes high level as shown in FIG. As LO~ω,,Llo, Fig. 49 (a
) is output for the right channel. vice versa,
At the time S1j timing of the left channel when the left channel clock LCLK becomes high level, the AND circuit/1604(L) in FIG. Data is output.

Similarly to the above, the envelope generator 4 in FIG.
In the part in 504 that outputs the modulation depth function, the AND circuits 4802 (11) and 4802 (L,) in FIG. As functions IO to 110, data for the right channel and for the left channel are alternately output as shown in FIG. 49(C).

On the other hand, in the accumulator 4502 of FIG. 45, since the accumulation operation is executed at every break in the time division timing of the right channel, the carrier wave phase angle ω. , 0~ωcdO, Fig. 49 (
As shown in b), data common to the left and right channels is output.

Similarly, envelope generator 4504 in FIG.
In the part that outputs the amplitude coefficients in the left and right channels, new envelope data is output at every break in the time division timing of the right channel. Data common to each channel is output.

Based on each data output as described above, the fourth
Carrier signal generation circuit 1003 and modulation signal generation circuit 91 in FIG.
005, the multiplier 1007, the adder 1008, the triangular wave decoder 1009, and the multiplier 101o execute the processes described above, so that the decoded output MA O-MA9 corresponding to each of the right channel and the left channel is You can get it in time.

Here, as shown in FIGS. 49(e) and (f), each sample hold signal S/H(R) and S/H(L) is alternately high at each time division timing of the right channel and left channel. level, and the gates 4507 (R) and 4507 (L) are turned on alternately. As a result, the decoded outputs MA O to MA 9 corresponding to each of the right and left channels are converted into 0g signals to be tared by the D/A converter 1011, and then the sample and hold circuits 4505 (R ) and 4505 (L) alternately. And L P F4506 (R
) and 4506 (L), musical sound outputs corresponding to each of the right channel and the left channel are obtained, and are emitted from a sound system, not specifically shown.

As described above, the entire circuit of FIG. 45 operates in a time-division manner corresponding to each of the left and right channels, and in this case, the modulated wave phase angle generated for each channel. island.

0 to ω1nt10 and the modulation depth function IO to +10 provide a stereo output in which each channel is modulated slightly differently.

In this case, for example, if you want to get a chorus feeling in stereo, set the modulated wave phase angle ωmto~ω, 100 to several Hz to several tens of Hz, and in that case, the modulated wave phase angle ωmto~ω for the right channel and the left channel. The frequency of ωmt10 may be slightly different, or the modulation depth function IO~1
The value of 10 may be slightly different.

In the tenth embodiment, the modulated wave phase angle ω□t0~ωm
t10 and modulation depth functions 10 to IIO can be set separately for each left and right channel.

On the other hand, the carrier phase angle ω. , 0~ωcvlO,
Based on the specified pitch value based on the performance operation, each left and right channel can be slightly detuned and the amplitude coefficient AMP
A stereo effect can also be obtained by making the value of O-AMP9 different for each left and right channel.

Further, in this embodiment, the circuit has been described as a circuit for outputting tone waveforms of one channel for each of the left and right stereo channels. In contrast, each of the circuits in FIG.
If the 5(L) manual stage is configured so that the musical tones of each time-division channel are accumulated at each sampling period, it is possible to generate multiple musical sound waveforms in parallel in stereo. Become.

Furthermore, although this embodiment was realized as an electronic musical instrument that performs only one stage of modulation, it is possible to arbitrarily combine multiple modules, with one stage of modulation circuit as one module, as in the second embodiment described above. It is also possible to apply it to a circuit connected by This makes it possible to produce musical tones containing richer overtone components.

Note that it is also possible to construct a circuit that generates musical tones not only in two-channel stereo but also in multi-channel stereo, such as four channels or five channels.

11th 1st word ■ Next, an eleventh embodiment of the present invention will be described.

FIG. 50 is a configuration diagram of an eleventh embodiment of the present invention.

In the same figure, carrier wave ROM10I, modulation wave ROM10
2, MUL103, ADD104, decoder 10
The basic constituent parts consisting of 5 and MUL 106 are:
This embodiment is similar to the first embodiment shown in FIG. 1, and therefore its basic operation is also as described above.

In this case, in this embodiment, the carrier phase angle ω. 5. Modulated wave phase angle ω, t, modulation depth function I (t) and amplitude coefficient A
The method of generating (t) is distinctive. When a musical tone is produced on a natural instrument in response to the performer's performance operations, the pitch, timbre, volume, etc. of the musical tone not only change at a constant rate over time, but also change to a certain extent in -i. It often fluctuates randomly. Therefore, in this embodiment, control is performed so that random changes are added when each of the above signals is generated. As a result, this embodiment can continuously generate musical tones ranging from a single sine wave to musical tones with many overtone components, while at the same time producing natural fluctuations in the pitch, timbre, volume, etc. of the musical tones produced. It becomes possible to add

In FIG. 50, when a player operates a keyboard section 5001, frequency number information corresponding to the operated key is read from a frequency number memory 5002.

The frequency number information is information indicating the read width when reading the carrier signal Wc from the carrier wave ROM10I.

And the frequency number information is ADD5003,M
The information is input to the accumulator 5009 via the U L 5007, where the same information is sequentially accumulated to obtain the carrier phase angle ω.
. , is generated.

In this case, the carrier wave phase angle ω determines the basic pitch of the waveform output e generated from M tJ L 106, so if the frequency number information is a large value, the waveform output e
The pitch of e becomes high, and if the value is small, the pitch of the waveform output e becomes small. In addition, in MUL 5007, the frequency number information is multiplied by a coefficient k having a value of 1 or more, so that the carrier wave phase angle ωc output from the accumulator 5009
The amplitude of l is relatively large compared to the amplitude of the modulated wave phase angle ω, , output from the accumulator 5012. This process is carried out by carrier signal W output from carrier wave ROM10I.
The pitch of the musical tone is controlled based on the frequency of the carrier signal Wc by making the frequency of C relatively larger than the frequency of the modulation signal W outputted via the modulation wave ROM 102, which will be described later. This is a process for

Now, the random envelope generator 5004 (hereinafter referred to as random EC; 5004) is connected to the keyboard section 50.
An envelope signal having characteristics as shown in FIG. 51 is generated according to the key pressing speed at 01. Here, AT is the attack part, DK is the decay part, SU is the sustain part,
RE indicates a release part. Then, this envelope signal passes through the ADD5006 and the ADD500
3, it is added to the frequency number information. Therefore,
The pitch of the waveform output e changes according to the envelope characteristics shown in FIG. That is, for example, the pitch suddenly increases in the attack part AT immediately after key-on, the pitch attenuates in the decay part DK, becomes a constant pitch-sochi in the sustain part SU, and the pitch further attenuates in the release part RE after key-off. do.

In the above operation, when the random EG 5004 is outputting the envelope signal of the attack section AT, an instruction is issued to the random generator 5005 (hereinafter referred to as RND 5005). RN D5005 is a device that generates random numbers and outputs them as random signals. As a result, RN D 500 is generated only during the attack part AT.
A random signal is output from ADD 5006 and added to the envelope signal from random EG 5004. And the above addition result is ADD 50
03, it is added to the frequency number information. Therefore, only during the attack portion AT, a randomly changing component is added to the changing component of the frequency number information, and natural fluctuations can be added to the pitch of the musical tone immediately after the start of sound generation.

Next, the frequency number information output from the ADD5003 passes through the ADD5011 to the accumulator 5012.
are input and are accumulated sequentially here. and accumulator 50
A modulated wave phase angle ω, L is generated as an output of 12.

In this case, the modulated wave phase angle ω, , determines the timbre of the waveform output e produced by the MUL 106, and in particular determines the frequency of the harmonic components of the waveform output e.

In the above operation, when the random EG 5004 is outputting the envelope signal of the attack section AT as described above, an instruction is issued to the RN D 5010. R.N.
D5010 is a device that generates a random value asynchronously with RN D 5005 and outputs it as a random signal. As a result, a random signal is output from the RND 5010 only during the attack portion AT, and is added to the frequency number information in the ADD 5011. Therefore, attack part A
Only during the period T, a randomly changing component different from that when the carrier wave phase angle ωct is generated is added to the changing component of the frequency number information, and the timbre of the musical sound immediately after the start of sound generation, especially the frequency of the overtone component, is naturally changed. Fluctuation can be added.

The amplitude of the modulation signal WM is then controlled by the modulation depth function I (t) multiplied by M U L 103, which determines the depth of modulation as explained in the first embodiment (Fig. 4). (see (a) to (C), etc.), the amplitude characteristics of each overtone component of the waveform output e are determined. And the modulation depth function r
The basic characteristics of (t) are the modulation depth function envelope generator 5013 (hereinafter referred to as modulation depth function EG5
013).

Now, EG5013 for modulation depth function is EG5013 for random
Similarly to 5004, an envelope signal is generated according to the speed of key depression on the keyboard section 5001. Its characteristics are similar to those shown in FIG. Of course, the characteristics of the attack section AT, decay section DK, sustain section SU, and release section RE may be different. Then, this envelope signal passes through the ADD 5015 and modulation depth function r (t
) is supplied to the MUL 103. Therefore, based on the characteristics of the envelope signal, the modulation characteristics by the carrier signal Wc change, and the timbre of the waveform output e, especially the amplitude characteristics of each harmonic component, change.

In the above operation, when the modulation depth function EG 5013 is outputting the envelope signal of the sustain section SU (see FIG. 51), an instruction is issued to the RN D 5014. RND5014 is RND5005, RND5
010 is a device that asynchronously generates random numbers and outputs them as random signals. As a result, the sustain part S
A random signal is output from the RN D5010 only during the period U, and the EG50 for modulation depth function is output in the ADD5015.
It is added to the envelope signal from 13. Then, the above addition result is multiplied by the modulation signal WM in M U L 103 as the modulation depth function 1 (t) as described above. Therefore, only during the sustain section SU, a randomly changing component is added to the changing component of the modulation signal WM,
Natural fluctuations can be added to the timbre of the musical sound in the last part, particularly to changes in the amplitude characteristics of overtone components.

Next, the final amplitude (volume) of the waveform output e is M U
It is controlled by the amplitude coefficient A (t) multiplied by L 106, which determines the volume characteristics of the waveform output e. The basic characteristics of the amplitude coefficient A (t) are the volume envelope generator 5018 (hereinafter referred to as the volume EC
;5016).

Currently, EG5016 for volume is EG5004 for random.
, similar to the EG5013 for modulation depth function, the keyboard section 5001
Generates an envelope signal depending on the speed of the key press.

Its characteristics are similar to those shown in FIG. This envelope signal passes through ADD501B and has an amplitude coefficient A (t
) to the MUL 106. Therefore, the amplitude characteristics, ie, the volume characteristics, of the waveform output e change based on the characteristics of the envelope signal.

In the above operation, when the volume EG 5016 is outputting the envelope signal of the sustain section SU (see FIG. 51), an instruction is issued to the RN D 5017. R.N.
D5017 is RN D 5005, RN D501
0, Random 5014 is a device that asynchronously generates a random value and outputs it as a random signal. As a result, a random signal is output from the RN D5017 only during the sustain section SU, and the volume E is output in the ADD5018.
It is added to the envelope signal from G5016.

Then, the above addition result is the amplitude coefficient A (t,
), the decoding output is multiplied in MUL 106. Therefore, only during the sustain portion SU, a randomly changing component is added to the changing component of the waveform output e, and natural fluctuations can be added to the change in the volume of the musical tone in the sustain portion.

In the above embodiment, a randomly changing component is added to the pinch characteristic and the frequency characteristic of the harmonic component in the attack part AT of the musical tone characteristics, and a component that changes randomly is added to the frequency characteristic of the harmonic component in the sustain part SU. Although a randomly changing component is added, it is not limited to this; attack part AT, decay part DK
, the last part SU, the release part RE, and the like may perform the above operation.

Further, in the above embodiment, the keyboard section 5 of the electronic keyboard instrument
Although the control is performed based on the performance operation in 001, the present invention is not limited to this, and the control may be performed based on the performance operation of an electronic wind instrument, an electronic string instrument, or the like.

Chapter 12 of Service II Finally, a twelfth embodiment of the present invention will be described.

FIG. 52 is a configuration diagram of a twelfth embodiment of the present invention.

In the same figure, a carrier wave ROM 101, a modulation wave ROM 10
2, MUL103, ADD104, decoder 10
The basic constituent parts consisting of 5 and MUL 106 are:
This embodiment is similar to the first embodiment shown in FIG. 1, and therefore its basic operation is also as described above.

In this case, in this embodiment, the carrier phase angle ω. , and the modulated wave phase angle ω are set. In natural musical instruments, the frequency composition of the harmonic components of the musical tones produced differs not only depending on the timbre of the musical sound (the type of instrument), but also depending on, for example, the low and high ranges, or the speed (strength and weakness) of the playing operation. Often. Therefore, in this embodiment, when each of the above-mentioned signals is generated, control is performed so that the overtone characteristics of the musical tones to be produced are changed in accordance with the tone color setting and performance operation. As a result, this embodiment can continuously generate musical tones from only a single sine wave to musical tones containing many harmonic components, and at the same time, the frequency structure of the harmonic components at that time can be changed to tone settings and performance operations. It is possible to change it accordingly.

In FIG. 52, when a player operates a keyboard section 5201, frequency number information corresponding to the operated key is read from a frequency number memory 5202.

The frequency number information is information indicating the read width when reading the carrier signal WC from the carrier wave ROM10I.

The frequency number information is then input to the accumulator 5205 via the MUL 5203, where the information is sequentially accumulated to generate the carrier wave phase angle ωcl.

In this case, as in the case of the eleventh embodiment, if the carrier wave phase angle ωcL is the waveform output e generated from MUL 106,
To determine the basic pitch of the waveform output e, if the frequency number information is a large value, the pitch of the waveform output e will be high, and if the frequency number information is a small value, the pitch of the waveform output e will be small.

On the other hand, the frequency number information read from the frequency number memory 5202 is input to the accumulator 5207 through the MUL 5206, where it is sequentially accumulated.

Then, as the output of the accumulator 5207, the modulated wave phase angle ω
1 is generated.

In this case, as in the case of the eleventh embodiment, the modulated wave phase angle ω1 determines the timbre of the waveform output e generated from the MUL 106.

Here, the carrier phase angle ω generated as described above,
and the modulated wave phase angle ω, determine the frequency structure of the harmonic components of the waveform output e. Therefore, in this example,
The small ratio of the carrier wave phase angle ω, and the modulation wave phase angle ω, t is expressed as
Control as follows.

The frequency ratio control information generator 5204 generates different frequency ratio control information Kc depending on the type of tone set by the performer, the range of the keys pressed on the keyboard section 5201 for each tone, and the speed at which the keys are pressed. It remembers a set of zeros. Therefore, the tone color is set by a tone setting switch (not shown), and then the key code K is generated from the keyboard section 52o1 by the player's key press operation on the keyboard section 5201.
Based on C and velocity ■, the corresponding frequency ratio control information Kc and KmO set is generated by the frequency ratio control information generator 5204.
is output.

The frequency ratio control information Kc is M U L52
03, the frequency number information is multiplied by the frequency number information to generate the carrier phase angle ω. Further, the frequency ratio control information is multiplied by the frequency number information for generating the modulated wave phase angle ω in MUL 5206. As a result, the carrier wave phase angle ω is determined depending on the set timbre, the range of the pressed key, and the speed of the pressed key. The ratio of the values of the modulated wave phase angle ω and L changes, and the frequency structure of the harmonic components of the waveform output e output from the M UL 106 changes.

Through the above operation, the frequency composition of the harmonic components of the musical tone can be changed not only by the set tone, but also by the range of the pressed key and the speed of the pressed key, similar to the musical tone of an acoustic instrument. This makes it possible to produce musical tones.

Note that the modulated wave phase angle ω. , based on the modulated wave ROM10
The amplitude of the modulation signal WM output from MU L 1
This is controlled by the modulation depth function r (t) multiplied by The amplitude characteristics of each overtone component of e are determined. In this case, the modulation depth function r (t) can be configured to change depending on the speed of key depression on the keyboard section 5201, the elapse of time after the key depression, etc., although not specifically shown. Thereby, each amplitude characteristic of the overtone component of the waveform output e can be controlled.

Moreover, the final amplitude (volume) of the waveform output e is M U
It is controlled by the amplitude coefficient A (t) multiplied by L 106, which determines the volume characteristics of the waveform output e. In this case, the amplitude coefficient A (t) can also be configured to change depending on the speed of key depression on the keyboard section 5201, the elapse of time after the key depression, etc., although not specifically shown. Thereby, the volume characteristics of the waveform output e can be controlled.

In the above embodiment, the frequency ratio control information generator 520
Frequency ratio control information output from 4 (. Toni, the combination of n values is, for example, ``1 and 2j Town and 31'' ``1 and 4''
As a result, the pitch frequency of the waveform output e based on the carrier wave phase angle ωct is determined by the frequency number memory 5.
The frequency directly corresponds to the frequency number information from 2o2. However, for example, if the combination of Kc and K is ``2 and 5'',
J may be set as "3 and 6", and in this case, the pitch frequency of the waveform output e becomes a frequency corresponding to the value obtained by multiplying the frequency harmonic information by the value of.

Further, in the above embodiment, the keyboard section 5 of the electronic keyboard instrument
Although the control is performed based on the performance operation at 201, the present invention is not limited to this, and the control may be performed based on the performance operation on an electronic musical instrument such as an electronic wind instrument or an electronic stringed instrument.

〔Effect of the invention〕

According to the first aspect of the present invention, harmonic components can be added as frequency characteristics of a musical sound waveform, and musical tones that are close to the musical tones of an actual musical instrument can be synthesized, and unique synthesized tones can also be obtained. .

In particular, by setting a functional relationship other than the sine function and cosine function as the predetermined functional relationship in the waveform output section,
It is possible to include more high-order overtone components in the output musical sound waveform.

Furthermore, by allowing the mixing control section to arbitrarily change the mixing ratio of the modulation signal to the carrier signal, musical sound waveforms having various frequency characteristics can be generated.

In this case, by not only setting the mixing ratio before the start of the performance, but also changing it over time after the start of sound generation of the musical sound waveform, it is possible to gradually change the frequency characteristics of the musical sound waveform after the start of sound generation.

In particular, in the present invention, if the mixing ratio of the modulation signal is set to O in advance in the mixing control section, it is possible to generate a musical sound waveform consisting only of a sine wave or a cosine wave of a single frequency.

Alternatively, during a performance, for example, by setting the mixing ratio to a high value immediately after the start of sound generation, and then increasing the mixing ratio to O as time passes, the state containing many high-order harmonics can be changed to a single sine wave. It is possible to gradually control the frequency characteristics of the musical waveform so that it contains only a component or a single cosine wave component. In this way, it is possible to realize a process in which, like the musical tones of an actual musical instrument, after the start of sound generation, the amplitude of the high-order harmonic components gradually decreases, until only a single sine wave component remains.

Note that it is also possible to obtain the same effect when the mixing ratio is a predetermined value and the waveform shapes of the carrier signal and modulation signal are specific shapes.

In addition to the above control, the amplitude envelope characteristic of the musical waveform output from the waveform output section is also controlled by the amplitude envelope control section so as to attenuate over time, so that sound generation starts like the musical tone of an actual musical instrument. Thereafter, it is possible to realize a process in which the musical sound waveform gradually attenuates.

As described above, in the first aspect of the present invention, both a state containing many high-order harmonics and a state containing only a single sine wave component or a single cosine wave component can be easily generated. ,
This can be achieved using only a combination of ordinary ROMs, decoders, adders, multipliers, etc., making it possible to realize complex musical waveforms with a simple circuit configuration, resulting in improved quality. It becomes possible to provide high-quality electronic musical instruments and the like at low cost.

Next, according to the second aspect of the present invention, in addition to the features of the first aspect, the mixing characteristics in the mixing control section are not only set before the start of the performance, but also velocity information or key By changing the frequency characteristics in accordance with the range information, etc., it is possible to change the frequency characteristics of the musical sound waveform in accordance with the performance operation. In particular, by controlling the mixing characteristics, it is possible to control each amplitude value of the overtone component determined by the carrier signal and the modulation signal.

As a result, during a performance, for example, if the mixing ratio is set to a high value when the key is pressed strongly, and conversely, when the mixing ratio is set to be close to 0 when the key is pressed weakly, the high-order States containing many overtones and states containing only a single sine wave component or a single cosine wave component can be arbitrarily generated. It is also possible to control the frequency characteristics of a musical sound waveform to change over time by changing the mixing ratio over time, and also control the degree of change over time of the mixing ratio according to performance information. Then, the temporal change characteristics of the frequency characteristics of the musical sound waveform can also be varied in accordance with the performance operation.

As described above, in the second aspect of the present invention, it is possible to easily generate both a state containing many high-order harmonics and a state containing only a single sine wave component or a single cosine wave component, and
The state can be arbitrarily varied according to the performance operation.

Next, according to the third aspect of the present invention, first, with one basic processing unit, many high-frequency waves are processed from a musical sound waveform consisting only of a sine wave or a cosine wave of a single frequency, as in the first aspect. It is possible to easily generate musical sound waveforms including harmonic components.

Then, by making the first connection to the basic processing section, a waveform signal consisting only of a single sine wave or a cosine wave can be generated. Furthermore, if the second connection is made, the modulated waveform signal is used as the next modulated waveform, so it is possible to generate a very deeply modulated waveform signal. Furthermore, by performing the third connection, a waveform signal in which waveform signals containing different overtone components are mixed can be obtained. By combining these connections to finally obtain a tone waveform, it is possible to generate a tone waveform with extremely complex characteristics.

In particular, in the present invention, sufficient overtone components can be obtained even with simple connection combinations, and musical waveforms of only a single sine wave component or a single cosine wave component can also be easily obtained.

In addition, in the third aspect, instead of a configuration in which a plurality of basic processing units are connected, a configuration in which one basic processing unit is operated in a time-sharing manner allows one basic processing unit to be used, similar to the above case. The following effects can be obtained, the circuit scale can be reduced, and a configuration with a high degree of freedom in connection combinations can be realized.

According to the fourth aspect of the present invention, the user, the performer,
In the musical sound waveform generator of the third aspect, since it is possible to set efficient connection combinations and display this in an easy-to-understand format, it is possible to realize a musical sound waveform generator with very good operability. can do.

According to the fifth aspect of the present invention, for example, from a connection combination that can generate a musical sound waveform containing a large number of high-order harmonic components,
Since the connection combination can be automatically changed during sound generation to a connection combination that can generate a musical sound waveform containing only a single sine wave or cosine wave component, it is possible to perform a very wide range of sound generation operations.

According to the sixth aspect of the present invention, the operation based on the third aspect can be realized polyphonically.

Next, according to the seventh aspect of the present invention, in addition to the first to third connections in the third aspect, the modulation signal input to one basic processing unit is connected to the waveform obtained by the own basic processing unit. By including the fourth connection that makes the signal a feed-hacked signal, it is possible to make the amplitude envelope characteristic of the overtone component of the musical sound waveform unique, and it is possible to generate a U-like musical sound waveform.

In particular, as in the present invention, it is possible to obtain sufficient overtone components even with a simple connection combination, while also being applied to a configuration in which a musical sound waveform of only a single sine wave component or a single cosine wave component can be easily obtained. In this case, a great effect can be obtained.

According to the eighth aspect of the present invention, unlike the seventh aspect, the basic processing unit that feeds back the waveform signal to the modulation signal is
By using not the basic processing unit itself but a basic processing unit some time ago, the amplitude envelope characteristics of the overtone components of the musical sound waveform can be made unique and different from the seventh aspect,
It is possible to generate characteristic musical sound waveforms.

According to the ninth aspect of the present invention, since the modulation signal generation section can selectively generate a plurality of types of modulation signals, the mixing control section can vary the characteristics of the modulation signal mixed with the carrier signal. becomes. As a result, it becomes possible to output many types of musical sound waveforms having various overtone characteristics from the waveform output section.

Next, according to the tenth aspect of the present invention, the signals are controlled independently for each stereo channel so that, for example, the modulation signal, mixing rate, etc. are different between each stereo channel, and the carrier signal is common. By generating a mixed signal for each stereo channel and performing modulation based on these independently generated mixed signals, it is possible to easily obtain a musical sound waveform for each stereo channel.

In addition, by arbitrarily setting the mixing ratio of the modulated signal to the carrier signal in the mixing ratio control section between 0 and other values in advance or over time, it is possible to change the mixing ratio from a state containing many high-order harmonics to a simple one. It is possible to freely control the generation up to a state that includes only one sine wave component or a single cosine wave component, and by doing so, it is possible to obtain musical sounds close to the musical sounds of actual musical instruments or unique synthesized sounds in stereo. be able to.

According to the eleventh aspect of the present invention, it is possible to continuously generate a musical sound waveform having only a single sine wave or cosine wave component, which is a feature of the present invention, to a musical tone having many overtone components, and at the same time, it is possible to generate a musical sound waveform having a component of only a single sine wave or a cosine wave, and at the same time Natural fluctuations can be added to the pitch, timbre, volume, etc. of musical sounds.

This makes it possible to achieve characteristics similar to the fluctuations of natural musical instruments.

Finally, according to the twelfth aspect of the present invention, similarly to the second aspect, it is possible to change the frequency characteristics of the musical sound waveform according to the set tone, key press operation, or key range of the pressed key. becomes. In particular, by controlling the frequency ratio of the carrier signal and the modulation signal, it is possible to control the frequency structure of the harmonic components themselves. As a result, it becomes possible to add unique characteristics different from the second aspect to the musical sound waveform.

[Brief explanation of drawings]

FIG. 1 is a diagram showing the principle configuration of the first embodiment, and FIG. 2 is a diagram showing the principle configuration of the first embodiment.
Figure 3 is an explanatory diagram of the operation of the principle configuration of the first embodiment when no modulation is performed; Figures 4 (a) to (i) are , a diagram showing the relationship between I (t) and waveform output e in the principle configuration of the first embodiment (ωmt
-ωct), Figures 5(a) to (i) are diagrams showing the relationship between Bt) and the frequency characteristics of the waveform output e in the principle configuration of the first embodiment (ω1-ω.,). The figure shows the waveform output e in the principle configuration of the first embodiment.
FIG. 7 (aL (b) is a comparison diagram of the frequency characteristics of .
FIGS. 8(a) to 8(d) are diagrams showing other aspects of the stored waveforms of the carrier wave ROM and the triangular wave decoder in the principle configuration of the first embodiment, 9(a) to (C) are diagrams showing examples of stored waveforms of the modulated wave ROM in the principle configuration of the first embodiment, FIG. 10 is a concrete configuration diagram of the first embodiment, FIG. 11 is a diagram showing a first circuit example of the carrier signal generation circuit in the specific configuration of the first embodiment, and FIGS. 12(a) to (f) are diagrams showing the specific configuration of the first embodiment. FIG. 13 is a diagram illustrating the operation of a first circuit example of the carrier signal generation circuit in the configuration, and FIG. 14 is a diagram showing a second circuit example of the carrier signal generation circuit in the specific configuration of the first embodiment. (a)
~((2) is an operational explanatory diagram of the second circuit example of the carrier signal generation circuit in the specific configuration of the first embodiment, and FIG. 15 is an explanatory diagram of the triangular wave decoder in the specific configuration of the first embodiment. A diagram showing a circuit example, FIG. 16 is a specific configuration diagram of the second embodiment, FIG. 17 is an output characteristic diagram of the envelope generator in the specific configuration of the second embodiment,
FIG. 18 is a relationship diagram between address data values and setting data types in the specific configuration of the second embodiment, and FIG.
20 is a flowchart of the main operation in the specific configuration of the second embodiment. FIG. 21 is a flowchart of the operation of the CF seso 1- in the specific configuration of the second embodiment. FIG. 22 is a flowchart of the MF upper set operation in the configuration.
23 is an operation flowchart of the Ch2 set in the specific configuration of the second embodiment. FIG. 24 is an operation flowchart of the ON process in the specific configuration of the second embodiment. is an operation flowchart of off processing in a specific configuration of the second embodiment, FIG. 26 is a diagram showing tone data in a specific configuration of the second embodiment, and FIG. 27 is a diagram showing tone data in a specific configuration of the second embodiment. FIG. 28 is a diagram showing an example of the operation of the envelope generator in the specific configuration of
29 is a diagram showing the principle configuration of the second embodiment, FIG. 30 is a circuit example of the accumulator 2907 according to the specific configuration of the second embodiment. Figure 31 showing
The figure shows an accumulator 290 in a specific configuration of the second embodiment.
FIGS. 32(a) to 32(g) are operation timing charts of the specific configuration of the second embodiment, and FIGS. FIG. 34 is a diagram showing an example of the formation in the specific configuration of the example. FIG. 34 is a diagram showing the specific configuration of the fourth embodiment. FIG. , FIG. 36 is an operation timing chart of the fifth embodiment, FIGS. 37(a) and (b) are operation timing charts of the sixth embodiment, and FIG. 38 is a specific diagram of the seventh embodiment. Configuration diagram, Figure 39 (
a) to (d) are diagrams showing a formation example in the specific configuration of the seventh embodiment, FIG. 40 is a diagram showing a formation example in the eighth embodiment, and FIG. Fig. 42 (a) is a principle configuration diagram of the embodiment of
) to (C) are explanatory diagrams of the operation of the modulated wave phase angle ROM and the triangular wave decoder in the principle configuration of the ninth embodiment, and FIG. 43 is a case where W9 is a sawtooth wave in the principle configuration of the ninth embodiment. FIG. 44 is a diagram showing a circuit example of a modulated wave phase angle ROM in a specific configuration of the ninth embodiment, and FIG. 10th
46 is a diagram showing a circuit example of an accumulator for modulated signals in the specific configuration of the 10th embodiment, and FIG. FIG. 48 is a diagram showing a circuit example of the carrier signal accumulator in a specific configuration, and FIG. 49 is a diagram showing a circuit example of the enherobe generator in the specific configuration of the tenth embodiment. a) to (h) are timing charts 1-1 and 5 of stereo operation in the specific configuration of the tenth embodiment.
Fig. 0 is a configuration diagram of the eleventh embodiment, Fig. 51 is a diagram showing characteristic examples of the attack section, decay section, sustain section, and release section, and Fig. 52 is the configuration of the twelfth embodiment. It is a diagram. 101...Carrier wave ROM. 102... Modulated wave ROM, 103.106... Multiplier (MUL), 104...
Adder (ADD), 105...decoder. Patent applicant: Casio Computer Co., Ltd.
Real jig (-bug j no uu)
-Zushi Diagram Aa'I denifuzure divination dog day), zuY broiled, le bow I 1 CF
,,SoF,,7th shift)￥Front one-)・Figure 20Figure 22Figure 21 Figure-i2. j Mishira Hete-57 "j (-2 or 2-danbu 160
1 Tsuno 1〉、Nino゛1ri ch2 h・n) Hitoshi Yoryoku) Dō7
0-1 la\・-)-Fig. 23 ■ Staff arrangement ≦ pieces (C) 7th tiger j ← wing body reflection of stop J, 1 mi h-/su form Fig. 39 Butan-i series Diagram shown (G) WM (B element 9 implementation 4 row heavy engineering T side) Ebisu 2 11. maple mound

Claims (1)

[Claims] 1) A musical sound waveform generator that generates a musical sound waveform based on a mixed signal obtained by mixing a modulation signal with a carrier signal, comprising: a carrier signal generating means for generating the carrier signal; and a modulation signal. a modulated signal generating means that generates a modulated signal, and outputs a mixed signal by mixing the modulated signal with a carrier signal generated from the carrier signal generating means, and in this case, the mixing ratio of the modulated signal with respect to the carrier signal is set from 0 to 0. a mixing control means for controlling up to an arbitrary mixing ratio; and a waveform output means for outputting a musical waveform by inputting a mixing signal outputted from the mixing control means, the input and output of which have a predetermined functional relationship. The predetermined functional relationship in the waveform output means is neither a sine function nor a cosine function, and the carrier signal generated from the carrier signal generation means is the same as the modulated signal in the mixing control means. Mixing ratio for carrier signal is 0
The musical sound waveform generating device is characterized in that the musical sound waveform generated from the waveform output means is a signal set so that it becomes a sine wave or a cosine wave of a single frequency when controlled so that . 2) The carrier signal generating means inputs a carrier wave phase angle ω_c_t [rad] that increases at a constant angular velocity over time, and outputs a carrier signal W_c [rad] expressed by the following formula (π is pi, sin indicates sine wave operation), W_c=
(π/2) sinω_c_t ... (0≦ω_c_t≦π/2) W_c=π-(π/2) sinω_c_t ... (π/2≦ω_c_t≦3π/2) W_c=2π+(π/2) sinω_c_t...(3
π/2≦ω_c_t≦2π) The waveform output means inputs the mixed signal x and outputs a musical sound waveform D based on the following formula: D=(2/π)x (0≦x≦π/ 2) D=-1+(2/π)(3π/2-x)...(π/2≦x≦3π/2) D=-1+(2/π)(x-3π/2)... - (3π/2≦x≦2π) The musical sound waveform generating device according to claim 1, wherein: (3π/2≦x≦2π). 3) The carrier signal generating means inputs the carrier wave phase angle ω_c_t [rad] that increases at a constant angular velocity over time, and outputs the carrier signal W_c [rad] shown by the following formula (π is pi, sin indicates sine wave operation), W_c=
(π/4) sinω_c_t...(0≦ω_c_t≦π/2) W_c=-(π/4) sinω_c_t+π...(π
/2≦ω_c_t≦3π/2) W_c=(π/4) sinω_c_t+2π...(3
(π/2≦ω_c_t≦2π) The waveform output means inputs the mixed signal x and outputs a musical sound waveform D based on the following formula: D=(4/π)x (0≦x≦π/ 4) D=1...(π/4≦x≦3π/4) D=-(4/π)x+4...(3π/4≦x≦5π/4) D=-1...( 2. The musical sound waveform generator according to claim 1, wherein: 5π/4≦x≦7π/4) D=(4/π)x−8 (7π/4≦x≦2π). 4) The carrier signal generating means inputs a carrier wave phase angle ω_c_t [rad] that increases at a constant angular velocity over time, and outputs a carrier signal W_c [rad] expressed by the following formula (π is the constant of pi. ), W_c=ω_c_t/2...(0≦ω_c_t≦π/2) W_c=ω_c_t/2+π/2...(π/2≦ω_c_t≦3π/2) W_c=ω_c_t/2+π...( 3π/2≦ω_c_t≦2π) The waveform output means inputs the mixed signal x and outputs a musical sound waveform D based on the following formula (sin indicates a sine wave operation), D=sin2x (0≦ x≦π/4) D=1...(π/4≦x≦3π/4) D=sin(2x-π)...(3π/4≦x≦5π/4) D=-1 ・. . . (5π/4≦x≦7π/4) D=sin (2x−2π) . . . (7π/4≦x≦2π) The musical sound waveform generating device according to claim 1. 5) The carrier signal generating means inputs the carrier wave phase angle ω_c_t [rad] which increases at a constant angular velocity over time, and outputs the carrier signal W_c [rad] shown by the following formula (π is the pi ratio, sin indicates sine wave operation), W_c=
ω_c_t...(0≦ω_c_t≦π/2) W_c=-(π/2) sinω_c_t+π...(π
/2≦ω_c_t≦3π/2) W_c=ω_c_t (3π/2≦ω_c_t≦2π) The waveform output means inputs the mixed signal x and outputs a musical sound waveform D based on the following equation, D= sinx...(0≦x≦π/2) D=-(2/π)x+2...(π/2≦x≦3π/2) D=sinx...(3π/2≦x≦2π ) The musical sound waveform generator according to claim 1, characterized in that: 6) The carrier signal generating means inputs the carrier wave phase angle ω_c_t [rad] which increases at a constant angular velocity over time, and outputs the carrier signal W_c [rad] shown by the following formula (π is pi, sin indicates sine wave operation), W_c=
(π/2) sinω_c_t ...(0≦ω_c_t≦π/2) W_c=ω_c_t ...(π/2≦ω_c_t≦3π/2) W_c=(π/2) sinω_c_t+2π...(3
π/2≦ω_c_t≦2π) The waveform output means inputs the mixed signal x and outputs a musical sound waveform D based on the following formula: D=(2/π)x (0≦x≦π/ 2) D=sinx...(π/2≦x≦3π/2) D=(2/π)x-4...(3π/2≦x≦2π) According to claim 1, Musical sound waveform generator. 7) The musical sound waveform according to claim 1, further comprising: a mixing ratio control means for temporally changing the mixing ratio of the modulated signal to the carrier signal by the mixing control means after the sounding of the musical sound waveform starts. Generator. 8) The musical sound waveform generating device according to claim 1, further comprising amplitude envelope control means for temporally changing amplitude envelope characteristics of the musical sound waveform output from the waveform output means. 9) The carrier signal generation means, the modulation signal generation means, the mixing control means and the waveform output means perform processing on a plurality of sound generation channels in a time-sharing manner, and generate a plurality of musical tones assigned correspondingly to each sound generation channel. The musical sound waveform generator according to claim 1, wherein the waveform is output polyphonically. 10) A musical sound waveform generation method for generating a musical sound waveform based on a mixed signal obtained by mixing a modulation signal with a carrier signal, the method comprising a carrier signal generation step for generating a carrier signal, and a modulation signal generation step for generating a modulation signal. step, mixing the modulated signal with the carrier signal generated by the carrier signal generating step to output a mixed signal, and in that case, adjusting the mixing ratio of the modulated signal to the carrier signal from 0 to an arbitrary mixing ratio. and a waveform output step that outputs a musical waveform by inputting the mixed signal outputted by the mixing control step, the input and output of which have a predetermined functional relationship, and the waveform output step The predetermined functional relationship in is neither a sine function nor a cosine function, and the carrier signal generated in the carrier signal generation step has a mixing ratio of the modulated signal to the carrier signal in the mixing control step. 0, the musical sound waveform generated by the waveform output step is a signal set to be a sine wave or a cosine wave of a single frequency. Method. 11) A musical sound waveform generating device that generates a musical sound waveform based on a mixed signal obtained by mixing a modulation signal with a carrier signal, and controls the characteristics of the musical sound waveform based on performance information generated in response to a performance operation. a carrier signal generation means for generating a carrier signal corresponding to the performance information; a modulation signal generation means for generating a modulation signal corresponding to the performance information; and a modulation signal generation means for generating the modulation signal from the carrier signal generation means. mixing control means for outputting a mixed signal by mixing it with a carrier signal, and controlling the mixing ratio of the modulated signal with respect to the carrier signal to change in accordance with a mixing characteristic corresponding to the performance information; waveform output means that has a predetermined functional relationship and outputs a musical waveform by inputting the mixed signal output from the mixing control means, and the predetermined functional relationship in the waveform output means is a sine function or a cosine function. In either case, the carrier signal generated by the carrier signal generating means has a mixing ratio of the modulated signal to the carrier signal of 0 in the mixing control means.
The musical sound waveform generating device is characterized in that the musical sound waveform generated from the waveform output means is a signal set so that it becomes a sine wave or a cosine wave of a single frequency when controlled so that . 12) The performance operation is a key pressing operation on a keyboard, and the mixing control means controls the mixing characteristic in accordance with at least one of the speed of the key pressing operation and the range of the pressed key. The musical sound waveform generator according to claim 11, characterized in that: 13) The musical sound waveform generation according to claim 11, further comprising an amplitude envelope control means for temporally changing the amplitude envelope characteristic of the musical sound wave outputted from the waveform output means in correspondence with the performance information. Device. 14) The carrier signal generation means, modulation signal generation means, mixing control means and waveform output means time-divisionally process a plurality of sound generation channels, and generate a plurality of musical tones assigned correspondingly to each sound generation channel. The musical sound waveform generator according to claim 11, wherein the waveform is output polyphonically. 15) Each includes a carrier signal generating means for generating a carrier signal, a mixed signal outputting means for mixing a modulated signal with the carrier signal and outputting a mixed signal, and an input and an output having a predetermined functional relationship, and Waveform output means for outputting a waveform signal by inputting the mixed signal output by the mixed signal output means; and amplitude envelope characteristic control means for controlling the temporal amplitude envelope characteristic of the waveform signal output by the waveform output means. at least one basic processing means comprising: a first connection for inputting said modulated signal having a value of 0 or near 0 to one said basic processing means, or another waveform signal as a new modulated signal input; a second connection input to one of the basic processing means, or a new waveform signal by mixing the waveform signal obtained by one of the basic processing means with each waveform signal obtained by at least one other basic processing means; waveform input/output control means that connects the basic processing means and outputs the waveform signal output from the final stage as a musical sound waveform by combining the obtained third connections based on a preset connection combination; The predetermined functional relationship in the waveform output means is neither a sine function nor a cosine function, and the carrier signal generated by the carrier signal generation means is mixed by the mixed signal output means. The waveform signal generated by the waveform output means is a signal set to be a sine wave or cosine wave of a single frequency when a mixing ratio of the modulated signal to the carrier signal is 0. A musical sound waveform generator featuring: 16) a carrier signal generation step of generating a carrier signal; a mixed signal output step of mixing a modulation signal with the carrier signal and outputting a mixed signal; and input and output having a predetermined functional relationship and outputting the mixed signal. a waveform output step of inputting the mixed signal outputted by the step and outputting a waveform signal; and an amplitude envelope characteristic control step of controlling the temporal amplitude envelope characteristic of the waveform signal outputted by the waveform output step. A basic processing step of
Or the first calculation to obtain a waveform signal by executing the basic processing step as a value near 0, or the basic processing step using a waveform signal obtained at a processing timing earlier than the current processing timing as a new modulation signal input. or a second operation to obtain a new waveform signal by performing an operation similar to the first or second operation to obtain a waveform signal and at least one processing timing earlier than the current processing timing. A third operation of mixing each waveform signal obtained in the above is executed based on a preset connection combination, and the waveform signal obtained at the last processing timing in each operation period is a waveform input/output control step that is generated as a musical sound waveform, and the predetermined functional relationship in the waveform output step is neither a sine function nor a cosine function, and the carrier signal generated by the carrier signal generation step The signal is such that when the mixing ratio of the modulated signal mixed in the mixed signal output step to the carrier signal is 0, the waveform signal generated in the waveform output step is a sine wave or a cosine wave of a single frequency. A musical sound waveform generation method characterized in that the signal is set so that 17) A carrier signal generating means for generating a carrier signal, a mixed signal outputting means for mixing a modulated signal with the carrier signal and outputting a mixed signal, the input and output having a predetermined functional relationship, and the mixed signal outputting means. waveform output means for inputting the mixed signal output by the means and outputting a waveform signal; and amplitude envelope characteristic control means for controlling temporal amplitude envelope characteristics of the waveform signal output by the waveform output means. a plurality of processing timings are defined as one calculation period, and the basic processing means is operated with the modulation signal input set to a value of 0 or a value close to 0 for each of the processing timings within each calculation period; A first operation for obtaining a waveform signal, or a second operation for operating the basic processing means using a waveform signal obtained at a processing timing earlier than the current processing timing as a new modulation signal input to obtain a new waveform signal. , or the first or second
A third operation of obtaining a waveform signal by performing an operation similar to the operation of , and mixing it with each waveform signal obtained at at least one processing timing before the current processing timing,
a waveform input/output control means that executes based on a preset connection combination and generates a waveform signal obtained at the last processing timing in each calculation cycle as a musical sound waveform of the calculation cycle; The predetermined functional relationship in the waveform output means is neither a sine function nor a cosine function, and the carrier signal generated by the carrier signal generation means is the modulated signal mixed by the mixed signal output means. The waveform signal generated by the waveform output means is a signal set to be a sine wave or a cosine wave of a single frequency when a mixing ratio for the carrier signal is 0. Musical sound waveform generator. 18) The waveform input/output control means includes first and second accumulating means, and a first one that selectively inputs the waveform signal output from the basic processing means to the first or second accumulating means. a second switch means for selectively inputting a value of 0 or a value near 0 or the output of the second accumulation means as a modulation signal to the basic processing means; the calculation period, and the accumulation operations of the first and second accumulation means and the selection operations of the first and second switch means are performed in advance at each processing timing within each calculation period. a multistage operation control means for operating the basic processing means in multiple stages in each of the processing timing units by controlling based on a set connection combination; and the first accumulating means at the end of each calculation cycle. 18. The musical sound waveform generating device according to claim 17, further comprising: musical sound waveform output means for outputting the output of the calculation period as a musical sound waveform of the calculation cycle. 19) The musical sound waveform generator according to claim 17, further comprising: a setting means for causing the user to set the connection combination; and a display means for displaying the connection combination set by the setting means. . 20) The setting means causes the user to set the input/output relationship in the basic processing means between the respective processing timings using a symbolic arithmetic expression,
The display means sets the connection combination set by the setting means by displaying the input/output relationship in the basic processing means between each processing timing using a symbolic arithmetic expression. 20. The musical sound waveform generating device according to claim 19, wherein the musical sound waveform generating device displays a match. 21) The display means displays the connection combination set by the setting means by setting the basic processing means for each processing timing as one unit and displaying the connection relationship between the units as a graphic. 20. The musical sound waveform generator according to claim 19. 22) In the waveform input/output control step, the first, second, or third calculation is executed based on a preset connection combination that changes temporally after the start of sound generation of each musical sound waveform. 17. The musical sound waveform generation method according to claim 16, wherein the musical sound waveform is generated by performing the following steps. 23) The waveform input/output control means executes the first, second, or third calculation based on a preset connection combination that changes temporally after the start of sound generation of each musical sound waveform. The musical sound waveform generating device according to claim 17, wherein the musical sound waveform is generated by performing the following steps. 24) In the waveform input/output control step, processing is performed on a plurality of sound generation channels in a time-sharing manner, and a plurality of musical sound waveforms assigned to each of the sound generation channels are polyphonically output. 17. The musical sound waveform generation method according to claim 16. 25) The waveform input/output control means is characterized in that it processes a plurality of sound generation channels in a time-sharing manner, and polyphonically outputs a plurality of musical sound waveforms assigned to each of the sound generation channels. The musical sound waveform generator according to claim 17. 26) Each of them includes a carrier signal generation means for generating a carrier signal, and outputs a mixed signal by mixing a modulated signal with the carrier signal, and in that case, sets the mixing ratio of the modulated signal to the carrier signal to an arbitrary mixing ratio from 0 to the carrier signal. a plurality of waveform output means, the input and the output of which have a predetermined functional relationship, and which output a waveform signal by inputting the mixed signal output from the mixing control means; basic processing means; and a first connection for inputting the modulated signal having a value of 0 or a value near 0 to one of the basic processing means, or another waveform signal as a new modulation signal input to one of the basic processing means. or a third connection for obtaining a new waveform signal by mixing the waveform signal obtained by one of the basic processing means with each waveform signal obtained by at least one other basic processing means. , or by combining a fourth connection in which the modulation signal input to one of the basic processing means is a signal obtained by feeding back the waveform signal obtained by the basic processing means, based on a preset connection combination. , a waveform input/output control means that connects the plurality of basic processing means and outputs the waveform signal output from the final stage as a musical sound waveform, and the predetermined functional relationship in the waveform output means is a sine function or a cosine function. The carrier signal generated by the carrier signal generating means has the waveform when the mixing ratio of the modulated signal to the carrier signal mixed by the mixing control means is 0. A musical sound waveform generating device characterized in that the waveform signal generated by the output means is a signal set to be a sine wave or a cosine wave of a single frequency. 27) Each includes a carrier signal generating means for generating a carrier signal, and outputs a mixed signal by mixing a modulated signal with the carrier signal, and in that case, sets a mixing ratio of the modulated signal to the carrier signal from 0 to an arbitrary mixing ratio. a plurality of waveform output means, the input and the output of which have a predetermined functional relationship, and which output a waveform signal by inputting the mixed signal output from the mixing control means; The basic processing means of the previous stage and a connection for inputting the waveform signal obtained by the basic processing means of the previous stage to the current basic processing means as a new modulation signal input are combined in multiple stages in succession, and the basic processing means of the final stage waveform input/output control means for outputting the obtained waveform signal as a musical sound waveform and feeding it back as the modulation signal input to the basic processing means at the first stage, wherein the predetermined functional relationship in the waveform output means is a sine waveform. When the relationship is neither a function nor a cosine function, and the carrier signal generated by the carrier signal generating means has a mixing ratio of the modulated signal to the carrier signal mixed by the mixing control means is 0. A musical sound waveform generating device, wherein the waveform signal generated by the waveform output means is a signal set to be a sine wave or a cosine wave of a single frequency. 28) A musical sound waveform generator that generates a musical sound waveform based on a mixed signal obtained by mixing a modulation signal with a carrier signal, comprising: a carrier signal generating means for generating the carrier signal; a modulated signal generating means that generates a modulated signal, and mixes the selectively generated modulated signal with a carrier signal generated from the carrier signal generating means to output a mixed signal;
Mixing control means for controlling a mixing ratio of the modulated signal to the carrier signal in that case between 0 and an arbitrary mixing ratio; and an input and an output having a predetermined functional relationship and output from the mixing control means. a waveform output means for outputting a musical waveform by inputting a mixed signal, and the predetermined functional relationship in the waveform output means is neither a sine function nor a cosine function, and is generated from the carrier signal generation means. The mixing ratio of the modulated signal to the carrier signal is 0 by the mixing control means.
The musical sound waveform generating device is characterized in that the musical sound waveform generated from the waveform output means is a signal set so that it becomes a sine wave or a cosine wave of a single frequency when controlled so that . 29) The modulation signal generating means includes a storage means that stores in advance a plurality of types of modulation functions, and one of the plurality of types of modulation functions stored in the storage means.
a selection means for selecting one of the modulated wave phase angle signals; 29. The musical sound waveform generator according to claim 28, further comprising: output means for outputting the modulated signal by converting the modulated signal based on a function. 30) The musical tone waveform generating device according to claim 28, further comprising amplitude envelope control means for temporally changing the amplitude envelope characteristic of the musical tone waveform output from the waveform output means. 31) The carrier signal generation means, the modulation signal generation means, the mixing control means, and the waveform output means time-divisionally process a plurality of sound generation channels, and generate a plurality of musical tones assigned correspondingly to each sound generation channel. 29. The musical sound waveform generator according to claim 28, wherein the waveform is output polyphonically. 32) A musical sound waveform generation method for generating a musical sound waveform in stereo based on a mixed signal obtained by mixing a modulation signal with a carrier signal, the method comprising: at least one of the characteristics of the modulation signal, the characteristics of the carrier signal, or the mixing characteristics. a first step of performing a process of mixing the carrier signal and a modulation signal such that the carrier signal and the modulation signal are different between each stereo channel; and inputting each mixed signal obtained in the first step for each of the stereo channels; a second output that outputs an independently modulated stereo musical sound waveform as
A method for generating a musical sound waveform, comprising the following steps. 33) A musical sound waveform generator that generates a musical sound waveform in stereo based on a mixed signal obtained by mixing a modulation signal with a carrier signal, comprising: a carrier signal generating means for generating the carrier signal; and a modulator for generating the modulation signal. signal generating means; mixing means for mixing the modulated signal with a carrier signal generated from the carrier signal generating means and outputting a mixed signal; and a waveform output that outputs a musical waveform by inputting the mixed signal outputted from the mixing means and having a predetermined functional relationship between the input and the output. and time-divisionally controlling at least one of the carrier signal generating means, the modulating signal generating means, or the mixing rate controlling means so that they generate mutually different values between the respective stereo channels;
Based on this, by inputting the mixed signal for each stereo channel output from the mixing means at each time division timing to the waveform output means, each musical sound waveform is independently modulated for each stereo channel. time division control means for outputting a signal, the predetermined functional relationship in the waveform output means is neither a sine function nor a cosine function, and the carrier signal generated from the carrier signal generation means is When the mixing ratio control means controls the mixing ratio of the modulation signal to the carrier signal to be 0, the musical sound waveform generated from the waveform output means becomes a sine wave or a cosine wave of a single frequency. A musical sound waveform generator characterized in that the signal is set as follows. 34) An amplitude envelope control means for temporally changing the amplitude envelope characteristics of each of the musical sound waveforms independently outputted from the waveform output means for each of the stereo channels with characteristics that differ from each other between the respective stereo channels. 34. The musical sound waveform generator according to claim 33, characterized in that: . 35) The carrier signal generation means, the modulation signal generation means, the mixing means, the mixing rate control means, the waveform output means, and the time division control means further time-divide each of the stereo channels into a plurality of sound generation channels, and perform processing; 34. The musical sound waveform generator according to claim 33, wherein the musical sound waveforms assigned to each of the sound generation channels are output in stereo and polyphonically. 36) At least one of the carrier signal generated by the carrier signal generation means, the modulation signal generated by the modulation signal generation means, or the mixing ratio controlled by the mixing control means includes a randomly changing component. 2. The musical sound waveform generating apparatus according to claim 1, further comprising random control means for controlling the random control means to include the random control means. 37) At least one of the carrier signal generated by the carrier signal generating means, the modulating signal generated by the modulating signal generating means, or the mixing ratio controlled by the mixing control means starts sounding the musical sound waveform. 2. The musical sound waveform generator according to claim 1, further comprising random control means for controlling the sound waveform to include a component that changes randomly in a predetermined time interval thereafter. 38) The musical sound waveform generator according to claim 37, wherein the predetermined time interval is any one of an attack portion, a decay portion, a sustain portion, and a release portion in the amplitude envelope characteristic of the musical sound waveform. 39) Amplitude envelope random control means for controlling the amplitude envelope characteristic of the tone waveform outputted from the waveform output means to include a component that changes randomly in a predetermined time interval after the start of sound generation of the tone waveform; 38. The musical sound waveform generator according to claim 37. 40) A musical sound waveform generator that generates a musical sound waveform based on a mixed signal obtained by mixing a modulation signal with a carrier signal, and controls the characteristics of the musical sound waveform based on performance information generated in response to a performance operation. a carrier signal generating means for generating a carrier signal; a modulating signal generating means for generating a modulating signal; mixing the modulating signal with the carrier signal generated from the carrier signal generating means and outputting a mixed signal; Mixing control means for controlling a mixing ratio of the modulated signal to the carrier signal in that case between 0 and an arbitrary mixing ratio; and an input and an output having a predetermined functional relationship and output from the mixing control means. a waveform output means for outputting a musical sound waveform by inputting a mixed signal; and a frequency ratio control means for controlling the frequency ratio of the carrier signal and the modulation signal to a frequency ratio corresponding to the performance information, The predetermined functional relationship in the waveform output means is neither a sine function nor a cosine function, and the carrier signal generated from the carrier signal generation means is mixed with the carrier signal of the modulated signal by the mixing control means. The mixing ratio for
The musical sound waveform generating device is characterized in that the musical sound waveform generated from the waveform output means is a signal set so that it becomes a sine wave or a cosine wave of a single frequency when controlled so that . 41) The musical sound waveform generator according to claim 40, wherein the frequency ratio control means controls the frequency ratio based on the tone of the musical sound waveform that is generated. 42) The performance operation is a key press operation on a keyboard, and the frequency ratio control means controls the frequency ratio according to at least one of the speed of the key press operation or the range of the pressed key. 41. The musical sound waveform generating device according to claim 40, wherein 43) A musical sound waveform generator that generates a musical sound waveform based on a mixed signal obtained by mixing a modulation signal with a carrier signal, comprising a carrier signal generation means that generates the carrier signal, and a modulation signal generator that generates the modulation signal. means, a mixing control means for mixing the modulated signal with a carrier signal generated by the carrier signal generating means to output a mixed signal, and controlling a mixing ratio of the modulated signal with respect to the carrier signal in this case; and a waveform output means for outputting a musical waveform by inputting the mixed signal outputted from the mixing control means, the output of which has a predetermined functional relationship, and the predetermined functional relationship in the waveform output means is such that the predetermined functional relationship is a sine wave or a cosine wave of a single frequency is determined to be generated from the waveform output means when the ratio is a predetermined value and the waveform shapes of the carrier signal and the modulation signal are specific shapes; A musical sound waveform generator featuring: