JP3400594B2 - Power supply - Google Patents

Description

Detailed Description of the Invention

[0001]

BACKGROUND OF THE INVENTION 1. Field of the Invention The present invention relates to a power supply unit for converting a DC voltage obtained by rectifying and smoothing an AC power supply into a high frequency and supplying the high frequency to a load.

[0002]

2. Description of the Related Art FIG. 52 shows a conventional example.
An example is a full-wave rectifier DB for full-wave rectifying the AC power supply Vs, and a full-wave rectifier DB.
Diode D at DC output terminal of wave rectifier DB₃Through
Smoothing capacitor C connected₁And the smoothing capacitor C₁
Are connected in series at both ends of the
Langista Q₁, Q₂And each transistor Q₁, Q
₂Diode D connected in anti-parallel to₁, D₂And full wave adjustment
DC output terminal of sink DB and diode D₃To the connection point of
Inductor L with connected ends₂And capacitor C_FourIn series
Impedance element consisting of circuit and transistor
Q₁, Q₂And the other end of the impedance element
Capacitor C connected between₃, Inductor L₁Directly
Column circuit, DC output terminal of full wave rectifier DB and smoothing capacitor
SA C₁Between the connection point with and the other end of the impedance element
A discharge lamp La such as a fluorescent lamp that is a load connected between
And between the non-power supply side ends of the filament of this discharge lamp La
Connected capacitor C₂And the above transistor
Q₁, Q₂, Diode D₁, D ₂, Inductor L₁,
Capacitor C₂, C₃, Discharge lamp La and transistor Q
₁, Q₂Separately-excited control circuit (not shown) that alternately drives
Inverter circuit I is constituted by.

The operation of the conventional inverter circuit I will be described below. First, in the inverter circuit I, the transistors Q ₁ and Q ₂ are alternately turned on and off at a high speed by the control circuit, the DC voltage across the smoothing capacitor C ₁ is converted into a high frequency, and the discharge lamp La is lit at a high frequency. . Here, the capacitor C ₂ constitutes a preheating current conducting path of the filament of the discharge lamp La, and also functions as a resonance capacitor with the inductor L ₁ . The capacitor C ₃ is a coupling capacitor for cutting the DC component.

By the way, the conventional circuit is designed to improve the input power factor by the following operation. That is, when the transistor Q ₂ is turned on, the inductor L ₂ → the capacitor C ₄ → the inductor L ₁ → from the full-wave rectifier DB.
Full-wave rectifier D via capacitor C ₃ → transistor Q ₂
A current flows in the route returning to B.

When the transistor Q ₂ turns off, the residual energy of the inductors L ₂ and L ₁ causes a full-wave rectifier D for a while.
From B, inductor L ₂ → capacitor C ₄ → inductor L ₁ → capacitor C ₃ → diode D ₁ → capacitor C
_The current flows through the path that returns to the full-wave rectifier DB via ₁ and the directions of the currents flowing through the inductor L ₂ and the capacitor C ₄ are the same.

Next, when the transistor Q ₁ is turned on, a current flows from the capacitor C ₄ through the inductor L ₂ → diode D ₃ → transistor Q ₁ → capacitor C ₃ → inductor L ₁ and back to the capacitor C ₄ . At this time,
The capacitors C ₃ and C ₄ and the inductors L ₁ and L ₂ form a resonance circuit.

When the transistor Q ₁ is turned off, due to the residual energy of the inductors L ₂ and L ₁ , the inductor L is temporarily stopped.
₁ → capacitor C ₄ → inductor L ₂ → diode D ₃
-> Capacitor C _1- > Diode D _2- > Capacitor C _{3 A} current flows in the route returning to the inductor L ₁ . At this time, the capacitor C ₄ has a voltage V ₄ indicated by an arrow in the figure.
, Then the transistor Q ₂ turns on,
This voltage V ₄ is superimposed on the power supply voltage when the input current is passed.

[0008] Here, the inductor L _2, if there is no path of the impedance elements of the capacitor C _4, when the input voltage is low, the input current Iin this effect becomes remarkable is discontinuous, voltage V ₄ of capacitor C ₄ In particular, by providing a means for suppressing the voltage generated in the direction of being superimposed on the power supply voltage, the inconvenience of discontinuity of the input current Iin is solved.

The above operation is performed in all sections of the AC power source Vs.
Input current Iin always flows because it is repeated over
Therefore, the input power factor becomes high. Also a suitable fill
Input circuit with a high frequency component removed
The flow waveform should be close to a sine wave with few harmonic components.
be able to. FIG. 53 shows the waveform of each part of the above conventional example.
FIG. 53 (a) shows the diode D ₃Input side vibration
The voltage waveform is shown, and the waveform shown by the solid line in FIG.
Iodo D₃Fig. 53 (c) shows the voltage waveform on the output side of
Is the waveform of the input current to the full-wave rectifier DB.
53 (d) is close to a sine wave by adding an appropriate filter.
The waveform of the input current to the full-wave rectifier DB is shown.

FIG. 54 shows another conventional example.
In the conventional example, the AC power supply Vs is entirely supplied to the power supply section of the inverter circuit I.
Full-wave rectifier DB for full-wave rectification and DC output of full-wave rectifier DB
Capacitor C at the power end₁, C₁’, Diode D_FourThrough
D₆It consists of a 1/2 valley filling smoothing circuit consisting of
It The inverter circuit I is connected in parallel with the smoothing circuit as shown.
Transistor Q connected to₁, Q₂Series circuit of each
Langista Q₁, Q₂Anti-parallel connected diodes
D₁, D₂And transistor Q₂Inns connected to both ends of
Ducta L₁, Capacitor C₃, Capacitor C₂Series of
Path and capacitor C₂Discharge lamp connected in parallel to
Composed of La and a transistor Q₁, Q ₂In Figure 52
As in the conventional example, a control circuit (not shown) alternately turns on and off.
It is supposed to be turned off.

The circuit of this conventional example operates as follows.
First, in the smoothing circuit, full-wave rectifier DB → capacitor C₁→ Da
Iodo D_Four→ Capacitor C₁’→ Full wave rectifier DB
Current flows in the path, and each capacitor C₁, C₁’Is charged
Be done. On the other hand, an inverter circuit I connected in parallel with the smoothing circuit
Is the capacitor C ₁, C₁Energy stored in the power source
To supply high-frequency power to the discharge lamp La.

At this time, the capacitors C ₁ and C of the smoothing circuit
₁ 'by the action of the diode D ₄ to D _6, are respectively made to be connected in parallel when viewed from the inverter circuit I.
That is, the charging is 'carried out by a series circuit of the discharge capacitor C _1, C _1' capacitor C _1, C ₁ will be performed in parallel circuit. Therefore, the waveform of the voltage V ₁ after the full-wave rectifier DB is as shown by the solid line in FIG. 55 (a). Further, the input current I ₁ of the full-wave rectifier DB does not have a voltage after the full-wave rectifier DB to be approximately 1/2 or less of the peak of the AC power supply Vs voltage, so that a quiescent period is created and as shown in FIG. 55 (b). It becomes a waveform.

As a result of the above operation, the AC power source Vs
A voltage lower than the peak value of the pressure is applied to the power source of the inverter circuit I.
Can be supplied as
Star Q₁, Q₂Burden is reduced. FIG. 56 shows another subordinate
A conventional example is shown. In this conventional example, a smoothing circuit is not used,
Directly connect the inverter circuit I to the DC output terminal of the full-wave rectifier DB.
It is connected. In this conventional example, the full-wave rectifier DB
The output voltage, that is, the pulsating current voltage V as shown in FIG.
₁Becomes the power supply voltage waveform of the inverter circuit I,
Transistor Q of circuit I₁Full-wave rectification when is on
Bowl DB → transistor Q₁→ inductor L₁→ Conden
SA C₃→ Discharge lamp La → Full-wave rectifier DB path again
Langista Q₂Is on, the capacitor C₃Electric
As a source, capacitor C₃→ inductor L ₁→ Transi
Star Q₂→ discharge lamp La → condenser C₃Current in the path
Flowing.

In the conventional example of FIG. 56 in which the smoothing circuit is not provided as described above, the input current of the full-wave rectifier DB can be a sinusoidal waveform with less harmonic components as shown in FIG. 57 (b), and the discharge lamp can be used. The envelope of the current Ila flowing through La is shown in FIG.
7 (c). As a result of the above operation,
The input current waveform can be a waveform close to a sine wave with few harmonic components.

FIG. 58 shows a circuit of still another conventional example of the present invention. In this conventional example circuit, a smoothing capacitor C ₁ is connected to the DC output terminal of the full-wave rectifier DB. The output voltage of the inverter circuit I is the capacitor C
_Since it is smoothed by _1, it becomes substantially constant over the entire period as shown in FIG. The input current from the AC power supply Vs to the full-wave rectifier DB is as shown in FIG. 59 (b), and the envelope of the current flowing through the discharge lamp La is shown in FIG. 59.
As shown in (c).

In this conventional example, the envelope of the current flowing through the discharge lamp La is substantially constant, so that a lighting device with high luminous efficiency can be realized.

[0017]

In the case of the conventional example shown in FIG. 52, in order to make the input current Iin sinusoidal, the oscillating voltage waveform due to the inductor L ₂ and the capacitor C _{4 is} equal to or higher than the peak value of the AC power source Vs. Therefore, there is a problem that the voltage after the diode D _{3 which} is the power source of the inverter circuit I becomes high and the load on the transistor which is a switching element becomes large.

Further, in the case of the conventional example shown in FIG. 54, since the direct current voltage V _{1 serving as} the power source of the inverter circuit I is low, the load on the transistor which is the switching element of the inverter circuit I is small, but the direct current voltage V ₁ is Since the peak value of the power supply voltage does not fall below about 1/2, there is a problem that the input current has a pause section and the input power factor deteriorates.

Further, in the case of the conventional example shown in FIG. 56, although the input current has a sine wave shape, since the power supply voltage is directly switched, the current Ila flowing through the discharge lamp La is substantially zero.
However, there is a problem that the luminous efficiency is deteriorated. Further, in the case of the conventional example shown in FIG. 58, the current Ila is substantially constant because the voltage is switched at a substantially constant value, which is good in terms of light emission efficiency. There was a problem of getting worse.

The present invention has been made in view of the above problems, and it is possible to make the input current have a waveform close to a sine wave with few harmonic components, and to reduce the load on the switching element. To provide.

[0021]

In order to achieve the above object, according to the invention of claim 1, an AC power supply, a rectifier for rectifying an AC voltage of the AC power supply, and a high frequency voltage for receiving a DC output voltage of the rectifier. A load circuit including a resonance inductor, a resonance capacitor, and a discharge lamp that receive the high-frequency voltage; and a discharge circuit that is connected in parallel to the output terminal of the rectifier and that substantially re-ignites the discharge lamp. And an auxiliary power supply means including a smoothing capacitor capable of supplying a continuous current of a level capable of maintaining lighting without performing, and the inverter circuit receives the DC output voltage of the rectifier, and
DC-DC converting means for outputting a DC output voltage equal to or lower than the peak voltage of the DC output voltage of the rectifier, and DC for receiving a DC output voltage of the DC-DC converting means and outputting a high frequency voltage
-AC conversion means, the switching element of the DC-DC conversion means and the switching element of the DC-AC conversion means are formed so as to share at least one switching element, and the auxiliary power supply means comprises a plurality of capacitors. Is formed so as to be serially charged by a plurality of diodes, and is formed so that a plurality of capacitors are discharged in parallel by a plurality of diodes, and a DC voltage is supplied to the inverter circuit at a predetermined voltage of an AC power supply or less.
At the output of the rectifier via a first diode
Is connected to the auxiliary power source means, the auxiliary power source means
The first capacitor, the forward diode and the second capacitor
Series circuit with the sensor, the first capacitor and the forward die
Reverse diode connected in parallel with series circuit
And a diode in the forward direction and a second capacitor in series
It consists of a reverse diode connected in parallel to the circuit.
The inverter circuit is connected to both ends of the auxiliary power supply means.
Series circuit of first and second switching elements connected
Connected to both ends of at least one switching element
Of the resonance inductor, the resonance capacitor, and the discharge lamp
A load circuit including an oscillating circuit, and a part of the load circuit
Magnetically and electrically between the rectifier and the output of the rectifier.
Of the DC-DC conversion means connected including the impedance element
The auxiliary power supply, which is composed of a part of bypass circuit
By the means , a DC voltage is supplied to the inverter circuit at a voltage equal to or lower than a predetermined voltage of the AC power supply.

According to a second aspect of the invention, an AC power source and this
Rectifier that rectifies the AC voltage of the current source and the rectifier
Inverter circuit that receives high-frequency output voltage and outputs high-frequency voltage
Resonance with the resonance inductor that receives this high-frequency voltage
A load circuit including a capacitor for discharge and a discharge lamp;
It is connected in parallel to the output of the rectifier and the discharge lamp is virtually re-pointed.
Continuous current of a level that can maintain lighting without being isolated
And auxiliary power supply means including a smoothing capacitor
The inverter circuit receives the DC output voltage of the rectifier.
And a DC voltage that is less than the peak voltage of the DC output voltage of the rectifier.
DC-DC converting means for outputting a current output voltage, and this DC
-Receives the DC output voltage of the DC conversion means and outputs a high frequency voltage.
And a DC-AC conversion means for applying
Stage switching element and DC-AC conversion means switch
Among the switching elements, at least one switching element
The auxiliary power supply means is configured to
To charge the capacitor in series with multiple diodes
Formed, multiple capacitors and multiple dios
Of the AC power supply.
DC voltage is supplied to the inverter circuit below a certain voltage
In that power supply, it said auxiliary power unit via a first diode is connected to the output end of said rectifier, said auxiliary power supply means is a series circuit of a first capacitor and a forward diode and a second capacitor , A reverse diode connected in parallel to the series circuit of the first capacitor and the forward diode, and a reverse diode connected in parallel to the series circuit of the forward diode and the second capacitor is, the inverter circuit includes a first is connected to both ends of the auxiliary power unit, discharge a series circuit of the second switching element, a resonance inductor connected to both ends of at least one switching element and the resonance capacitor a load circuit comprising the oscillation circuit of the lamp, magnetic, electrical impedance between the part and one end of the AC power supply of the load circuit Is composed of a bypass circuit which is part of the DC-DC converting means connected include iodine, DC voltage to the inverter circuit than a predetermined voltage of the AC power supply is to be supplied by the auxiliary power unit it shall be the features a.

According to a third aspect of the invention, an AC power source and this
Rectifier that rectifies the AC voltage of the current source and the rectifier
Inverter circuit that receives high-frequency output voltage and outputs high-frequency voltage
Resonance with the resonance inductor that receives this high-frequency voltage
A load circuit including a capacitor for discharge and a discharge lamp;
It is connected in parallel to the output of the rectifier and the discharge lamp is virtually re-pointed.
Continuous current of a level that can maintain lighting without being isolated
And auxiliary power supply means including a smoothing capacitor
In the power supply device to obtain, it said rectifier first output terminal of the diode and via the parallel circuit of the capacitor is an auxiliary power supply means is connected, the auxiliary power supply means comprises a diode and a second of the first capacitor and the forward A series circuit with a capacitor, a reverse diode connected in parallel with a series circuit of a first capacitor and a forward diode, and a reverse diode connected in parallel with a series circuit of a forward diode and a second capacitor Direction diode and the auxiliary power
A small capacitor is connected across the source means
Serial inverter circuit, a series circuit of first and second switching elements connected to both ends of the auxiliary power unit, the
Connected in antiparallel with the first and second switching elements, respectively
A second diode, and a cathode of the first diode
Between the switch side and the connection point of the first and second switching elements
Connected DC blocking capacitor and transformer primary winding
And a series circuit connected between the transformer and the secondary winding of the transformer
A series circuit of a vibration inductor and a discharge lamp, and
A resonance capacitor connected between the non-power supply terminals and
Series circuit of flow blocking capacitor and transformer primary winding
An inductor and a coil between the connection point and the output of the rectifier.
It is composed of a which is part bypass circuit of the DC-DC converter the series circuit is connected to the capacitor, so that the DC voltage to the inverter circuit with a predetermined voltage or lower of the AC power source by the auxiliary power unit is supplied that in the it said.

[0024]

[0025]

[0026]

[0027]

[0028]

According to the invention of claim 1, the inverter circuit comprises:
DC- that receives the DC output voltage of the rectifier and outputs a DC output voltage that is less than or equal to the peak voltage of the DC output voltage of the rectifier
A DC conversion means and a DC-AC conversion means for receiving a DC output voltage of the DC-DC conversion means and outputting a high frequency voltage are provided, and a switching element of the DC-DC conversion means and a DC.
-It is formed so as to share at least one switching element among the switching elements of the AC conversion means, and the auxiliary power supply means is formed so as to charge a plurality of capacitors in series by a plurality of diodes, and a plurality of capacitors. Are formed so as to be discharged in parallel by a plurality of diodes, and the DC voltage is supplied to the inverter circuit at a predetermined voltage of the AC power supply or less, so that the AC power is always supplied to the DC-DC converting means. Therefore, it is possible to prevent a rest period from occurring in the input current from the AC power supply, and the power supply voltage of the DC-AC conversion means is between the peak value of the output value of the rectifier and the output voltage of the auxiliary power supply voltage. Since the voltage fluctuates, the fluctuation range of the voltage is small, and moreover, the output voltage of the DC-DC converting means is the peak of the DC output voltage of the rectifier. Because less click value, the voltage applied to the DC-AC converting means compares hardly rises when using a conventional smoothing capacitor as the stress is reduced to the switching element.

Further, it comprises a bypass circuit which is a part of DC-DC converting means which is magnetically and electrically connected to a part of the load circuit and an output terminal of the rectifier and which includes an impedance element. Therefore, except near the peak value of the output value of the rectifier, the current can be made to flow continuously by the effect of high frequency superposition, and the input current waveform becomes a substantially sinusoidal wave with less harmonic components similar to the power supply voltage waveform. it is possible.

According to the invention of claim 2, the operation of claim 1
It is possible to provide a concrete circuit of the auxiliary power supply means for obtaining the above.

According to the invention of claim 3, the action of claim 1 can be obtained.

[0032]

[0033]

[0034]

Embodiments of the present invention will be described below with reference to the drawings. (Embodiment 1) FIG. 1 shows a circuit configuration of a basic embodiment of the present invention. The circuit configuration will be described below. In this embodiment, a full-wave rectifier DB that rectifies the AC power supply Vs
, And an impedance element Z is connected between the DC output terminals of the full-wave rectifier DB and a diode D ₃
The valley-filled smoothing circuit H is connected as auxiliary power supply means, and the inverter circuits I are connected to both ends of the smoothing circuit H.

Here, the inverter circuit I receives the DC output voltage of the full-wave rectifier DB and outputs DC output voltage less than the peak voltage of the DC output voltage of the full-wave rectifier DB, and DC-DC converting means. A DC-AC converting means for receiving a DC output voltage of the DC-DC converting means and outputting a high frequency voltage, and at least one of a switching element of the DC-DC converting means and a switching element of the DC-AC converting means. An element formed so as to share a switching element is used, and by appropriately selecting a circuit constant of an inductor, a capacitor, a discharge lamp La that is a load, or a circuit constant of an impedance element Z, a circuit configuration having no boosting action can be obtained. can do. Specifically, when the oscillating voltage of the oscillating circuit of the inverter circuit I is applied to the DC output terminal of the full-wave rectifier DB via the impedance element Z that is a bypass circuit, it is applied to the DC output terminal of the full-wave rectifier DB. Since the peak value of the voltage that appears exceeds the voltage of the AC power supply Vs, the smoothing circuit H naturally does not have a boosting action if it is smaller than the peak value of the voltage of the AC power supply Vs.

Here, when only the smoothing capacitor C ₁ is used instead of the smoothing circuit H as in the conventional example of FIG. 52, the peak value of the voltage V ₁ appearing at the DC output terminal of the full-wave rectifier DB is the AC power supply. If it is smaller than the peak value of the voltage of Vs, a voltage that is not boosted can be obtained in the smoothing capacitor C ₁ . That is, from the peak value of the voltage V ₁ appearing at the DC output terminal of the full-wave rectifier DB as shown in FIG. 2A, the voltage across the smoothing capacitor C ₁ is as shown in FIG.
It is smaller than the peak value of. As shown in FIG. 2C, the input current at this time includes a lot of harmonics near the peak value of the AC power supply Vs, and conversely the AC power supply Vs.
In the vicinity of 0 V of s, a current can be continuously flowed by the action of high frequency superposition via the impedance element Z. Here, by adding an appropriate filter to the input side, the waveform becomes as shown in FIG. However, as a whole, the input power factor has a fairly bad waveform.

Therefore, in this embodiment, the smoothing capacitor C ₁
1 composed of a circuit constant that does not have a boosting effect instead of
The above-mentioned smoothing circuit H of 1/2 valley filling is used.
Shows a specific circuit of the embodiment including the inverter circuit I.
In this concrete circuit, a smoothing circuit H is provided instead of the smoothing capacitor C ₁ provided in the conventional example of FIG.
_It differs from the conventional example of FIG. 51 in that a capacitor C ₆ for removing high frequencies after ₃ is connected in parallel to the smoothing circuit H.

In the inverter circuit I of this embodiment, the smoothing circuit H is used as a power source, the inductor L ₁ and the capacitor are turned on by turning on and off the transistors Q ₁ and Q ₂ at high speed by a control circuit (not shown). A high frequency voltage is applied to the discharge lamp La, which is a load in the resonance system of C ₂ . Here, the inverter circuit I is approximately 1/1 of the peak value of the voltage of the AC power supply Vs.
In the section smaller than 2, the DC voltage of about 1 / 2.Vs is used as the power source, and in the section larger than about 1/2 of the peak value of the voltage of the AC power source Vs, the voltage corresponding to the voltage of the AC power source Vs is supplied. Operates as a power source.

Here, the operation of improving the input power factor will be described. First, the voltage across the discharge lamp La oscillates at high frequency due to the inverter operation. In addition, the inductor L ₂ ,
Since the impedance element Z composed of the capacitor C ₄ also constitutes a resonance system, the resonance voltage applied to the discharge lamp La and the resonance voltage due to the inductor L ₂ and the capacitor C ₁ are present at the DC output terminal of the full-wave rectifier DB. Is applied. Here, the synthetically applied voltage is V _1, and the circuit constants are selected so that the condition of 1/2 · Vs (peak) ≦ V ₁ (Peak) ≦ Vs (peak) is satisfied.

The voltage V ₁ oscillates at a high frequency as the transistors Q ₁ and Q ₂ of the inverter circuit I are turned on and off. A section in which the amplitude value of the voltage of the AC power supply Vs is larger than the amplitude of the voltage V ₁ , that is, FIG.
In the t ₁ section shown in (a), current flows directly from the AC power supply Vs in the path of full-wave rectifier DB → diode D ₃ → capacitor C ₁ → diode D ₄ → capacitor C ₁ ′ → full-wave rectifier DB, Capacitor C of smoothing circuit H at low frequency
Charge ₁ , C ₁ '. On the other hand, in a section in which the amplitude of the voltage V ₁ is large in the amplitude of the voltage of the AC power supply Vs, that is, in the section of t ₂ , the voltage V ₁ is superimposed on the pulsating current voltage output to the DC output terminal of the full-wave rectifier DB, and this high frequency As a result, the capacitors C ₁ and C ₁ 'of the smoothing circuit H are charged. In this way, the low-frequency capacitor C ₁ of the smoothing circuit H,
'The section t ₁ to charge the capacitor C _1, C ₁ of the smoothing circuit H in the high frequency' C ₁ and the section t ₂ to charge the is to be repeated every period. FIG. 4B shows the voltage across the smoothing circuit H, that is, the power supply voltage of the inverter circuit I.

The amplitude of the voltage V ₁ fed back to the DC output terminal of the full-wave rectifier DB in this manner is about 1 of the AC power supply voltage Vs.
/ 2 or more, the capacitor C of the smoothing circuit H
A current for charging ₁ , C ₁ 'will flow, and a pause section does not occur in the waveform of the input current Iin as shown in FIG. 4 (c). Here, in the concrete circuit of FIG. 3, since the low-pass filter including the inductor L ₀ and the capacitor C ₀ is provided on the input side of the full-wave rectifier DB, the input current Iin is as shown in FIG.
As shown in, a continuous current waveform similar to a sine wave similar to the voltage waveform of the AC power supply Vs is obtained, and a high input power factor is obtained. Further, the voltage across the smoothing circuit H, which serves as the power supply for the inverter circuit I, does not exceed the peak value of the AC power supply Vs, and the voltage at the valley is approximately 1 / 2.Vs. The burden on ₁ and Q ₂ is reduced. (Embodiment 2) Although the above-mentioned Embodiment 1 uses the 1/2 valley-filling smoothing circuit H, any part of the dotted line may be a partial smoothing circuit, and generally n / m valley-filling smoothing circuit. In this case, n / m · Vs (peak) ≦ V ₁ (Peak) ≦ Vs (peak).

This embodiment is based on the above conditions and has a smoothing circuit.
H, the capacitor C as shown in FIG.₁, C₁’,
C₁'', Diode D_FourThrough D₉1 / composed by
A smoothing circuit H of 3 valleys is used. In the case of this embodiment
The voltage at the valley portion of the sliding voltage is more than that in the first embodiment.
Since it is low, the switch of the inverter circuit I is more than the first embodiment.
Transistor Q ₁, Q₂Burden on
Be done.

(Embodiment 3) In each of the above embodiments, the oscillating voltage of the oscillating circuit of the inverter circuit I is set to the impedance element Z.
Although it superimposed in a manner to be applied to the resonance voltage generated by, in this embodiment by inserting a primary winding of the transformer T ₁ in series with the inductor L ₁ of the oscillating circuit as shown in FIG. 6, the transformer T ₁ Is connected to the secondary winding of the discharge lamp La and a series circuit of the tertiary winding and the impedance element Z is connected in parallel to the DC output terminal of the full-wave rectifier DB.
Due to the oscillating voltage generated in the tertiary winding, a current flows in the series circuit of the inductor L ₂ and the capacitor C ₄ of the impedance element Z to generate a resonance voltage.
_The voltage across the tertiary winding of _{No. 1} is added, and the same operation as that of the above-described first embodiment can be obtained.

The inductor L ₁ may be provided on the secondary side of the transformer T ₁ . The direction of the electromotive force of the transformer T ₁ may be opposite to the direction shown. (Embodiment 4) This embodiment is different from Embodiment 6 only in the connection point of the inductor L ₁ of the vibration circuit and the connection point of the transformer T ₁ for feeding back the vibration voltage as shown in FIG. The operation of is basically the same as that of the third embodiment.

(Embodiment 5) In each of the above embodiments, an inductor is used.
L₂And capacitor C_FourAnd an in-line circuit composed of
The high-frequency voltage is converted into a full-wave rectifier D by using the impedance element Z.
It is designed to return to B. This embodiment is shown in FIG.
As an impedance element Z, an inverter circuit I
Of the vibration circuit of the discharge lamp La, which is a capacitor and a load.
Transformer T that is composed of the primary winding of the inductor
₂This transformer T uses the secondary winding of₁
Secondary winding of the full-wave rectifier DB direct current output terminal and diode
D₃It is inserted between and. FIG. 9 is a specific example of the fifth embodiment.
Shows the road and the transformer T ₂Primary winding of the discharge lamp La
And between the non-power supply side end of the filament of the discharge lamp La.
Capacitor C₂Together with the vibration circuit
It

Thus, in this embodiment, the oscillating voltage generated in the oscillating circuit of the inverter circuit I is superimposed on the pulsating voltage generated at the DC output terminal of the full-wave rectifier DB through the secondary winding of the transformer T _2. It is possible to charge the capacitors C ₁ and C ₁ ′ of the smoothing circuit H having a half-valley filling with a low frequency as in the first embodiment, and at a high frequency to allow a continuous input current Iin to flow. You can do it.

(Embodiment 6) In Embodiment 5, the secondary winding of the transformer T ₂ constituting the impedance element Z for superimposing a high frequency wave is connected to the DC output terminal of the full-wave rectifier DB and the diode D.
It is inserted between ₃ and ₃ , but in this embodiment, as shown in FIG.
0, which is inserted on the input side of the full-wave rectifier DB as shown in FIG.
It is designed to be superimposed on the s voltage.

Since the operation is similar to that of the fifth embodiment, the description will be omitted. (Embodiment 7) In this embodiment, as shown in FIG. 12, an oscillator circuit Z ₀ including a load of an inverter circuit I is connected to a transistor Q ₁ ,
Connected via a DC blocking capacitor C ₃ between the cathode connection point and the diode D ₃ of Q _2, the transistor Q ₁ the impedance element Z for feedback superimposing a high frequency voltage, Q ₂ of the connection point between the diode It is connected to the anode of D ₃ via a DC cut capacitor C ₃ . Figure 13 shows the specific circuits, oscillation circuits Z ₀ In this specific circuit inserts a primary winding of the transformer T ₃ between the capacitor C ₃ and a diode D _3, 2-order of the transformer T ₃ Inductor L _{1 in} winding and discharge lamp L as load
It is configured by connecting a series circuit with a, and connecting in parallel a capacitor C ₂ for supplying a preheating current that also functions as a resonance capacitor to the non-power source side of the filament of the discharge lamp La.

On the other hand, impedance element Z is inductor L
_It is composed of a series circuit of ₂ and a capacitor C ₄ . Next, the operation when the AC power supply Vs of the inverter circuit I for improving the input distortion of this embodiment is near 0 V will be described with reference to FIGS.
6 will be described. In the inverter circuit I, the transistors Q ₁ and Q ₂ are alternately turned on and off at high speed by a control circuit (not shown).

Here, the transistor Q₁, Q₂On, oh
F, vibration circuit Z₀And the current flowing through the impedance element Z
It is divided into the following 6 modes depending on the direction of. First figure
Mode 1 shown in 14 (a) is a transistor Q₁Is on,
Transistor Q ₂If the inverter is in the off mode
In circuit I transformer T₃Primary winding → Capacitor C₃→
Diode D₁→ Transformer T₃Current in the primary winding path
ia flows as a regenerative current. On the other hand, capacitor C_Four→ a
Inductor L₂→ Diode D₃→ Transistor Q₁→
Indexer C₃→ Capacitor C_FourCurrent ib flows through the path
Resonance voltage due to impedance element Z is full-wave rectifier D
It is applied to the DC output terminal of B.

The mode 2 shown in FIG. 14B is shown in FIG.
Transistor Q as in (a)₁Is on, tran
Dista Q₂In another mode, when is on, when illustrated
Inverter circuit I has a capacitor C₃→ Transformer T
₃Primary winding → Transistor Q₁→ Capacitor C₃Sutra
Current ia flows in the path, while capacitor C_Four→ inductor
L ₂→ Diode D₃→ Transistor Q₁→ Capacitor
C₃→ Capacitor C_FourThe current ib flows through the path.

The mode 3 shown in FIG. 15A is shown in FIG.
As in the case of modes 1 and 2 in (a) and (b), this is a mode in which the transistor Q ₁ is on and the transistor Q ₂ is on. In this case, in the inverter circuit I, the capacitor C
₃ → current ia flows through the primary winding → transistor Q ₁ → capacitor C ₃ of the transformer T _3. On the other hand, full-wave rectifier DB →
The current ib flows through the path of the inductor L ₂ → capacitor C ₄ → capacitor C ₃ → diode D ₁ → capacitor C ₁ → diode D ₄ → capacitor C ₁ '→ full-wave rectifier DB.

In the above operation, the DC cut capacitor C ₃ is used as a power source while the transistor Q ₁ is on. Mode 4 shown in FIG. 15 (b) shown below is a mode in which the transistor Q ₁ is off and the transistor Q ₂ is on. In the inverter circuit I, the primary winding of the transformer T ₃ → the capacitor C ₁ → the diode D ₄ → Capacitor C ₁ '→ Diode D ₂ → Capacitor C ₃ → Current Ia flows as a line current in the path of the primary winding of transformer T ₃ . On the other hand, full-wave rectifier D
B → inductor L ₂ → capacitor C ₄ → capacitor C ₃
→ transistor Q ₂ → current ib in the path of full-wave rectifier DB
Flows.

The mode 5 shown in FIG. 16A is shown in FIG.
As in the case of mode 4 in (b), in the mode in which the transistor Q ₁ is off and the transistor Q ₂ is on, the capacitor C ₁ → the primary winding of the transformer T ₃ → the capacitor C ₃ →
The path of transistor Q ₂ → diode D ₅ → capacitor C ₁ and capacitor C ₁ '→ diode D ₆ → primary winding of transformer T ₃ → capacitor C ₃ → transistor Q ₂ →
'Path and the current ia of, ia' capacitor C ₁ flows respectively.

On the other hand, full-wave rectifier DB → inductor L ₂
→ Capacitor C ₄ → Capacitor C ₃ → Transistor Q ₂
→ The current ib flows through the path of the full-wave rectifier DB. FIG.
The mode 6 shown in (b) is a mode in which the transistor Q ₁ is off and the transistor Q ₂ is on, as in the mode 5 of FIG. 16 (a). As in the case of FIG. 16 (a), the capacitor C ₁ → The path of the primary winding of the transformer T ₃ → capacitor C ₃ → transistor Q ₂ → diode D ₅ → capacitor C ₁ and capacitor C ₁ '→ diode D ₆ → transformer T
₃ of the primary winding → capacitor C ₃ → transistor Q ₂ → 'path and the current ia of, ia' capacitor C ₁ flows respectively.

On the other hand, the capacitor C ₄ → the inductor L ₂
→ diode D ₃ → capacitor C ₁ → diode D ₄ →
Capacitor C ₁ '→ Diode D ₂ → Capacitor C ₃ →
The current ib flows through the path of the capacitor C ₄ . As described above, in Modes 4 to 6 of FIGS. 15B and 16A and 16B, the capacitors C ₁ and C ₁ are connected while the transistor Q ₂ is on.
Operates with ₁ 'power supply.

Here, FIG. 15 (b) and FIG. 16 (a)
In modes 4 to 6 of (b), since the charging of the capacitors C ₁ and C ₁ ′ of the smoothing circuit H directly flows from the AC power supply Vs via the full-wave rectifier DB, the input current flows even when the voltage of the AC power supply Vs is near 0V. It can be continued and the input distortion can be improved. When the AC power supply Vs voltage is near the peak, the full-wave rectifier DB is used in the mode 2 shown in FIG.
→ diode D ₃ → capacitor C ₁ → diode D ₄ →
A path from the capacitor C ₁ 'to the full-wave rectifier DB is added. Further, since the primary voltage of the transformer T ₃ becomes a rectangular wave determined by the smoothing circuit H of ½ valley filling, the discharge lamp L which is a load.
The feature is that it is difficult to boost the voltage regardless of the state of a.

Further, by replacing the inductor L ₁ with the leakage magnetic flux of the transformer T ₃ , the inductor L ₁ can be omitted and the device can be made more compact. Further, although the bipolar transistor is used as the switching element of the inverter circuit I in the present embodiment, the invention is not limited to the bipolar transistor and may be, for example, a MOS-FET.
Since the parasitic diode in this case MOD-FET is, with the role of diodes D _1, D _2, diodes D _1, D ₂
Can be omitted, and the device can be further downsized.

Further, by adding one high speed diode to the output of the full wave rectifier DB, a low speed type full wave rectifier DB can be used, so that the cost can be simplified. The discharge lamp La, which is a load, is not limited to one lamp and may be two or more lamps. In the case of two or more lamps, it may be either in series or in parallel.

(Embodiment 8) In this embodiment, as shown in FIG. 17, the impedance element Z is connected between the connecting point of the oscillator circuit Z ₀ of the inverter circuit I and the capacitor C ₃ and the input side end of the full-wave rectifier DB. It differs from the seventh embodiment in that it is connected between them, and FIG. 18 shows a specific circuit of the present embodiment.

Next, the operation of this embodiment will be described along with modes 1 to 6 of each operation as in the case of the seventh embodiment. Since the operation on the side of the inverter circuit I is the same as that of the seventh embodiment in each of modes 1 to 6, the operation of the impedance element Z will be described. First, in modes 1 and 2 when the transistor Q ₁ is on and the transistor Q ₂ is off, the path of capacitor C ₄ → inductor L ₂ → full wave rectifier DB → diode D ₃ → transistor Q ₁ → capacitor C ₃ → capacitor C ₄ The current flows through. In mode 3, AC power supply Vs → inductor L ₀ → inductor L ₂ → capacitor C ₄ → capacitor C ₃ → diode D ₁ → capacitor C ₁ → diode D ₄ → capacitor C ₁ '→ full-wave rectifier DB → AC power supply. V
An electric current flows through the path of s.

Next, in modes 4 and 5 when the transistor Q ₁ is off and the transistor Q ₂ is on, the AC power source Vs
→ inductor L ₀ → inductor L ₂ → capacitor C ₄ →
Capacitor C ₃ → Transistor Q ₂ → Full wave rectifier DB →
A current flows through the path of the AC power supply Vs. Further, in mode 6, the current flows along the path of capacitor C ₄ → inductor L ₂ → full wave rectifier DB → diode D ₃ → capacitor C ₁ → diode D ₄ → capacitor C ₁ '→ diode D ₂ → capacitor C ₃ → capacitor C _4. Flowing.

When superposing a high frequency wave through the impedance element Z in this way, in modes 1, 2, and 6, the full-wave rectifier D is provided in the current path flowing when charging the smoothing circuit H.
B is added, and conversely in modes 3, 4 and 5, full wave rectifier D
The only difference is that the path passing through B is omitted and the current flows directly from the AC power supply Vs. The operation and effect of this embodiment are similar to those of the seventh embodiment.

(Embodiment 9) This embodiment is based on FIGS.
This is different from the seventh embodiment in that a capacitor C ₇ is connected in parallel with the diode D _{3 as} shown in FIG. The feature of this embodiment is that it rises or falls near 0 V of the AC power supply Vs voltage shown in FIG.
The point is that the input distortion can be improved with respect to the input current Iin shown in (b).

Next, the operation when the AC power supply Vs of the inverter circuit I for improving the input distortion according to the present embodiment is near 0 V will be described with reference to FIGS. First, in the mode 1 shown in FIG. 22A, in the inverter circuit I, the current ia is a regenerative current in the path of the primary winding of the transformer T ₃ → the capacitor C ₃ → the diode D ₁ → the primary winding of the transformer T _3. Flows as. On the other hand, the current ib flows through the path of the capacitor C ₄ → the inductor L ₂ → the capacitor C ₇ → the transistor Q ₁ → the capacitor C ₃ → the capacitor C ₄ .

[0066] In mode 2 shown in FIG. 22 (b), 1 winding → transistor Q ₁ → currents ia a path of the capacitor C ₃ of the inverter circuit I the capacitor C ₃ → transformer T ₃ flows, whereas the capacitor C _The current ib flows through the path of ₄ → inductor L ₂ → diode D ₃ → transistor Q ₁ → capacitor C ₃ → capacitor C ₄ . FIG. 23 (a)
In the case of mode 3 shown in FIG. 22B, as in the case of mode 2 in FIG. 22B, in the inverter circuit I, the capacitor C ₃ → the primary winding of the transformer T ₃ → the transistor Q ₁ → the capacitor C
_A current ia flows through ₃ . On the other hand, the current ib flows through the path of the capacitor C ₄ → the capacitor C ₃ → the diode D ₁ → the capacitor C ₇ → the inductor L ₂ → the capacitor C ₄ .

Further, in the case of mode 4 shown in FIG. 23 (b),
In the inverter circuit I, the transformer T ₃Primary winding →
Densa C₁→ Diode D_Four→ Capacitor C₁’→ Die
Aether D₂→ Capacitor C₃→ Transformer T₃Primary winding
The regenerative current ia flows through the path. As shown in FIG.
In the case of mode 5, in the inverter circuit I, the capacitor C
₁→ Transformer T₃Primary winding → Capacitor C₃→ Tran
Dista Q₂→ Diode D _Five→ Capacitor C₁The path of
Capacitor C₁’→ Diode D₆→ Transformer T₃Of 1
Next winding → Capacitor C₃→ Transistor Q₂→ Conden
SA C₁A current ia flows through each of the ‘’ paths. On the other hand all
Wave rectifier DB → capacitor C₇→ Capacitor C₁→ die
Aether D_Four→ Capacitor C₁’→ Path of full-wave rectifier DB
The current ib flows at.

In the case of mode 6 shown in FIG.
In the converter circuit I, the capacitor C₁→ Transformer T₃Of 1
Next winding → Capacitor C₃→ Transistor Q₂→ Daio
De D _Five→ Capacitor C₁And the capacitor C₁’→
Diode D₆→ Transformer T ₃Primary winding → capacitor
C₃→ Transistor Q₂→ Capacitor C₁’
Currents ia and ia 'respectively flow. Also the capacitor C_Four→
Inductor L₂→ Capacitor C₇→ Capacitor C₁→ Da
Iodo D_Four→ Capacitor C₁’→ Diode D₂→
Indexer C₃→ Capacitor C_FourThe current flows through the path.

As described above, in this embodiment, the impedance
Of the smoothing circuit H by superimposing the high frequency by the element Z
SA C₁, C₁When charging ‘
Only mode 5 is the mode that flows directly into the smooth circuit H.
And this is the capacitor C ₇Due to the current flowing in
, Diode D₃Because the voltage on the anode side of
Is. As a result, when the AC power supply Vs voltage is near 0V,
The force current Iin also approaches 0. Therefore, as shown in FIG.
Capacitor C to make a waveform like a sine wave₇Is effective
It is fruitful. The other operational effects are similar to those of the seventh embodiment.
It

(Embodiment 10) In this embodiment, as shown in FIG. 25, the terminal not connected to the internal DC cut capacitor C ₃ at both ends of the vibration circuit Z ₀ of the inverter circuit I is connected to the diode D ₃ . It differs from the seventh embodiment in that it is connected not to the cathode side but to the ground side of the circuit (the negative side DC output terminal of the full-wave rectifier DB). FIG. 26 shows a specific circuit of this embodiment.

The circuit operation of this embodiment can be divided into 6 modes as in the case of the seventh embodiment, but the impedance element Z
_Since the charging operation for the capacitors C ₁ and C ₁ ′ of the smoothing circuit H passing through the ₀ side is the same as that of the seventh embodiment, it is omitted.
Only the operation of the inverter circuit I when the AC power supply Vs voltage is near 0 V will be described. First, in the case of mode 1 described above, in the inverter circuit I, the primary winding of the transformer T ₃ →
A regenerative current flows in the path of the primary winding of the capacitor C ₃ → diode D ₁ → capacitor C ₁ → diode D ₄ → capacitor C ₁ '→ transformer T ₃ .

In modes 2 and 3, in the inverter circuit I, capacitor C ₁ → transistor Q ₁ → capacitor C ₃ → primary winding of transformer T ₃ → diode D ₅
→ flow and path of the capacitor C _1, to the path of the capacitor C ₁ '→ diode D ₆ → transistor Q ₁ → capacitor C ₃ → 1 winding → capacitor C ₁ of the transformer T _1'.

Further, in the mode 4, in the inverter circuit I, a regenerative current flows in the path of the primary winding of the transformer T ₃ → the diode D ₂ → the capacitor C ₃ → the primary winding of the transformer T ₃ . In modes 5 and 6, capacitor C
_A current flows through a path of ₃ → transistor Q ₂ → primary winding of transformer T ₃ → capacitor C ₃ .

Therefore, the inverter circuit I has the capacitors C ₁ and C ₁ while the transistor Q ₁ is on (modes 1 to 3).
It operates by using C ₁ 'as a power supply, and the capacitor C ₃ for cutting the direct current is supplied during the period when the transistor Q ₂ is on (modes 4 to 6).
It is different from the case of the seventh embodiment in that it is operated by using as a power source. When the AC power supply Vs is near the peak, a path of full-wave rectifier DB → diode D ₃ → capacitor C ₁ → diode D ₄ → capacitor C ₁ ′ → full-wave rectifier DB is added in the mode 2.

The other operational effects are similar to those of the seventh embodiment. (Embodiment 11) In this embodiment, as shown in FIG. 27, the connection is made between the connection point of the oscillating circuit Z ₀ of the inverter circuit I and the capacitor C ₃ and one input end of the full-wave rectifier DB. The configuration is different from that of the eighth embodiment. FIG. 28 shows a specific circuit of this embodiment.

The circuit operation is the same as that of the tenth embodiment.
The operation of the inverter circuit I is divided into two modes, and the operation is exactly the same as that of the tenth embodiment. In addition, the capacitor C ₁ of the smoothing circuit H through the impedance element Z,
The charging for C ₁ 'is the same as in Example 8, and the same effects as in Example 7 can be obtained. (Embodiment 12) In this embodiment, as shown in FIG. 29, the terminal not connected to the capacitor C ₃ at both ends of the vibration circuit Z ₀ of the inverter circuit I is connected to the ground side of the circuit (the full-wave rectifier DB − The connection point of the vibration circuit Z _{0 and} the connection point of the impedance element Z are closer to the full-wave rectifier DB than the connection point of the vibration circuit Z ₀ , and the connection point of the vibration circuit Z ₀ to the impedance element Z. A diode D ₃ is connected in the forward direction to the connection point. FIG. 30 shows a specific circuit of this embodiment.

The circuit operation of this embodiment can be divided into six modes as in the seventh embodiment. Of these, the operation of the inverter circuit I is the same as that of the tenth embodiment, so the description thereof is omitted and the AC power supply Vs is 0V. The charging operation by high frequency superposition through the nearby impedance element Z will be described below. First, in mode 1 and mode 2, full-wave rectifier DB →
Transistor Q ₁ → Capacitor C ₃ → Inductor L ₂ →
A current flows through the path of the capacitor C ₄ → full-wave rectifier DB.

In mode 3, a current flows through the route of capacitor C ₄ → inductor L ₂ → capacitor C ₃ → diode D ₁ → capacitor C ₁ → diode D ₄ → capacitor C ₁ '→ diode D ₃ → capacitor C ₄ . Further, in modes 4 and 5, current flows through the capacitor C ₄ → inductor L ₂ → capacitor C ₃ → transistor Q ₂ → diode D ₃ → capacitor C ₄ .

In mode 6, the current flows in the path of full-wave rectifier DB → capacitor C ₁ → diode D ₄ → capacitor C ₁ ′ → diode D ₂ → capacitor C ₃ → inductor L ₂ → capacitor ₄ → full-wave rectifier DB. . When the voltage of the AC power supply Vs is near the peak, a path of full-wave rectifier DB → capacitor C ₁ → diode D ₄ → capacitor C ₁ ′ → diode D ₃ → full-wave rectifier DB is added in the above mode 5.

Therefore, the inverter circuit I includes the transistor Q.
_{While 1} is on (modes 1 to 3), capacitors C ₁ , C
₁ 'operates as a power source, the transistor Q ₂ is a period of one (Mode 4-6) operates the capacitor C ₃ of the DC-cut as a power supply, a capacitor C ₁ of the smoothing circuit H by high frequency superposition through the impedance element Z, Charging of C ₁ 'is performed in modes 1, 2, and 6 by flowing a current from the AC power supply Vs via the full-wave rectifier DB, so that the input current can continue to flow even when the voltage of the AC power supply Vs is near 0V. Input distortion is improved.

The function and effect of the present embodiment configured as described above are similar to those of the seventh embodiment. (Embodiment 13) In this embodiment, as shown in FIG. 31, an impedance element Z is connected between a connection point between an oscillating circuit Z _{0 of} an inverter circuit H and a capacitor C ₃ and an input end of a full-wave rectifier DB. Is different from the twelfth embodiment. FIG. 32 shows a specific circuit of this embodiment.

The circuit operation of the present embodiment when the voltage of the AC power supply Vs is near 0 is divided into 6 modes as in the case of the eighth embodiment.
Of these, the operation of the inverter circuit I is exactly the same as that of the twelfth embodiment, so that the description thereof will be omitted and only the operation of the impedance element Z in each mode will be described. First, in modes 1 and 2, a current flows through a path of AC power supply Vs → inductor L ₀ → full-wave rectifier DB → transistor Q ₁ → capacitor C ₃ → inductor L ₂ → capacitor C ₄ → AC power supply Vs.

In mode 3, the capacitor C_Four→ Inda
Kuta L₂→ Capacitor C₃→ Diode D₁→ Conden
SA C₁→ Diode D_Four→ Capacitor C₁’→ Daio
De D ₃→ Full wave rectifier DB → Capacitor C_FourCurrent in the path of
Flows. Capacitor C in modes 4 and 5_Four→ Indak
L₂→ Capacitor C₃→ Transistor Q₂→ Daio
De D₃→ Full wave rectifier DB → Capacitor C_FourCurrent in the path of
Flows. In mode 6, AC power supply Vs → inductor
L₀→ Full wave rectifier DB → Capacitor C₁→ Diode D
_Four→ Capacitor C₁’→ Diode D₂→ Capacitor C
₃→ inductor L₂→ Capacitor C_Four→ AC power supply Vs
A current flows along the path.

Compared with the twelfth embodiment, this embodiment has modes 3, 4 and 6 in the path through which the current flows via the impedance element Z.
In 5, a full wave rectifier DB is added, and conversely, modes 1, 2 and
6 is different in that the path passing through the full-wave rectifier DB is omitted and the AC power source Vs directly flows. The function and effect of this embodiment configured as described above are similar to those of the seventh embodiment. (Embodiment 14) In this embodiment, as shown in FIG. 33, an oscillating circuit Z ₀ of an inverter circuit H is provided between a connection point of an impedance element Z and a capacitor C ₃ and a positive side DC output terminal of a full-wave rectifier DB. It differs from the twelfth embodiment in that it is connected. FIG. 34 shows a specific circuit of this embodiment.

The circuit operation of this embodiment when the voltage of the AC power supply Vs is near 0 can be divided into 6 modes as in the case of the twelfth embodiment. Of these, the operation of the inverter circuit I is exactly the same as that of the seventh embodiment. Further, a high frequency is superposed via the impedance element Z, and the capacitor C _{1 of} the smoothing circuit H,
Since the operation of charging C ₁ 'is the same as that in the twelfth embodiment, the description of each operation is omitted.

The operational effects of this embodiment are similar to those of the seventh embodiment. (Embodiment 15) In this embodiment, as shown in FIG. 35, an impedance element Z is connected between a connection point between an oscillating circuit Z _{0 of} an inverter circuit H and a capacitor C ₃ and an input end of a full-wave rectifier DB. And is different from the fourteenth embodiment. FIG. 36 shows a specific circuit of this embodiment.

The circuit operation of the present embodiment when the voltage of the AC power supply Vs is near 0 is divided into 6 modes as in the fourteenth embodiment. Among them, the operation of the inverter circuit I is the same as that of the fifteenth embodiment. In addition, the high frequency is superposed via the impedance element Z, and the capacitors C ₁ and C of the smoothing circuit H are
_Since the operation of charging 1'is the same as that in the thirteenth embodiment, the description of each operation will be omitted.

The operational effects of this embodiment are similar to those of the seventh embodiment. (Embodiment 16) In this embodiment, as shown in FIG.
And a resonant circuit Z ₀ of the impedance element Z and the inverter circuit I which was constituted by one circuit in the connection position of the impedance elements Z in Example 9 an oscillating circuit Z ₀ of the inverter circuit I is also used as the impedance element Z To the vibration circuit Z ₀ . FIG. 38 shows a specific circuit of this embodiment.

Next, the voltage of the AC power supply Vs of this embodiment is 0V.
The operation in the vicinity will be described based on FIGS. 39 to 40. First
Transistor Q of inverter circuit I₁, Q₂On, oh
And the vibration circuit Z ₀Depending on the direction of the current flowing through
It can be divided into the following 4 modes. First, as shown in Fig. 39 (a).
Sea urchin, transistor Q₁Is on, transistor Q₂Is o
In the case of mode 1 of F, the transformer of the inverter circuit I is
T₃Primary winding → Capacitor C₃→ Diode D₁→
Indexer C₇→ Transformer T₃Of the primary winding path of
The current ia flows.

The current ib flows through the path of the full-wave rectifier DB → capacitor C ₇ → capacitor C ₁ → diode D ₄ → capacitor C ₁ ′ → full-wave rectifier DB. FIG. 39 (b)
As shown in, in the mode 2 in which the transistor Q ₁ is on and the transistor Q ₂ is off, the primary winding of the transformer T ₃ of the inverter circuit I → capacitor C ₇ → transistor Q ₁ → capacitor C ₃ → transformer. The current ia flows in the path of the secondary winding of T ₃ .

Further, as shown in FIG. 40A, in the mode 3 in which the transistor Q ₁ is off and the transistor Q ₂ is on, the primary winding of the transformer T ₃ of the inverter circuit I →
A regenerative current ia flows in the path of the primary winding of the diode D ₃ → capacitor C ₁ → diode D ₄ → capacitor C ₁ ′ → diode D ₂ → capacitor C ₃ → transformer T ₃ .

Furthermore, as shown in FIG. 40B, in the mode 4 in which the transistor Q ₁ is off and the transistor Q ₂ is on, the capacitor C ₁ → the capacitor C ₇ → the primary of the transformer T ₃ of the inverter circuit I is Winding → Capacitor C ₃
→ Transistor Q ₂ → Diode D ₅ → Capacitor C ₁
And the capacitor C ₁ '→ diode D ₆ → capacitor C ₇ → primary winding of transformer T ₃ → capacitor C ₃ →
Transistor Q ₂ → capacitor C ₁ 'and the current i
a and ia 'flow.

As described above, in the mode 1, since the current directly flows from the AC power supply Vs through the full-wave rectifier DB, even if the voltage of the AC power supply Vs is near 0V, the input current Iin
Can be kept flowing and the input distortion can be improved. Further, in the vicinity of the peak of the voltage of the AC power supply Vs, the following mode 5 appears instead of the above mode 4.

That is, in this mode 5, as shown in FIG. 40C, the capacitor C ₁ of the inverter circuit I → the capacitor C ₇ → the primary winding of the transformer T ₃ → the capacitor C ₃ → the transistor Q ₂ → the diode D ₅ → a path of the capacitor C _1, the capacitor C ₁ '→ diode D ₆ → 1 winding → capacitor C of the capacitor C ₇ → transformer T _{3 3} → transistor Q ₂ → capacitor C _1' to other current flows in the path of , The full-wave rectifier DB → the primary winding of the transformer T ₃ → the capacitor C ₃ → the transistor Q ₂ → the current ib flows in the path of the full-wave rectifier DB.

As described above, in this embodiment, the high frequency power is supplied to the discharge lamp La, which is a load, by turning on / off the transistors Q ₁ and Q ₂ , as in the case of the seventh embodiment. In this case, the smoothing circuit H which is buried in the ½ trough serves as the power source of the inverter circuit I over the entire cycle of the AC power source Vs. Mainly the smoothing circuit H and the AC power supply V
The difference is that the AC power supply Vs is mainly supplied to the inverter circuit I via the full-wave rectifier DB near the peak voltage of s.

Impedance is required as compared with the ninth embodiment.
Since the element Z can be omitted, the size of the device can be further reduced.
it can. The other effects are similar to those of the seventh embodiment.
It (Embodiment 17) In this embodiment, as shown in FIG.
Vibration circuit Z of circuit circuit I₀Capacitor C₃And the circuit graph
To the ground (minus DC output of full-wave rectifier DB)
Connect and diode D₃And capacitor C₇Parallel circuit
To ground side transistor Q ₂From vibration circuit Z₀Heda
Iodo D₃Is connected in such a way that
Different from Example 16. FIG. 42 shows a specific circuit of this embodiment.
You

The operation when the voltage of the AC power supply Vs of this embodiment is around 0 V is divided into four modes as in the sixteenth embodiment. That is, in the mode 1 in which the transistor Q ₁ is on and the transistor Q ₂ is off, the primary winding of the transformer T ₃ of the inverter circuit I → capacitor C ₃ → diode D ₁ → capacitor C ₁ → diode D ₄ → A regenerative current flows in the path of the capacitor C ₁ '→ diode D ₃ → primary winding of the transformer T ₃ .

In the mode 2 in which the transistor Q ₁ is on and the transistor Q ₂ is off, the inverter circuit I
Capacitor C ₁ → transistor Q ₁ → capacitor C ₃
→ transformer T ₃ primary winding → capacitor C ₇ → diode D ₅ → capacitor C ₁ path and capacitor C ₁ '→
Diode D ₆ → Transistor Q ₁ → Capacitor C ₃ →
A current flows through the path of the primary winding of the transformer T ₃ → the capacitor C ₇ → the capacitor C ₁ '.

Further, the transistor Q₁Off, transition
Star Q₂When the mode is ON, the inverter circuit I
Trance of₃Primary winding → Capacitor C₇→ Daio
De D ₂→ Capacitor C₃→ Transformer T₃Of the primary winding of
A regenerative current flows on the road, and the full-wave rectifier DB →
Indexer C₁→ Diode D_Four→ Capacitor C₁’→
Indexer C₇→ High frequency is superposed on the path of full wave rectifier DB
Current flows.

Further, in the mode 4 in which the transistor Q ₁ is off and the transistor Q ₂ is on, the capacitor C ₃ of the inverter circuit I → transistor Q ₂ → capacitor C ₇ → primary winding of the transformer T ₃ → capacitor C 3. Current flows through the path of ₃ . Further, in the vicinity of the peak of the voltage of the current source Vs, the following mode 5 appears instead of the mode 2.

That is, in this mode 5, the capacitor C ₁ of the inverter circuit I → transistor Q ₁ → capacitor C ₃ →
Primary winding of transformer T ₃ → capacitor C ₇ → diode D ₅ → capacitor C ₁ path and capacitor C ₁ '→ diode D ₆ → transistor Q ₁ → capacitor C ₃ → transformer T ₃ primary winding → Capacitor C ₇ → Capacitor C
_In addition to the current flowing through the 1'path, a current flows through the path of the full-wave rectifier DB → transistor Q ₁ → capacitor C ₃ → primary winding of the transformer T ₃ → full-wave rectifier DB.

The operation and effect of this embodiment described above are the same as those of the sixteenth embodiment. (Embodiment 20) Although no particular reference was made to the control circuit CT in each of the above embodiments, the present embodiment 20 is as shown in FIG. 43, which is an astable multi-M1, a monostable multi-M2 and a drive circuit D.
Embodiment 16 uses a control circuit composed of R and
On the basis of the above circuit, the switching elements of the inverter circuit I use transistors Q ₁ and Q _{2 formed} of MOSFETs, parasitic diodes are used instead of the diodes D ₁ and D ₂ , and the inductor L _{1 of the} vibration circuit is connected to the transformer T _{1. 3} is inserted between the primary winding and the capacitor C _3, and further a diode D ₀ is inserted between the diode D ₃ and the full-wave rectifier DB, and the capacitor C ₈ is connected in parallel with the output terminal of the full-wave rectifier DB. Is different from Example 9 in that F in FIG. 43
Is a low-pass filter.

Next, the operation of this embodiment will be described focusing on the control circuit CT. First, the astable multi M1 is the capacitor C
The oscillation cycle is determined by the time constant of T 1 and the resistance RT ₁ , and this oscillation output is given to the monostable multi-M 2 as a trigger signal. In the monostable multi-M2, the width of the output pulse is determined by the time constant of the capacitor CT ₂ and the resistor RT ₂ , and the output pulse is given as an ON / OFF signal to the gates of the transistors Q ₁ and Q ₂ through the drive circuit DR. There is.

Here, the voltage across the capacitor C ₆ connected in parallel to the smoothing circuit H is connected to the connection point between the capacitor CT ₂ and the resistor RT ₂ through the resistor RT ₃ . That is, when the power supply voltage of the inverter circuit I is high, the charging of the capacitor CT ₂ is accelerated and the output pulse width of the monostable multi-M 2 is shortened, and when the power supply voltage of the inverter circuit I is low, the charging of the capacitor CT ₂ is delayed. The output pulse width of the stable multi M2 is made longer.

[0105] The drive circuit DR is to be turned off on and Q ₂ is a transistor Q ₁ when the output of the monostable M2 is "H" on off the transistor Q _1, the Q ₂ is when, "L" It is designed to output a drive signal. With the above configuration, when the voltage across the capacitor C ₆ is high, the diode D ₀ → the primary winding of the transformer T ₃ → the inductor L ₁ → the capacitor C ₃ → the transistor during one cycle of the operation of the inverter circuit I. Shorten the period in which the current flows in the path of Q ₂ to reduce diode D ₀ → diode D
The parallel circuit of ₃ and the capacitor C ₇ → capacitor C ₁ → diode D ₄ → capacitor C ₁ ′ is controlled so as to lengthen the period of current flow and vice versa when the voltage across the capacitor C ₆ is low. It will be.

By controlling the period during which the current flows in each path according to the power supply voltage of the inverter circuit I, the harmonic components contained in the input current waveform are reduced and the ripple rate (crest factor) of the lamp current is improved. It becomes possible to do. That is, when the voltage of the capacitor C ₆ is high by controlling the pulse width of the transistor Q _1, Q ₂ in accordance with the voltage of the capacitor C _6, suppressing the instantaneous value of the lamp current, when the voltage of the capacitor C ₆ is low in the reverse By increasing the instantaneous value of the lamp current, the stress factor of the lamp current can be improved.

FIG. 44 shows the capacitor C ₆ shown in FIG.
Of the lamp current waveform (FIG. 7B) and the input current Iin (FIG. 7C) in the case where the resistor RT ₃ for detecting the voltage is not provided, and the capacitor C ₆ shown in FIG. shows a waveform obtained when a resistor RT ₃ for detecting the voltage of the lamp current waveform (Fig. (b) ') and the input current Iin (FIG (c)'). By the way, in the lamp current waveform of FIG. 44, there is a second peak value of the lamp current in the vicinity of the zero cross of the input current, but such a lamp current is due to the load characteristics of the inverter circuit I. The voltage of the capacitor C ₇ is an operating voltage as shown in FIG. 45 (a), and in the vicinity of the zero cross of the voltage of the AC power supply Vs shown in FIG. 45 (b), the voltage of the capacitor C ₁ is higher than that of the AC power supply Vs. C ₁ 'and the voltage of C ₆ is high enough, (equal to the potential of the C ₆₎ cathode potential relative to the anode side potential of the diode D ₃ is longer to lower, the diode D ₃ Is almost off.

Therefore, regarding the load of the inverter circuit I, the period in which the capacitor C ₇ is connected in series with the inductor L ₁ which is a current limiting element of the lamp current becomes long in one operation cycle of the inverter circuit I, and the lamp current is increased. The action of substantially reducing the current limiting impedance of the above-mentioned works, and the lamp current increases near the zero cross of the voltage of the AC power supply Vs by the above.

Although the output pulse width of the monostable multi M2 is controlled in this embodiment, the oscillation cycle of the astable multi M1 may be controlled, or both the oscillation cycle and the pulse width may be controlled. But naturally good. (Embodiment 21) In this embodiment, the control circuit CT of Embodiment 20 is used in a circuit based on Embodiment 9, and FIG.
As shown in FIG. 7, transistors Q ₁ and Q _{2 formed} of MOSFETs are used as switching elements of the inverter circuit I, parasitic diodes are used instead of the diodes D ₁ and D ₂ , and the inductor L _{1 of the} oscillating circuit is connected to the transformer T _3. The circuit configuration is different from that of the ninth embodiment in that the diode D ₀ is inserted between the primary winding and the capacitor C ₃ and the diode D ₀ is inserted between the diode D ₃ and the full-wave rectifier DB. F in FIG. 46
Is a low-pass filter.

Thus, also in this embodiment, the control circuit CT causes the transistors Q ₁ and Q ₂ to respond to the voltage of the capacitor C ₆ through the resistor RT ₃ , that is, the power source voltage of the inverter circuit I.
It is possible to improve the crest factor of the lamp current while improving the waveform distortion of the input current Iin by changing the frequency or pulse width of the output pulse for driving the lamp.

FIGS. 47 (a) to 47 (c) show the lamp current (FIG. (B)) and the input current (FIG. ()) With respect to the voltage of the capacitor C ₆ (FIG. (A)) when the resistor RT ₃ is not provided. (a) 'to (c)' in the same figure show the lamp current ((b) 'in the figure) and the input current ((b)' in the figure) with respect to the voltage ((a) 'in the figure) of the capacitor C ₆ of this embodiment. (Fig. (C) ')
Indicates. (Embodiment 22) In this embodiment, as shown in FIG. 48, diodes D ₇ and D ₃ are inserted in the ground side of the circuit and connected to capacitors C ₃ for cutting DC in both ends of the vibration circuit of the inverter circuit I. Connect the other terminal to diodes D ₇ and D ₃
Which was connected to a connection point between, but in effect basically as Example 20 are those not change the operation of the inverter circuit I, consisting of MOSFET in parallel circuit of a diode D ₃ and a capacitor C ₇ transistor Q ₃ is connected in parallel and the transistor Q ₃ is controlled by the output of the comparator CP to improve the waveform distortion of the input current Iin. The control circuit CT does not use the resistor RT ₃ as in the twentieth and twenty-first embodiments, but drives the transistors Q ₁ and Q ₂ with an output having a predetermined frequency and a constant pulse width.

The comparator CP has the circuit shown in FIG.
Indexer C₆Across the voltage of the smoothing circuit H
The voltage of C1 and C1 'to the resistance R₁, R₂Obtained by partial pressure with
As shown in FIG. 49 (b), the voltage applied to the reference voltage Vref
By comparison, when the divided voltage is larger than the reference voltage Vref, FIG.
The output of "H" shown in FIG. ₃
Turn on.

Thus, the above capacitor C₆AC than voltage
When it becomes lower than the voltage of the power supply Vs, the transistor Q₃Is o
Turn on the transistor Q of the inverter circuit I₁→ Conden
SA C ₃→ inductor L₁→ Transformer T₃Primary winding →
Iodo D₇The current flows through the path. On the other hand, AC power supply Vs
If the voltage is high, the full-wave rectifier DB will be changed according to the power supply voltage.
Through the capacitor C of the smoothing circuit H₁, C₁Charging to ’
The flow flows. That is, the period when the power supply voltage of the AC power supply Vs is high
Through the full-wave rectifier DB to the smoothing circuit H according to the power supply voltage
When the charging current flows from the AC power supply Vs and the power supply voltage is low
Input current flows through the inverter circuit I,
The energy stored in the circuit I is charged to the smoothing circuit H.
An electric current flows, and the input power is input in the entire section of one cycle of the AC power supply Vs.
Current Iin flows and can improve the waveform distortion of the input current.
It

When the voltage of the AC power supply Vs is high, the transistor
Register Q₃By turning on the capacitor
C₁Of the voltage between both ends of the
Since it can be prevented from rising, it does not affect the state of the load circuit.
Without a capacitor C₆The voltage across the
Can be suppressed. In this example, the control
Resistance CT to road CT₃Through capacitor C₆The voltage across
Take in the transformer of the inverter circuit I according to its voltage.
Dista Q₁, Q ₂Together with the operation to control the switching of
You may.

The oscillator circuit Z ₀ has the structure shown in FIG. 50, and the impedance element Z has the structure shown in FIG. May be. Note that C
₂ 'constitutes a resonant capacitor together with the C _2, T denotes a transformer.

[0116]

According to the invention of claim 1, the inverter circuit comprises:
DC- that receives the DC output voltage of the rectifier and outputs a DC output voltage that is less than or equal to the peak voltage of the DC output voltage of the rectifier
A DC conversion means and a DC-AC conversion means for receiving a DC output voltage of the DC-DC conversion means and outputting a high frequency voltage are provided, and a switching element of the DC-DC conversion means and a DC.
-It is formed so as to share at least one switching element among the switching elements of the AC conversion means, and the auxiliary power supply means is formed so as to charge a plurality of capacitors in series by a plurality of diodes, and a plurality of capacitors. Are formed so as to be discharged in parallel by a plurality of diodes, and the DC voltage is supplied to the inverter circuit at a predetermined voltage of the AC power supply or less, so that the AC power is always supplied to the DC-DC converting means. Therefore, it is possible to prevent a rest period from occurring in the input current from the AC power supply, and the power supply voltage of the DC-AC conversion means is between the peak value of the output value of the rectifier and the output voltage of the auxiliary power supply voltage. Since the voltage fluctuates, the fluctuation range of the voltage is small, and moreover, the output voltage of the DC-DC converting means is the peak of the DC output voltage of the rectifier. Because less click value, compared to the voltage applied to the DC-AC conversion means it is hardly increased in the case of using a conventional smoothing capacitor, such as an effect that the stress to the switching element is reduced.

[0117] From further to the part of the previous SL load circuit magnetically between an output terminal of the rectifier, a bypass circuit is part of a DC-DC converter means connected comprise electrically impedance element Since it is configured, a current can be continuously flowed by the effect of high frequency superposition except near the peak value of the output value of the rectifier, and the input current waveform is a substantially sine wave with few harmonic components similar to the power supply voltage waveform. There is an effect that can be done. The invention of claim 2 is the invention of claim 1.
Specific embodiment of the auxiliary power supply means that can obtain the same effect as
It is like.

[0118]

The invention of claim 3 has an effect that each of the actions in the invention of claim 1 can be obtained.

[0120]

[Brief description of drawings]

FIG. 1 is a circuit configuration diagram of a first embodiment of the present invention.

FIG. 2 is a waveform diagram for explaining the operation of the above.

FIG. 3 is a specific circuit diagram of the above.

FIG. 4 is a waveform diagram for explaining the operation of the above.

FIG. 5 is a specific circuit diagram of the second embodiment of the present invention.

FIG. 6 is a specific circuit diagram according to the third embodiment of the present invention.

FIG. 7 is a specific circuit diagram of the fourth embodiment of the present invention.

FIG. 8 is a circuit configuration diagram of a fifth embodiment of the present invention.

FIG. 9 is a specific circuit diagram of the above.

FIG. 10 is a circuit configuration diagram of a sixth embodiment of the present invention.

FIG. 11 is a specific circuit diagram of the above.

FIG. 12 is a circuit configuration diagram of a seventh embodiment of the present invention.

FIG. 13 is a specific circuit diagram of the above.

FIG. 14 is an explanatory diagram of an operation of the above.

FIG. 15 is an operation explanatory diagram of the above.

FIG. 16 is an explanatory diagram of an operation of the above.

FIG. 17 is a circuit configuration diagram of an eighth embodiment of the present invention.

FIG. 18 is a specific circuit diagram of the above.

FIG. 19 is a circuit configuration diagram of a ninth embodiment of the present invention.

FIG. 20 is a waveform diagram for explaining the same operation as above.

FIG. 21 is a specific circuit diagram of the above.

FIG. 22 is an explanatory diagram of an operation of the above.

FIG. 23 is an explanatory diagram of the operation of the above.

FIG. 24 is an explanatory diagram of the operation of the above.

FIG. 25 is a circuit configuration diagram of a tenth embodiment of the present invention.

FIG. 26 is a specific circuit diagram of the above.

FIG. 27 is a circuit configuration diagram of Embodiment 11 of the present invention.

FIG. 28 is a specific circuit diagram of the above.

FIG. 29 is a circuit configuration diagram of a twelfth embodiment of the present invention.

FIG. 30 is a specific circuit diagram of the above.

FIG. 31 is a circuit configuration diagram of Embodiment 13 of the present invention.

FIG. 32 is a specific circuit diagram of the above.

FIG. 33 is a circuit configuration diagram of Embodiment 14 of the present invention.

FIG. 34 is a specific circuit diagram of the above.

FIG. 35 is a circuit configuration diagram of a fifteenth embodiment of the present invention.

FIG. 36 is a specific circuit diagram of the above.

FIG. 37 is a circuit configuration diagram of Embodiment 16 of the present invention.

FIG. 38 is a specific circuit diagram of the above.

[Fig. 39] Fig. 39 is an operation explanatory view of the above.

FIG. 40 is an operation explanatory diagram of the above.

FIG. 41 is a circuit configuration diagram of a seventeenth embodiment of the present invention.

FIG. 42 is a specific circuit diagram of the above.

FIG. 43 is a circuit configuration diagram of Embodiment 18 of the present invention.

FIG. 44 is a waveform diagram for explaining the same operation as above.

FIG. 45 is a waveform diagram for explaining the same operation as above.

FIG. 46 is a circuit configuration diagram of Embodiment 19 of the present invention.

FIG. 47 is a waveform diagram for explaining the operation of the above.

FIG. 48 is a circuit configuration diagram of a twentieth embodiment of the present invention.

FIG. 49 is a waveform diagram for explaining the operation in the above.

FIG. 50 is a diagram showing a configuration example of a vibration circuit used in the present invention.

FIG. 51 is a structural example diagram of an impedance element used in the present invention.

FIG. 52 is a circuit configuration diagram of a conventional example.

FIG. 53 is a waveform chart for explaining the operation in the above.

FIG. 54 is a circuit configuration diagram of another conventional example.

FIG. 55 is a waveform chart for explaining the operation in the above.

FIG. 56 is a circuit configuration diagram of another conventional example.

FIG. 57 is a waveform chart for explaining the operation of the above.

FIG. 58 is a circuit configuration diagram of another conventional example.

FIG. 59 is a waveform diagram for explaining the operation of the above.

[Explanation of symbols]

Z impedance element H smoothing circuit I inverter circuit DB full-wave rectifier Vs AC power supply La discharge lamp D ₃ diode

─────────────────────────────────────────────────── --Continued from the front page (56) References JP-A-5-56647 (JP, A) JP-A-6-225540 (JP, A) JP-A-5-276756 (JP, A) JP-A-5- 56660 (JP, A) JP-A-5-56659 (JP, A) JP-A-6-315272 (JP, A) (58) Fields investigated (Int.Cl. ⁷ , DB name) H02M 7/48 H02M 7 / 06 H05B 41/24 H05B 41/282

Claims (3)

(57) [Claims] 1. An AC power supply, a rectifier that rectifies an AC voltage of the AC power supply, an inverter circuit that receives a DC output voltage of the rectifier and outputs a high frequency voltage, a resonance inductor that receives the high frequency voltage, and a resonance inductor. A load circuit including a capacitor and a discharge lamp, and a smoothing capacitor connected in parallel to the output terminal of the rectifier and capable of supplying a continuous current of a level capable of substantially maintaining lighting of the discharge lamp without re-ignition. And a DC-DC converting means for receiving a DC output voltage of the rectifier and outputting a DC output voltage equal to or lower than the peak voltage of the DC output voltage of the rectifier, and the DC-DC converting means. A DC-AC conversion unit for receiving a DC output voltage of the DC conversion unit and outputting a high frequency voltage, and a switching element of the DC-DC conversion unit and a DC-AC conversion unit. Among the switching elements of the stages, at least one switching element is formed in common, and the auxiliary power supply means is formed so as to charge a plurality of capacitors in series by a plurality of diodes, and a plurality of capacitors. In a power supply device that is formed by diodes so as to be discharged in parallel and supplies a DC voltage to the inverter circuit at a predetermined voltage or less of an AC power supply.
Through the first diode to the output of the rectifier
The auxiliary power supply means is connected, and the auxiliary power supply means is the first
A capacitor, a forward diode and a second capacitor
Series circuit with first capacitor and forward diode
A reverse diode connected in parallel with the series circuit of
In the series circuit of the forward diode and the second capacitor
Consisting of a reverse diode connected in parallel,
The inverter circuit is connected to both ends of the auxiliary power supply means.
A series circuit of the first and second switching elements,
Resonance connected across both switching elements
Circuit of inductor for resonance, capacitor for resonance and discharge lamp
A load circuit comprising: a part of the load circuit;
Magnetically and electrically impedance between the output end of the sink
It is a part of the DC-DC conversion means connected including the elements.
And a bypass circuit for
Ri power and wherein the DC voltage is to be supplied to the inverter circuit with a predetermined voltage or lower of the AC power source. 2. An AC power supply and an AC voltage of this AC power supply are adjusted.
The rectifier that flows and the DC output voltage of this rectifier
An inverter circuit for outputting a frequency voltage, the high-frequency voltage
Resonant inductor, resonant capacitor and discharge lamp
And a load circuit including and a parallel connection to the output terminal of the rectifier.
Is connected to the discharge lamp and the discharge lamp can be turned on without re-ignition.
A smoothing capacitor that can supply a continuous level of current that can be maintained
And an auxiliary power supply unit including a capacitor,
The path receives the DC output voltage of the rectifier and is connected directly to the rectifier.
Output a DC output voltage that is less than the peak voltage of the output voltage
DC-DC conversion means and direct current of this DC-DC conversion means
DC-AC conversion that receives output voltage and outputs high frequency voltage
And a switching element of the DC-DC conversion means.
And of the switching elements of the DC-AC conversion means
Both are formed to share one switching element.
The auxiliary power supply means includes a plurality of capacitors and a plurality of capacitors.
It is formed to be series-charged by the ion
In addition, multiple capacitors are connected in parallel with multiple diodes.
It is formed so as to be electrically charged,
For power supply devices that supply DC voltage to the inverter circuit
Te, before via the first diode to the output of the rectifier
Serial auxiliary power means is connected, the auxiliary power source means is connected in parallel to the series circuit of the series circuit and the first capacitor and the forward diode of the first capacitor and the forward direction of the diode and a second capacitor Reverse diode,
A diode in the forward direction and a diode in the reverse direction connected in parallel to the series circuit of the second capacitor ,
The inverter circuit includes a series circuit of first and second switching elements connected to both ends of the auxiliary power supply means, a resonance inductor, a resonance capacitor, and a discharge lamp connected to both ends of at least one of the switching elements. the exchange and the load circuit comprising the oscillation circuit, a part of the load circuit
Magnetic between one end of the flow source, is composed of a bypass circuit which is part of the DC-DC converting means connected comprise electrically impedance element, the alternating current power supply of a predetermined voltage by the auxiliary power unit power supplies you characterized in that the direct-current voltage is supplied to the inverter circuit below. 3. An AC power supply and an AC voltage of this AC power supply are adjusted.
The rectifier that flows and the DC output voltage of this rectifier
Inverter circuit that outputs frequency voltage and this high frequency voltage
Resonant inductor, resonant capacitor and discharge lamp
And a load circuit including and a parallel connection to the output terminal of the rectifier.
Is connected to the discharge lamp and the discharge lamp can be turned on without re-ignition.
A smoothing capacitor that can supply a continuous level of current that can be maintained
Power supply odor and a including an auxiliary power source means to capacitors
A rectifier at the output end of the first diode and a capacitor.
The auxiliary power supply means is connected via a parallel circuit of a service,
The auxiliary power supply means includes a series circuit including a first capacitor, a forward diode and a second capacitor, and a reverse diode connected in parallel to the series circuit including the first capacitor and the forward diode. Direction diode and a reverse direction diode connected in parallel to the series circuit of the second capacitor, and between the both ends of the auxiliary power supply means.
Smaller capacitor is connected, the inverter circuit includes a first is connected to both ends of the auxiliary power unit, a series circuit of the second switching element, the first, second Sui
Second diode connected in anti-parallel with each other
The cathode side of the first diode and the first and second
DC block connected between the connection point of
A series circuit of a stopping capacitor and the primary winding of the transformer,
A resonance inductor connected between the secondary windings of the transformer
Connect the series circuit with the discharge lamp and the non-power supply terminal of the discharge lamp.
Continuous resonance capacitor and the DC blocking capacitor
Connection point of the series circuit between the primary winding of the transformer and the transformer
Inductor and capacitor in series with the output of the current transformer
Is composed of a bypass circuit which is part of the DC-DC conversion means circuit is connected, said to DC voltage to the inverter circuit at a predetermined voltage below the <br/> AC power source by the auxiliary power supply means is supplied power supplies you characterized in that the.