JP2016226097A - Rotary electric machine - Google Patents

Abstract

PROBLEM TO BE SOLVED: To suppress generation of core loss by supplying a current to multi-phase stator winding so that harmonic magnetic flux generated at a field magnetic pole core is canceled.SOLUTION: In a rotary electric machine 10, stator winding of one phase or more among multiple phases has a winding set including first winding (U-phase winding Ua, V-phase winding Va and W-phase winding Wa) where a current flows in a predetermined direction so as to cancel magnetic flux generated at a field magnetic pole core, and second winding (U-phase winding Ub, V-phase winding Vb and W-phase winding Wb) where a current flows in the opposite direction from the first winding. This constitution includes the first winding and second winding where flow directions of the currents are opposite to each other. Pieces of magnetic flux generated with the currents flowing to the first winding and second winding are opposite in direction, so magnetic flux (specially, harmonic magnetic flux) generated at the field magnetic pole core with a current flowing to the stator winding is canceled. Magnetic flux generated at the field magnetic pole core is therefore reduced (or eliminated), and then generation of iron loss can be suppressed.SELECTED DRAWING: Figure 3

Description

  The present invention relates to a rotating electrical machine having a stator, a rotor, a field pole core, a field winding, and the like.

  Conventionally, it is a rotary motor capable of adjusting the amount of interlinkage magnetic flux in the armature winding, and the rotor can be made compact. An example of a technique related to a rotary electric motor intended to reduce is disclosed (for example, see Patent Document 1). In this rotary electric motor, the field yoke is disposed at a position axially separated from the ends of the stator core and the rotor core, and includes a top plate portion, a side wall portion, and a cylindrical protrusion. The protrusion is formed to protrude toward the axial end of the second rotor core. The winding is wound around the outer peripheral surface of the protrusion.

Japanese Patent No. 4623471

  In the rotary electric motor described in Patent Document 1, a magnetic circuit having a coil end as a magnetomotive force is formed. The magnetic flux flows in the magnetic circuit, for example, stator → field yoke → rotor → stator. When a current is applied to the armature winding, a magnetomotive force is generated at the coil end and a magnetic field is generated, so that a magnetic flux flows through the field yoke. If a harmonic component is included in the magnetic flux flowing through the field yoke, iron loss occurs and becomes a problem.

  The present invention has been made in view of the above points, and is designed to cancel the multi-phase stator winding (the armature winding described above) so as to cancel the harmonic magnetic flux generated in the field pole core (corresponding to the field yoke). An object of the present invention is to provide a rotating electrical machine that can suppress the occurrence of iron loss by passing a current through a wire).

  1st invention made | formed in order to solve the said subject, The stator (14) containing the stator core (14a) and the multiphase stator winding (14b) wound around the said stator core, A rotor (13) provided rotatably with the stator core and a gap (G), a field pole core (11, 15) provided so as to sandwich the stator core in the axial direction, and the field pole A magnetic circuit (MC1a, MC1b, MC2a, MC2b) having magnetic field windings (16, 17) wound around the core and magnetic flux (ψa, ψb) flowing through the stator, the rotor and the field pole core. In the rotating electrical machine (10) in which the first and second stator coils are formed, a current flows in a predetermined direction in the stator winding of one or more of the multiphases so as to cancel the magnetic flux generated in the field pole core. Winding (Ua, Va, Wa) and a winding set including a second winding (Ub, Vb, Wb) in which a current flows in a direction opposite to that of the first winding.

  According to this configuration, the stator winding of one or more phases among the polyphases has a winding set including the first winding and the second winding in which the current flowing directions are opposite to each other. In particular, it is preferable that the directions of current flow are opposite to each other in the first winding and the second winding in the coil end portion protruding from the stator core. Since the magnetic flux generated by the current flowing in the first winding and the second winding is in the opposite direction, the magnetic flux generated in the field pole core is canceled by the current flowing in the stator winding. Therefore, since the magnetic flux (especially harmonic magnetic flux) generated in the field pole core is reduced (or eliminated), the generation of iron loss can be suppressed.

  According to a second aspect of the present invention, the in-phase stator winding having the winding set is wound around the stator core so as to be adjacent in the circumferential direction.

  According to this configuration, the set windings included in the stator windings in the same phase, that is, the first winding and the second winding are wound around the stator core so as to be adjacent in the circumferential direction. Since the magnetic flux generated by the current flowing through the first winding and the second winding is canceled, it is possible to suppress the occurrence of iron loss in the field pole core. In addition, the short coefficient can be increased with this configuration. For example, in the structural example (for example, 6 slots, 4 poles) of the first winding and the second winding that are wound apart in the circumferential direction, the coil pitch is 120 degrees in electrical angle, but adjacent in the circumferential direction. In the structural example (for example, 6 slots, 5 poles) of the first winding and the second winding wound so as to fit with each other, the coil pitch is 150 degrees in terms of electrical angle, and thus the short node coefficient is high. Furthermore, the connecting wire connecting between the first winding and the second winding can be shortened by arranging the stator windings adjacent to each other.

  A third aspect of the invention is characterized in that the same-phase stator windings having the winding set are wound around the stator core while being spaced apart in the circumferential direction.

  According to this configuration, the set windings included in the stator windings of the same phase, that is, the first winding and the second winding are wound around the stator core while being separated in the circumferential direction. Since the first and second windings are separated, the radial force generated by the magnetic flux linked to the magnetic pole teeth (also called teeth) is dispersed, reducing the vibration of the stator and suppressing the generation of noise. it can.

  “Outside” means the outer diameter side or outer periphery side in the radial direction, and “inner side” means the inner diameter side or inner periphery side in the radial direction. The “rotor (rotor)” is formed into a circular shape (including an annular shape and a cylindrical shape). The “rotary electric machine” is arbitrary as long as it is a device having a rotating member (for example, a shaft or a shaft). For example, a generator, a motor, a motor generator, and the like are applicable. The generator includes a case where the motor generator is a generator, and the motor includes a case where the motor generator is an electric motor. The “inner rotor type” is a configuration in which the rotor is disposed inside the stator (stator). The “outer rotor type” is a configuration in which the rotor is arranged outside the stator. The “stator winding” is a stator winding, and may be a single winding, or may be a single winding formed by electrically connecting a plurality of conductor wires or coils. The number of phases of the stator winding is not limited as long as it is three or more. The “core” is also called an iron core, and at least a portion where magnetic flux flows is formed of a magnetic material.

It is a perspective view which shows the structural example of a rotary electric machine typically. It is sectional drawing which shows typically the 1st structural example of a rotary electric machine. It is sectional drawing of the III-III line shown in FIG. It is sectional drawing which developed the 1st example of winding of the stator coil | winding in the circumferential direction. It is sectional drawing of the VV line shown in FIG. It is sectional drawing of the VI-VI line shown in FIG. It is a time chart figure which shows the example of a change of the magnetic flux with respect to an electrical angle. It is a time chart figure which shows the example of a change of the magnetic flux with respect to the electrical angle of a prior art. It is a graph which shows the example of a relationship between a field linkage magnetic flux and an armature magnetomotive force. It is a graph which shows the example of a relationship between an iron loss and an armature magnetomotive force. It is sectional drawing which shows the 2nd structural example of a rotary electric machine typically. It is sectional drawing which expand | deployed the 2nd example of winding of the stator coil | winding in the circumferential direction. It is sectional drawing which shows typically the 3rd structural example of a rotary electric machine. It is sectional drawing which shows typically the 4th structural example of a rotary electric machine. It is sectional drawing which shows typically the 5th structural example of a rotary electric machine. It is sectional drawing which shows typically the 6th structural example of a rotary electric machine.

  Hereinafter, embodiments for carrying out the present invention will be described with reference to the drawings. Note that unless otherwise specified, “connecting” means electrically connecting. Each figure shows elements necessary for explaining the present invention, and does not necessarily show all actual elements. Elements other than the illustrated elements (such as a housing) are not shown in each drawing, and description thereof is omitted in the specification. The directions such as up, down, left and right are based on the description in the drawings. Alphanumeric continuous codes are abbreviated using the symbol “˜”. For example, “rotating electrical machines 10A to 10E” means “rotating electrical machines 10A, 10B, 10C, 10D, and 10E”. In the case of “fixing”, the fixing method is arbitrary and the fixing method is not limited.

[Embodiment 1]
The first embodiment will be described with reference to FIGS. A rotating electrical machine 10 shown in an exploded perspective view in FIG. 1 is an inner rotor type and includes field pole cores 11 and 15, a rotating shaft 12, a rotor 13, a stator 14, and the like. These elements are arranged axially as shown. The field pole cores 11 and 15 are provided so as to sandwich the rotor 13 and the stator 14.

  FIG. 2 is a sectional view of the rotary electric machine 10A after assembly. The rotating electrical machine 10 </ b> A is an example of the rotating electrical machine 10, and is variable by controlling the field current If (see FIG. 2) that flows the magnetic flux density between the rotor 13 and the stator 14 through the field winding 16. Configured to be able to. The rotating shaft 12 (shaft) is rotatably provided. The rotating shaft 12 is fixed to the rotor 13 directly or indirectly. Therefore, the rotating shaft 12 and the rotor 13 rotate integrally.

  The rotor 13 and the stator 14, and the field pole core 11 (particularly the wound portion 11 a) and the rotor 13 are all provided via the gap G. As long as the magnetic flux flows between the rotor 13 and the stator 14 and the magnetic flux flows between the field pole core 11 and the rotor 13, the distance (width) of the gap G is set to an arbitrary value individually. Good.

  The rotor 13 includes a rotor core 13a and a magnet 13b. The rotor core 13a may be configured by laminating electromagnetic steel plates or may be configured by a single magnetic material. The magnet 13b is provided outside the rotor core 13a on the side facing the stator 14. The magnet 13b may be exposed to the outside of the rotor core 13a or may be embedded in the rotor core 13a. The number of magnets 13b can be set arbitrarily, and is “2” in this embodiment (see FIG. 3). That is, the number of magnetic poles of N pole and S pole is “4”, and the number of magnetic pole pairs is “2”. A bearing (bearing) may be interposed between the rotor 13 and the field pole core 11 (not shown).

  The stator 14 includes a stator core 14a and a stator winding 14b. The stator core 14a may be configured by laminating electromagnetic steel plates or may be configured by a single magnetic material. In the stator core 14a, magnetic pole teeth TE (tooth; see FIG. 4), slots SL that are spaces provided between adjacent magnetic pole teeth, and the like are formed to wind the stator winding 14b. Both the number of magnetic pole teeth TE and the number of slots SL may be set arbitrarily. Usually, since the magnetic pole teeth TE and the slots SL are alternately arranged, the number of the magnetic pole teeth TE and the slots SL is equal. In this embodiment, the number of slots SL is “6” (see FIG. 3).

  The stator winding 14b is a multi-phase winding, and three phases (for example, U phase, V phase, W phase) are applied in this embodiment. The winding around the stator core 14a may be concentrated winding or distributed winding. In this embodiment, concentrated winding is applied. The stator winding 14b includes a U-phase winding Ua, a V-phase winding Va, a W-phase winding Wa, and a U-phase winding Ub, a V-phase winding Vb, and a W-phase winding Wb. The former U-phase winding Ua, V-phase winding Va, and W-phase winding Wa correspond to “first winding”. The latter U-phase winding Ub, V-phase winding Vb, and W-phase winding Wb correspond to “second winding”. The first winding and the second winding correspond to a “winding set” and are provided so that currents flow in opposite directions. The first winding and the second winding may be wound in opposite directions, or may be wound in the same direction and current may flow in the opposite direction. In this embodiment, a set of U-phase winding Ua and U-phase winding Ub, a set of V-phase winding Va and V-phase winding Vb, and a set of W-phase winding Wa and W-phase winding Wb are respectively “windings”. Corresponds to “set”.

  A portion of the stator winding 14b wound around the stator 14 that protrudes from the stator core 14a is referred to as a coil end portion CE (see FIG. 4). The coil end portion CE of this embodiment includes a first winding (U-phase winding Ua, V-phase winding Va, W-phase winding Wa in this example) and a second winding (U-phase winding Ub in this example). , V-phase winding Vb, W-phase winding Wb) (see FIG. 4).

  The field pole core 11 has a wound portion 11 a for winding the field winding 16 and the like. Similarly, the field pole core 15 has a wound portion 15a for winding the field winding 17 and the like. Each of the field pole cores 11 and 15 is formed of a magnetic material at least where a magnetic flux (for example, the magnetic flux ψa shown in FIG. 5 or the magnetic flux ψb shown in FIG. 6) flows.

  The winding group will be described with reference to FIG. In the configuration example shown in FIG. 3, the U-phase winding Ua and the U-phase winding Ub are wound so as to be adjacent in the circumferential direction. The V-phase winding Va and the V-phase winding Vb are also wound so as to be adjacent in the circumferential direction. W-phase winding Wa and W-phase winding Wb are also wound so as to be adjacent in the circumferential direction. A broken line including an arrow indicates a direction of current flowing in the coil end portion CE. The direction of current shown in the legend indicates the direction of current flowing in the slot SL.

  As shown in FIG. 4, the U-phase winding Ua and the U-phase winding Ub have currents flowing in opposite directions. That is, the U-phase current Iua flowing in the U-phase winding Ua and the U-phase current Iub flowing in the U-phase winding Ub are set in opposite directions. The magnetic flux generated by the current flowing in the U-phase winding Ua and the magnetic flux generated by the current flowing in the U-phase winding Ub are canceled because they are in opposite directions. This is because the relationship between the V-phase winding Va, the V-phase current Iva and the V-phase winding Vb, the V-phase current Ivb, the W-phase winding Wa, the W-phase current Iwa, the W-phase winding Wb, and the W-phase current. The same applies to the relationship with Iwb.

  FIG. 5 shows an example of the magnetic circuits MC1a and MC2a formed by the magnetic flux ψa generated by passing a current through the first winding. The magnetic circuit MC1a is formed by a magnetic flux ψa flowing through the stator 14, the rotor 13, and the field pole core 11. The magnetic circuit MC2a is formed by a magnetic flux ψb flowing through the stator 14, the rotor 13, and the field pole core 15.

  FIG. 6 shows an example of the magnetic circuits MC1b and MC2b formed by the magnetic flux ψb generated by passing a current through the second winding. The magnetic circuit MC1b is formed by a magnetic flux ψb flowing through the stator 14, the rotor 13, and the field pole core 11. The magnetic circuit MC2b is formed by a magnetic flux ψb flowing through the stator 14, the rotor 13, and the field pole core 15.

  Since the currents flowing through the first winding and the second winding are in opposite directions, the magnetic flux ψa shown in FIG. 5 and the magnetic flux ψb shown in FIG. 6 are also generated in opposite directions. FIG. 7 shows an example of change between the magnetic flux ψa indicated by the one-dot chain line and the magnetic flux ψb indicated by the two-dot chain line. The combined magnetic flux ψc (indicated by the solid line) obtained by synthesizing the magnetic flux ψa and the magnetic flux ψb is theoretically zero. Thus, the magnetic flux ψa and the magnetic flux ψb (particularly harmonic magnetic flux) generated in the field pole cores 11 and 15 are canceled each other. Since the magnetic flux ψa and the magnetic flux ψb are canceled in this way, the magnetic circuits MC1a, MC1b, MC2a, MC2b are not generated. Therefore, the magnetic circuits MC1a, MC1b, MC2a, and MC2b shown in FIGS. 5 and 6 are merely shown for convenience of explanation.

  As shown in FIG. 8, in the prior art, a combined magnetic flux ψx (indicated by a two-dot chain line) synthesized by a magnetic flux ψu by a U-phase winding, a magnetic flux ψv by a V-phase winding, and a magnetic flux ψw by a W-phase winding. ) Occurs and flows to the field pole core 11. On the other hand, as shown in FIG. 7, since the magnetic flux ψa and the magnetic flux ψb are canceled, the combined magnetic flux ψc becomes zero.

  FIG. 9 shows the relationship between the field linkage magnetic flux (corresponding to the combined magnetic flux ψc) flowing in the field pole cores 11 and 15 and the armature magnetomotive force generated when the current flowing in the stator winding 14b is changed. An example is shown. A characteristic line L1 indicated by a two-dot chain line is a change when currents flowing through the first winding and the second winding are the same as in the conventional case. A characteristic line L2 indicated by a solid line is a change when the currents flowing through the first winding and the second winding are reversed. In the characteristic line L1, the field linkage magnetic flux increases as the armature magnetomotive force increases. On the other hand, in the characteristic line L2, the field linkage magnetic flux hardly changes even when the armature magnetomotive force increases.

  FIG. 10 shows an example of the relationship between the iron loss generated in the field pole cores 11 and 15 by the combined magnetic flux ψc and the armature magnetomotive force generated when the current flowing through the stator winding 14b is changed. A characteristic line L3 indicated by a two-dot chain line is a change when the currents flowing through the first winding and the second winding are the same as in the conventional case. A characteristic line L4 indicated by a solid line is a change when the currents flowing through the first winding and the second winding are reversed. In the characteristic line L3, the iron loss increases as the armature magnetomotive force increases. On the other hand, in the characteristic line L4, the iron loss hardly changes even when the armature magnetomotive force increases.

[Embodiment 2]
The second embodiment will be described with reference to FIGS. For simplicity of illustration and description, unless otherwise specified, the same elements as those used in the first embodiment are denoted by the same reference numerals and description thereof is omitted. Therefore, differences from the first embodiment will be mainly described.

  A rotating electrical machine 10 </ b> B illustrated in FIG. 11 is an example of the rotating electrical machine 10. This rotating electrical machine 10B is a modification of the rotating electrical machine 10A shown in FIG. 3, and the magnetic flux density between the rotor 13 and the stator 14 can be varied by controlling the field current If flowing in the field winding 16. Configured to be able to.

  The rotating electrical machine 10B differs from the rotating electrical machine 10A in the arrangement of the winding set. That is, the rotating electrical machine 10A includes a first winding (U-phase winding Ua, V-phase winding Va, W-phase winding Wa) and a second winding (U-phase winding Ub, V-phase winding Vb, W-phase winding). The wire Wb) is wound so as to be adjacent in the circumferential direction. On the other hand, the rotating electrical machine 10B winds the first winding and the second winding apart in the circumferential direction.

  FIG. 11 shows a development view in the circumferential direction in the winding described above. 12 is the same as FIG. 5 and the VI-VI line is the same as FIG. The first winding (U phase winding Ua, V phase winding Va, W phase winding Wa) and the second winding (U phase winding Ub, V phase winding Vb, W phase winding Wb) are separated from each other. However, the flowing currents are in opposite directions. In the entire field pole core 11, 15, the magnetic flux ψa and the magnetic flux ψb are canceled each other. Therefore, the rotary electric machine 10B also has characteristics such as the characteristic lines L2 and L4 shown in FIG. 9 and FIG.

[Embodiment 3]
The third embodiment will be described with reference to FIG. For simplicity of illustration and description, unless otherwise specified, the same elements as those used in the first and second embodiments are denoted by the same reference numerals and description thereof is omitted. Therefore, differences from Embodiments 1 and 2 will be mainly described.

  A rotating electrical machine 10 </ b> C shown in FIG. 13 is an example of the rotating electrical machine 10 so that the magnetic flux density between the rotor 13 and the stator 14 can be varied by controlling the field current If flowing in the field winding 16. Configured.

  The rotating electrical machine 10C is a modification of the rotating electrical machine 10A shown in FIG. The rotating electrical machine 10C differs from the rotating electrical machine 10A in the number of slots SL and the number of magnets 13b. That is, in the rotating electrical machine 10A, the number of slots SL is “6”, and the number of magnets 13b is “2”. On the other hand, in the rotating electrical machine 10C, the number of slots SL is “12”, and the number of magnets 13b is “5”.

  The arrangement of the winding sets is the same as that of the first embodiment although the number of slots SL is different. Therefore, the rotating electrical machine 10C can obtain characteristics such as the characteristic lines L2 and L4 shown in FIG. 9 and FIG. Further, since the magnetic fluxes ψa and ψb (particularly harmonic magnetic flux) generated in the field pole cores 11 and 15 are canceled and become smaller (or eliminated), generation of iron loss in the field pole cores 11 and 15 can be suppressed. In addition, the short coefficient can be increased with this configuration. A first winding (U-phase winding Ua, V-phase winding Va, W-phase winding Wa) and a second winding (U-phase winding Ub, V-phase winding Vb, In the W-phase winding Wb), the coil pitch becomes an electrical angle θ (for example, 120 degrees ≦ θ ≦ 240 degrees) in accordance with the number of slots SL and the number of magnets 13b, so that the short-node coefficient becomes high. Furthermore, by arranging the stator windings 14b so as to be adjacent to each other, the connecting wire connecting the first winding and the second winding can be shortened.

  Although not shown, in the same manner as in the second embodiment, the first winding (U-phase winding Ua, V-phase winding Va, W-phase winding Wa) and the second winding (U-phase winding Ub, The V-phase winding Vb and the W-phase winding Wb) may be wound apart in the circumferential direction. The developed view in the circumferential direction is the same as FIG. Therefore, the rotary electric machine 10C also has characteristics such as the characteristic lines L2 and L4 shown in FIG. 9 and FIG.

[Embodiment 4]
Embodiment 4 will be described with reference to FIG. For simplicity of illustration and description, unless otherwise specified, the same elements as those used in the first to third embodiments are denoted by the same reference numerals and description thereof is omitted. Therefore, differences from Embodiments 1 to 3 will be mainly described.

  A rotating electrical machine 10D shown in FIG. 14 is an example of the rotating electrical machine 10 so that the magnetic flux density between the rotor 13 and the stator 14 can be varied by controlling the field current If flowing in the field winding 16. Configured.

  The rotating electrical machine 10D is a modification of the rotating electrical machine 10B shown in FIG. The rotating electrical machine 10D differs from the rotating electrical machine 10A in the number of slots SL and the number of magnets 13b. That is, in the rotating electrical machine 10A, the number of slots SL is “6”, and the number of magnets 13b is “2”. On the other hand, in the rotating electrical machine 10D, the number of slots SL is “12”, and the number of magnets 13b is “7”.

  The arrangement of the winding sets is the same as that of the first embodiment although the number of slots SL is different. Therefore, the rotating electrical machine 10D can obtain characteristics such as the characteristic lines L2 and L4 shown in FIG. 9 and FIG. Further, since the magnetic fluxes ψa and ψb (particularly harmonic magnetic flux) generated in the field pole cores 11 and 15 are canceled and become smaller (or eliminated), generation of iron loss in the field pole cores 11 and 15 can be suppressed. In addition, the short coefficient can be increased with this configuration. A first winding (U-phase winding Ua, V-phase winding Va, W-phase winding Wa) and a second winding (U-phase winding Ub, V-phase winding Vb, In the W-phase winding Wb), the coil pitch becomes an electrical angle θ (for example, 120 degrees ≦ θ ≦ 240 degrees) in accordance with the number of slots SL and the number of magnets 13b, so that the short-node coefficient becomes high. Furthermore, by arranging the stator windings 14b so as to be adjacent to each other, the connecting wire connecting the first winding and the second winding can be shortened.

  Although not shown, in the same manner as in the second embodiment, the first winding (U-phase winding Ua, V-phase winding Va, W-phase winding Wa) and the second winding (U-phase winding Ub, The V-phase winding Vb and the W-phase winding Wb) may be wound apart in the circumferential direction. The developed view in the circumferential direction is the same as FIG. Therefore, the rotating electrical machine 10D can also have characteristics such as the characteristic lines L2 and L4 shown in FIG. 9 and FIG.

[Embodiment 5]
Embodiment 5 will be described with reference to FIG. For simplicity of illustration and description, unless otherwise specified, the same elements as those used in the first to fourth embodiments are denoted by the same reference numerals and description thereof is omitted. Therefore, the points different from the first to fourth embodiments will be mainly described.

  A rotating electrical machine 10E shown in FIG. 15 is an example of the rotating electrical machine 10, and the magnetic flux density between the rotor 13 and the stator 14 can be varied by controlling the field current If flowing in the field winding 16. Configured.

  The rotating electrical machine 10E is a modification of the rotating electrical machine 10A shown in FIG. The rotating electrical machine 10E is different from the rotating electrical machine 10A in the number of magnets 13b. That is, the rotating electrical machine 10A has “2” in the number of magnets 13b, whereas the rotating electrical machine 10E has “1” in the number of magnets 13b.

  The arrangement of the winding set is the same as in the first embodiment, and the first winding (U-phase winding Ua, V-phase winding Va, W-phase winding Wa) and the second winding (U-phase winding Ub). , V-phase winding Vb, W-phase winding Wb) are wound adjacent to each other in the circumferential direction. The developed view in the circumferential direction in this case is the same as FIG. Although not shown, the first winding and the second winding may be wound apart in the circumferential direction as in the second embodiment. The developed view in the circumferential direction in this case is the same as FIG. In any case, the rotating electrical machine 10E can obtain characteristics such as characteristic lines L2 and L4 shown in FIGS. Therefore, the generation of sound can be suppressed.

[Other Embodiments]
In the above, although the form for implementing this invention was demonstrated according to Embodiment 1-5, this invention is not limited to the said form at all. In other words, various forms can be implemented without departing from the scope of the present invention. For example, the following forms may be realized.

  In the first to fifth embodiments described above, the stator winding 14b is wound around the stator core 14a by concentrated winding (see FIGS. 3, 11, 13, 14, and 15). Instead of this configuration, as shown in FIG. 16, the stator winding 14b may be wound around the stator core 14a by distributed winding. A rotary electric machine 10F shown in FIG. 16 is an example of the rotary electric machine 10, U-phase windings Ua and Ub are shown by solid lines, V-phase windings Va and Vb are shown by two-dot chain lines, and W-phase windings Wa and Wb are shown. Shown with a dashed line. The first winding (U-phase winding Ua, V-phase winding Va, W-phase winding Wa) and the second winding (U-phase winding Ub, V-phase winding Vb, W-phase winding Wb) are: Wrap in the opposite direction to the circumferential direction. Since only the winding of the stator winding 14b around the stator core 14a is different, the same effect as in the first to fifth embodiments can be obtained.

  In the first to fifth embodiments described above, the rotor 13 is configured to have one or more magnets 13b (see FIGS. 2, 3, 5, 6, 11, and 13 to 15). Instead of this form, the rotor 13 may have an arbitrary configuration. Regardless of the number or arrangement of the magnets 13b provided in the rotor 13, the rotor 13 without the magnet 13b may be used. That is, a rotation in which a magnetic circuit including one or both of the field pole core 11 and the field pole core 15 and a combination of the first winding and the second winding and having the coil end portion CE as a magnetomotive force is formed. It can be applied to the electric machine 10. Since the stator 14 has a first winding and a second winding in which currents flow in opposite directions, the same effect as in the first to fifth embodiments can be obtained.

  In the first to fifth embodiments described above, the first winding (U-phase winding Ua, V-phase winding Va, W-phase winding Wa) and the second winding (U-phase winding) whose current directions are opposite to each other. Ub, V-phase winding Vb, and W-phase winding Wb) are provided in the stator 14 (see FIGS. 3, 4, 11, 12, and 13 to 15). Instead of this configuration, the stator 14 may be provided with other windings corresponding to the stator winding 14b together with the first winding and the second winding. Other windings are the same as the first winding and the second winding, for example, the third winding (U-phase winding Uc, V-phase winding Vc, W-phase winding Wc) or the third winding. The fourth winding (U-phase winding Ud, V-phase winding Vd, W-phase winding Wd) and the like correspond to the wires (not shown). The third winding and the fourth winding correspond to a “winding set” and may be arranged so that the current direction is reversed in the coil end portion CE or the like. Regarding the other windings, regardless of the number, regardless of winding (concentrated winding, distributed winding, etc.), it does not matter whether they are a winding group or not. Since only the configuration of the stator winding 14b is different, the same effects as those of the first to fifth embodiments can be obtained.

  In the first to fifth embodiments described above, the stator winding 14b is configured by three-phase windings, that is, U-phase windings Ua and Ub, V-phase windings Va and Vb, and W-phase windings Wa and Wb ( (See FIGS. 3, 4 and 11-15). Instead of this form, the stator winding 14b may be formed of four or more phase windings. Since only the number of phases of the stator winding 14b is different, the same effect as the first to fifth embodiments can be obtained.

  In the first to fifth embodiments described above, the first winding (U-phase winding Ua, V-phase winding Va, W-phase) that constitutes a winding set for all of the multi-phase (three-phase) stator windings 14b. Winding Wa) and the second winding (U-phase winding Ub, V-phase winding Vb, W-phase winding Wb) are included (see FIGS. 3, 4, and 11 to 15). Instead of this form, it is good also as a structure containing a 1st coil | winding and a 2nd coil | winding about one or more phases except all among the multiphase stator windings 14b. For example, the stator winding 14b includes a winding set of a U-phase winding Ua as a first winding and a U-phase winding Ub as a second winding. Although all the polyphase stator windings 14b are inferior to the configuration including the winding set, the operational effects shown in the first to fifth embodiments can be obtained as compared with the conventional ones.

  In the first and second embodiments described above, the stator 14 is configured with the number of slots SL being “6” and the number of magnets 13b being “2” (see FIGS. 3 and 11). In the third and fourth embodiments, the number of slots SL is set to “12” and the number of magnets 13b is set to “5” to configure the stator 14 (see FIGS. 13 and 14). In the fifth embodiment, the number of slots SL is set to “6” and the number of magnets 13b is set to “1” to configure the stator 14 (see FIG. 15). Instead of these forms, the number of slots SL and the number of magnets 13b may be set by other numbers. An appropriate number may be set in accordance with the rating and purpose of use of the rotating electrical machine 10 (such as emphasis on torque and rotation speed). Since only the number of slots SL and magnets 13b is different, the same effect as in the first to fifth embodiments can be obtained.

  In Embodiments 1 to 5 described above, the rotating electrical machine 10 (10A to 10E) is configured as an inner rotor type (see FIGS. 1 to 3, 5, 6, 11, and 13 to 15). Instead of this form, the rotating electrical machine 10 may be configured as an outer rotor type. Since only the arrangement of the rotor 13 and the stator 14 is different, the same effect as the first to fifth embodiments can be obtained.

  In the above-described first to fifth embodiments, the field pole core 11 and the field winding 16 and both the field pole core 15 and the field winding 17 are configured (FIGS. 1, 2, and 4 to 4). 6, see FIG. Instead of this form, any one of the field pole core 11 and the field winding 16 and the field pole core 15 and the field winding 17 may be provided with any one of the field pole core and the field winding. Good. Even in this configuration, the magnetic flux ψa and the magnetic flux ψb generated in the field pole core can be canceled each other, so that the same effect as in the first to fifth embodiments can be obtained.

[Function and effect]
According to the first to fifth embodiments and other embodiments described above, the following effects can be obtained.

  (1) In the rotating electrical machine 10, the stator winding 14 b of one or more phases among the multiple phases is a first in which a current flows in a predetermined direction so as to cancel the magnetic fluxes ψa and ψb generated in the field pole cores 11 and 15. Winding (U-phase winding Ua, V-phase winding Va, W-phase winding Wa) and second winding (U-phase winding Ub, V-phase winding) in which current flows in the opposite direction to the first winding Vb, W-phase winding Wb) is included (see FIGS. 1 to 15). According to this configuration, the stator winding 14b of one or more phases among the multiple phases has a winding set including the first winding and the second winding in which the directions of current flow are opposite to each other. Since the magnetic fluxes ψa and ψb generated by the current flowing in the first winding and the second winding are in opposite directions, the magnetic fluxes ψa and ψb (particularly, the magnetic fluxes ψa and ψb generated in the field pole cores 11 and 15 by the current flowing in the stator winding 14b). Harmonic magnetic flux) is canceled. Therefore, since the magnetic fluxes ψa and ψb generated in the field pole cores 11 and 15 are reduced (or eliminated), the occurrence of iron loss can be suppressed.

  Since the magnetic flux passing through the field pole cores 11 and 15 is linked to the field windings 16 and 17, a magnetic flux change such as a harmonic magnetic flux becomes a disturbance when a current is applied to the field windings 16 and 17. Due to this disturbance, a problem arises in the control, for example, the command current cannot be flowed or the current controllability is deteriorated. However, since the present invention includes a winding set composed of the first winding and the second winding in which the directions of current flow are opposite to each other, the harmonic magnetic flux is canceled and the problem is solved.

  (2) The direction of the current flowing through the coil end portion CE protruding from the stator core 14a of the first winding and the second winding is opposite (see FIGS. 4 and 12). According to this configuration, since the coil end portion CE includes the first winding and the second winding in the stator winding 14b that is a generation source of the magnetic fluxes ψa and ψb generated in the field pole cores 11 and 15, the magnetic flux ψa , Ψb (particularly harmonic flux) is more reliably canceled. Therefore, since the magnetic fluxes ψa and ψb are further reduced (or eliminated), the occurrence of iron loss can be further suppressed.

  (3) All the multiphase stator windings 14b have a winding set (see FIGS. 4 and 12). According to this configuration, since all of the multiphase stator windings 14b have the winding sets, the magnetic fluxes ψa and ψb (particularly harmonic magnetic fluxes) are more reliably canceled. Therefore, since the magnetic fluxes ψa and ψb are further reduced (or eliminated), the occurrence of iron loss can be further suppressed.

  (4) The in-phase stator winding 14b having the winding set is configured to be wound around the stator core 14a so as to be adjacent in the circumferential direction (see FIGS. 3, 4, and 13 to 15). According to this configuration, the combined winding included in the stator winding 14b having the same phase, that is, the first winding and the second winding are wound around the stator core 14a so as to be adjacent in the circumferential direction. Since magnetic fluxes ψa and ψb (particularly harmonic magnetic flux) generated by the current flowing through the first winding and the second winding are canceled and reduced (or eliminated), iron loss occurs in the field pole cores 11 and 15. Can be suppressed. In addition, the short coefficient can be increased with this configuration.

  (5) The in-phase stator winding 14b having a winding set is configured to be wound around the stator core 14a so as to be separated in the circumferential direction (see FIGS. 11 and 12). According to this configuration, the set windings included in the stator winding 14b having the same phase, that is, the first winding and the second winding are wound around the stator core 14a while being separated in the circumferential direction. Since the first winding and the second winding are separated from each other, the radial force generated by the magnetic flux linked to the magnetic pole teeth TE (teeth) is dispersed, so the vibration of the stator 14 is reduced and the generation of noise is suppressed. it can.

  (6) The in-phase stator winding 14b having the winding set is configured to be wound around the stator core 14a with a coil pitch of 120 degrees or more of the electrical angle θ in the circumferential direction (FIGS. 3, 13, and 14). See). According to this configuration, it is possible to increase the short clause coefficient more reliably.

10 (10A to 10E) Rotating electric machine 11, 15 Field pole core 13 Rotor (rotor)
14 Stator
14a Stator core (stator core)
14b Stator winding (stator winding)
16, 17 Field winding ψa, ψb Magnetic flux G Gap Ua, Va, Wa First winding (stator winding)
Ub, Vb, Wb Second winding (stator winding)

Claims (6)

A stator (14) including a stator core (14a) and a multiphase stator winding (14b) wound around the stator core;
A rotor (13) rotatably provided through the stator core and a gap (G);
Field pole cores (11, 15) provided to sandwich the stator core in the axial direction;
Field windings (16, 17) wound around the field pole core;
In a rotating electrical machine (10) in which a magnetic circuit (MC1a, MC1b, MC2a, MC2b) is formed by magnetic flux (ψa, ψb) flowing through the stator, the rotor, and the field pole core,
The stator winding of one or more phases among the multiphases, the first winding (Ua, Va, Wa) through which a current flows in a predetermined direction so as to cancel the magnetic flux generated in the field pole core, A rotating electrical machine having a winding set including a second winding (Ub, Vb, Wb) through which a current flows in a direction opposite to that of the first winding.   2. The rotating electrical machine according to claim 1, wherein a direction of a current flowing through a coil end portion (CE) protruding from the stator core of the first winding and the second winding is opposite.   3. The rotating electrical machine according to claim 1, wherein all the stator windings of the multiphase have the winding set.   4. The rotating electrical machine according to claim 1, wherein the same-phase stator windings having the winding sets are wound around the stator core so as to be adjacent to each other in the circumferential direction.   4. The rotating electrical machine according to claim 1, wherein the same-phase stator windings having the winding set are wound around the stator core so as to be spaced apart from each other in a circumferential direction.   5. The rotating electrical machine according to claim 4, wherein the stator winding of the same phase having the winding set is wound around the stator core with a coil pitch of 120 degrees or more in the circumferential direction.

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