JP2012060714A - Integrated circuit - Google Patents

Integrated circuit Download PDF

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JP2012060714A
JP2012060714A JP2010199182A JP2010199182A JP2012060714A JP 2012060714 A JP2012060714 A JP 2012060714A JP 2010199182 A JP2010199182 A JP 2010199182A JP 2010199182 A JP2010199182 A JP 2010199182A JP 2012060714 A JP2012060714 A JP 2012060714A
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Prior art keywords
overcurrent
circuit
switching element
voltage
terminal
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JP2010199182A
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Japanese (ja)
Inventor
Kazuyoshi Ishikawa
Masahiro Maruki
雅大 丸木
和義 石川
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On Semiconductor Trading Ltd
オンセミコンダクター・トレーディング・リミテッド
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Abstract

PROBLEM TO BE SOLVED: To adjust the balance between responsiveness and prevention of overheating of an element due to a load short circuit or the like.
A terminal connected to a predetermined potential directly or via an externally connected resistor or first capacitor, an overcurrent determination circuit for determining whether or not an overcurrent state is present, and an overcurrent determination When it is determined that the circuit is in an overcurrent state, the output voltage of the switching element is rectified if the current supply circuit that supplies a predetermined current to the terminal and the overcurrent determination circuit does not determine that the circuit is in an overcurrent state When the switching element is subjected to switching control according to the pulse width modulation signal having a duty ratio corresponding to the smoothed second DC voltage, and the overcurrent determination circuit determines that the overcurrent state is present, the terminal voltage is A switching control circuit that turns off the switching element until a predetermined reference voltage is reached, and is connected to a predetermined potential directly or through a resistor and supplied with a predetermined current. The voltage at the terminal is less than a predetermined reference voltage.
[Selection] Figure 1

Description

  The present invention relates to integrated circuits.

  For example, a switching power supply circuit as shown in FIG. 9 of Patent Document 1 prevents an overcurrent exceeding a predetermined value from flowing in a switching element when a load is short-circuited, and prevents the switching element and other elements from being damaged. Current protection function is generally provided. For example, the overcurrent protection circuit shown in FIG. 10 of Patent Document 1 operates to control the switching element to be turned off when the current value flowing through the switching element reaches a predetermined current value.

  In addition, since the above overcurrent protection circuit has a disadvantage that current superimposition occurs, in Patent Document 1, the inconvenience is solved without a long start-up time or a slow response to a sudden load change. A method is disclosed. In the overcurrent protection circuit shown in FIG. 2 and FIG. 5 of Patent Document 1, during the overcurrent protection operation, until the flywheel current flowing through the diode and the lowside switching element becomes substantially zero, Control to turn on is performed.

  Thus, when the value of the current flowing through the switching element is monitored and an overcurrent is detected, the switching element is turned off each time, so that the on-time can be relatively shortened and the element can be prevented from being damaged.

JP 2004-364488 A

  However, in the overcurrent protection method as described above, even when the load short-circuit continues, the switching element is turned on again in a relatively short time as in the case where the current temporarily increases. Therefore, when the load is continuously short-circuited, an overcurrent flows each time the switching element is turned on, and the switching element and the coil (inductor) may not be able to sufficiently dissipate heat.

  On the other hand, in an overcurrent protection method called a latch-off method or the like, damage to the element can be prevented by continuing to turn off the switching element when an overcurrent is detected for a predetermined time or longer. However, in the latch-off method, since the switching element continues to be turned off until reset by a reset signal or the like, the response of the switching power supply circuit is degraded.

  When the switching power supply circuit is configured as an integrated circuit, it is common to have an overheat protection function that turns off the switching element until the integrated circuit is sufficiently heated when it is overheated. However, even in this case, since the coil is usually an external part, the coil may overheat and burn out.

The main present invention for solving the above-described problems is that a terminal connected to a predetermined potential directly or via an externally connected resistor or first capacitor and a switching element for switching the first DC voltage are more than predetermined. An overcurrent determination circuit that determines whether or not an overcurrent state flows, and a current supply that supplies a predetermined current to the terminal when the overcurrent determination circuit determines that the overcurrent state is present When the circuit and the overcurrent determination circuit do not determine that the overcurrent state is present, the output voltage of the switching element is converted into a pulse width modulation signal having a duty ratio corresponding to the second DC voltage rectified and smoothed. In response to the switching control of the switching element, when the overcurrent determination circuit determines that the overcurrent state is present, the voltage at the terminal reaches a predetermined reference voltage. And a switching control circuit that turns off the switching element until the first voltage is connected to the predetermined potential directly or via the resistor, and the voltage of the terminal when the predetermined current is supplied is An integrated circuit having a voltage lower than the predetermined reference voltage.
Other features of the present invention will become apparent from the accompanying drawings and the description of this specification.

  According to the present invention, it is possible to adjust the balance between the response of the switching power supply circuit and the prevention of overheating of the element due to a load short circuit or the like.

In one Embodiment of this invention, it is a circuit block diagram which shows the structure of the whole switching power supply circuit at the time of connecting the capacitor | condenser C1 externally to the terminal 32 of the integrated circuit 1a. In one Embodiment of this invention, it is a circuit block diagram which shows the structure of the whole switching power supply circuit at the time of connecting resistance R1 to the terminal 32 of the integrated circuit 1a externally. It is a figure explaining operation | movement of the switching power supply circuit in one Embodiment of this invention. It is a circuit block diagram which shows the other structural example of a switching power supply circuit. FIG. 6 is a circuit block diagram showing a configuration example of an integrated circuit that keeps switching element 2 turned off when it is determined a predetermined number of times as being in an overcurrent state. 3 is a circuit block diagram showing a configuration example of an integrated circuit including a capacitor C2 internally connected to a terminal 32. FIG.

  At least the following matters will become apparent from the description of this specification and the accompanying drawings.

=== Configuration of Entire Switching Power Supply Circuit ===
Hereinafter, the configuration of the entire switching power supply circuit according to the embodiment of the present invention will be described with reference to FIGS.

  The switching power supply circuit shown in FIGS. 1 and 2 includes an integrated circuit 1a, a switching element 2, a diode 3, a coil 4, a capacitor 5, and resistors 6 and 7, and is externally connected to the integrated circuit 1a. The capacitor C1 or the resistor R1 is included. In the following, a case where the switching element 2 is an NMOS (N-channel Metal-Oxide Semiconductor) transistor will be described as an example. 1 and 2 show a case where a capacitor C1 and a resistor R1 are externally connected to the integrated circuit 1a, respectively.

  The integrated circuit 1a includes a voltage adjustment circuit 11, a switching control circuit 12, a current source 21, switch circuits 22, 28, a current detection circuit 23, an overcurrent detection circuit 24, an overcurrent determination circuit 25, a comparator (comparator) 26, and An inverter (inverting circuit) 27 is included. Further, the integrated circuit 1 a includes terminals 31 to 34.

  An input voltage Vin (first DC voltage) is input to the voltage adjustment circuit 11 via a terminal 31. Further, the voltage adjustment circuit 11 outputs a constant voltage Vreg and a reference voltage Vref. The constant voltage Vreg is supplied to the switching control circuit 12 and the current source 21, and the reference voltage Vref is supplied to the comparator 26.

  A current I5 (predetermined current) is output from the current source 21. The terminal 32 is externally connected to a capacitor C1 (first capacitor) or a resistor R1 having one end connected to the ground potential (predetermined potential). Then, the current I5 is supplied to the terminal 32 via the switch circuit 22. In the present embodiment, the current source 21 and the switch circuit 22 correspond to a current supply circuit.

  The detection current I4 is input from the current detection circuit 23 to the overcurrent detection circuit 24. The overcurrent detection signal DT output from the overcurrent detection circuit 24 is input to the switching control circuit 12 and the overcurrent determination circuit 25. The overcurrent determination signal OC output from the overcurrent determination circuit 25 is input to the switching control circuit 12 and the inverter 27 and is a control signal for the switch circuit 22.

  The reference voltage Vref is applied to the inverting input of the comparator 26, and the non-inverting input is connected to the terminal 32. The restart signal RST output from the comparator 26 is input to the switching control circuit 12 and the overcurrent determination circuit 25.

  One end of the switch circuit 28 is connected to the terminal 32, and the other end is connected to the ground potential. The output signal of the inverter 27 (inverted signal of the overcurrent determination signal OC) is a control signal for the switch circuit 28.

  A switching signal SW1 is output from the switching control circuit 12. Further, the input voltage Vin is input to the drain of the switching element 2, and the switching signal SW <b> 1 is input to the gate via the terminal 33. Furthermore, the anode of the diode 3 is connected to the ground potential, and the cathode is connected to the source of the switching element 2.

  One end of the coil 4 is connected to a connection point between the switching element 2 and the diode 3, and the other end is connected to one end of the capacitor 5. The other end of the capacitor 5 is connected to the ground potential. A connection point between the coil 4 and the capacitor 5 is an output node of the switching power supply circuit that outputs the output voltage Vout (second DC voltage).

  The resistors 6 and 7 are connected in series, one end of the resistor 6 is connected to the output node, and one end of the resistor 7 is connected to the ground potential. The connection point of the resistors 6 and 7 is connected to the terminal 34, and the voltage at the connection point is input to the switching control circuit 12 as the feedback voltage Vfb.

=== Operation of Switching Power Supply Circuit ===
The operation of the switching power supply circuit according to this embodiment will be described below with reference to FIG.

First, the operation when the capacitor C1 is externally connected to the terminal 32 of the integrated circuit 1a as shown in FIG. 1 will be described.
The voltage adjustment circuit 11 of the integrated circuit 1a generates a constant voltage Vreg from the input voltage Vin and supplies it to the switching control circuit 12 and the current source 21. The constant voltage Vreg is used not only as a power supply voltage in the switching control circuit 12, but also for generating a voltage (bootstrap voltage) for turning on the switching element 2. Further, the voltage adjustment circuit 11 generates a reference voltage Vref from the constant voltage Vreg and supplies it to the comparator 26.

  The switching element 2 switches the input voltage Vin according to the switching signal SW1 output from the switching control circuit 12, and converts it into an AC voltage. The diode 3, the coil 4, and the capacitor 5 constitute a rectifying and smoothing circuit, rectifying and smoothing the AC voltage, and outputting an output voltage Vout that is a DC voltage. The current I3 flowing through the coil 4 is the sum of the current I1 flowing while the switching element 2 is on and the current I2 flowing through the diode 3 while the switching element 2 is off.

  Resistors 6 and 7 divide output voltage Vout to generate feedback voltage Vfb. Further, the switching control circuit 12 generates a PWM (Pulse Width Modulation) signal whose duty ratio is controlled based on the feedback voltage Vfb so that the output voltage Vout becomes a desired target voltage. The PWM signal is used for switching control of the switching element 2 at a normal time (period A in FIG. 3) when the current value of the detection current I4 does not reach a reference current value Iref described later.

  Since the switching element 2 is an NMOS transistor, it is turned on while the switching signal SW1 is at a high level, and is turned off while the switching signal SW1 is at a low level. Therefore, when the output voltage Vout is lower than the target voltage, the PWM signal is at a high level, that is, the period during which the switching element 2 is turned on becomes longer, and the output voltage Vout increases. On the other hand, when the output voltage Vout is higher than the target voltage, the period during which the switching element 2 is turned on is shortened, and the output voltage Vout decreases.

  The current detection circuit 23 detects a current I1 flowing through the switching element 2 using a current detection resistor, a current mirror circuit, or the like, and outputs a detection current I4. The overcurrent detection circuit 24 detects that the current value of the detection current I4 has reached the reference current value Iref (predetermined current value) due to a load short circuit or the like, and outputs an overcurrent detection signal DT. For example, the overcurrent detection circuit 24 uses a comparator or the like to output an overcurrent detection signal DT that becomes low level when I4 <Iref and becomes high level when I4 ≧ Iref. The current detection circuit 23 and the overcurrent detection circuit 24 that output such an overcurrent detection signal DT may have the same configuration as that of FIG.

  The overcurrent detection signal DT is input to the switching control circuit 12, and the switching control circuit 12 outputs the switching signal SW1 every time the overcurrent detection signal DT becomes high level as shown in the period B of FIG. Low level. Further, when the switching signal SW1 becomes low level, the switching element 2 is turned off, and the current I1 does not flow through the switching element 2, so that the overcurrent detection signal DT becomes low level again. Therefore, the switching control circuit 12 turns off the switching element 2 in accordance with the pulse-shaped overcurrent detection signal DT, thereby overheating the element until the overcurrent determination circuit 25 determines that the overcurrent state is present. Is suppressed.

  Furthermore, the overcurrent detection signal DT is also input to the overcurrent determination circuit 25, and the overcurrent determination circuit 25 is in an overcurrent state in which a predetermined current or more flows through the switching element 2 based on the overcurrent detection signal DT. It is determined whether or not. For example, the overcurrent determination circuit 25 determines that the current is in an overcurrent state when a pulsed overcurrent detection signal DT is input a predetermined number of times (for example, 8 times) using a counter circuit or the like. The determination signal OC is set to high level. Note that the overcurrent determination circuit 25 may determine whether or not the overcurrent state is present using another method such as detecting a decrease in the feedback voltage Vfb due to a load short circuit. Moreover, you may use combining the said other method.

  The overcurrent determination signal OC is input to the switching control circuit 12, and the switching control circuit 12 sets the switching signal SW1 to the low level while the overcurrent determination signal OC is at the high level as shown in the period C in FIG.・ Hold at level. Therefore, the switching element 2 is not turned on, and the current I3 flowing through the coil 4 decreases to substantially zero.

Further, when the overcurrent determination signal OC becomes high level, the switch circuit 22 is turned on, the switch circuit 28 is turned off, and the current I5 is supplied from the current source 21 to the capacitor C1. Therefore, the capacitor C1 is charged by the current I5, and when the voltage V32 of the terminal 32 (the voltage across the capacitor C1) is differentiated with respect to time t,
dV32 / dt = I5 / C1
Therefore, the voltage V32 rises with a certain slope as shown in the period C of FIG.

  The comparator 26 compares the voltage V32 with the reference voltage Vref, and when the voltage V32 reaches the reference voltage Vref, the restart signal RST becomes a high level. Further, when the restart signal RST becomes high level, the overcurrent determination signal OC becomes low level again. Further, when the overcurrent determination signal OC becomes low level, the switch circuit 22 is turned off, the switch circuit 28 is turned on, the capacitor C1 is discharged, and the voltage V32 rapidly decreases as shown in the period D in FIG. Then, the restart signal RST becomes low level again. And the switching control circuit 12 starts switching control of the switching element 2 again according to a PWM signal.

  In this way, when the overcurrent determination signal OC becomes high level, the switching control of the switching element 2 is suspended until the voltage V32 reaches the reference voltage Vref. Here, the suspension period of the switching control (period C in FIG. 3) is determined according to the slope at which the voltage V32 rises to the reference voltage Vref, and therefore can be adjusted according to the capacitance of the externally connected capacitor C1.

On the other hand, as shown in FIG. 2, when the resistor R1 is externally connected to the terminal 32 of the integrated circuit 1a, the current I5 is supplied to the resistor R1 while the overcurrent determination signal OC is at the high level. The voltage V32 (the voltage across the resistor R1) is
V32 = I5 × R1
It becomes. Therefore, by setting the resistance value of the resistor R1 so that Vref> I5 × R1, the voltage V32 does not reach the reference voltage Vref, and the switching control circuit 12 starts switching control of the switching element 2 again. There is no.

  As described above, the switching power supply circuit according to the present embodiment selects the operation when it is determined that the overcurrent state is established depending on whether the capacitor C1 is externally connected to the terminal 32 of the integrated circuit 1a or the resistor R1 is externally connected. can do. That is, when the capacitor C1 is externally connected, the switching control of the switching element 2 is suspended only during a pause period determined according to the capacitance of the capacitor C1. Device 2 is kept off. Therefore, using the terminal 32 of the integrated circuit 1a, the balance between the response of the switching power supply circuit and the prevention of overheating of the element due to a load short circuit or the like can be adjusted.

=== Other Configuration Examples of Switching Power Supply Circuits ===
In the above embodiment, the switching power supply circuit includes only the high-side switching element 2 that is an NMOS transistor, but is not limited thereto. For example, as shown in FIG. 4, it is good also as a structure further provided with the switching element 8 of the low side. In this case, it is desirable to have a configuration that prevents both switching elements from being simultaneously turned on simultaneously. Further, when the high-side switching element is a PMOS (P-channel MOS: P-channel metal oxide semiconductor) transistor, a circuit for generating a bootstrap voltage is not required, and on-resistance is reduced. It is necessary to increase the size of the transistor.

=== Other Configuration Examples of Integrated Circuits ===
In the above embodiment, the switching control circuit 12 starts the switching control of the switching element 2 again when the voltage V32 reaches the reference voltage Vref after the overcurrent determination circuit 25 determines that the overcurrent state is present. However, the present invention is not limited to this. For example, when the overcurrent determination circuit 25 determines that the current is in an overcurrent state a predetermined number of times (for example, 16 times), the switching element 2 is kept off to further prevent overheating of the element during continuous load short-circuiting. Can do.

  Such an operation can be realized by providing a counter circuit that counts the number of times that the overcurrent determination signal OC has become high level. Further, for example, as shown in FIG. 5, it is also realized by a counter circuit 29 that counts the number of times that the voltage V32 reaches the reference voltage Vref, and holds the restart signal RST at a low level after counting the predetermined number of times. be able to.

  In the above embodiment, the operation when it is determined that the overcurrent state is determined by connecting the capacitor C1 or the resistor R1 to the terminal 32 of the integrated circuit 1a is selected. However, the present invention is not limited to this. . For example, when the switching element 2 is kept off by connecting a resistor between the current source 21 and the switch circuit 22 or between the switch circuit 22 and the terminal 32, the terminal 32 is directly connected to the ground potential (predetermined). The potential can be connected to the potential of the other.

  The integrated circuit may further include a capacitor C2 (second capacitor) internally connected to the terminal 32 as shown in FIG. In this case, the switching control of the switching element 2 can be paused for a pause period set in advance according to the capacitance of the capacitor C2 by connecting nothing to the terminal 32. Further, the external period of the switching control can be adjusted by externally connecting the capacitor C1 to the terminal 32.

  As described above, when it is determined that the switching power supply circuit shown in FIGS. 1 and 2 is in the overcurrent state, the current I5 is supplied to the terminal 32 of the integrated circuit 1a, and the voltage V32 of the terminal 32 is the reference voltage V32. When the capacitor C1 is externally connected to the terminal 32 by suspending the switching control of the switching element 2 until the voltage Vref is reached, the switching control of the switching element 2 is performed only during the quiescent period determined according to the capacitance of the capacitor C1. When the operation is stopped and the resistor R1 is externally connected, the switching element 2 can be kept off. Therefore, using the terminal 32 of the integrated circuit 1a, the balance between the response of the switching power supply circuit and the prevention of overheating of the element due to a load short circuit or the like can be adjusted.

  In addition, it is possible to reliably determine the occurrence of a continuous load short circuit, not a temporary current increase, by determining that the overcurrent state is detected when the overcurrent detection signal DT is input a predetermined number of times. it can.

  Further, when it is not determined that the current is in an overcurrent state, the switching element 2 is subjected to switching control according to the PWM signal, and the switching element 2 is turned off each time the pulsed overcurrent detection signal DT is input. The overheating of the element until it is determined that it is in an overcurrent state can be suppressed.

  Further, in the switching power supply circuit shown in FIG. 5, when the overcurrent state is determined a predetermined number of times, the switching element 2 is kept off to further prevent overheating of the element during continuous load short-circuiting. it can.

  Further, in the switching power supply circuit shown in FIG. 6, by further including a capacitor C2 internally connected to the terminal 32 of the integrated circuit 1d, when nothing is externally connected to the terminal 32, the capacitor C2 When the switching control of the switching element 2 is suspended for a preset idle period according to the capacity and the capacitor C1 is externally connected to the terminal 32, the idle period of the switching control can be adjusted.

  In addition, the said embodiment is for making an understanding of this invention easy, and is not for limiting and interpreting this invention. The present invention can be changed and improved without departing from the gist thereof, and the present invention includes equivalents thereof.

DESCRIPTION OF SYMBOLS 1a-1d Integrated circuit 2, 8 Switching element 3 Diode 4 Coil 5 Capacitor 6, 7 Resistance 11 Voltage adjustment circuit 12 Switching control circuit 21 Current source 22, 28 Switch circuit 23 Current detection circuit 24 Overcurrent detection circuit 25 Overcurrent determination circuit 26 Comparator
27 Inverter (inverting circuit)
29 Counter circuit 31-35 Terminal C1, C2 Capacitor R1 Resistance

Claims (5)

  1. A terminal connected to a predetermined potential directly or via an externally connected resistor or first capacitor;
    An overcurrent determination circuit that determines whether or not an overcurrent state in which a current greater than or equal to a predetermined value flows in the switching element that switches the first DC voltage;
    A current supply circuit for supplying a predetermined current to the terminal when the overcurrent determination circuit determines that the overcurrent state is present;
    If the overcurrent determination circuit does not determine that the overcurrent state is present, the output voltage of the switching element is rectified and smoothed according to a pulse width modulation signal having a duty ratio corresponding to a second DC voltage. A switching control circuit that controls switching of the switching element and turns off the switching element until the voltage at the terminal reaches a predetermined reference voltage when the overcurrent determination circuit determines that the overcurrent state is in the overcurrent state; ,
    Have
    An integrated circuit, wherein the voltage of the terminal when connected to the predetermined potential directly or through the resistor and supplied with the predetermined current is less than the predetermined reference voltage.
  2. An overcurrent detection circuit that detects that a current value flowing through the switching element has reached a predetermined current value and outputs an overcurrent detection signal;
    2. The integrated circuit according to claim 1, wherein the overcurrent determination circuit determines that the overcurrent state is present when the overcurrent detection signal is input a predetermined number of times.
  3.   When the overcurrent determination circuit does not determine that the overcurrent state is in the overcurrent state, the switching control circuit performs switching control of the switching element according to the pulse width modulation signal, and according to the overcurrent detection signal. The integrated circuit according to claim 2, wherein the switching element is turned off.
  4.   4. The switching control circuit according to claim 1, wherein when the overcurrent determination circuit determines that the overcurrent state is in the overcurrent state a predetermined number of times, the switching control circuit continues to turn off the switching element. An integrated circuit according to 1.
  5.   The integrated circuit according to claim 1, further comprising a second capacitor internally connected to the terminal.
JP2010199182A 2010-09-06 2010-09-06 Integrated circuit Pending JP2012060714A (en)

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Cited By (16)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JP2016512944A (en) * 2013-03-15 2016-05-09 エーエムピーティー, エルエルシー High efficiency interleaved solar power supply system
JP2016197994A (en) * 2016-08-18 2016-11-24 エーエムピーティー, エルエルシー High-efficiency interleaving solar power supply system
US10007288B2 (en) 2012-03-05 2018-06-26 Solaredge Technologies Ltd. Direct current link circuit
US10032939B2 (en) 2009-10-19 2018-07-24 Ampt, Llc DC power conversion circuit
US10097007B2 (en) 2006-12-06 2018-10-09 Solaredge Technologies Ltd. Method for distributed power harvesting using DC power sources
US10116140B2 (en) 2013-03-15 2018-10-30 Ampt, Llc Magnetically coupled solar power supply system
US10230245B2 (en) 2006-12-06 2019-03-12 Solaredge Technologies Ltd Battery power delivery module
US10230310B2 (en) 2016-04-05 2019-03-12 Solaredge Technologies Ltd Safety switch for photovoltaic systems
US10326282B2 (en) 2009-04-17 2019-06-18 Ampt, Llc Safety methods and apparatus for adaptive operation of solar power systems
US10326283B2 (en) 2007-10-15 2019-06-18 Ampt, Llc Converter intuitive photovoltaic electrical energy power system
US10381977B2 (en) 2012-01-30 2019-08-13 Solaredge Technologies Ltd Photovoltaic panel circuitry
US10396662B2 (en) 2011-09-12 2019-08-27 Solaredge Technologies Ltd Direct current link circuit
US10447150B2 (en) 2006-12-06 2019-10-15 Solaredge Technologies Ltd. Distributed power harvesting systems using DC power sources
US10461687B2 (en) 2008-12-04 2019-10-29 Solaredge Technologies Ltd. Testing of a photovoltaic panel
US10468878B2 (en) 2008-05-05 2019-11-05 Solaredge Technologies Ltd. Direct current power combiner
US10516336B2 (en) 2007-08-06 2019-12-24 Solaredge Technologies Ltd. Digital average input current control in power converter

Cited By (16)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US10230245B2 (en) 2006-12-06 2019-03-12 Solaredge Technologies Ltd Battery power delivery module
US10447150B2 (en) 2006-12-06 2019-10-15 Solaredge Technologies Ltd. Distributed power harvesting systems using DC power sources
US10097007B2 (en) 2006-12-06 2018-10-09 Solaredge Technologies Ltd. Method for distributed power harvesting using DC power sources
US10516336B2 (en) 2007-08-06 2019-12-24 Solaredge Technologies Ltd. Digital average input current control in power converter
US10326283B2 (en) 2007-10-15 2019-06-18 Ampt, Llc Converter intuitive photovoltaic electrical energy power system
US10468878B2 (en) 2008-05-05 2019-11-05 Solaredge Technologies Ltd. Direct current power combiner
US10461687B2 (en) 2008-12-04 2019-10-29 Solaredge Technologies Ltd. Testing of a photovoltaic panel
US10326282B2 (en) 2009-04-17 2019-06-18 Ampt, Llc Safety methods and apparatus for adaptive operation of solar power systems
US10032939B2 (en) 2009-10-19 2018-07-24 Ampt, Llc DC power conversion circuit
US10396662B2 (en) 2011-09-12 2019-08-27 Solaredge Technologies Ltd Direct current link circuit
US10381977B2 (en) 2012-01-30 2019-08-13 Solaredge Technologies Ltd Photovoltaic panel circuitry
US10007288B2 (en) 2012-03-05 2018-06-26 Solaredge Technologies Ltd. Direct current link circuit
US10116140B2 (en) 2013-03-15 2018-10-30 Ampt, Llc Magnetically coupled solar power supply system
JP2016512944A (en) * 2013-03-15 2016-05-09 エーエムピーティー, エルエルシー High efficiency interleaved solar power supply system
US10230310B2 (en) 2016-04-05 2019-03-12 Solaredge Technologies Ltd Safety switch for photovoltaic systems
JP2016197994A (en) * 2016-08-18 2016-11-24 エーエムピーティー, エルエルシー High-efficiency interleaving solar power supply system

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