JP2003284349A - Power unit - Google Patents

Abstract

<P>PROBLEM TO BE SOLVED: To provide a small and efficient power unit which suppresses an interference between an input and an output. <P>SOLUTION: The power unit has a conversion means which has a smoothing capacitor C1 and generates a DC voltage at a desired level between both ends of the smoothing capacitor C1 by switching an input current from a commercial power AC with a high frequency, a current limiting means which limits a supply current to a load circuit LD, and a control circuit 1 which turns on or off switching elements Q1-Q4 constituting the conversion means and the current limiting means, and an inductor L1 serves as an inductor of the conversion means and that of the current limiting means. The control circuit 1 controls the ON and OFF of the switching elements Q1-Q4 so as to provide a period for forming a current loop including at least the inductor L1 and the smoothing capacitor C1 and not including the commercial power source AC and the load circuit LD, and a period for forming a current loop including at least the inductor L1, the commercial power source AC, and the load circuit LD. <P>COPYRIGHT: (C)2004,JPO

Description

Detailed Description of the Invention

[0001]

BACKGROUND OF THE INVENTION 1. Field of the Invention The present invention relates to a power supply device.

[0002]

2. Description of the Related Art A circuit diagram of a conventional power supply device is shown in FIG. This power supply device has a rectifier circuit DB such as a diode bridge for full-wave rectifying the AC voltage of the commercial power supply AC, and an inductor L1 is provided between the DC output terminals of the rectifier circuit DB.
1, a diode D11, a switching element Q12, an inductor L12, and a load circuit LD are connected in series, and an inductor L11 and a diode D1 are connected.
A switching element Q11 is connected between the connection point of 1 and the low-voltage side output terminal of the rectifier circuit DB, and a smoothing capacitor is provided between the connection point of the diode D11 and the switching element Q12 and the low-voltage side output terminal of the rectifier circuit DB. C11 is connected to the switching element Q12 and inductor L1.
A diode D12 is connected between the connection point 2 and the low-voltage side output terminal of the rectifier circuit DB.

Here, the inductor L11, the switching element Q11, and the diode D11 constitute a boost converter, and the inductor L12 and the switching element Q12.
The diode D12 constitutes a buck converter, and the switching elements Q11 and Q12 are switched by the control signals a and b input from the control circuit 1 at a frequency sufficiently higher than the power supply frequency.

FIG. 35 shows switching elements Q11 and Q12.
Control signals a and b, and inductors L11 and L1
2 is a waveform diagram of choke currents IL11 and IL12 flowing in No. 2, and the switching elements Q11 and Q12 are turned on when the signal levels of the control signals a and b become H level.
In this circuit, a period in which both the switching elements Q11 and Q12 are turned on and a period in which both of them are turned off are alternately provided.

During a period in which both switching elements Q11 and Q12 are turned on, as shown in FIG. 36 (a), commercial power supply AC → rectifier circuit DB → inductor L11 → switching element Q11 → rectifier circuit DB → commercial power supply AC As the choke current IL11 flows, the smoothing capacitor C
11 as a power source, smoothing capacitor C11 → inductor L
12 → load circuit LD → smoothing capacitor C11 causes choke current IL12 to flow, and inductors L11 and L12
Energy is stored in the load circuit LD and energy is supplied to the load circuit LD.

Further, in a period in which both the switching elements Q11 and Q12 are turned off, energy accumulated in the inductors L11 and L12 is released during the on period, as shown in FIG. 36 (b), and the inductor L11 → diode D11 →
Smoothing capacitor C11 → rectifier circuit DB → commercial power supply AC →
The choke current IL11 flows through the path of the rectifier circuit DB → the inductor L11 to charge the smoothing capacitor C11, and the choke current IL1 flows through the path of the inductor L12 → the load circuit LD → the diode D12 → the inductor L12.
2 flows and energy is supplied to the load circuit LD.

As described above, in the boost converter, the switching element Q11 is repeatedly turned on and off,
The smoothing capacitor C11 is charged while suppressing the input current distortion, and in the buck converter, the switching element Q12 is repeatedly turned on and off to supply a desired current to the load circuit LD using the smoothing capacitor C11 as a power source.

By the way, in this power supply device, since the boost converter having the harmonic distortion improving function and the buck converter having the current limiting function are connected in series to perform the two-stage power conversion, the circuit efficiency is lowered. Moreover, since the inductor L21 of the boost converter and the inductor L22 of the buck converter are separately provided and two inductors which are relatively large parts are provided, there is a problem that the power supply device becomes large.

Therefore, as shown in FIG. 37, there has conventionally been proposed a power supply device in which a boost converter and a buck converter share an inductor to simplify the circuit configuration. This power supply device has a rectifier circuit DB such as a diode bridge for full-wave rectifying the AC voltage of the commercial power supply AC, and a switching element Q21, an inductor L21, a diode D22 and a smoothing capacitor C21 are provided between the DC output terminals of the rectifier circuit DB. And connecting a switching element Q22 between the connection point of the switching element Q21 and the inductor L21 and the connection point of the diode D22 and the smoothing capacitor C21, and rectifying the connection point of the switching element Q21 and the inductor L21. A diode D21 is provided between the low-voltage side output terminal of the circuit DB and
, Inductor L21 and diode D2
A series circuit of a switching element Q24 and a load circuit LD and a switching element Q23 are connected between the connection point of 2 and the low-voltage side output terminal of the rectifier circuit DB.

Here, the switching elements Q21 to Q24
Is a transistor, for example, whose on / off is controlled by control signals a to d input from the control circuit 1.
FIG. 38 shows the choke current IL2 flowing through the inductor L21.
1 and a waveform diagram of control signals a to d for controlling on / off of the switching elements Q21 to Q24, in which the switching elements Q21 and Q23 are turned on and the switching element Q2 is turned on.
2, a period T1 in which Q24 is off, a period T2 in which the switching element Q21 is on and the switching elements Q22 to Q24 are off, and a period T3 in which the switching elements Q21 and Q23 are off and the switching elements Q22 and Q24 are on. The period T4 in which the switching element Q24 is turned on and the switching elements Q21 to Q23 are turned off is sequentially repeated.

First, in the period T1, the switching elements Q21 and Q23 are turned on, and the switching elements Q22 and Q2.
When 4 is turned off, as shown in FIG. 39 (a), commercial power supply AC → rectifier circuit DB → switching element Q21 → inductor L21 → switching element Q23 → rectifier circuit DB.
→ The input current is drawn in the path of the commercial power supply AC, the choke current IL21 flows, and energy is stored in the inductor L21.

After that, when the switching element Q21 is turned on and the switching elements Q22 to Q24 are turned off in the period T2, the energy accumulated in the inductor L21 is released in the period T1 and, as shown in FIG. 39 (b), the inductor L21. → diode D22 → smoothing capacitor C21 → rectifier circuit DB → commercial power supply AC → rectifier circuit D
The choke current IL21 flows through the path of B → switching element Q21 → inductor L21, and smoothing capacitor C2
1 is charged.

Next, in the period T3, the switching elements Q22 and Q24 are turned on, and the switching elements Q21 and Q2.
When 3 is turned off, the smoothing capacitor C21 is used as a power source and the smoothing capacitor C21 →
Switching element Q22 → inductor L21 → switching element Q24 → load circuit LD → smoothing capacitor C21
A current flows through the path of, the load current is supplied to the load circuit LD, and energy is stored in the inductor L21.

When the switching element Q24 is turned on and the switching elements Q21 to Q23 are turned off in the period T4, as shown in FIG. 39 (d), the energy accumulated in the inductor L21 is released in the period T3 and the inductor L21 is released. → Current flows through the path of switching element Q24 → load circuit LD → diode D21 → inductor L21, and the load current is supplied to the load circuit LD.

The control circuit 1 controls on / off of the switching elements Q21 to Q24 so that the repetition frequency of the periods T1 to T4 becomes sufficiently higher than the power supply frequency, and the power supply shown in FIG. 34 described above. Like the device,
While suppressing the input current distortion, the smoothing capacitor C21 is charged, and the smoothing capacitor C21 is used as a power source for the load circuit L.
A desired current can be supplied to D.

[0016]

In the above-mentioned two types of power supply devices, all the energy input from the power supply is stored in the smoothing capacitors C11 and C21 via the boost converter, and then the smoothing capacitors C11 and C21 are supplied to the power supplies. Since the buck converter supplies energy to the load circuit LD and each of the boost converter and the buck converter performs power conversion corresponding to the input / output power, the actual output power of the boost converter and the buck converter is reduced. This means that power conversion of about twice the power is being performed by both. Generally, the circuit loss generated by power conversion increases as the power to be converted increases. Therefore, by performing the power conversion operation twice in the conventional power supply device, the circuit loss increases and the circuit efficiency decreases. result,
There is a problem in that a large-sized element having a large rated value must be used, and the power supply device becomes large.

Further, in the latter power supply device described above, the inductor of the boost converter and the inductor of the buck converter are integrated into one inductor L in order to reduce the number of parts.
In such a dual-purpose converter, the behavior of each converter may affect the behavior of the other converter, and the output current fluctuates due to an instantaneous fluctuation of the input voltage, There is a problem that interference between input and output occurs, such as an increase in input current distortion due to a sudden change in load impedance.

Furthermore, in the latter power supply device described above,
By sharing one inductor L21 between the boost converter and the buck converter, the number of inductors L21 can be reduced compared to the former power supply device, but the period Ta (= T1, T2) for performing the boost operation and the buck operation Since the period Tb (= T3, T4) for performing
In order to make the output substantially the same as that of the former power supply device, the peak value of the choke current IL21 flowing in the inductor L21 becomes
The peak values of the choke currents IL11, IL12 flowing in the inductors L11, L12 of the former power supply device increase significantly. For example, as shown in FIG. 40, if the peak values of the choke currents IL11 and IL12 flowing in the inductors L11 and L12 of the former power supply device are both Ip, the peak value of the choke current IL21 flowing in the inductor L21 is 2 × Ip. Become. Therefore, it is necessary to use an element having a large rated current for the inductor L21, and as a result, the inductor L21 becomes large and it is difficult to downsize the power supply device.

The present invention has been made in view of the above problems, and an object thereof is to provide a small-sized and highly efficient power supply device in which interference between input and output is suppressed.

[0020]

In order to achieve the above object, according to the invention of claim 1, a harmonic distortion improving function for improving harmonic distortion contained in an input current from a commercial power supply and a load circuit are provided. In a power supply device having a current limiting function for limiting a current to a desired value, a smoothing capacitor is provided,
Converting the input current from the input power supply at high frequency to generate a DC voltage of a desired level across the smoothing capacitor, and the output of the conversion means or the current supplied to the load circuit from the input power supply. The current limiting means for limiting the current and the control means for controlling ON / OFF of the switching means and the switching element forming the current limiting means are provided, and the inductor forming the converting means and the inductor forming the current limiting means are the same. It is also used as an inductor, and the control means is
A period of forming a current loop including at least an inductor and a smoothing capacitor and not including an input power supply and a load circuit, and a period of forming a current loop including at least an inductor, an input power supply and a load circuit within one cycle of switching. It is characterized in that the switching element is controlled to be turned on / off so as to be provided with.

According to a second aspect of the present invention, in the first aspect of the present invention, the control means includes at least a first period in which a positive voltage is applied to the inductor within one switching cycle,
Set between a third period in which a negative voltage is applied to the inductor and a first period and a third period in which the voltage applied to the inductor is lower than the first period and higher than the third period. ON / OFF of the switching element is controlled so as to set at least the second period.

According to a third aspect of the present invention, in the control means according to the second aspect, the inductor has a first current loop in which a discharge current flows from at least the smoothing capacitor, and a second current loop in which no current flows in the smoothing capacitor. On / off of the switching element is controlled so that each current loop is included in the order of the third current loop in which the charging current flows through the smoothing capacitor.

According to a fourth aspect of the present invention, in the invention according to any one of the first to third aspects, the converting means includes a first switching element at an output terminal on a high voltage side of a rectifying circuit for full-wave rectifying the AC power source. Connect the cathode of the first diode to one end of the inductor, and connect one end of the second switching element, the anode of the first diode, and the cathode of the second diode to the output terminal on the low voltage side. Two
To the other end of the switching element, the cathode of the third diode and one end of the smoothing capacitor are connected, the anode of the third diode is connected to one end of the third and fourth switching elements, and the other end of the inductor to the other end. The other end of the switching element 3 is connected to the anode of the fourth diode,
A load circuit is connected between the cathode of the diode and the anode of the third diode, and the other end of the smoothing capacitor and the other end of the fourth switching element are connected to the anode of the second diode. Is characterized by.

[0024]

DESCRIPTION OF THE PREFERRED EMBODIMENTS (Embodiment 1) FIG. 1 shows a circuit diagram of a power supply device of this embodiment. This power supply device has a rectifier circuit DB such as a diode bridge for full-wave rectifying the AC voltage of the commercial power supply AC, and a switching element Q1 (first switching element) is provided at the high-voltage side output terminal of the rectifier circuit DB. Connect the cathode of the diode D1 (first diode) to one end of the inductor L1, and
The output terminal on the low voltage side is connected to one end of the switching element Q2 (second switching element), the anode of the diode D1 and the cathode of the diode D2 (second diode), and the other end of the switching element Q2 is connected to the diode D3 (second (The diode of 3) and one end of the smoothing capacitor C1 are connected, and switching elements Q3 and Q4 (third and fourth switching elements) are connected to the anode of the diode D3.
Is connected to one end of the inductor L1, and the other end of the inductor L1 is connected to the other end of the switching element Q3 and the diode D4 (fourth diode).
The load circuit LD is connected between the cathode of the diode D4 and the anode of the diode D3, and the other end of the smoothing capacitor C1 and the other end of the switching element Q4 are connected to the anode of the diode D2. To be done. A load circuit including a discharge lamp is used as the load circuit LD.

The switching elements Q1 to Q4 are composed of, for example, transistors, and ON / OFF is controlled by control signals a to d input from the control circuit 1. FIG. 2 is a time chart of control signals a to d for controlling on / off of the switching elements Q1 to Q4. The period T1 in which the switching elements Q2 to Q4 are on and the switching element Q1 is off, and the switching element Q1 are shown. , Q4 is on and switching elements Q2 and Q3 are off, and period T2 is that all switching elements Q1 to Q4 are off.
Is sequentially repeated in the order of periods T1, T2, T3. The control circuit 1 controls on / off of the switching elements Q1 to Q4 so that the repetition frequency of the periods T1 to T3 becomes sufficiently higher than the power supply frequency.

Here, the operation of this circuit in each of the periods T1 to T3 will be described with reference to FIGS. Incidentally, FIG.
(A)-(c) is explanatory drawing of the current path in period T1-T3, respectively, and the path through which a current flows is shown by the dotted line.

In the period T1, the switching elements Q2-
When Q4 is turned on and the switching element Q1 is turned off, as shown in FIG. 3A, in the period T3, the electric charge charged in the smoothing capacitor C1 which is an electrolytic capacitor is discharged, and the smoothing capacitor C1 → the switching element Q2 → the diode. D1 → inductor L1 → switching element Q3
→ Current flows through the path of switching element Q4 → smoothing capacitor C1, and energy is stored in inductor L1.
FIG. 4A is an equivalent circuit of this circuit in the period T1, which is a circuit in which the inductor L1 is connected across the smoothing capacitor C1.

Next, when the switching elements Q1 and Q4 are turned on and the switching elements Q2 and Q3 are turned off in the period T2, the input current is drawn from the commercial power source AC as shown in FIG. → Rectifier circuit DB →
Switching element Q1 → inductor L1 → diode D
4 → load circuit LD → switching element Q4 → diode D2 → rectifier circuit DB → current flows through the path of commercial power source AC, energy is accumulated in inductor L1, and
A load current is supplied to the load circuit LD. FIG. 4 (b) is an equivalent circuit of this circuit in the period T2, and the commercial power supply AC
And a series circuit of an inductor L1 and a load circuit LD is connected between both ends of a DC power source E composed of a rectifier circuit DB.

After that, when all the switching elements Q1 to Q4 are turned off in the period T3, the energy stored in the inductor L1 is released in the periods T1 and T2 as shown in FIG. D4
→ load circuit LD → diode D3 → smoothing capacitor C1
The current flows through the path of the diode D2, the diode D1, and the inductor L1, the load current is supplied to the load circuit LD, and the smoothing capacitor C1 is charged. Figure 4
(C) is an equivalent circuit of this circuit in the period T3, and is a circuit in which a series circuit of the load circuit LD and the smoothing capacitor C1 is connected across the inductor L1.

Thus, in this circuit, one inductor L
Since the choke of the boost converter having the harmonic distortion improving function and the choke of the buck converter having the output current limiting function are also used in 1, the number of components is smaller than that of the power supply device of FIG. 34 described in the conventional example. it can.

FIG. 5 shows a waveform diagram of the choke current IL flowing in the inductor L1.
The current waveform has a trapezoidal waveform that gradually increases in the periods T1 and T2 and gradually decreases in the period T3. The portion of the choke current IL that contributes to the input current is the current that flows in the period T2 (A1 portion in FIG. 5), and the portion that contributes to the output current is the current that flows in the periods T2 and T3 (the portion of FIG. 5). A2 part).

Here, the voltage across the smoothing capacitor C1 is
VC1, input voltage (output voltage of rectifier circuit DB) Vin, negative
If the applied voltage of the load circuit LD is VLD
Choke voltage VL_T1Is VL_T1= VC1, in period T2
Choke voltage VL_T2Is VL _T2= Vin-VLD, period T3
Voltage VL at_T3Is VL_T3= -VLD-VC1 <
It becomes 0. Smoothing capacitor by operation as conversion means
The voltage VC1 across C1 is always higher than the input voltage Vin.
Because (VC1> Vin), VL_T1> VL_T2> VL_T3Seki
The clerk is always established. Here, in each period T1 to T3
Slope (rate of change) ΔIL of choke current IL_T1~ ΔIL_T3
Is the choke voltage VL during that period. _T1~ VL_T3Electric power
Since it depends on the pressure value, the slope in the first period T1
ΔIL_T1Is a positive value, the slope ΔIL in the third period T3
_T3Is a negative value. In addition, the first period T1 and the third period T
Choke current in the second period T2 provided between
Slope of IL ΔIL_T2Is the slope ΔIL during the period T1_T1Than
Is also small, and the slope ΔIL during the period T3_T3Greater than
Since it has a positive value, the slope of the choke current IL is
It gradually decreases in the order of 1, T2, T3 (ΔIL_T1>
ΔIL_T2> ΔIL_T3), The waveform is as shown in FIG.
The waveform becomes a shape.

By the way, the power conversion amount with respect to the input / output voltage increases or decreases in proportion to the average value of the choke current IL flowing through the inductor L1, but in the power supply device of FIG. In contrast to the triangular waveform, the current waveform of the choke current IL is a trapezoidal waveform in this embodiment. The peak value of the choke current IL can be reduced as compared with the case. Therefore, the inductor L
1 can be a small one with a small rated current,
The power supply device can be downsized.

In the power supply device described in the prior art,
All the energy input from the power supply is stored in the smoothing capacitor C21 via the boost converter, and then,
The buck converter supplies energy to the load circuit LD using the smoothing capacitor as a power source, and each of the boost converter and the buck converter performs power conversion corresponding to input / output power. It means that the power conversion of double power is being performed. Generally, the circuit loss generated by power conversion increases as the power to be converted increases. Therefore, by performing the power conversion operation twice in the conventional power supply device, the circuit loss increases and the circuit efficiency decreases. As a result, it was necessary to use a large element having a large rated value.

Here, the function required for this circuit is to stably supply the load current to the load circuit LD. If this function can be ensured, the input power source is directly supplied to the load circuit LD. Alternatively, this circuit is provided with a period T2 in which the input current directly flows into the load circuit LD via the inductor L1. In this period, since the power conversion operation between the input and the output is only required once, the redundant power conversion operation in which the power converted by the boost converter is further converted by the buck converter as compared with the conventional power supply device. It is possible to reduce the amount, and it is possible to reduce the circuit loss of the power conversion circuit. As a result, it is possible to use a small component having a small rated value as a circuit component of the power conversion circuit.

Further, in this circuit, a closed loop consisting only of the inductor L1 and the smoothing capacitor C1 is formed, and a period T1 in which energy is transferred between the inductor L1 and the smoothing capacitor C1 is provided. In a dual-purpose converter in which one inductor L1 also serves as the inductor of the boost converter and the inductor of the buck converter, the behavior of each converter easily influences the behavior of the other converter, but the inductor L1 does not operate during the period T1. By forming a closed loop consisting only of the smoothing capacitor C1 and the operation independent of the input side and the load side, the initial current in the period T2 can be stabilized. Therefore, even if the input power supply fluctuates or the load fluctuates, interference between input and output can be suppressed, and as a result, a compact and highly efficient power supply device that can be used even when the input power supply or load is unstable is realized. it can.

(Embodiment 2) FIG. 6 shows Embodiment 2 of the present invention.
It will be described with reference to FIGS. Since the circuit configuration of the power supply device is the same as that of the first embodiment, the description thereof is omitted, and only the circuit operation which is the feature of this embodiment will be described below.

FIG. 6 is a time chart of the control signals a to d for controlling the on / off of the switching elements Q1 to Q4. The period T1 in which the switching elements Q2 to Q4 are on and the switching element Q1 is off, A period T2 in which the switching element Q4 is on and the switching elements Q1 to Q3 are off, and a period T3 in which the switching element Q1 is on and the switching elements Q2 to Q4 are off are
It repeats in order of 1, T2, T3. The control circuit 1 controls on / off of the switching elements Q1 to Q4 so that the repetition frequency of the periods T1 to T3 becomes sufficiently higher than the power supply frequency.

The operation of this circuit in each of the periods T1 to T3 will be described with reference to FIGS. Incidentally, FIG.
(A)-(c) is explanatory drawing of the current path in period T1-T3, respectively, and the path through which a current flows is shown by the dotted line.

In the period T1, the switching elements Q2-
When Q4 is turned on and the switching element Q1 is turned off, as shown in FIG. 7 (a), the electric charge charged in the smoothing capacitor C1 is released during the period T3, and the smoothing capacitor C1 → the switching element Q2 → the diode D1 → the inductor. L1 → switching element Q3 → switching element Q
4 → Current flows through the path of the smoothing capacitor C1 and energy is stored in the inductor L1. FIG. 8A shows a period T1.
Is an equivalent circuit of this circuit in, and smoothing capacitor C1
The circuit is such that the inductor L1 is connected between both ends of the.

Next, when the switching element Q4 is turned on and the switching elements Q1 to Q3 are turned off in the period T2, as shown in FIG. 7B, the inductor L is fed in the period T1.
The energy stored in 1 is released, and the inductor L1 →
Diode D4 → load circuit LD → switching element Q4
The current flows through the path of the diode D2, the diode D1, and the inductor L1, and the load current is supplied to the load circuit LD. FIG. 8B is an equivalent circuit of this circuit in the period T2, which is a circuit in which the load circuit LD is connected across the inductor L1.

Thereafter, when the switching element Q1 is turned on and the switching elements Q2 to Q4 are turned off in the period T3, the input current is drawn from the commercial power source AC as shown in FIG. Circuit DB → switching element Q1 → inductor L1 → diode D4
→ load circuit LD → diode D3 → smoothing capacitor C1
→ Diode D2 → Rectifier circuit DB → Current flows through the path of commercial power supply AC, the load current is supplied to the load circuit LD, and the smoothing capacitor C1 is charged. Figure 8 (c)
Is an equivalent circuit of this circuit in the period T3, and is a circuit in which a series circuit including an inductor L1, a load circuit LD, and a smoothing capacitor C1 is connected between both ends of a DC power source E including a commercial power source AC and a rectifier circuit DB. Become.

Thus, in this circuit, one inductor L
Since the choke of the boost converter having the harmonic distortion improving function and the choke of the buck converter having the output current limiting function are also used in 1, the number of components is smaller than that of the power supply device of FIG. 34 described in the conventional example. it can.

FIG. 9 shows a waveform diagram of the choke current IL flowing through the inductor L1.
The current waveform of gradually increases in the period T1, and the current waveform of
At T3, the waveform is a trapezoid that gradually decreases. The portion of the choke current IL that contributes to the input current is the current that flows in the period T2 (A1 portion in FIG. 9), and the portion that contributes to the output current is the current that flows in the periods T2 and T3 (the portion of FIG. 9). A2 part).

Here, the choke voltage V in the period T1
L_T1Is VL_T1= VC1, choke voltage V in period T2
L_T2Is VL_T2= -VLD, choke voltage in period T3
VL _T3Is VL_T3= Vin-VLD-VC1. With conversion means
The voltage VC1 across the smoothing capacitor C1 is
Since it is always higher than the input voltage Vin (VC1> Vin),
VL_T1> VL_T2> VL_T3The relationship always holds. This
Here, the slope of the choke current IL in each period T1 to T3
(Change rate) ΔIL_T1~ ΔIL_T3In that period
Choke voltage VL_T1~ VL_T3Depends on the voltage value of
Then, the slope ΔIL in the first period T1_T1Is a positive value,
Slope ΔIL in period T3 of 3_T3Is a negative value. Well
The second period provided between the first period T1 and the third period T3
Slope IL of choke current IL in period T2 of
_T2Is the slope ΔIL during the period T1_T1Less than, and
Slope ΔIL during period T3_T3Will be a negative value greater than
Therefore, the slope of the choke current IL varies in the periods T1, T2, and T3.
Gradually decreases in order (ΔIL_T1> ΔIL_T2> ΔIL
_T3), The waveform is a trapezoidal waveform as shown in FIG.
It

As described above, also in the present circuit, as in the first embodiment, since the switching elements Q1 to Q4 are controlled to be turned on and off so that the choke current IL has a trapezoidal waveform, the choke current is controlled. If the average current value and the switching cycle are the same, the peak value of the choke current IL can be reduced as compared with the case where the current waveform is a triangular waveform. Therefore, a small inductor having a small rated current can be used as the inductor L1, and the power supply device can be downsized.

In this circuit, the input current is the inductor L
The period T3 in which the current directly flows into the load circuit LD via 1 is provided. In this period, since the power conversion operation between the input and the output is only required once, the power consumption by the boost converter is higher than that of the conventional power supply device. It is possible to reduce redundant power conversion operations in which the converted power is further converted by the buck converter, and it is possible to reduce the circuit loss of the power conversion circuit. As a result, it is possible to use a small component having a small rated value as a circuit component of the power conversion circuit.

Further, in this circuit, a closed loop consisting only of the inductor L1 and the smoothing capacitor C1 is formed, and a period T1 for transferring energy between the inductor L1 and the smoothing capacitor C1 is provided. One inductor L1
In a dual-purpose converter that doubles as the choke of the boost converter and the choke of the buck converter, the behavior of each converter easily influences the behavior of the other converter, but only the inductor L1 and the smoothing capacitor C1 are included in the period T1. By forming a closed loop consisting of and performing an operation independent of the input side and the load side, the initial current in the period T2 can be stabilized. Therefore, even if the input power supply fluctuates or the load fluctuates, interference between input and output can be suppressed, and as a result, a compact and highly efficient power supply device that can be used even when the input power supply or load is unstable is realized. it can.

(Embodiment 3) Embodiment 3 of the present invention is shown in FIG.
This will be described with reference to FIGS. Since the circuit configuration of the power supply device is the same as that of the first embodiment, the description thereof is omitted, and only the circuit operation which is the feature of this embodiment will be described below.

FIG. 10 is a time chart of the control signals a to d for controlling the on / off of the switching elements Q1 to Q4. The period T1 in which the switching elements Q1, Q2 and Q4 are on and the switching element Q3 is off. And the switching element Q4 is turned on, and the switching elements Q1 to Q
The period T2 in which 3 is off and the period T3 in which the switching element Q3 is on and the switching elements Q1, Q2, Q4 are off are sequentially repeated in the order of periods T1, T2, T3. The control circuit 1 controls on / off of the switching elements Q1 to Q4 so that the repetition frequency of the periods T1 to T3 becomes sufficiently higher than the power supply frequency.

Here, the operation of this circuit in each period T1 to T3 will be described with reference to FIGS. 11A to 11C are explanatory diagrams of the current paths in the periods T1 to T3, respectively, and the paths through which the current flows are indicated by dotted lines.

In the period T1, the switching elements Q1,
When Q2 and Q4 are turned on and the switching element Q3 is turned off, as shown in FIG. 11 (a), the input current is drawn from the commercial power source AC, and the electric charge charged in the smoothing capacitor C1 is released during the period T3. , Commercial power supply AC → rectifier circuit DB → switching element Q1 → inductor L1 → diode D4 → load circuit LD → switching element Q4 → smoothing capacitor C1 → switching element Q2
→ Rectifier circuit DB → Current flows through the path of commercial power supply AC.
During this period, energy is accumulated in the inductor L1 and the load current is supplied to the load circuit LD. Figure 1
2 (a) is an equivalent circuit of this circuit in the period T1,
The circuit is such that a series circuit of the inductor L1 and the load circuit LD is connected across the series circuit of the DC power source E and the smoothing capacitor C1.

Next, when the switching element Q4 is turned on and the switching elements Q1 to Q3 are turned off in the period T2, the energy accumulated in the inductor L1 is released in the period T1 as shown in FIG. L1
→ diode D4 → load circuit LD → switching element Q
4 → Diode D2 → Diode D1 → Inductor L1
The current flows through the path of, and the load current is supplied to the load circuit LD. FIG. 12B is an equivalent circuit of this circuit in the period T2, which is a circuit in which the load circuit LD is connected across the inductor L1.

Thereafter, when the switching element Q3 is turned on and the switching elements Q1, Q2 and Q4 are turned off in the period T3, the energy accumulated in the inductor L1 is continuously released from the period T2 as shown in FIG. 11 (c). Then, a current flows through the path of inductor L1 → switching element Q3 → diode D3 → smoothing capacitor C1 → diode D2 → diode D1 → inductor L1 to charge smoothing capacitor C1. FIG. 12C shows a period T3.
Is an equivalent circuit of the present circuit, and the smoothing capacitor C1 is connected across the inductor L1 in the opposite direction to the period T1.

Thus, in this circuit, one inductor L
Since the choke of the boost converter having the harmonic distortion improving function and the choke of the buck converter having the output current limiting function are also used in 1, the number of components is smaller than that of the power supply device of FIG. 34 described in the conventional example. it can.

FIG. 13 shows a waveform diagram of the choke current IL flowing in the inductor L1. The current waveform of the choke current IL gradually increases in the period T1, and the period T2, T3.
Shows a trapezoidal waveform that gradually decreases.
The portion of the choke current IL that contributes to the input current is the current flowing in the period T1 (A1 portion in FIG. 13),
The portion that contributes to the output current is the current that flows in the periods T1 and T2 (A2 portion in FIG. 13).

Here, the choke voltage V in the period T1
L _T1 is _{VL T1 = Vin + VC1-VLD} , choke voltage VL _T2 in the period T2 choke voltage VL _T3 in VL _T2 = -VLD, period T3 becomes VL _T3 = -VC1. By the operation as the conversion means, the voltage VC1 across the smoothing capacitor C1
Is always higher than the input voltage Vin (VC1> Vi
n), the relationship of VL _T1 > VL _T2 > VL _T3 always holds. Here, the choke current I in each period T1 to T3
L gradient (rate of change) ΔIL _T1 ~ΔIL _T3 of, so determined by the voltage value of the choke voltage VL _T1 ～VL _T3 in the period, the inclination AIL _T1 in the first period T1 positive value, the third period T3 The slope ΔIL _{T3 at} is a negative value. In addition, the slope ΔI of the choke current IL in the second period T2 provided between the first period T1 and the third period T3.
L _T2 is smaller than the slope AIL _T1 during the period T1, and, since a negative value greater than the slope AIL _T3 during the period T3, the slope of the choke current IL periods T1, T2, T
It becomes smaller gradually in the order of 3 (ΔIL _T1 > ΔIL _T2 > Δ
IL _T3 ), and its waveform becomes a trapezoidal waveform as shown in FIG.

As described above, also in this circuit, as in the first embodiment, since the switching elements Q1 to Q4 are controlled to be turned on / off so that the current waveform of the choke current IL becomes a trapezoidal waveform, the choke current is controlled. If the average current value and the switching cycle are the same, the peak value of the choke current IL can be reduced as compared with the case where the current waveform is a triangular waveform. Therefore, a small inductor having a small rated current can be used as the inductor L1, and the power supply device can be downsized.

In this circuit, the input current is the inductor L.
The period T1 in which the current directly flows into the load circuit LD via 1 is provided, and in this period, the power conversion operation between the input and the output is performed only once. Therefore, it is possible to reduce the redundant power conversion operation such as the power conversion by the boost converter and the power conversion by the buck converter as in the conventional power supply device, and it is possible to reduce the circuit loss of the power conversion circuit. It is possible to use small parts with small rated values as circuit parts of the circuit.

Further, in the present circuit, a closed loop consisting of only the inductor L1 and the smoothing capacitor C1 is formed, and a period T3 in which energy is transferred between the inductor L1 and the smoothing capacitor C1 is provided. One inductor L1
In a dual-purpose converter that doubles as the choke of the boost converter and the choke of the buck converter, the behavior of each converter easily affects the behavior of the other converter, but only the inductor L1 and the smoothing capacitor C1 are included in the period T3. By forming a closed loop consisting of and performing an operation independent of the input side and the load side, the initial current in the period T1 can be stabilized. Therefore, even if the input power supply fluctuates or the load fluctuates, interference between input and output can be suppressed, and as a result, a compact and highly efficient power supply device that can be used even when the input power supply or load is unstable is realized. it can.

(Embodiment 4) FIG. 1 shows Embodiment 4 of the present invention.
This will be described with reference to FIGS. Since the circuit configuration of the power supply device is the same as that of the first embodiment, the description thereof is omitted, and only the circuit operation which is the feature of this embodiment will be described below.

FIG. 14 shows a time chart of the control signals a to d for controlling the on / off of the switching elements Q1 to Q4. The period T1 in which the switching elements Q2 and Q4 are on and the switching elements Q1 and Q3 are off. And the switching elements Q1 and Q4 are turned on, and the switching element Q
2, the period T2 in which Q3 is off and the switching element Q
The period T3 in which 3 is on and the switching elements Q1, Q2, Q4 are off is sequentially repeated in the order of periods T1, T2, T3. In the control circuit 1, the periods T1 to T3 are set.
ON / OFF of the switching elements Q1 to Q4 is controlled so that the repetition frequency of is a frequency sufficiently higher than the power supply frequency.

Here, the operation of this circuit in each of the periods T1 to T3 will be described with reference to FIGS. 15A to 15C are explanatory diagrams of the current paths in the periods T1 to T3, respectively, and the paths through which the current flows are indicated by dotted lines.

In the period T1, the switching element Q2,
When Q4 is turned on and the switching elements Q1 and Q3 are turned off, as shown in FIG. 15A, the electric charge charged in the smoothing capacitor C1 is discharged during the period T3, and the smoothing capacitor C1 → the switching element Q2 → the diode D1.
→ Inductor L1 → Diode D4 → Load circuit LD → Switching element Q4 → Current flows through the path of smoothing capacitor C1, energy is accumulated in inductor L1, and load current is supplied to load circuit LD. FIG.
(A) is an equivalent circuit of this circuit in the period T1, and is a circuit in which a series circuit of the inductor L1 and the load circuit LD is connected across the smoothing capacitor C1.

Next, when the switching elements Q1 and Q4 are turned on and the switching elements Q2 and Q3 are turned off in the period T2, the input current is drawn from the commercial power source AC as shown in FIG. → Rectifier circuit DB
→ Switching element Q1 → Inductor L1 → Diode D4 → Load circuit LD → Switching element Q4 → Diode D2 → Rectifier circuit DB → Current flows through the path of commercial power supply AC, and energy is stored in inductor L1,
A load current is supplied to the load circuit LD. FIG. 16B is an equivalent circuit of this circuit in the period T2, and the DC power source E
Is a circuit in which a series circuit of the inductor L1 and the load circuit LD is connected between both ends of.

After that, when the switching element Q3 is turned on and the switching elements Q1, Q2 and Q4 are turned off in the period T3, as shown in FIG.
The energy stored in 1 is released and the inductor L1
→ Switching element Q3 → diode D3 → smoothing capacitor C1 → diode D2 → diode D1 → inductor L1 causes current to flow and smoothing capacitor C1 is charged. FIG. 16C is an equivalent circuit of this circuit in the period T3, which is a circuit in which the smoothing capacitor C1 is connected across the inductor L1 in the opposite direction to the period T1.

Thus, in this circuit, one inductor L
Since the choke of the boost converter having the harmonic distortion improving function and the choke of the buck converter having the output current limiting function are also used in 1, the number of components is smaller than that of the power supply device of FIG. 34 described in the conventional example. it can.

FIG. 17 shows a waveform diagram of the choke current IL flowing in the inductor L1. The current waveform of the choke current IL gradually increases in the periods T1 and T2, and the period T3.
Shows a trapezoidal waveform that gradually decreases.
The portion of the choke current IL that contributes to the input current is the current that flows in the period T2 (A1 portion in FIG. 17), and the portion that contributes to the output current is the current that flows in the periods T1 and T2 (the portion of FIG. 17). A2 part).

Here, the choke voltage V in the period T1
L _T1 is VL _T1 = VC1-VLD, the period T2 choke voltage VL _T2 in the VL _T2 = Vin-VLD, choke voltage VL _T3 in the period T3 becomes VL _T3 = -VC1. Since the voltage VC1 across the smoothing capacitor C1 is always higher than the input voltage Vin due to the operation as the conversion means (VC1> Vin),
The relationship of VL _T1 > VL _T2 > VL _T3 always holds. Here, the slope (rate of change) ΔIL _T1 ~ΔIL _T3 of the choke current IL in each period T1~T3 because determined by the voltage value of the choke voltage VL _T1 ~VL _T3 in the period, the inclination AIL in the first period T1 _T1 has a positive value, and the slope ΔIL _T3 in the third period _T3 has a negative value. In addition, the second period provided between the first period T1 and the third period T3.
Slope IL of choke current IL in period T2 of
_T2 is smaller than the slope AIL _T1 during the period T1, and,
Since a positive value greater than the slope AIL _T3 during the period T3, the slope of the choke current IL gradually decreases in the order of the period _{T1, T2, T3 (ΔIL T1} > ΔIL T2> ΔIL
_T3 ), and its waveform becomes a trapezoidal waveform as shown in FIG.

As described above, also in this circuit, as in the first embodiment, since the switching elements Q1 to Q4 are controlled to be turned on and off so that the current waveform of the choke current IL becomes a trapezoidal waveform, the choke current is controlled. If the average current value and the switching cycle are the same, the peak value of the choke current IL can be reduced as compared with the case where the current waveform is a triangular waveform. Therefore, a small inductor having a small rated current can be used as the inductor L1, and the power supply device can be downsized.

In this circuit, the input current is the inductor L
The period T2 in which the current directly flows into the load circuit LD via 1 is provided, and in this period, the power conversion operation between the input and the output is required only once. Therefore, it is possible to reduce the redundant power conversion operation such as the power conversion by the boost converter and the power conversion by the buck converter as in the conventional power supply device, and it is possible to reduce the circuit loss of the power conversion circuit. It is possible to use small parts with small rated values as circuit parts of the circuit.

Further, in this circuit, a closed loop consisting of only the inductor L1 and the smoothing capacitor C1 is formed, and a period T3 in which energy is transferred between the inductor L1 and the smoothing capacitor C1 is provided. One inductor L1
In a dual-purpose converter that doubles as the choke of the boost converter and the choke of the buck converter, the behavior of each converter easily affects the behavior of the other converter, but only the inductor L1 and the smoothing capacitor C1 are included in the period T3. By forming a closed loop consisting of and performing an operation independent of the input side and the load side, the initial current in the period T1 can be stabilized. Therefore, even if the input power supply fluctuates or the load fluctuates, interference between input and output can be suppressed, and as a result, a compact and highly efficient power supply device that can be used even when the input power supply or load is unstable is realized. it can.

(Fifth Embodiment) FIG. 1 shows a fifth embodiment of the present invention.
This will be described with reference to FIGS. Since the circuit configuration of the power supply device is the same as that of the first embodiment, the description thereof is omitted, and only the circuit operation which is the feature of this embodiment will be described below.

FIG. 18 is a time chart of the control signals a to d for controlling the on / off of the switching elements Q1 to Q4. The period T1 in which the switching elements Q2 to Q4 are on and the switching element Q1 is off, Switching elements Q1, Q4 are on, switching elements Q2, Q3
Is turned off during the period T2 and the switching elements Q1 and Q3.
Is on and the switching elements Q2 and Q4 are off, and the period T3 is sequentially repeated in the order of periods T1, T2 and T3. The control circuit 1 controls on / off of the switching elements Q1 to Q4 so that the repetition frequency of the periods T1 to T3 becomes sufficiently higher than the power supply frequency.

Here, the operation of this circuit in each period T1 to T3 will be described with reference to FIGS. 19A to 19C are explanatory diagrams of the current paths in the periods T1 to T3, respectively, and the paths through which the current flows are indicated by dotted lines.

In the period T1, the switching elements Q2-
When Q4 is turned on and the switching element Q1 is turned off, as shown in FIG. 19A, the electric charge charged in the smoothing capacitor C1 is discharged during the period T3, and the smoothing capacitor C1 → the switching element Q2 → the diode D1 → the inductor. A current flows through the path of L1 → switching element Q3 → switching element Q4 → smoothing capacitor C1, and energy is accumulated in the inductor L1. FIG. 20A is an equivalent circuit of the present circuit in the period T1, which is a circuit in which the inductor L1 is connected between both ends of the smoothing capacitor C1.

Next, when the switching elements Q1 and Q4 are turned on and the switching elements Q2 and Q3 are turned off in the period T2, the input current is drawn from the commercial power source AC as shown in FIG. → Rectifier circuit DB
→ Switching element Q1 → Inductor L1 → Diode D4 → Load circuit LD → Switching element Q4 → Diode D2 → Rectifier circuit DB → Current flows through the path of commercial power supply AC, and energy is stored in inductor L1,
A load current is supplied to the load circuit LD. FIG. 20B shows an equivalent circuit of this circuit in the period T2, and the direct current power source E
Is a circuit in which a series circuit of the inductor L1 and the load circuit LD is connected between both ends of.

After that, when the switching elements Q1 and Q3 are turned on and the switching elements Q2 and Q4 are turned off in the period T3, as shown in FIG.
1 is discharged and an input current is drawn from the commercial power supply AC, and the commercial power supply AC → rectifier circuit DB → switching element Q1 → inductor L1 → switching element Q3 → diode D3 → smoothing capacitor C1 → diode D2. → Rectifier circuit DB → Current flows through the path of the commercial power source AC, and the smoothing capacitor C1 is charged. FIG. 20C shows an equivalent circuit of this circuit in the period T3, which is a circuit in which a series circuit of the inductor L1 and the smoothing capacitor C1 is connected across the DC power source E.

Thus, in this circuit, one inductor L
Since the choke of the boost converter having the harmonic distortion improving function and the choke of the buck converter having the output current limiting function are also used in 1, the number of components is smaller than that of the power supply device of FIG. 34 described in the conventional example. it can.

FIG. 21 shows a waveform diagram of the choke current IL flowing in the inductor L1. The current waveform of the choke current IL gradually increases in the periods T1 and T2, and then the period T3.
Shows a trapezoidal waveform that gradually decreases.
Of the choke current IL, the portion contributing to the input current is the current flowing in the periods T2 and T3 (A1 portion in FIG. 21), and the portion contributing to the output current is the current flowing in the period T2 (in FIG. 21). A2 part).

Here, the choke voltage V in the period T1
L_T1Is VL_T1= VC1, choke voltage V in period T2
L_T2Is VL_T2= Vin-VLD, choke in period T3
Voltage VL_T3Is VL_T3= Vin-VC1. As a conversion means
As a result, the voltage VC1 across the smoothing capacitor C1 is turned on.
Since it is always higher than the output voltage Vin (VC1> Vin), V
L_T1> VL_T2> VL_T3The relationship always holds. here
And the slope of the choke current IL in each period T1 to T3
(Rate of change) ΔIL_T1~ ΔIL_T3Is the
Voltage VL_T1~ VL_T3Depends on the voltage value of
Then, the slope ΔIL in the first period T1_T1Is a positive value,
Slope ΔIL in period T3 of 3_T3Is a negative value. Well
The second period provided between the first period T1 and the third period T3
Slope IL of choke current IL in period T2 of
_T2Is the slope ΔIL during the period T1_T1Less than, and
Slope ΔIL during period T3_T3Is a positive value greater than
Therefore, the slope of the choke current IL varies in the periods T1, T2, and T3.
Gradually decreases in order (ΔIL _T1> ΔIL_T2> ΔIL
_T3), The waveform is a trapezoidal waveform as shown in FIG.
It

As described above, also in the present circuit, as in the first embodiment, since the switching elements Q1 to Q4 are controlled to be turned on and off so that the current waveform of the choke current IL becomes a trapezoidal waveform, the choke current is controlled. If the average current value and the switching cycle are the same, the peak value of the choke current IL can be reduced as compared with the case where the current waveform is a triangular waveform. Therefore, a small inductor having a small rated current can be used as the inductor L1, and the power supply device can be downsized.

In this circuit, the input current is the inductor L
The period T2 in which the current directly flows into the load circuit LD via 1 is provided, and in this period, the power conversion operation between the input and the output is required only once. Therefore, it is possible to reduce the redundant power conversion operation such as the power conversion by the boost converter and the power conversion by the buck converter as in the conventional power supply device, and it is possible to reduce the circuit loss of the power conversion circuit. It is possible to use small parts with small rated values as circuit parts of the circuit.

Furthermore, in this circuit, a closed loop consisting of only the inductor L1 and the smoothing capacitor C1 is formed, and a period T1 for transferring energy between the inductor L1 and the smoothing capacitor C1 is provided. One inductor L1
In a dual-purpose converter that doubles as the choke of the boost converter and the choke of the buck converter, the behavior of each converter easily influences the behavior of the other converter, but only the inductor L1 and the smoothing capacitor C1 are included in the period T1. By forming a closed loop consisting of and performing an operation independent of the input side and the load side, the initial current in the period T2 can be stabilized. Therefore, even if the input power supply fluctuates or the load fluctuates, interference between input and output can be suppressed, and as a result, a compact and highly efficient power supply device that can be used even when the input power supply or load is unstable is realized. it can.

Embodiment 6 FIG. 2 shows Embodiment 6 of the present invention.
It will be described with reference to FIGS. Since the circuit configuration of the power supply device is the same as that of the first embodiment, the description thereof is omitted, and only the circuit operation which is the feature of this embodiment will be described below.

FIG. 22 is a time chart of the control signals a to d for controlling the on / off of the switching elements Q1 to Q4. The period T1 in which the switching elements Q2 to Q4 are on and the switching element Q1 is off, Switching elements Q1, Q3, Q4 are on, switching element Q2
Is turned off, and a period T3 when the switching element Q1 is turned on and the switching elements Q2 to Q4 are turned off.
Is sequentially repeated in the order of periods T1, T2, T3. The control circuit 1 controls on / off of the switching elements Q1 to Q4 so that the repetition frequency of the periods T1 to T3 becomes sufficiently higher than the power supply frequency.

Here, the operation of this circuit in each of the periods T1 to T3 will be described with reference to FIGS. 23 (a) to 23 (c) are explanatory diagrams of the current paths in the periods T1 to T3, respectively, and the paths through which the current flows are indicated by dotted lines.

In the period T1, the switching elements Q2-
When Q4 is turned on and the switching element Q1 is turned off, as shown in FIG. 23 (a), the electric charge charged in the smoothing capacitor C1 is discharged during the period T3, and the smoothing capacitor C1 → the switching element Q2 → the diode D1 → the inductor. A current flows through the path of L1 → switching element Q3 → switching element Q4 → smoothing capacitor C1, and energy is accumulated in the inductor L1. FIG. 24A is an equivalent circuit of the present circuit in the period T1, which is a circuit in which the inductor L1 is connected between both ends of the smoothing capacitor C1.

Next, when the switching elements Q1, Q3 and Q4 are turned on and the switching element Q2 is turned off in the period T2, the input current is drawn from the commercial power source AC as shown in FIG. → Rectifier circuit DB
→ switching element Q1 → inductor L1 → switching element Q3 → switching element Q4 → diode D2 →
A current flows through the path from the rectifier circuit DB to the commercial power supply AC, and energy is stored in the inductor L1. FIG. 24B is an equivalent circuit of this circuit in the period T2, which is a circuit in which the inductor L1 is connected across the DC power source E.

After that, when the switching element Q1 is turned on and the switching elements Q2 to Q4 are turned off in the period T3, the input current is drawn from the commercial power source AC as shown in FIG. Circuit DB →
Switching element Q1 → inductor L1 → diode D
4 → load circuit LD → diode D3 → smoothing capacitor C
A current flows through the path of 1 → diode D2 → rectifier circuit DB → commercial power supply AC, the load current is supplied to the load circuit LD, and the smoothing capacitor C1 is charged. Figure 24
(C) is an equivalent circuit of this circuit in the period T3, and the inductor L1, the load circuit LD, and the smoothing capacitor C are provided between both ends of the DC power source E including the commercial power source AC and the rectifier circuit DB.
It becomes a circuit in which a series circuit with 1 is connected.

Thus, in this circuit, one inductor L
Since the choke of the boost converter having the harmonic distortion improving function and the choke of the buck converter having the output current limiting function are also used in 1, the number of components is smaller than that of the power supply device of FIG. 34 described in the conventional example. it can.

FIG. 25 shows a waveform diagram of the choke current IL flowing in the inductor L1. The current waveform of the choke current IL gradually increases in the periods T1 and T2, and the period T3.
Shows a trapezoidal waveform that gradually decreases.
The portion of the choke current IL that contributes to the input current is the current flowing in the periods T2 and T3 (A1 portion in FIG. 25), and the portion that contributes to the output current is the current flowing in the period T3 (see FIG. 25). A2 part).

Here, the choke voltage V in the period T1
L_T1Is VL_T1= VC1, choke voltage V in period T2
L_T2Is VL_T2= Vin, choke voltage V in period T3
L_T3Is VL_T3= Vin-VLD-VC1. As a conversion means
As a result, the voltage VC1 across the smoothing capacitor C1 is turned on.
Since it is always higher than the output voltage Vin (VC1> Vin), V
L_T1> VL_T2> VL_T3The relationship always holds. here
And the slope of the choke current IL in each period T1 to T3
(Rate of change) ΔIL_T1~ ΔIL_T3Is the
Voltage VL_T1~ VL_T3Depends on the voltage value of
Then, the slope ΔIL in the first period T1_T1Is a positive value,
Slope ΔIL in period T3 of 3_T3Is a negative value. Well
The second period provided between the first period T1 and the third period T3
Slope IL of choke current IL in period T2 of
_T2Is the slope ΔIL during the period T1_T1Less than, and
Slope ΔIL during period T3_T3Is a positive value greater than
Therefore, the slope of the choke current IL varies in the periods T1, T2, and T3.
Gradually decreases in order (ΔIL _T1> ΔIL_T2> ΔIL
_T3), The waveform is a trapezoidal waveform as shown in FIG.
It

As described above, also in the present circuit, as in the first embodiment, since the switching elements Q1 to Q4 are controlled to be turned on / off so that the current waveform of the choke current IL becomes a trapezoidal waveform, the choke current is controlled. If the average current value and the switching cycle are the same, the peak value of the choke current IL can be reduced as compared with the case where the current waveform is a triangular waveform. Therefore, a small inductor having a small rated current can be used as the inductor L1, and the power supply device can be downsized.

In this circuit, the input current is the inductor L
The period T3 in which the current directly flows into the load circuit LD via 1 is provided, and in this period, the power conversion operation between the input and the output is required only once. Therefore, it is possible to reduce the redundant power conversion operation such as the power conversion by the boost converter and the power conversion by the buck converter as in the conventional power supply device, and it is possible to reduce the circuit loss of the power conversion circuit. It is possible to use small parts with small rated values as circuit parts of the circuit.

Further, in this circuit, a closed loop consisting only of the inductor L1 and the smoothing capacitor C1 is formed to provide a period T1 for transferring energy between the inductor L1 and the smoothing capacitor C1. One inductor L1
In a dual-purpose converter that doubles as the choke of the boost converter and the choke of the buck converter, the behavior of each converter easily influences the behavior of the other converter, but only the inductor L1 and the smoothing capacitor C1 are included in the period T1. By forming a closed loop consisting of and performing an operation independent of the input side and the load side, the initial current in the period T2 can be stabilized. Therefore, even if the input power supply fluctuates or the load fluctuates, interference between input and output can be suppressed, and as a result, a compact and highly efficient power supply device that can be used even when the input power supply or load is unstable is realized. it can.

Embodiment 7 FIG. 2 shows Embodiment 7 of the present invention.
6 to 29, a description will be given. Since the circuit configuration of the power supply device is the same as that of the first embodiment, the description thereof is omitted, and only the circuit operation which is the feature of this embodiment will be described below.

FIG. 26 is a time chart of the control signals a to d for controlling the on / off of the switching elements Q1 to Q4. The period T1 in which the switching elements Q1, Q2 and Q4 are on and the switching element Q3 is off. A period T2 in which the switching elements Q1, Q3, Q4 are on and the switching element Q2 is off, and the switching element Q
The period T3 in which 3 is on and the switching elements Q1, Q2, Q4 are off is sequentially repeated in the order of periods T1, T2, T3. In the control circuit 1, the periods T1 to T3 are set.
ON / OFF of the switching elements Q1 to Q4 is controlled so that the repetition frequency of is a frequency sufficiently higher than the power supply frequency.

Here, the operation of this circuit in each period T1 to T3 will be described with reference to FIGS. 27A to 27C are explanatory diagrams of the current paths in the periods T1 to T3, respectively, and the paths through which the current flows are indicated by dotted lines.

In period T1, switching element Q1,
When Q2 and Q4 are turned on and the switching element Q3 is turned off, as shown in FIG. 27 (a), the input current is drawn from the commercial power source AC and the electric charge charged in the smoothing capacitor C1 is discharged during the period T3. , Commercial power supply AC → rectifier circuit DB → switching element Q1 → inductor L1 → diode D4 → load circuit LD → switching element Q4 → smoothing capacitor C1 → switching element Q2
→ Rectifier circuit DB → Current flows through the path of commercial power supply AC.
During this period, energy is accumulated in the inductor L1 and the load current is supplied to the load circuit LD. Figure 2
8 (a) is an equivalent circuit of this circuit in the period T1,
The circuit is such that a series circuit of the inductor L1 and the load circuit LD is connected across the series circuit of the DC power source E and the smoothing capacitor C1.

Next, when the switching elements Q1, Q3 and Q4 are turned on and the switching element Q2 is turned off in the period T2, the input current is drawn from the commercial power source AC as shown in FIG. → Rectifier circuit DB
→ switching element Q1 → inductor L1 → switching element Q3 → switching element Q4 → diode D2 →
A current flows through the path from the rectifier circuit DB to the commercial power supply AC, and energy is stored in the inductor L1. FIG. 28B is an equivalent circuit of this circuit in the period T2, which is a circuit in which the inductor L1 is connected across the DC power source E.

Thereafter, when the switching element Q3 is turned on and the switching elements Q1, Q2 and Q4 are turned off in the period T3, as shown in FIG. 27 (c), the inductor L
The energy stored in 1 is released and the inductor L1
→ Switching element Q3 → diode D3 → smoothing capacitor C1 → diode D2 → diode D1 → inductor L1 causes current to flow and smoothing capacitor C1 is charged. FIG. 28C is an equivalent circuit of this circuit in the period T3, which is a circuit in which the smoothing capacitor C1 is connected across the inductor L1 in the opposite direction to the period T1.

Thus, in this circuit, one inductor L
Since the choke of the boost converter having the harmonic distortion improving function and the choke of the buck converter having the output current limiting function are also used in 1, the number of components is smaller than that of the power supply device of FIG. 34 described in the conventional example. it can.

FIG. 29 shows a waveform diagram of the choke current IL flowing in the inductor L1. The current waveform of the choke current IL gradually increases in the periods T1 and T2, and the period T3.
Shows a trapezoidal waveform that gradually decreases.
The portion of the choke current IL that contributes to the input current is the current that flows in the periods T1 and T2 (the portion A1 in FIG. 29), and the portion that contributes to the output current is the current that flows in the period T1 (the portion of FIG. 29). A2 part).

Here, the choke voltage V in the period T1
L _T1 is _{VL T1 = Vin + VC1-VLD} , choke voltage VL _T3 in the choke voltage VL _T2 is VL _T2 = Vin, the period T3 in the period T2 VL _T3 = -VC1 next, the load voltage V
Since the voltage VC1 across the smoothing capacitor C1 is sufficiently higher than that of the LD, the relationship VL _T1 > VL _T2 > VL _T3 always holds. Here, the slope (rate of change) ΔIL _T1 ~ΔIL _T3 of the choke current IL in each period T1~T3 because determined by the voltage value of the choke voltage VL _T1 ~VL _T3 in the period, the inclination AIL in the first period T1 _T1 has a positive value, and the slope ΔIL _T3 in the third period _T3 has a negative value. Further, the slope Δ of the choke current IL in the second period T2 provided between the first period T1 and the third period T3.
IL _T2 is smaller than the slope AIL _T1 during the period T1, and, since a positive value greater than the slope AIL _T3 during the period T3, the slope of the choke current IL periods T1, T2, T
It becomes smaller gradually in the order of 3 (ΔIL _T1 > ΔIL _T2 > Δ
IL _T3 ), and its waveform becomes a trapezoidal waveform as shown in FIG.

As described above, also in this circuit, as in the first embodiment, since the switching elements Q1 to Q4 are controlled to be turned on / off so that the current waveform of the choke current IL becomes a trapezoidal waveform, the choke current is controlled. If the average current value and the switching cycle are the same, the peak value of the choke current IL can be reduced as compared with the case where the current waveform is a triangular waveform. Therefore, a small inductor having a small rated current can be used as the inductor L1, and the power supply device can be downsized.

In this circuit, the input current is the inductor L
The period T1 in which the current directly flows into the load circuit LD via 1 is provided, and in this period, the power conversion operation between the input and the output is performed only once. Therefore, it is possible to reduce the redundant power conversion operation such as the power conversion by the boost converter and the power conversion by the buck converter as in the conventional power supply device, and it is possible to reduce the circuit loss of the power conversion circuit. It is possible to use small parts with small rated values as circuit parts of the circuit.

Further, in this circuit, a closed loop consisting of only the inductor L1 and the smoothing capacitor C1 is formed, and a period T3 for providing energy between the inductor L1 and the smoothing capacitor C1 is provided. One inductor L1
In a dual-purpose converter that doubles as the choke of the boost converter and the choke of the buck converter, the behavior of each converter easily affects the behavior of the other converter, but only the inductor L1 and the smoothing capacitor C1 are included in the period T3. By forming a closed loop consisting of and performing an operation independent of the input side and the load side, the initial current in the period T1 can be stabilized. Therefore, even if the input power supply fluctuates or the load fluctuates, interference between input and output can be suppressed, and as a result, a compact and highly efficient power supply device that can be used even when the input power supply or load is unstable is realized. it can.

(Embodiment 8) FIG. 3 shows Embodiment 8 of the present invention.
This will be described with reference to FIGS. Since the circuit configuration of the power supply device is the same as that of the first embodiment, the description thereof is omitted, and only the circuit operation which is the feature of this embodiment will be described below.

FIG. 30 is a time chart of the control signals a to d for controlling the on / off of the switching elements Q1 to Q4. The period T1 in which all the switching elements Q1 to Q4 are on and the switching elements Q1 and Q4 are shown. Is on,
A period T2 in which the switching elements Q2 and Q3 are off,
Switching element Q3 is on, switching element Q1,
The period T3 in which Q2 and Q4 are turned off is the period T1, T2,
It repeats in order of T3. In the control circuit 1, the switching element Q1 is set so that the repetition frequency of the periods T1 to T3 becomes a frequency sufficiently higher than the power supply frequency.
The on / off of Q4 is controlled.

Here, the operation of this circuit in each of the periods T1 to T3 will be described with reference to FIGS. 31 and 32. 31A to 31C are explanatory diagrams of the current paths in the periods T1 to T3, respectively, and the paths through which the current flows are indicated by dotted lines.

In the period T1, the switching elements Q1.about.
When all Q4 are turned on, as shown in FIG.
While the input current is drawn from the commercial power supply AC, the electric charge charged in the smoothing capacitor C1 is released during the period T3, and the commercial power supply AC → rectifier circuit DB → switching element Q1 → inductor L1 → switching element Q3 →
Current flows through the path of switching element Q4 → smoothing capacitor C1 → switching element Q2 → rectifier circuit DB → commercial power supply AC, and energy is stored in inductor L1. FIG. 32A is an equivalent circuit of this circuit in the period T1, which is a circuit in which an inductor L1 is connected between both ends of a series circuit of the DC power source E and the smoothing capacitor C1.

Next, when the switching elements Q1 and Q4 are turned on and the switching elements Q2 and Q3 are turned off in the period T2, as shown in FIG. 31 (b), the input current is drawn from the commercial power source AC and the commercial power source AC. → Rectifier circuit DB
→ Switching element Q1 → Inductor L1 → Diode D4 → Load circuit LD → Switching element Q4 → Diode D2 → Rectifier circuit DB → Current flows through the path of commercial power supply AC, and energy is stored in inductor L1,
A load current is supplied to the load circuit LD. FIG. 32 (b) is an equivalent circuit of this circuit in the period T2.
Is a circuit in which a series circuit of the inductor L1 and the load circuit LD is connected between both ends of.

Thereafter, when the switching element Q3 is turned on and the switching elements Q1, Q2 and Q4 are turned off in the period T3, as shown in FIG. 31 (c), the inductor L
The energy stored in 1 is released and the inductor L1
→ Switching element Q3 → diode D3 → smoothing capacitor C1 → diode D2 → diode D1 → inductor L1 causes current to flow and smoothing capacitor C1 is charged. FIG. 32C shows an equivalent circuit of this circuit in the period T3, which is a circuit in which the smoothing capacitor C1 is reversely connected between both ends of the inductor L1.

Thus, in this circuit, one inductor L
Since the choke of the boost converter having the harmonic distortion improving function and the choke of the buck converter having the output current limiting function are also used in 1, the number of components is smaller than that of the power supply device of FIG. 34 described in the conventional example. it can.

FIG. 33 shows a waveform diagram of the choke current IL flowing in the inductor L1. The current waveform of the choke current IL gradually increases in the periods T1 and T2, and the period T3.
Shows a trapezoidal waveform that gradually decreases.
Of the choke current IL, the portion contributing to the input current is the current flowing in the periods T1 and T2 (A1 portion in FIG. 33), and the portion contributing to the output current is the current flowing in the period T2 (in FIG. 33). A2 part).

Here, the choke voltage V in the period T1
L _T1 is VL _T1 = Vin + VC1, choke voltage VL _T3 in the choke voltage VL _T2 is VL _T2 = Vin-VLD, the period T3 in the period T2 VL _T3 = -VC1 next, the load voltage V
Since the voltage VC1 across the smoothing capacitor C1 is sufficiently higher than that of the LD, the relationship VL _T1 > VL _T2 > VL _T3 always holds. Here, the slope (rate of change) ΔIL _T1 ~ΔIL _T3 of the choke current IL in each period T1~T3 because determined by the voltage value of the choke voltage VL _T1 ~VL _T3 in the period, the inclination AIL in the first period T1 _T1 has a positive value, and the slope ΔIL _T3 in the third period _T3 has a negative value. Further, the slope Δ of the choke current IL in the second period T2 provided between the first period T1 and the third period T3.
IL _T2 is smaller than the slope AIL _T1 during the period T1, and, since a positive value greater than the slope AIL _T3 during the period T3, the slope of the choke current IL periods T1, T2, T
It becomes smaller gradually in the order of 3 (ΔIL _T1 > ΔIL _T2 > Δ
IL _T3 ), and its waveform becomes a trapezoidal waveform as shown in FIG.

As described above, also in the present circuit, as in the first embodiment, since the switching elements Q1 to Q4 are controlled to be turned on / off so that the current waveform of the choke current IL becomes a trapezoidal waveform, the choke current is controlled. If the average current value and the switching cycle are the same, the peak value of the choke current IL can be reduced as compared with the case where the current waveform is a triangular waveform. Therefore, a small inductor having a small rated current can be used as the inductor L1, and the power supply device can be downsized.

In this circuit, the input current is the inductor L
The period T2 in which the current directly flows into the load circuit LD via 1 is provided, and in this period, the power conversion operation between the input and the output is required only once. Therefore, it is possible to reduce the redundant power conversion operation such as the power conversion by the boost converter and the power conversion by the buck converter as in the conventional power supply device, and it is possible to reduce the circuit loss of the power conversion circuit. It is possible to use small parts with small rated values as circuit parts of the circuit.

Further, in the present circuit, a closed loop consisting of only the inductor L1 and the smoothing capacitor C1 is formed, and a period T3 in which energy is transferred between the inductor L1 and the smoothing capacitor C1 is provided. One inductor L1
In a dual-purpose converter that doubles as the choke of the boost converter and the choke of the buck converter, the behavior of each converter easily affects the behavior of the other converter, but only the inductor L1 and the smoothing capacitor C1 are included in the period T3. By forming a closed loop consisting of and performing an operation independent of the input side and the load side, the initial current in the period T1 can be stabilized. Therefore, even if the input power supply fluctuates or the load fluctuates, interference between input and output can be suppressed, and as a result, a compact and highly efficient power supply device that can be used even when the input power supply or load is unstable is realized. it can.

[0121]

As described above, according to the first aspect of the invention, the harmonic distortion improving function for improving the harmonic distortion contained in the input current from the commercial power source and the current supplied to the load circuit are set to desired values. In a power supply device having a current limiting function for limiting current,
A conversion unit that has a smoothing capacitor and that generates a DC voltage of a desired level across the smoothing capacitor by switching the input current from the input power supply at a high frequency,
A current limiting means for limiting a current supplied to the load circuit from either the output of the converting means or an input power source; and a control means for controlling on / off of a switching element forming the converting means and the current limiting means, The same inductor serves as the inductor that constitutes the conversion means and the inductor that constitutes the current limiting means, and the control means includes at least an inductor and a smoothing capacitor within one cycle of switching, and
On / off of the switching element is controlled so that a period for forming a current loop that does not include the input power supply and the load circuit and a period for forming a current loop that includes at least the inductor, the input power supply, and the load circuit are provided. ,
The control means provides a period for forming a current loop including at least the inductor, the input power supply and the load circuit,
Current can be supplied directly from the input power source to the load circuit via the inductor that functions as a current limiting element. During this period, power conversion is not performed by the conversion means, so the number of power conversion stages is reduced and circuit loss is reduced. As a result, it is possible to use a small component having a small rating as a component of the circuit, and thus it is possible to miniaturize the power supply device. Further, since the same inductor is used for both the inductor forming the conversion means and the inductor forming the current limiting means for the purpose of reducing the number of parts, each operation of the conversion means and the current limiting means affects the other. However, the control means includes a period for forming a current loop that includes at least the inductor and the smoothing capacitor and does not include the input power supply and the load circuit. In this period, the control circuit is related to the input power supply and the load circuit. Instead, since energy is transferred between the inductor and the smoothing capacitor,
The effect of the operation as the current limiting means on the operation of the converting means can be reduced, and the operation of the converting means can be stabilized even when the operation of the input power supply or the load circuit is unstable.

According to a second aspect of the present invention, in the first aspect of the present invention, the control means includes at least a first period in which a positive voltage is applied to the inductor within one cycle of switching,
Set between a third period in which a negative voltage is applied to the inductor and a first period and a third period in which the voltage applied to the inductor is lower than the first period and higher than the third period. The switching element is controlled to be turned on and off so as to set at least the second period. The rate of change of the current flowing through the inductor is proportional to the value of the voltage applied to the inductor. The rate of change of the current flowing through is positive in the first period, negative in the third period, lower than the first period and higher than the third period in the period between the first period and the third period. By setting it to a value, the waveform of the current flowing through the inductor can be made trapezoidal. As a result, if the average value of the current flowing through the inductor is the same,
Since the peak current can be reduced and a small component with a small rating can be used for the inductor, there is an effect that the power supply device can be downsized.

According to a third aspect of the present invention, in the control means according to the second aspect, the inductor has a first current loop in which a discharge current flows from at least the smoothing capacitor, and a second current loop in which no current flows in the smoothing capacitor. And a third current loop through which a charging current flows through the smoothing capacitor, the on / off of the switching element is controlled so as to be included in each current loop, and the same effect as the invention of claim 2 is obtained. Play.

According to a fourth aspect of the present invention, in the invention according to any one of the first to third aspects, the converting means includes a first switching element at an output terminal on a high voltage side of a rectifying circuit for full-wave rectifying the AC power source. Connect the cathode of the first diode to one end of the inductor, and connect one end of the second switching element, the anode of the first diode and the cathode of the second diode to the output terminal on the low voltage side. The other end of the second switching element is connected to the cathode of the third diode and one end of the smoothing capacitor, the anode of the third diode is connected to one end of the third and fourth switching elements, and the other end of the inductor is connected. The other end of the third switching element is connected to the anode of the fourth diode, and a load circuit is connected between the cathode of the fourth diode and the anode of the third diode. Continue, and by connecting the other ends of and fourth switching elements of the smoothing capacitor to the anode of the second diode is characterized in that it is configured, the same effects as the invention of claims 1 to 3.

[Brief description of drawings]

FIG. 1 is a circuit diagram of a power supply device according to a first embodiment.

FIG. 2 is a timing chart explaining the operation of the switching element used in the above.

3A to 3C are explanatory diagrams of current paths in periods T1 to T3.

4A to 4C are equivalent circuit diagrams of the present circuit in periods T1 to T3.

FIG. 5 is a waveform diagram of a choke current flowing in the above inductor.

FIG. 6 is a timing chart illustrating an operation of a switching element used in the power supply device according to the second embodiment.

7A to 7C are explanatory diagrams of current paths in periods T1 to T3.

8A to 8C are equivalent circuit diagrams of this circuit in periods T1 to T3.

FIG. 9 is a waveform diagram of a choke current flowing in the above inductor.

FIG. 10 is a timing chart illustrating an operation of a switching element used in the power supply device according to the third embodiment.

11A to 11C are explanatory diagrams of current paths in periods T1 to T3.

12A to 12C are equivalent circuit diagrams of this circuit in periods T1 to T3.

FIG. 13 is a waveform diagram of a choke current flowing in the above inductor.

FIG. 14 is a timing chart illustrating an operation of a switching element used in the power supply device according to the fourth embodiment.

15A to 15C are explanatory diagrams of current paths in periods T1 to T3.

16A to 16C are equivalent circuit diagrams of this circuit in periods T1 to T3.

FIG. 17 is a waveform diagram of a choke current flowing through the inductor of the above.

FIG. 18 is a timing chart illustrating the operation of the switching element used in the power supply device according to the fifth embodiment.

19A to 19C are explanatory diagrams of current paths in periods T1 to T3.

20A to 20C are equivalent circuit diagrams of this circuit in periods T1 to T3.

FIG. 21 is a waveform diagram of a choke current flowing through the inductor of the above.

FIG. 22 is a timing chart illustrating the operation of the switching element used in the power supply device according to the sixth embodiment.

23 (a) to 23 (c) are explanatory diagrams of current paths in periods T1 to T3.

24 (a) to (c) are equivalent circuit diagrams of the present circuit in periods T1 to T3.

FIG. 25 is a waveform diagram of a choke current flowing in the above inductor.

FIG. 26 is a timing chart illustrating the operation of the switching element used in the power supply device according to the seventh embodiment.

27A to 27C are explanatory diagrams of current paths in periods T1 to T3.

28A to 28C are equivalent circuit diagrams of this circuit in periods T1 to T3.

FIG. 29 is a waveform diagram of a choke current flowing through the inductor of the above.

FIG. 30 is a timing chart illustrating the operation of the switching element used in the power supply device according to the eighth embodiment.

31A to 31C are explanatory diagrams of current paths in periods T1 to T3.

32A to 32C are equivalent circuit diagrams of this circuit in periods T1 to T3.

FIG. 33 is a waveform diagram of a choke current flowing in the above inductor.

FIG. 34 is a circuit diagram of a conventional power supply device.

FIG. 35 is a waveform chart of each part of the above.

FIG. 36 shows the same as above, (a) shows a switching element Q1.
1, an explanatory view of a current path when Q12 is on, (b)
FIG. 6 is an explanatory diagram of a current path when the switching elements Q11 and Q12 are off.

FIG. 37 is a circuit diagram of another conventional power supply device.

FIG. 38 is a waveform chart of each part of the above.

FIG. 39 shows the same as above, and (a) to (d) are explanatory diagrams of current paths in periods T1 to T4, respectively.

FIG. 40 is a waveform diagram of currents flowing in inductors of two types of conventional power supply devices.

[Explanation of symbols]

1 control circuit AC commercial power supply C1 smoothing capacitor L1 inductor LD load circuit Q1-Q4 switching elements

Claims (4)

[Claims] 1. A power supply having a harmonic distortion improving function for improving harmonic distortion contained in an input current from a commercial power supply and a current limiting function for limiting a current supplied to a load circuit to a desired value. In the device, there is a smoothing capacitor, a conversion means for generating a DC voltage of a desired level across the smoothing capacitor by switching the input current from the input power supply at a high frequency,
A current limiting means for limiting a current supplied to the load circuit from either the output of the converting means or an input power source; and a control means for controlling on / off of a switching element forming the converting means and the current limiting means, The same inductor serves as the inductor that constitutes the conversion means and the inductor that constitutes the current limiting means, and the control means includes at least an inductor and a smoothing capacitor within one cycle of switching, and the input power supply and the A power supply device controlling ON / OFF of a switching element so as to provide a period for forming a current loop that does not include a load circuit and a period for forming a current loop that includes at least an inductor, an input power supply, and a load circuit. .. 2. The control means comprises at least a first period in which a positive voltage is applied to the inductor and a third period in which a negative voltage is applied to the inductor within one switching cycle. At least a second period set between the first period and the third period, in which the voltage applied to the inductor is lower than the first period and higher than the third period, is set, The power supply device according to claim 1, wherein ON / OFF of the switching element is controlled. 3. The control means comprises: a first current loop through which a discharging current flows from at least a smoothing capacitor, a second current loop through which a current does not flow through the smoothing capacitor, and a third current through which a charging current flows through the smoothing capacitor. 3. The power supply device according to claim 2, wherein on / off of the switching element is controlled so as to be included in each current loop in the order of. 4. The converting means connects a cathode of a first diode and one end of an inductor to a high-voltage side output terminal of a rectifying circuit for full-wave rectifying an AC power source via a first switching element, One end of the second switching element, the anode of the first diode and the cathode of the second diode are connected to the output terminal on the low voltage side, and the other end of the second switching element is connected to the cathode of the third diode and the smoothing capacitor. To the anode of the third diode, the ends of the third and fourth switching elements are connected to the anode of the third diode, and the other end of the inductor is connected to the other end of the third switching element and the anode of the fourth diode. Connect a load circuit between the cathode of the fourth diode and the anode of the third diode, and connect the other end of the smoothing capacitor to the anode of the second diode. Claims 1 to 3, characterized in that it is constituted by connecting a beauty other end of the fourth switching element
The power supply device according to any one of 1.