GB2213994A - Adaptive antennas - Google Patents
Adaptive antennas Download PDFInfo
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- GB2213994A GB2213994A GB8428889A GB8428889A GB2213994A GB 2213994 A GB2213994 A GB 2213994A GB 8428889 A GB8428889 A GB 8428889A GB 8428889 A GB8428889 A GB 8428889A GB 2213994 A GB2213994 A GB 2213994A
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- stage
- output
- signal
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- input
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Classifications
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- H—ELECTRICITY
- H01—ELECTRIC ELEMENTS
- H01Q—ANTENNAS, i.e. RADIO AERIALS
- H01Q3/00—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system
- H01Q3/26—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system varying the relative phase or relative amplitude of energisation between two or more active radiating elements; varying the distribution of energy across a radiating aperture
- H01Q3/2605—Array of radiating elements provided with a feedback control over the element weights, e.g. adaptive arrays
- H01Q3/2611—Means for null steering; Adaptive interference nulling
- H01Q3/2617—Array of identical elements
Abstract
An adaptive antenna array comprises a plurality of antenna elements the outputs of which feed a cascaded beamforming network having a succession of stages connected as shown, each stage including a group of signal decorrelation cells (DC), the group in each stage having one less cell than the group of the preceding stage, and includes means for applying weighting to the signals applied as inputs to the cells of at least the first stage. A reference signal being a representation of the desired signal output is applied to the beamforming network as an input additional to the outputs of the antenna elements, and a delayed 40 version of the reference signals subtracted from the output of the last stage. Feedback means (not shown) are provided whereby the difference signal so obtained is used to generate the succeeding reference signal. <IMAGE>
Description
ADAPTIVE ANTENNAS
This invention relates to adaptive antennas using cascade beamforming architectures.
Adaptive beamforming provides a powerful means of enhancing the performance of a broad range of communication, navigation and radar systems in hostile electromagnetic environments. In essence, adaptive arrays are antenna systems which can automatically adjust their directional response to null interference or jamming and thus enhance the reception of wanted signals. In many applications, antenna platform dynamics, sophisticated jamming threats and agile waveform structures produce a requirement for adaptive systems having rapid convergence, high cancellation performance and operational flexibility.
In recent years, there has been considerable interest in the application of direct solution or 'lopes loop" techniques to adaptive antenna processing in order to accommodate these increasing demands. In the context of adaptive antenna processing these algorithms have the advantage of requiring only limited input data to accurately describe the external environment and provide an antenna pattern capable of suppressing a wide dynamic range of jamming signals.
The objective of an optimal adaptive antenna system is'to minimise the total noise residue (including -jamming and receiver noise) at the array output whilst maintaining a fixed gain in the direction of the desired signal and hence lead to a maximisation of resultant signal to noise ratio.
According to the present invention there is provided an adaptive antenna array comprising a plurality of antenna elements the outputs of which feed a cascaded beamforming network having a succession of stages, each stage including a group of signal decorrelation cells, the group in each stage having one less cell than the group of the preceding stage and the first stage group having one less cell than the number of antenna elements, each cell of the first stage having as one input the output of a respective antenna element and as a second input the output of the remaining antenna element to produce an output signal and each cell of each subsequent stage having as one input the output of a respective cell of the preceding stage and as a second input the output from the remaining cell of the preceding stage to produce an output signal, the whole arrangement including means for applying weighting to the signals applied as inputs to the cells of at least the first stage, characterised in that means are provided for generating a reference signal being a representation of the desired signal output, each stage including a further decorrelation cell which in the first stage has as one input the reference signal and as a second input the output of the remaining antenna element and the further cell of each succeeding stage having as one input the output of the further cell in the preceding stage and as a second input the output from the remaining cell of the preceding stage, means for subtracting a delayed version of the reference signal from the output of the last stage and feedback means whereby the difference signal so obtained is used to generate the succeeding reference signal.
The invention will now be described with reference to the accompanying drawings, in which:
Fig. 1 illustrates an adaptive antenna arrangement to allow the inclusion of reference signals,
Figs. 2(i) and (ii) illustrate circuits for reference signal generation,
Fig. 3 illustrates a simplified adaptive antenna arrangement using a spread spectrum reference signal,
Fig. 4 illustrates a sequential decorrelator arrangement incorporating a reference signal,
Fig. 5 illustrates a systolic QR processor incorporating a reference signal, and
Fig. 6 illustrates acquisition and data detection performance using a systolic QR processor.
Consider the scheme shown by Figure 1. Signals from the antenna elements 10a-l0n are weighted and then combined in combiner 11 with the reference signal, r(t).
The adaptively controlled weights are adjusted to minimise the mean square residual from the combiner 11 corresponding to the minimum error residue between the reference and the combined element signals. The requisite beamformed response is obtained by subtracting the reference signal from the error residual.The residual from the combiner is:
e(t) = wTx(t) + r(t) ... (1) and the mean square of the residual is represented by
* T P = E e (t) e(t) = E E(w X(t) + * = E T0 r(t)) (w x(t) + r(t)) -
= E [WHX* (t) xT (t) W) + E [WHX* (t) r(t)
+ E [r (t) X (t) W + E [r*(t) r(t) = WH E Ex (t) xT (t)] W
* + / E [X* (t) r(t)
+ E Er (t) XT(t)] W + E [r*(t) r(t)]
...(2) where E[.] denotes the expectation operator.
The complex gradient of PO is: #Po= 2. [E [X* (t) XT (t)]. W - E
[X* (t). r(t))]] ...(3) and the optimal weight solution is obtained when #PO = O and is therefore given by: E CX (t) XT(t)] W = E Ex* (t) r(t) ... (4) This weight solution when applied to the antenna
element signals produces a resultant beamformed response which is the closest replica of the injected reference in
the least-squares sense.
The beamformer shown in Figure 1 could be
controlled adaptively by a closed loop processor which
attempts to minimise the error residual by a gradient descent algorithm This technique is known to have a poor convergence characteristic under adverse signal and
jamming conditions. Alternatively, the weight vector
could be solved by an "open-loop".approach where Maximum
Likelihood estimates of the covariance components are used instead of the values contained in the matrices
* T *
E Ex (t) X (t) and E CX (t) r(t). The direct
solution vector is then given by:
(XnHXn)W = XHnr ... (5) where Xn and r contain n time samples of X(t) and r(t) respectively.
It is well known that the solution to equations
(4) and (5) can be obtained by cascade adaptive beamforming architectures. For example, the general type of problem described by equation (4) is solved in the -steady-state by the Sequential Decorrelator, originally proposed by McQueen, J.G., "Adaptive Cancellation
Arrangement", UK Patent Specification No. 1,599,035.
Alternatively, the true least-squares solution of
equation (5) can be solved by a data domain algorithm
known as QR decomposition. This latter method can be
implemented in an efficient, pipelined systolic array.
For the generation of the reference signal
consider that the desired signal is bi-phase modulated by
a direct sequence outer PRN code and an attempt is made
to remove this at the array output by the injection of a
locally generated code, as shown by Figure 2(i). If the
local code is in perfect alignment with the received code
the desired signal at the output from the mixer 20 will be compressed in bandwidth, from that appropriate to the
code chipping rate to that of the underlying data
modulation. The mixer output may therefore be passed
through a narrow bandpass filter 21. The width of this
filter is constrained by the bandwidth of the data
modulation or the uncertainty in the Doppler shift of the
received carrier, whichever is the greater. If the data modulation also takes the form of biphase shift keying
the desired signal will have a constant amplitude at this point. It may then be fed to a bandpass limiter 22 and
remodulated by the local PRN code to produce a suitable
reference signal.
Initially there will be a timing offset between
the locally generated and received codes. We must
therefore slip the local code relative to the received
code until the correlation occurs. When the two codes
are misaligned by more than one chip there will be no
effective correlation, and the output from the reference
generation circuit will be meaningless. However, as soon as the two codes are within one chip of perfect alignment
the output signal from the reference signal generation circuit will begin to take on the correct form to assist
the convergence of the adaptive array. Provided that the -local and received codes are not slipping past each other
at too fast a rate the adaptive algorithm should move
appreciably towards convergence before the codes pass out
of alignment again.Provided this leads to an adequate
signal-to-noise ratio for detection of the correlation we
may discontinue the code slip. Thereafter the local and
received codes may be kept in alignment with the aid of a
code tracking loop.
Provided the jammers do not have a knowledge of
the outer PRN code they will not be able to capture the
reference signal generation circuit in preference to the
desired signal. This is because, even if the jammer is
of constant amplitude, the effect of the code injection
mixer and subsequent narrow bandpass filter will be to
induce amplitude fluctuations in the jamming waveform.
This waveform will therefore have a time-dependent
amplitude at the input to the circuit designed to
preferentially select the component with constant
amplitude.
Figure 3 shows a simplified block diagram of the
total system. Here the antenna signals and reference
signal are applied to the adaptive combiner 30. A
delayed version of this reference is subtracted from the
error residual produced at the output of the combiner and
the resulting signal corresponds to the "beamformed"
response. This is used to (i) generate the next
reference signal sample and (ii) aid code generation and
tracking.
The delay 31 imposed on the reference signal is
necessary due to the throughput or pipeline delay through
the adaptive processor. This is usually of the order of
2N data samples where N is the size of the array. The
throughput delay also means that a forward prediction of
the locally generated PRN code must be used within the
reference generation circuit (see figure 2ii) so that, once acquired, the timing of the injected reference
signal will be in exact alignment with the received -code. Because we are now in effect using "old" data modulation to estimate the current desired signal, we must ensure that the time constant of the adaptive process is significantly long to prevent adaptation within a data bit period. Figure 2(ii) shows the revised spread spectrum reference generation circuit for use with adaptive beamforming architectures having an appreciable throughput delay.The code generator 23 must now provide a punctual code P and an advance code A.
It can be shown that the Sequential Decorrelator adapts to a steady-state condition which provides an effective weighting transformation identical to the linearly constrained adaptive combiner illustrated in
Figure 1.
Figure 4 shows a simplified block diagram of a
Sequential Decorrelator incorporating a reference signal. The reference is applied to the right hand input and the process of the decorrelation cells DC produces, at steady-state, a minimised residual power from the beamformer. A delayed version of the reference signal is then subtracted from the network output to obtain the desired beamformed response. The additional delay 40 is matched to the throughput delay imposed by the Sequential
Decorrelation process.
A systolic QR processor arrangement incorporating a reference signal is shown in Figure 5.
As with the Sequential Decorrelator, the reference signal is applied to the right-hand input and then a delayed version is subtracted from the error residual sequence.
The delay 50 must be matched to the pipeline delay through the systolic network.
Figure 6 illustrates the code acquisition performance of this scheme obtained by computer simulation. In this example, the desired signal was modelled as- a biphase, PRN sequence with random data modulation applied at a rate some 200 times slower than the chipping rate of the direct sequence outer code. The local code generator was initially set 2 chips out of alignment and then slipped at a rate of 0.001 chips/ sample to allow the tracking loop to lock. A 2 element adaptive antenna has been considered receiving signals from the desired source at a relative strength of -30 dB and a single jammer at O dB. The jammer and desired signal were spaced by 350 in angle.
The top curve shows the misalignment of the locally generated code as the beamformer adapts and the code tracking loop pulls in. The lower curves indicate the transmitted data sequence and the detected data sequence. In this example, the tracking loop bandwidth and sliprate were selected such that code acquisition would not be obtained without the adaptive antenna process.
Claims (4)
1. An adaptive antenna array comprising a plurality of antenna elements the outputs of which feed a cascaded beamforming network having a succession of stages, each stage including a group of signal decorrelation cells, the group in each stage having one less cell than the group of the preceding stage and the first stage group having one less cell than the number of antenna elements, each cell of the first stage having as one input the output of a respective antenna element and as a second input the output of the remaining antenna element to produce an output signal and each cell of each subsequent stage having as one input the output of a respective cell of the preceding stage and as a second input the output from the remaining cell of the preceding stage to produce an output signal, the whole arrangement including means for applying weighting to the signals applied as inputs to the cells of at least the first stage, characterised in that means are provided for generating a reference signal being a representation of the desired signal output, each stage including a further decorrelation cell which in the first stage has as one input the reference signal and as a second input the output of the remaining antenna element and the further cell of each succeeding stage having as one input the output of the further cell in the preceding stage and as a second input the output from the remaining cell of the preceding stage, means for subtracting a delayed version of the reference signal from the output of the last stage and feedback means whereby the difference signal so obtained is used to generate the succeeding reference signal.
2. An adaptive antenna array according to claim 1 characterised in that the array includes signal tracking means to which the difference signal is applied, the output of the signal tracking means controlling the timing of the generation of the reference signal.
3. An adaptive antenna array according to claim 1 or 2 wherein the beamforming network is implemented as a systolic QR processor arrangement.
4. An adaptive antenna array substantially as described with reference to the accompanying drawings.
Priority Applications (1)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
GB8428889A GB2213994B (en) | 1984-11-15 | 1984-11-15 | Adaptive antennas |
Applications Claiming Priority (1)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
GB8428889A GB2213994B (en) | 1984-11-15 | 1984-11-15 | Adaptive antennas |
Publications (3)
Publication Number | Publication Date |
---|---|
GB8428889D0 GB8428889D0 (en) | 1989-04-19 |
GB2213994A true GB2213994A (en) | 1989-08-23 |
GB2213994B GB2213994B (en) | 1990-03-28 |
Family
ID=10569781
Family Applications (1)
Application Number | Title | Priority Date | Filing Date |
---|---|---|---|
GB8428889A Expired - Lifetime GB2213994B (en) | 1984-11-15 | 1984-11-15 | Adaptive antennas |
Country Status (1)
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GB (1) | GB2213994B (en) |
Cited By (2)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
GB2265053A (en) * | 1992-03-11 | 1993-09-15 | Roke Manor Research | Digital signal receiver and signal processor. |
DE4039153B4 (en) * | 1989-12-08 | 2006-09-07 | Thomson - Csf | Method and device for generating a radiation pattern at rest in a group antenna |
-
1984
- 1984-11-15 GB GB8428889A patent/GB2213994B/en not_active Expired - Lifetime
Cited By (3)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
DE4039153B4 (en) * | 1989-12-08 | 2006-09-07 | Thomson - Csf | Method and device for generating a radiation pattern at rest in a group antenna |
GB2265053A (en) * | 1992-03-11 | 1993-09-15 | Roke Manor Research | Digital signal receiver and signal processor. |
GB2265053B (en) * | 1992-03-11 | 1995-11-01 | Roke Manor Research | Digital signal receiver and communications systems |
Also Published As
Publication number | Publication date |
---|---|
GB2213994B (en) | 1990-03-28 |
GB8428889D0 (en) | 1989-04-19 |
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Legal Events
Date | Code | Title | Description |
---|---|---|---|
732E | Amendments to the register in respect of changes of name or changes affecting rights (sect. 32/1977) | ||
732E | Amendments to the register in respect of changes of name or changes affecting rights (sect. 32/1977) | ||
732E | Amendments to the register in respect of changes of name or changes affecting rights (sect. 32/1977) | ||
PCNP | Patent ceased through non-payment of renewal fee |