EP4736303A1 - Extending the output voltage range of a converter - Google Patents

Extending the output voltage range of a converter

Info

Publication number
EP4736303A1
EP4736303A1 EP24736007.6A EP24736007A EP4736303A1 EP 4736303 A1 EP4736303 A1 EP 4736303A1 EP 24736007 A EP24736007 A EP 24736007A EP 4736303 A1 EP4736303 A1 EP 4736303A1
Authority
EP
European Patent Office
Prior art keywords
secondary winding
converter
switch
lsl
output voltage
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Pending
Application number
EP24736007.6A
Other languages
German (de)
French (fr)
Inventor
Reinhold Elferich
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Signify Holding BV
Original Assignee
Signify Holding BV
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Signify Holding BV filed Critical Signify Holding BV
Publication of EP4736303A1 publication Critical patent/EP4736303A1/en
Pending legal-status Critical Current

Links

Classifications

    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of DC power input into DC power output
    • H02M3/01—Resonant DC/DC converters
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0048—Circuits or arrangements for reducing losses
    • H02M1/0054—Transistor switching losses
    • H02M1/0058—Transistor switching losses by employing soft switching techniques, i.e. commutation of transistors when applied voltage is zero or when current flow is zero
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of DC power input into DC power output
    • H02M3/22—Conversion of DC power input into DC power output with intermediate conversion into AC
    • H02M3/24—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters
    • H02M3/28—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC
    • H02M3/325—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/33569—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements
    • H02M3/33571—Half-bridge at primary side of an isolation transformer
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of DC power input into DC power output
    • H02M3/22—Conversion of DC power input into DC power output with intermediate conversion into AC
    • H02M3/24—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters
    • H02M3/28—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC
    • H02M3/325—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/33569—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements
    • H02M3/33576—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements having at least one active switching element at the secondary side of an isolation transformer
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of AC power input into DC power output; Conversion of DC power input into AC power output
    • H02M7/02—Conversion of AC power input into DC power output without possibility of reversal
    • H02M7/04—Conversion of AC power input into DC power output without possibility of reversal by static converters
    • H02M7/06—Conversion of AC power input into DC power output without possibility of reversal by static converters using discharge tubes without control electrode or semiconductor devices without control electrode
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0067—Converter structures employing plural converter units, other than for parallel operation of the units on a single load
    • H02M1/0077—Plural converter units whose outputs are connected in series

Landscapes

  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Dc-Dc Converters (AREA)

Abstract

A converter comprising a transformer. A secondary winding of the transformer is split into two secondary winding portions. A switch arrangement selectively connects these two secondary winding portions in series or in parallel. The converter is configured such that the secondary winding portions contribute to an output voltage of the converter in different half cycles of an alternating current or voltage provided to the transformer.

Description

EXTENDING THE OUTPUT VOLTAGE RANGE OF A CONVERTER
FIELD OF THE INVENTION
The present invention relates to the field of converters.
BACKGROUND OF THE INVENTION
A converter is an electronic arrangement configured to convert a voltage and/or current of an (input) electrical power. Converters are generally designed to drive a load, such as an LED or LED arrangement. It is typical for a converter to comprise a transformer, formed of a pair of magnetically coupled windings. This achieves safety isolation.
A resonant converter is a particular type of electrical power converter that contains an arrangement of inductors and capacitors configured to resonate at particular frequencies. The windings of any transformer in such a resonant converter can form part of the resonant circuit, as well as performing the function of safety isolation.
One known type of resonant converter is an LLC converter. This shows a higher efficiency than an LCC converter and benefits from wide bandgap transistor technologies in terms of the potential size and loss reductions.
There is an ongoing desire to increase the output voltage range of a converter. For instance, an LLC converter can exhibit a hard limit for the minimum output voltage below which it cannot supply any load. One way to obtain a wide output voltage range is to use a further power stage.
It would be desirable to increase the output voltage range of a converter without the need for an additional and/or separate component or power stage, to provide a compact device and reduce material usage.
SUMMARY OF THE INVENTION
The invention is defined by the claims.
According to examples in accordance with an aspect of the invention, there is provided a converter for providing an output voltage. The converter comprises: a transformer comprising a primary winding and a secondary winding magnetically coupled together, the secondary winding being sub-divided into a first secondary winding and a second secondary winding, wherein a voltage between a first end of the first secondary winding and a first end of the second secondary winding defines the output voltage; and a switch arrangement configured to controllably switch the first secondary winding and the second secondary winding between being connected in parallel and being connected in series.
When an alternating current flows through the primary winding, the first secondary winding and second secondary winding are configured to alternately contribute to the output voltage.
The present invention provides a converter with an AC -DC portion that performs bidirectional rectification using separate portions of the secondary winding of a transformer. In particular the secondary winding of a transformer is sub-divided or split into two portions, with the connection(s) being appropriately configured such that the two portions of the secondary winding contribute to the output voltage during different halfcycles of the alternating current.
The present invention also advantageously allows for an increase in the voltage range of the output voltage. The voltage range for the output voltage, when the two parts of the secondary winding are connected in series, is different to when the two parts of the secondary winding are connected in parallel. By facilitating the selective connection of the two parts of the secondary winding (between being in series and being in parallel), an improved overall voltage range can be achieved.
In some examples, the first end of the second secondary winding is connected to a ground or reference voltage.
The switch arrangement may comprise a switch having: a first switch end connected to a second end of the first secondary winding and; a second switch end connected to a second end of the second secondary winding. In the context of the present invention, a first end and a second end of a winding are opposite ends of the winding. Thus, the first end of each winding is different to the second end of each winding. The connection between the switch and the end(s) of the first/secondary winding(s) may be via one or more further electrical components, such as diodes.
The converter may further comprise a first diode connected from the second end of the second secondary winding to the switch. The converter may further comprise a second diode connected from the switch to the second end of the first secondary winding.
The converter may further comprise a third diode connected from the first end of the second secondary winding to the second end of the first secondary winding.
The converter may further comprise a fourth diode connected from the second end of the second secondary winding to the first end of the first secondary winding.
The converter may further comprise a first capacitor connected between the first switch end and the first end of the first secondary winding.
The converter may further comprise a second capacitor connected between the second switch end and the first end of the second secondary winding.
The converter may further comprise an output capacitor connected between the first end of the first secondary winding and the first end of the second secondary winding.
The converter may further comprise a switch controller configured to control the operation of the switch arrangement.
The switch controller may be configured to: monitor the output voltage; responsive to the output voltage exceeding a first voltage level, control the switch arrangement to connect the first secondary winding and the second secondary winding in parallel; and responsive to the output voltage falling below a second voltage level, control the switch arrangement to connect the first secondary winding and the second secondary winding in series.
Thus, the converter may be adapted to dynamically respond to changes in demand for the output voltage by changing the effective voltage range of the output voltage, i.e., changing whether the secondary windings are connected in series or in parallel. This facilitates automated control and provision of the enhanced voltage range for the output voltage.
In some examples, the first voltage level is greater than the second voltage level. This provides hysteretic control over the operation of the converter. In particular, this can avoid repeated changes in the operation of the switch arrangement due to fluctuations in the demand for the output voltage, e.g., natural or known fluctuations such as those caused by noise or minor changes in the task of a load drawing from the output voltage. This improves the efficiency of the converter and reduces noise, e.g., reduces switching noise.
The converter may comprise a resonant tank. For instance, the resonant tank may be an LLC resonant tank. The converter may comprise a switch network configured to controllably connect a DC power to the resonant tank.
These and other aspects of the invention will be apparent from and elucidated with reference to the embodiment s) described hereinafter.
BRIEF DESCRIPTION OF THE DRAWINGS
For a better understanding of the invention, and to show more clearly how it may be carried into effect, reference will now be made, by way of example only, to the accompanying drawings, in which:
Figure 1 illustrates a portion of a proposed converter; and
Figure 2 illustrates a proposed converter.
DETAILED DESCRIPTION OF THE EMBODIMENTS
The invention will be described with reference to the Figures.
It should be understood that the detailed description and specific examples, while indicating exemplary embodiments of the apparatus, systems and methods, are intended for purposes of illustration only and are not intended to limit the scope of the invention. These and other features, aspects, and advantages of the apparatus, systems and methods of the present invention will become better understood from the following description, appended claims, and accompanying drawings. It should be understood that the Figures are merely schematic and are not drawn to scale. It should also be understood that the same reference numerals are used throughout the Figures to indicate the same or similar parts.
The invention provides a converter comprising a transformer. A secondary winding of the transformer is split into two secondary winding portions. A switch arrangement selectively connects these two secondary winding portions in series or in parallel. The converter is configured such that the secondary winding portions contribute to an output voltage of the converter in different half cycles of an alternating current or voltage provided to the transformer.
Figure 1 illustrates a portion of a converter 100 for providing an output voltage Vo. More particular, the portion converts an alternating voltage VAC into the (DC) output voltage Vo.
The converter comprises a transformer 110 comprising a primary winding Lp and a secondary winding Lsl, Ls2 magnetically coupled together. The secondary winding is sub-divided into a first secondary winding Lsl (or first secondary winding portion) and a second secondary winding Ls2 (or a second secondary winding portion). For ease of reference, the sub-divided parts of the secondary winding Lsl, Ls2 are referred to as separate secondary windings, although it will be appreciated that they are different parts or portions of a same secondary winding (e.g., analogously to a tapped secondary winding).
A voltage Vo between a first end Lsl A of the first secondary winding Lsl and a first end Ls2A of the second secondary winding Ls2 defines the output voltage Vo.
For the sake of later reference, components of the converter that are electronically coupled to the first Lsl and second Ls2 secondary windings can be together referred to as secondary side circuitry 150. The secondary side circuitry 150 produces the output voltage Vo for provision to a load.
The converter 100 also comprises a switch arrangement SI, 120 configured to controllably switch the first secondary winding Lsl and the second secondary winding Ls2 between being connected in parallel and being connected in series.
The converter is adapted such that, when an alternating current VAC flows through the primary winding Lp, the first secondary winding Lsl and second secondary winding Ls2 are configured to alternately contribute to the output voltage Vo.
Thus, the first Lsl and second Ls2 secondary windings are connected to the first end Lsl A of the first secondary winding Lsl such that, with respect to said first end Lsl a, the secondary windings Lsl, Ls2 have opposite winding directions. Put yet another way, the first and second secondary windings are configured such that: a current flow into a first end of the primary winding will cause a current to flow from only the first secondary winding (and not the second secondary winding) to contribute to the output voltage; and a current flow into a second end of the primary winding will cause a current to flow from only the second secondary winding (and not the first secondary winding) to contribute to the output voltage.
Example winding directions of the first and second secondary windings are illustrated in Figure 1 using dot notation. However, the winding direction of both the first and second secondary windings may be opposite (to that illustrated) in other examples.
The first end of the second secondary winding is connected to a ground or reference voltage GND. The illustrated switch arrangement comprises a switch SI having a first switch end s connected to a second end LslB of the first secondary winding and a second switch end d connected to a second end Ls2B of the second secondary winding. The switch SI may, for instance, be a MOSFET or similar switch.
The converter further comprises a first diode DI connected from the second end Ls2B of the second secondary winding Ls2 to the switch SI, i.e., to the second switch end d. More particularly, the anode of the first diode DI connects to the second end Ls2B of the second secondary winding Ls2 and the cathode of the first diode DI connects to the second switch end d.
The converter further comprises a second diode D2 connected from the switch SI to the second end LslB of the first secondary winding Lsl. Thus, the second diode D2 connects from the first switch end s to the second end LslB of the first secondary winding Lsl. More particularly, the anode of the second diode D2 is connected to the first switch end s and the cathode of the second diode D2 is connected to the second end LslB of the first secondary winding Lsl .
The converter further comprises a third diode D3 connected from the first end Ls2A of the second secondary winding Ls2 to the second end LslB of the first secondary winding Lsl. More particularly, the anode of the third diode is connected to the first end Ls2A of the second secondary winding (which is here coupled to a ground/reference voltage GND), and the cathode of the third diode D3 is connected to the second end LslB of the first secondary winding Lsl .
The converter further comprises a fourth diode D4 connected from the second end Ls2B of the second secondary winding Ls2 to the first end Lsl A of the first secondary winding Lsl. More particularly, the anode of the fourth diode is connected to the second end Ls2B of the second secondary winding Ls2 and the cathode of the fourth diode D4 is connected to the first end Lsl A of the first secondary winding Lsl.
The second diode D2 and third diode D3 thereby define a common anode rectifier node at the second end LslB of the first secondary winding Lsl. The first diode DI and fourth diode D4 define a common cathode rectifier node at the second end Ls2B of the second secondary winding Ls2.
The converter comprises a first capacitor Col2 and/or a second capacitor Co22. If present, the first capacitor Col2 is connected between the first switch end s and the first end Lsl A of the first secondary winding Lsl. If present, the second capacitor Co22 is connected between the second switch end d and the first end Ls2A of the second secondary winding Ls2.
Use of both the first and second capacitors reduces a ripple in the output voltage Vo. However, one of these capacitors can be omitted if such a ripple is acceptable and/or a more compact converter is desired.
The converter further comprises an output capacitor Co connected between the first end LslA of the first secondary winding Lsl and the first end Ls2A of the second secondary winding Ls2. Thus, the output capacitor connects between the first end LslA of the first secondary winding and a ground GND.
The proposed converter is operable in a series connection mode and a parallel connection mode. When operating in the series-connection mode, the switch SI is conductive (i.e., closed) and the first and second secondary windings are effectively connected in series. When operating in the parallel connection mode, the switch SI is non-conductive (i.e., open) and the first and second secondary windings are effectively connected in series.
Discounting all other operating procedures or changes, and assuming the number of turns is the same in the first and second secondary windings is the same, when the converter is operated in the series-connection mode, the output voltage is effectively double that of the output voltage when the converter operates in the parallel-connection mode (discounting any voltage drops across the diode(s)).
One advantage of the proposed converter is to increase the potential range of the output voltage, i.e., the operational range of the output voltage.
Another advantage of the proposed converter is that the portion achieves bidirectional rectification of the alternating voltage VAC in producing the output voltage Vo. This advantageously achieves improved efficiency in converting an alternating voltage, e.g., compared to a unidirectional rectification, and facilitates increased flexibility in use and selection of other components of the converter.
The operation of the illustrated converter will be hereafter described, for the purposes of improved contextual understanding. However, the skilled person will readily appreciate how the operation will change for different variants (e.g., if the winding directions of the first and second secondary windings are reversed). For explanative purposes, any nonideal effects (e.g., diode voltage drops) are ignored, although the skilled person will readily appreciate how this can affect the performance of the converter.
The alternating voltage VAC alternates between a first half cycle, in which a current flow enters the dotted end LpA of the primary winding Lp, and a second half cycle, in which a current flow reverses and exits the dotted end LpA of the primary winding Lp (i.e., enters a non-dotted end LpB).
When the converter operates in the parallel connection mode (i.e., the switch SI is open), during the first half cycle of the alternating voltage, a current is induced to flow out of the second end Ls2B of the second secondary winding Ls2. This current is passed through the fourth diode D4 to charge the output capacitor Co. During the second half cycle of the alternating voltage, a current is induced to flow out of the first end Lsl A of the first secondary winding Lsl, which charges the output capacitor.
The output capacitor Co is thereby (directly) charged in both half cycles of the alternating current VAC. Due to the smoothing nature of the output capacitor Co, the voltage across the output capacitor Co is effectively the average of the maximum voltage output by the second secondary winding during the first half cycle of the alternating current and the maximum voltage output by the first secondary winding during the second half cycle of the alternating current.
When the converter operates in the series connection mode (i.e., the switch SI is closed), then during a first half cycle of the alternating current VAC, the alternating current VAC causes a current to flow out of the second end Ls2B of the second secondary winding Ls2, which passes through to charge the second capacitor Co22 and/or a second plate P12 of the first capacitor Col2. During a second half cycle of the alternating current VAC, the current flow of the alternating current will cause a current to flow out of the first end Lsl A of the first secondary winding Lsl which charges the first plate Pl 1 of the first capacitor Co 12 and the output capacitor Co. The voltage across the output capacitor Co is thereby the sum of the voltage output by the second secondary winding during the first half cycle of the alternating current and the voltage output by the first secondary winding during the second half cycle of the alternating current.
In both connection modes, during the first-half cycle, the second diode D2 and third diode D3 act as blocking diodes to prevent current flow through the first secondary winding. Similarly, during the second half-cycle, the first diode DI and fourth diode D4 act as blocking diodes to prevent current flow through the second secondary winding.
The proposed approach thereby facilitates switching between the parallel connection mode and the series connection mode to effectively extend the range of the output voltage.
Accordingly, the converter 100 may further comprise a switch controller 120 configured to (dynamically) control the operation of the switch arrangement. By way of example, the switch controller 120 may control a gate voltage of the switch SI, to thereby control whether or not the switch SI is conductive. This controls whether the converter 100 operates in the series connection mode or the parallel connection mode.
The switch controller 120 may be configured to control the operation of the switch arrangement responsive to the output voltage Vo. The output voltage Vo is generally controlled to achieve a voltage desired or demanded by a load (not shown). The value of the output voltage Vo may, for instance, be achieved by controlling the magnitude of the alternating voltage VAC.
In particular, the switch controller 120 may be configured to, responsive to the output voltage Vo exceeding a first voltage level, control the switch arrangement to connect the first secondary winding and the second secondary winding in parallel (i.e., configure the converter to operate in the parallel connection mode).
The switch controller 120 may also be configured to, responsive to the output voltage falling below a second voltage level, control the switch arrangement to connect the first secondary winding and the second secondary winding in series (i.e., configure the converter to operate in the series connection mode).
The switch controller 120 may perform hysteretic operation. Thus, the first voltage level may be greater than the second voltage level. This reduces or minimizes an effect of repeated mode switching, e.g., due to expected variations in the output voltage (e.g., due to temperature variations or small changes in load demand). This can improve the performance and reduce the noise of the controller.
The switch SI can be a transistor of any type, such as a MOSFET. In particular examples, the body diode of a MOSFET forming the switch SI is connected in anti-series with the first diode DI and the second diode D2. By way of example, an n-channel MOSFET is preferably connected with its source to the anode of D2, whereas the source of a p-channel MOSFET would instead be connected to the cathode of DI.
In some preferred examples, the reverse voltage of the switch is preferably more than half the maximum output voltage Vo.
Although each diode is illustrated as a two-terminal diode, it will be appreciated that any one or more of the diodes (if present) can be replaced by an appropriately controlled switch or transistor, e.g., a synchronously controlled switch or synchronous rectifier. This are controlled to perform the function of diodes whilst reducing conduction losses (e.g., reducing the effect of a voltage drop across the diode). The term “diode”, in the context of the present disclosure, is therefore used to refer to both traditional diodes and actively controlled switches that are controlled to behave as a diode.
Figure 2 illustrates additional components of the converter 100 according to an example. More particularly, Figure 2 further illustrates an example of primary side circuitry for the converter 100, being circuitry connected to the primary side (i.e., the primary winding Lp) of the transformer 110.
In particular, the converter 100 may comprise a resonant tank 210 configured to produce the alternating voltage VAC to pass through the first winding. The resonant tank 210 may comprise an LLC resonant tank, e.g., comprising appropriately positioned and configured capacitors Csl, Cs2 and inductors Lp, Lsl, Ls2 (which may also form part of the transformer 110).
The converter 100 may further comprise a switch network 220 configured to controllably connect a DC power Vb to the resonant tank. The switch network 220 comprises a high side switch S2 and a low side switch S3, wherein a switch network output is defined from a switch output node 221 between the switches. The resonant tank is connected to the switch output node 221 to drive the transformer 110. The high side switch S2 controllably connects the switch output node 221 to a high voltage node 222. The low side switch controllably connects the switch output node 221 to a low voltage node 223. The voltage Vb between the high voltage node 222 and the low voltage node 223 is a DC voltage (e.g., a rectified mains voltage).
In use, each switch SI, S2 of the switch network 220 has its timing of operation controlled by its respective switching signal delivered by a switch network controller 230. More particularly, during operation of the converter 100, the switch network controller 230 controls the switches SI, S2, at a particular frequency and in a complementary manner. Feedback may be used to determine the timing of the control of the switches SI, S2, e.g., to achieve a desired output voltage and/or output current.
It will be appreciated that a deadtime (or non-overlap time) may be introduced into each switching signal. Approaches for incorporating deadtime in this way are well known in the art and are not described in detail for the sake of conciseness.
Approaches for controlling a switch network are well established in the art and are not described for the sake of conciseness.
The skilled person would be readily capable of replacing the primary side circuitry illustrated in Figure 2 with any other suitable form of primary side circuitry for a converter. One example would be components for an LCC converter. Variations to the disclosed embodiments can be understood and effected by those skilled in the art in practicing the claimed invention, from a study of the drawings, the disclosure and the appended claims. In the claims, the word "comprising" does not exclude other elements or steps, and the indefinite article "a" or "an" does not exclude a plurality. The mere fact that certain measures are recited in mutually different dependent claims does not indicate that a combination of these measures cannot be used to advantage.
If the term "adapted to" is used in the claims or description, it is noted the term "adapted to" is intended to be equivalent to the term "configured to". If the term "arrangement" is used in the claims or description, it is noted the term "arrangement" is intended to be equivalent to the term "system", and vice versa.
Any reference signs in the claims should not be construed as limiting the scope.

Claims

CLAIMS:
1. A converter for providing an output voltage (Vo), the converter comprising: a transformer comprising a primary winding (Lp) and a secondary winding
(Lsl, Ls2) magnetically coupled together, the secondary winding being sub-divided into a first secondary winding (Lsl) and a second secondary winding (Ls2), wherein a voltage (Vo) between a first end (Lsl A) of the first secondary winding and a first end (Ls2A) of the second secondary winding defines the output voltage; and a switch arrangement comprising a switch (SI) having a first switch end (s) connected to a second end (LslB) of the first secondary winding and a second switch end (d) connected to a second end (Ls2B) of the second secondary winding and wherein the switch arrangement is configured to controllably switch the first secondary winding and the second secondary winding between being connected in parallel and being connected in series, a first diode (DI) connected from the second end (Ls2B) of the second secondary winding to the switch (SI); a second diode (D2) connected from the switch (SI) to the second end (LslB) of the first secondary winding (Lsl); a third diode (D3) connected from the first end (Ls2A) of the second secondary winding (Ls2) to the second end (LslB) of the first secondary winding (Lsl); a fourth diode (D4) connected from the second end (Ls2B) of the second secondary winding (Ls2) to the first end (Lsl A) of the first secondary winding (Lsl); a first capacitor (Co 12) connected between the first switch end (s) and the first end (Lsl A) of the first secondary winding (Lsl), and a second capacitor (Co22) connected between the second switch end (d) and the first end (Ls2A) of the second secondary winding (Ls2), wherein, when an alternating current flows through the primary winding, the first secondary winding and second secondary winding are configured to alternately contribute to the output voltage.
2. The converter of claim 1, wherein the first end of the second secondary winding is connected to a ground or reference voltage (GND).
3. The converter of any of claims 1 or 2, further comprising an output capacitor
(Co) connected between the first end (Lsl A) of the first secondary winding (Lsl) and the first end (Ls2A) of the second secondary winding (Ls2).
4. The converter of any of the preceding claims, further comprising a switch controller configured to control the operation of the switch arrangement, wherein the switch controller is configured to: monitor the output voltage; responsive to the output voltage exceeding a first voltage level, control the switch arrangement to connect the first secondary winding and the second secondary winding in parallel; and responsive to the output voltage falling below a second voltage level, control the switch arrangement to connect the first secondary winding and the second secondary winding in series.
5. The converter of claim 4, wherein the first voltage level is greater than the second voltage level.
6. The converter of any of the preceding claims comprising a resonant tank.
7. The converter of claim 6, wherein the resonant tank is an LLC resonant tank.
8. The converter of any of claims 6 or 7 comprising a switch network configured to controllably connect a DC power to the resonant tank.
EP24736007.6A 2023-06-28 2024-06-24 Extending the output voltage range of a converter Pending EP4736303A1 (en)

Applications Claiming Priority (2)

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EP23182003 2023-06-28
PCT/EP2024/067666 WO2025003069A1 (en) 2023-06-28 2024-06-24 Extending the output voltage range of a converter

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Publication number Priority date Publication date Assignee Title
CN1906837B (en) * 2004-03-18 2011-02-23 三井物产株式会社 DC-DC converter
US10944329B2 (en) * 2018-01-15 2021-03-09 Queen's University At Kingston Power converter topologies and control methods for wide input and output voltage ranges
CN112701918A (en) * 2020-12-18 2021-04-23 国创新能源汽车智慧能源装备创新中心(江苏)有限公司 Control circuit for wide-range output of LLC converter
CN112928919B (en) * 2021-01-15 2022-04-22 西安交通大学 Isolated high-frequency resonant DC-DC converter with wide output voltage range and method
CN114079384B (en) * 2021-11-02 2024-05-07 西安交通大学 A variable structure LLC converter with wide output voltage range and method

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