EP2814161B1 - Power stage precharging and dynamic braking apparatus for multilevel inverter - Google Patents
Power stage precharging and dynamic braking apparatus for multilevel inverter Download PDFInfo
- Publication number
- EP2814161B1 EP2814161B1 EP14163824.7A EP14163824A EP2814161B1 EP 2814161 B1 EP2814161 B1 EP 2814161B1 EP 14163824 A EP14163824 A EP 14163824A EP 2814161 B1 EP2814161 B1 EP 2814161B1
- Authority
- EP
- European Patent Office
- Prior art keywords
- circuit
- power
- bus
- resistor
- switching
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Active
Links
- 239000003990 capacitor Substances 0.000 claims description 34
- 238000000034 method Methods 0.000 claims description 24
- 238000006243 chemical reaction Methods 0.000 claims description 15
- AKXUUJCMWZFYMV-UHFFFAOYSA-M tetrakis(hydroxymethyl)phosphanium;chloride Chemical compound [Cl-].OC[P+](CO)(CO)CO AKXUUJCMWZFYMV-UHFFFAOYSA-M 0.000 claims description 12
- 238000004804 winding Methods 0.000 description 10
- 230000006870 function Effects 0.000 description 8
- 230000008569 process Effects 0.000 description 8
- 239000004065 semiconductor Substances 0.000 description 7
- 238000010586 diagram Methods 0.000 description 6
- 230000007935 neutral effect Effects 0.000 description 6
- 238000004146 energy storage Methods 0.000 description 3
- 230000003750 conditioning effect Effects 0.000 description 2
- 230000007274 generation of a signal involved in cell-cell signaling Effects 0.000 description 2
- XUIMIQQOPSSXEZ-UHFFFAOYSA-N Silicon Chemical compound [Si] XUIMIQQOPSSXEZ-UHFFFAOYSA-N 0.000 description 1
- 230000004075 alteration Effects 0.000 description 1
- 230000003321 amplification Effects 0.000 description 1
- 230000000712 assembly Effects 0.000 description 1
- 238000000429 assembly Methods 0.000 description 1
- 230000000903 blocking effect Effects 0.000 description 1
- 230000001419 dependent effect Effects 0.000 description 1
- 238000007599 discharging Methods 0.000 description 1
- 235000019800 disodium phosphate Nutrition 0.000 description 1
- 230000009977 dual effect Effects 0.000 description 1
- 238000009499 grossing Methods 0.000 description 1
- 230000001939 inductive effect Effects 0.000 description 1
- 238000012986 modification Methods 0.000 description 1
- 230000004048 modification Effects 0.000 description 1
- 238000003199 nucleic acid amplification method Methods 0.000 description 1
- 230000010363 phase shift Effects 0.000 description 1
- 230000001172 regenerating effect Effects 0.000 description 1
- 238000009877 rendering Methods 0.000 description 1
- 229910052710 silicon Inorganic materials 0.000 description 1
- 239000010703 silicon Substances 0.000 description 1
Images
Classifications
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
- H02P3/00—Arrangements for stopping or slowing electric motors, generators, or dynamo-electric converters
- H02P3/06—Arrangements for stopping or slowing electric motors, generators, or dynamo-electric converters for stopping or slowing an individual dynamo-electric motor or dynamo-electric converter
- H02P3/18—Arrangements for stopping or slowing electric motors, generators, or dynamo-electric converters for stopping or slowing an individual dynamo-electric motor or dynamo-electric converter for stopping or slowing an ac motor
- H02P3/22—Arrangements for stopping or slowing electric motors, generators, or dynamo-electric converters for stopping or slowing an individual dynamo-electric motor or dynamo-electric converter for stopping or slowing an ac motor by short-circuit or resistive braking
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M5/00—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases
- H02M5/40—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc
- H02M5/42—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc by static converters
- H02M5/44—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc by static converters using discharge tubes or semiconductor devices to convert the intermediate dc into ac
- H02M5/453—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc by static converters using discharge tubes or semiconductor devices to convert the intermediate dc into ac using devices of a triode or transistor type requiring continuous application of a control signal
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
- H02P27/00—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage
- H02P27/04—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage
- H02P27/06—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage using dc to ac converters or inverters
- H02P27/08—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage using dc to ac converters or inverters with pulse width modulation
- H02P27/14—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage using dc to ac converters or inverters with pulse width modulation with three or more levels of voltage
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
- H02P3/00—Arrangements for stopping or slowing electric motors, generators, or dynamo-electric converters
- H02P3/06—Arrangements for stopping or slowing electric motors, generators, or dynamo-electric converters for stopping or slowing an individual dynamo-electric motor or dynamo-electric converter
- H02P3/18—Arrangements for stopping or slowing electric motors, generators, or dynamo-electric converters for stopping or slowing an individual dynamo-electric motor or dynamo-electric converter for stopping or slowing an ac motor
Definitions
- Power converters are used to convert input electrical energy from one form to another for driving a load.
- One form of power conversion system is a motor drive, which may be employed for variable speed operation of an electric motor load.
- Multilevel inverters such as Cascaded H-Bridge (CHB) inverters are sometimes employed in motor drives and other power conversion systems to generate and provide high voltage drive signals, with individual power cells or power stages being connected in series. Each stage provides a separate DC source and is driven by switch signals to generate positive or negative output voltage, with the series combination of multiple stage outputs providing multilevel inverter output capability for driving the load at variable speeds and torques.
- CHB Cascaded H-Bridge
- WO 2010/022765 A1 relates to a drive unit for comprising: a control power supply for supplying the drive unit with control power, a power source producing direct current to one or more inverters, at least one inverter producing current to the motor, an energy storage arranged at the output of the power source for smoothing direct current and storing energy recovered during braking of the motor, and a discharge circuit for discharging the energy stored in said energy storage, wherein the discharge circuit includes a power resistor arranged to discharge the energy stored in the energy storage.
- US 2004/0160792 A1 describes a motor power supply having an inrush current protection mode, a motor driver mode, an overvoltage protection mode and a dynamic braking mode.
- a first resistance limits an inrush current to a capacitor which smoothes a rectifier output to provide DC power to an inverter during the motor drive mode.
- a controller controls a multi-contact relay and the switching element to implement the various modes of operation.
- EP 2 368 749 A2 discloses a power supply device including a battery, an output switch that connects the battery to a load including a parallel capacitor, and a control circuit that controls the output switch.
- the parallel capacitor of the load is precharged in the precharge state. After the parallel capacitor of the load is precharged, the load is supplied with electric power from the battery with the semiconductor switching element being brought into the electrically conducted state in which the ON resistance of the semiconductor switching element is smaller than the precharge state.
- WO 92/17929 A1 relates to an inductive power distribution system having a current limiting controller for the resonant DC-AC power converter.
- a power conversion system which includes a multilevel inverter with one or more inverter legs each having a plurality of power stages individually providing multiple distinct output voltage levels, as well as a converter system controller providing switching control signals to set the individual output levels of the power stages.
- the individual power stages include a DC bus circuit provided with DC voltage by a rectifier, as well as a switching circuit that provides a power stage output voltage at one of a plurality of distinct levels.
- a precharge and dynamic braking circuit is provided within the individual power stages, including a resistor connected between the rectifier and the switching circuit.
- the precharge and dynamic braking circuit operates in a first mode to conduct current from the rectifier through the resistor to charge the DC bus capacitor, as well as in a second mode to bypass the resistor and allow current to flow from the rectifier to the switching circuit for normal operation.
- the precharge and dynamic braking circuit connects the resistor in parallel with a capacitor to facilitate dynamic braking operation.
- the precharge and dynamic braking circuit includes a first switch coupled in a DC circuit branch between the rectifier and the switching circuit, as well as a first diode coupled in parallel with the first switch.
- the first switch is closed or otherwise rendered conductive to bypass the resistor, and the switches are opened or rendered nonconductive so that precharging current from the rectifier flows through the resistor to charge the capacitor in a precharge operating mode.
- a second switch is coupled between another DC circuit branch and the resistor, with the second switch being open or non-conductive during normal and precharging operation, and the second switch is closed or pulse width modulated during dynamic braking for selective connection of the resistor in parallel with the DC bus capacitor.
- a power stage controller provides control signals to the first and second switches to set the operating mode according to the DC bus voltage of the power stage, such as by setting the circuit to a first or precharge operating mode if the DC bus voltage is less than a first (e.g., lower) threshold, operating in a second or normal mode with the resistor not conducting any current when the DC bus voltage is above the first threshold and below a second (e.g., higher) threshold, and operating in a third or dynamic braking mode when the DC bus voltage exceeds the second threshold.
- a first e.g., lower
- a second e.g., higher
- Methods and non-transitory computer readable mediums are provided with computer executable instructions for operating individual power stages of a multilevel inverter. These techniques include precharging a DC bus capacitance of the power stage through a resistor if the DC bus voltage is less than a first threshold, and connecting the resistor in parallel with the DC bus capacitance if the voltage is greater than a second threshold. In certain embodiments, the resistor is bypassed to allow current flow between the rectifier and the power stage switching circuit if the DC bus voltage is between the first and second threshold values.
- Multilevel inverter power stage architectures are presented in which precharging and dynamic braking functions are achieved using a single shared resistor with switching circuitry in an intermediate DC bus circuit to selectively connect the resistor to control charging of a DC bus capacitance or to connect the resistor in parallel with the DC bus capacitance to facilitate dissipation of back EMF from a driven motor or other load, while further facilitating normal operation with the resistor bypassed.
- Dynamic braking and precharging functionality is a desirable combination of features for cascaded H bridge and other multilevel power converter architectures, and the present disclosure provides simple and effective designs for implementing both functions with localized circuitry within the individual power stages forming the cascaded or series-connected multi-cell structures.
- Dynamic braking apparatus may be used to selectively slow down a motor load being driven by a power converter, and the present disclosure provides selective switching to connect an impedance to dissipate power returning from the motor load as the motor decelerates.
- Precharging is also performed using the same impedance to charge up the DC bus capacitor, for example on startup or after disruption of power, where the DC bus voltage drops below a nominal level.
- Circuitry within the individual power stages is activated when the DC bus voltage is below a predetermined threshold value to charge up the capacitor at a controlled rate by conducting current from the power stage rectifier or other local DC source through the impedance to limit the inrush current to the capacitor thereby protecting the capacitor and charging semiconductor devices against overcurrent conditions.
- the shared resistor is sized so as to reduce the current spike upon charge up to a manageable level, and also to facilitate dynamic braking operation. The circuitry thus presents a significant advance over conventional multilevel inverters by providing both these functions with a minimal number of circuit elements.
- the techniques of the present disclosure find utility in association with low-voltage as well as medium or high voltage power converter applications involving any number of cascaded power stages using on-board circuitry with a shared resistor sized for the power levels associated with the individual power cell or stage.
- FIG. 1 An exemplary multilevel inverter motor drive power conversion system 10 is shown in Fig. 1 , in which the individual power cells or power stages 100 incorporate precharging and dynamic braking circuitry employing a shared resistor.
- the power converter 10 includes a three-phase multilevel inverter 40 with series-connected power stages 100-1, 100-2, 100-3, 100-4, 100-5, 100-6 for each of three sections or inverter legs 102U, 102V and 102W associated with the corresponding motor phases U, V and W of a motor load 50.
- the individual power stages 100 include an H-bridge switching circuit or inverter 40 with switching devices (e.g., Q1-Q4 with associated diodes D11-D14 in Fig.
- output switching circuit 40 may be provided in the individual power stages 100 with two or more switches forming a switching circuit for generating a power stage output having one of two or more possible levels according to switching control signals 62 provided by an inverter control component or controller 64 of a power converter controller 60.
- Fig. 1 is a multiphase 13-level inverter 40 with six power cells or power stages 100 for each of three motor load phases U, V and W (e.g., 100-U1, 100-U2, 100-U3, 100-U4, 100-U5 and 100-U6 forming a first inverter leg 102U for phase U; 100-V1, 100-V2, 100-V3, 100-V4, 100-V5 and 100-V6 forming a second inverter leg 102V for phase V; and stages 100-W1, 100-W2, 100-W3, 100-W4, 100-W5 and 100-W6 forming a third inverter leg 102W for phase W).
- 100-U1, 100-U2, 100-U3, 100-U4, 100-U5 and 100-U6 forming a first inverter leg 102U for phase U
- 100-V1, 100-V2, 100-V3, 100-V4, 100-V5 and 100-V6 forming a second inverter leg 102V for phase V
- Each of the inverter legs 102 in this example is connected between a power converter neutral point N and the corresponding motor lead U, V or W.
- the various aspects of the present disclosure may be implemented in association with single phase or multiphase multilevel inverter type power conversion systems having any integer number "N" power stages 100, where N is greater than one.
- the illustrated embodiments utilize H-Bridge stages 100 cascaded to form multilevel inverter legs 102 for each output phase of the motor drive system 10
- other types and forms of power stages 100 can be used, such as a stage 100 with a switching circuit having more or less than four switching devices, wherein the broader aspects of the present disclosure are not limited to H-Bridge power cells 100 shown in the illustrated embodiments.
- the individual cells 100 may include as few as two switching devices or any integer number of switches greater than or equal to two.
- the power converter 10 is supplied with multiphase AC input power from a phase shift transformer 30 having a multiphase primary 32 (a delta configuration in the illustrated embodiment) receiving three-phase power from an AC power source 20.
- the transformer 30 includes 18 three-phase secondaries 34, with six sets of three delta-configured three-phase secondaries 34, each set being at a different phase relationship.
- the primary 32 and the secondaries 34 are configured as delta windings in the illustrated example, "Y" connected primary windings and/or secondary windings or other winding configurations can alternatively be used.
- the transformer has three-phase primary and secondary windings 32, 34, other single or multiphase implementations can be used, and the secondaries or sets thereof need not be phase shifted.
- the inverter 40 in this example is a 13-level inverter with six cascaded H-Bridge power stages 100-U1 through 100-U6 having outputs 104-U1 through 104-U6 connected in series with one another (cascaded) between the neutral N and a first winding U of the three-phase motor load 50.
- power stages 100-V1 through 100-V6 provide series connected voltage outputs 104-V1 through 104-V6 between the neutral N and the second winding V
- power stages 100-W1 through 100-W6 provide series connected voltage outputs 104-W1 through 104-W6 between the neutral N and the third winding W of the motor 50.
- the motor drive controller 60 provides control signals 62U to the power stages 100-U1 through 100-U6 associated with the first motor winding U, and also provides control signals 62V to the power stages 100-V1 through 100-V6 and control signals 62W to the power stages 100-W1 through 100-W6.
- the inverter 40 shown in Fig. 1 is a multiphase unit supplying output power to phases U, V and W to drive a three-phase motor 50
- the concepts of the present disclosure are also applicable to single phase converters, for example, a three-phase-to-single phase converter receiving a three phase input from the source 20, with a single series-connected group of cells 100 providing power to a single phase motor or other single phase output load.
- other multiphase outputs can be provided using corresponding series-connected groups of power stages 100 having more than three phases or inverter legs 102.
- the motor drive controller 60 and its component 64 can be implemented using any suitable hardware, processor executed software or firmware, or combinations thereof, wherein an exemplary embodiment of the controller 60 includes one or more processing elements such as microprocessors, microcontrollers, FPGAs, DSPs, programmable logic, etc., along with electronic memory, program memory and signal conditioning driver circuitry, with the processing element(s) programmed or otherwise configured to generate the inverter switching control signals 62 suitable for operating the switching devices of the power stages 100, as well as to perform other motor drive operational tasks to drive the load 50.
- processing elements such as microprocessors, microcontrollers, FPGAs, DSPs, programmable logic, etc.
- electronic memory, program memory and signal conditioning driver circuitry with the processing element(s) programmed or otherwise configured to generate the inverter switching control signals 62 suitable for operating the switching devices of the power stages 100, as well as to perform other motor drive operational tasks to drive the load 50.
- Fig. 2 illustrates one possible implementation of an H-Bridge power stage 100 which can be replicated to form the cascaded power stages of single or multi-phase multilevel inverters 40 such as that shown in Fig. 1 .
- the power stage in Fig. 2 includes a three phase AC input 108 with input terminals 108A, 108B and 108C connectable to receive AC input power, in this case three-phase power from an AC source such as a secondary winding 34 of the transformer 30 in Fig. 1 .
- Other implementations are possible in which the individual power stages or cells 100 receive single-phase AC input power, or in which the individual power stages 100 receive DC input power from an external DC source (not shown).
- AC input power is provided from the cell input 108 to a rectifier circuit 120 having onboard rectifier diodes D1-D6 forming a three-phase rectifier 120 which receives three-phase AC power from the corresponding transformer secondary 34 and provides DC output power at output terminals 121 (+) and 122 (-) connected to a DC bus circuit 130.
- a passive rectifier 120 is used, but active rectifier circuits or other forms of rectifiers can be used, whether having a single or multi-phase AC input.
- the power stage 100 in Fig. 2 also includes a DC link or bus circuit 130 and an output switching circuit 140 (e.g., H-Bridge inverter) providing an output voltage V OUT at a controlled one of a plurality of distinct output voltage levels to a power cell output 104 having first and second output terminals 104A and 104B.
- output switching circuit 140 e.g., H-Bridge inverter
- bypass circuitry can be provided in the individual power stages 100 to bypass the output 104 (not shown).
- the DC bus circuit 130 includes a DC bus capacitor C connected between an upper or first circuit branch extending between the positive output node 121 of the rectifier 120 and a positive input node 131 connected to the output switching circuit 140, and a second or lower circuit branch extending between the negative output node 122 of the rectifier 120 and the negative input node 132 of the output switching circuit 140.
- a precharge and dynamic braking circuit 200 is provided between the rectifier 120 and the output switching circuit 140.
- the rectifier 120 provides DC power across the DC bus capacitor C.
- the DC link circuit 130 provides an input to an H-Bridge inverter 140 formed by four switching devices Q1-Q4 configured in an "H" bridge circuit.
- the illustrated power stage 100 operates based on DC power provided by an internal rectifier circuit 120 driven by an AC input from the corresponding transformer secondary 34, any suitable form of a DC input can be provided to the power stages 100 in accordance with the present disclosure, and the power stages 100 may, but need not, include on-board rectification circuitry 120.
- any suitable switching circuit configuration can be used in the output switching circuits 140 (e.g., inverter) of individual stages 100 having at least two switching devices Q configured to selectively provide voltage at the stage output 104 of at least two distinct levels.
- any suitable type of switching devices Q may be used in the power stages 100, including without limitation semiconductor-based switches such as insulated gate bipolar transistors (IGBTs), silicon controlled rectifiers (SCRs), gate turn-off thyristors (GTOs), integrated gate commutated thyristors (IGCTs), etc.
- the illustrated four-switch H-Bridge output switching circuit 140 advantageously allows selective switching control signal generation by the controller 60 to provide at least two distinct voltage levels at the output 104 in a controlled fashion.
- a voltage output V OUT is provided at the output terminals 104A and 104B of a positive DC level substantially equal to the DC bus voltage across the capacitor C (e.g., +VDC) when the switching devices Q1 and Q4 are turned on (conductive) while the other devices Q2 and Q3 are off (nonconductive).
- a negative output voltage level V OUT is provided when Q2 and Q3 are turned on while Q1 and Q4 are off (e.g., -VDC).
- This configuration also allows a third distinct output voltage level of approximately zero volts by turning on Q1 and Q3 while maintaining Q2 and Q4 off (or alternatively by turning on Q2 and Q4 while maintaining Q1 and Q3 off).
- the exemplary H-Bridge power stage 100 advantageously allows selection of two or more distinct output voltages, and the cascaded configuration of six such stages (e.g., Fig. 1 ) allows selective switching control signal generation by the inverter control component 64 to implement 13 different voltage levels (line to neutral) for application to the corresponding motor phase U, V or W. This, in turn, allows for 25 different line to line voltage levels.
- switching circuitry may be used to implement a two, three, or K-level selectable output for individual stages 100, where K is any positive integer greater than 1.
- Any suitable logic or circuitry in the motor drive controller 60 can be used for providing inverter switching control signals 62 to a given power stage 100, such as carrier-based switching circuitry and/or digital logic implementing pulse width modulated switching control signals 62.
- the controller 60 may include signal level amplification and/or driver circuitry (not shown) to provide suitable drive voltage and/or current levels sufficient to selectively actuate the switching devices Q1-Q4, for instance, such as comparators, carrier wave generators or digital logic and signal drivers.
- the individual power stages 100 also include a dual function precharge and dynamic braking circuit 200 which may be connected anywhere in the DC path between the rectifier 120 (or other DC input) and the output switching circuit 140.
- the precharge and dynamic braking circuit 200 is configured between the rectifier 120 and the DC bus capacitance C, although other implementations are possible.
- the precharge and dynamic braking circuit 200 advantageously employs a single shared resistor 206 operable both for controlled precharging of the DC link capacitor voltage as well as for dynamic braking operation.
- first and second switches 202 and 210 are provided in the circuit 200 for selective connection of the resistor 206 for both these purposes.
- a precharge and dynamic braking control circuit 220 is provided within each power stage 100 to control the operation of the power stage 100 in one of three distinct modes, as summarized in the table shown in Fig. 2 .
- the controller 220 selectively changes the switching states of the precharge and dynamic braking circuit 200 to implement a first mode for precharging the DC link capacitor C, as well as to implement a normal operating mode and a third mode for dynamic braking.
- the controller 220 selectively sets the operating mode at least partially according to the DC bus voltage in the circuit 130.
- the controller 220 may receive one or more feedback signals indicative of the voltage across the DC bus capacitor C (VDC).
- Any suitable hardware, processor-executed firmware, processor-executed software, logic circuitry, FPGA, etc. may be used to construct the precharge and dynamic braking controller 220, and any suitable feedback signal or signals may be used by the controller 220 to selectively set the operating mode of the power stage 120 as described herein.
- the exemplary precharge and dynamic braking controller 220 operates the power stage 100 according to the sensed DC bus voltage of the intermediate DC circuit 130, and selectively places the precharge and dynamic braking circuit 200 in one of three distinct operating modes by comparison of the bus voltage with first and second thresholds.
- Other forms of operational mode switching may be based in various implementations, in whole or in part, on one or more other operating conditions of the motor drive 10 or the power stage 100 thereof.
- circuit 200 includes a resistor 206 coupled between the rectifier 120 and the output switching circuit 140, with the controller 220 operating the circuit 200 in a first operating mode (precharge) to conduct current from the rectifier 120 through the resistor 206 to the capacitor C.
- the controller 220 operates the circuit 200 to bypass the resistor 206 thereby allowing current to flow directly from the rectifier 120 to the switching circuit 140. Dynamic braking is achieved in a third operating mode to connect the resistor 206 in parallel with the capacitor C.
- the first switch 202 is coupled in the first DC bus circuit branch between the nodes 121 and 131, and operates according to a first control signal 222 from the controller 220 in a first state (open or non-conductive) to prevent current from flowing directly through the switch 202 between the rectifier 120 and the switching circuit 140.
- the first switching device 202 is also operable in a second state (closed or conductive) to allow current to flow through the switch 202 according to the control signal 222.
- any suitable switching device 202 may be used, such as a contactor, relay, or a semiconductor-based switching device (e.g., IGBT, SCR, GTO, IGCT, etc.), wherein the switching device 202 is preferably sized to accommodate the maximum current flow required in normal operation.
- a contactor e.g., IGBT, SCR, GTO, IGCT, etc.
- a semiconductor-based switching device e.g., IGBT, SCR, GTO, IGCT, etc.
- the switching device 202 is preferably sized to accommodate the maximum current flow required in normal operation.
- the embodiment of Fig. 2 provides the first switching device 202 in the upper or positive DC circuit branch 121, 131
- the first switch 202 is alternatively provided in the lower DC circuit branch between the nodes 122 and 132.
- a diode 204 is connected across the switch 202, with the anode terminal connected to the output switching circuit node 131 and the cathode connected to the output
- the diode 204 allows regenerative current flow from the output switching circuit 140 to the node 121, for example, during dynamic braking operation, but prevents or blocks forward current flow from the node 121 to the output switching circuit 140 when the switching device 202 is open or non-conductive.
- the resistor 206 and a second diode 208 are connected in a circuit branch in parallel with the contacts of the first switching device 202, with the resistor 206 being connected between the node 121 and an internal node 209, with the anode of the second diode 208 being connected to the node 209 and the cathode being connected to the node 131 as shown.
- a second switching device 210 is coupled between the second DC circuit branch at nodes 122 and 132 and the first internal node 209.
- the second switch 210 operates according to a second control signal 224 from the precharge and dynamic braking controller 220, and can be any suitable type of switching device, including without limitation a contactor, relay, or a semiconductor-based switching device (e.g., IGBT, SCR, GTO, IGCT, etc.).
- the controller 220 includes any suitable logic and signal conditioning and/or driver circuitry to provide the control signals 222 and 224 to properly operate the first and second switching devices 202 and 210 according to the operation and functionality described herein.
- Fig. 3 illustrates an exemplary process or method 300 for operating a power conversion system, which may be implemented using the precharge and dynamic braking controller 220 of individual power stages 104 three-mode operation thereof in accordance with various aspects of the present disclosure.
- Various aspects of the present disclosure further provide non-transitory computer readable mediums, such as an electronic memory operatively associated with the controller 220, which include computer executable instructions for performing the described methods, including the illustrated method 300 of Fig. 3 .
- the method 300 is illustrated and described below in the form of a series of acts or events, it will be appreciated that the various methods of the disclosure are not limited by the illustrated ordering of such acts or events.
- the illustrated process 300 begins at 302 with application of power to the conversion system 10.
- the precharging features may be employed on initial power up of the system 10 and/or upon resumption of power after a temporary disruption.
- a determination is made by the controller 220 at 304 as to whether the DC bus voltage is less than a first (precharge) threshold TH PC .
- the precharge threshold TH PC can be set at or near the nominal DC bus voltage associated with normal operation of the power stage 100. If the DC bus voltage is at or above the first threshold (NO at 304) the process 300 continues to 308 as described below.
- the controller 220 switches to a first operating mode at 306 for precharging the bus capacitor C. As shown in Fig. 4 , the controller 220 provides the first control signal 222 in order to open the first (precharge) switch 202 and provides the second control signal 224 to keep the second switch 210 off (non-conductive). As seen in Fig.
- current from the rectifier 120 in this first precharge mode flows from the node 121 through the resistor 206 and the diode 208 to the node 131, and then through the DC bus capacitor C to the lower DC circuit branch at node 132 to return to the negative rectifier terminal at node 122.
- the resistor 206 has a resistance value selected or designed according to the capacitance of the DC bus capacitor C to control the charging time of the capacitor C.
- the resistance of resistor 206 sets the limit to the inrush current, particularly for a fully discharged bus capacitor C, thereby protecting the semiconductor devices (e.g., a passive rectifier diodes and/or active rectifier switches) of the rectifier 120 from over current conditions, and also protects the capacitor C from high inrush currents.
- the process 300 returns to again assess the DC bus voltage level relative to the threshold TH PC and continues the precharging operation at 304, 306 until the DC bus voltage is at the threshold level TH PC .
- the process 300 in Fig. 3 proceeds to 308 where a determination is made (e.g., by the controller 220) as to whether the DC bus voltage exceeds a second (dynamic braking) threshold TH DB , which is higher than the first threshold TH PC .
- the second threshold TH DB can be set to any desired level suitable for triggering dynamic braking in the power cell or stage 100, such as about 5% - 10% above the nominal DC bus voltage level in one non-limiting example.
- the controller 220 operates in a second or normal mode at 310, with the control signals 222 and 224 maintaining the first switch 202 in the closed or on (e.g., conductive) state and the second switch 210 in an open/off (e.g., non-conductive) state.
- This operation is further illustrated in Fig. 5 , where the DC current flows from the positive rectifier node 121 through the closed first switch 202 to the upper input node 131 of the output switching circuit 140, thereby maintaining the DC bus voltage across the capacitor C and allowing switching operation of the switching circuit 140 according to the switching control signals 62 from the power converter controller 60 ( Fig. 1 above).
- this normal mode operation continues at 304, 308 and 310 while the DC bus voltage is between the first and second thresholds. If, however, the DC bus voltage exceeds the second (upper) threshold TH DB (YES at 308), the process 300 proceeds to 312 with the controller 220 entering a third (dynamic braking) mode.
- This dynamic braking operation is further illustrated in Fig. 6 , with the controller 220 maintaining the first switch 202 in the closed or conductive state via control signal 222, and selectively closing (rendering conductive) the second switch 210 via control signal 224. In certain embodiments, the controller 220 may simply close the switch 210 during the third (dynamic braking) operating mode.
- the controller 220 may provide the control signal 224 so as to pulse width modulate the switch 210.
- the pulse width modulation operation of the control signal 224 may be controlled at least in part according to the DC bus voltage level, for example, with the controller 220 increasing the pulse width for larger excursions of the DC bus voltage above the threshold TH DB .
- any suitable switching frequency may be used in controlling the operation of the second switch 210 via the control signal 224. As seen in Fig.
- the operation of the controller 220 in the dynamic braking mode provides a circuit path through the resistor 206 for conducting current from the output switching circuit node 131 back through the closed switch 202 (and/or through the blocking diode 204), and then through the resistor 206 and the switch 210.
- the operation of the controller 220 in the dynamic braking mode provides an impedance via the resistor 206 to dissipate excess energy flowing back from the output switching circuit 140.
- the resistance value of the shared resistor 206 may be set according to a desired braking impedance value, in addition to the above-mentioned inrush current limiting function performed by the resistor 206 in the precharge operating mode.
- the resistance 206 determines the braking torque, and thus the decelleration rate of a driven motor load 50, and the duty cycle of the pulse width modulated switch 210 determines the power rating of the braking resistor.
- the resistor 206 may be set to approximately 5 ⁇ - 10 ⁇ .
- the process 300 returns to again assess the DC bus voltage at 304 and 308 as described above, thereby implementing three-mode operation of the power cell 100 for selectively precharging the bus capacitor C, operating in normal mode and/or providing dynamic braking.
Landscapes
- Engineering & Computer Science (AREA)
- Power Engineering (AREA)
- Inverter Devices (AREA)
- Electric Propulsion And Braking For Vehicles (AREA)
Description
- Power converters are used to convert input electrical energy from one form to another for driving a load. One form of power conversion system is a motor drive, which may be employed for variable speed operation of an electric motor load. Multilevel inverters such as Cascaded H-Bridge (CHB) inverters are sometimes employed in motor drives and other power conversion systems to generate and provide high voltage drive signals, with individual power cells or power stages being connected in series. Each stage provides a separate DC source and is driven by switch signals to generate positive or negative output voltage, with the series combination of multiple stage outputs providing multilevel inverter output capability for driving the load at variable speeds and torques.
-
WO 2010/022765 A1 relates to a drive unit for comprising: a control power supply for supplying the drive unit with control power, a power source producing direct current to one or more inverters, at least one inverter producing current to the motor, an energy storage arranged at the output of the power source for smoothing direct current and storing energy recovered during braking of the motor, and a discharge circuit for discharging the energy stored in said energy storage, wherein the discharge circuit includes a power resistor arranged to discharge the energy stored in the energy storage. -
US 2004/0160792 A1 describes a motor power supply having an inrush current protection mode, a motor driver mode, an overvoltage protection mode and a dynamic braking mode. In the inrush protection mode, a first resistance limits an inrush current to a capacitor which smoothes a rectifier output to provide DC power to an inverter during the motor drive mode. A controller controls a multi-contact relay and the switching element to implement the various modes of operation. -
EP 2 368 749 A2 discloses a power supply device including a battery, an output switch that connects the battery to a load including a parallel capacitor, and a control circuit that controls the output switch. The parallel capacitor of the load is precharged in the precharge state. After the parallel capacitor of the load is precharged, the load is supplied with electric power from the battery with the semiconductor switching element being brought into the electrically conducted state in which the ON resistance of the semiconductor switching element is smaller than the precharge state. -
WO 92/17929 A1 - It is the object of the present invention to provide an improved power conversion system and method that limits voltage spikes to a manageable level.
- This object is solved by the subject matter of the independent claims.
- Embodiments are defined by the dependent claims.
- Various aspects of the present disclosure are now summarized to facilitate a basic understanding of the disclosure, wherein this summary is not an extensive overview of the disclosure, and is intended neither to identify certain elements of the disclosure, nor to delineate the scope thereof. Rather, the primary purpose of this summary is to present various concepts of the disclosure in a simplified form prior to the more detailed description that is presented hereinafter. The present disclosure provides apparatus and techniques for precharging DC bus capacitors of individual multilevel inverter power stages or cells, as well as for implementing dynamic braking within the power stage using a shared resistor. The invention is described by the contents of the independent claims. In accordance with one or more aspects of the disclosure, a power conversion system is provided which includes a multilevel inverter with one or more inverter legs each having a plurality of power stages individually providing multiple distinct output voltage levels, as well as a converter system controller providing switching control signals to set the individual output levels of the power stages. The individual power stages include a DC bus circuit provided with DC voltage by a rectifier, as well as a switching circuit that provides a power stage output voltage at one of a plurality of
distinct levels. A precharge and dynamic braking circuit is provided within the individual power stages, including a resistor connected between the rectifier and the switching circuit. The precharge and dynamic braking circuit operates in a first mode to conduct current from the rectifier through the resistor to charge the DC bus capacitor, as well as in a second mode to bypass the resistor and allow current to flow from the rectifier to the switching circuit for normal operation. In a third operating mode, the precharge and dynamic braking circuit connects the resistor in parallel with a capacitor to facilitate dynamic braking operation. - In certain embodiments, the precharge and dynamic braking circuit includes a first switch coupled in a DC circuit branch between the rectifier and the switching circuit, as well as a first diode coupled in parallel with the first switch. For normal or dynamic braking operation, the first switch is closed or otherwise rendered conductive to bypass the resistor, and the switches are opened or rendered nonconductive so that precharging current from the rectifier flows through the resistor to charge the capacitor in a precharge operating mode. In various embodiments, moreover, a second switch is coupled between another DC circuit branch and the resistor, with the second switch being open or non-conductive during normal and precharging operation, and the second switch is closed or pulse width modulated during dynamic braking for selective connection of the resistor in parallel with the DC bus capacitor. In certain implementations, a power stage controller provides control signals to the first and second switches to set the operating mode according to the DC bus voltage of the power stage, such as by setting the circuit to a first or precharge operating mode if the DC bus voltage is less than a first (e.g., lower) threshold, operating in a second or normal mode with the resistor not conducting any current when the DC bus voltage is above the first threshold and below a second (e.g., higher) threshold, and operating in a third or dynamic braking mode when the DC bus voltage exceeds the second threshold.
- Methods and non-transitory computer readable mediums are provided with computer executable instructions for operating individual power stages of a multilevel inverter. These techniques include precharging a DC bus capacitance of the power stage through a resistor if the DC bus voltage is less than a first threshold, and connecting the resistor in parallel with the DC bus capacitance if the voltage is greater than a second threshold. In certain embodiments, the resistor is bypassed to allow current flow between the rectifier and the power stage switching circuit if the DC bus voltage is between the first and second threshold values.
- The following description and drawings set forth certain illustrative implementations of the disclosure in detail, which are indicative of several exemplary ways in which the various principles of the disclosure may be carried out. The illustrated examples, however, are not exhaustive of the many possible embodiments of the disclosure. Other objects, advantages and novel features of the disclosure will be set forth in the following detailed description when considered in conjunction with the drawings, in which:
-
Fig. 1 is a schematic diagram illustrating a three-phase 13-level CHB inverter-based motor drive power conversion system with three inverter legs, each having six power stages or power cells connected in series between a neutral point and a motor load phase; -
Fig. 2 is a schematic diagram illustrating an exemplary power stage in the power converter ofFig. 1 having a precharge and dynamic braking circuit using a shared resistor in accordance with one or more aspects of the present disclosure; -
Fig. 3 is a flow diagram illustrating an exemplary method for operating individual power stages in a multilevel inverter in accordance with further aspects of the present disclosure; -
Fig. 4 is a schematic diagram illustrating operation of the power stage ofFig. 2 during a first mode for controlled precharging of a DC bus capacitor through a resistor in a first operating mode; -
Fig. 5 is a schematic diagram showing operation of the power stage ofFig. 2 during normal operation; and -
Fig. 6 is a schematic diagram illustrating dynamic braking operation of the power stage ofFig. 2 with the resistor connected in parallel across the DC bus capacitor. - Referring now to the figures, several embodiments or implementations are hereinafter described in conjunction with the drawings, wherein like reference numerals are used to refer to like elements throughout, and wherein the various features are not necessarily drawn to scale. Multilevel inverter power stage architectures are presented in which precharging and dynamic braking functions are achieved using a single shared resistor with switching circuitry in an intermediate DC bus circuit to selectively connect the resistor to control charging of a DC bus capacitance or to connect the resistor in parallel with the DC bus capacitance to facilitate dissipation of back EMF from a driven motor or other load, while further facilitating normal operation with the resistor bypassed. Dynamic braking and precharging functionality is a desirable combination of features for cascaded H bridge and other multilevel power converter architectures, and the present disclosure provides simple and effective designs for implementing both functions with localized circuitry within the individual power stages forming the cascaded or series-connected multi-cell structures. Dynamic braking apparatus may be used to selectively slow down a motor load being driven by a power converter, and the present disclosure provides selective switching to connect an impedance to dissipate power returning from the motor load as the motor decelerates.
- Precharging is also performed using the same impedance to charge up the DC bus capacitor, for example on startup or after disruption of power, where the DC bus voltage drops below a nominal level. Circuitry within the individual power stages is activated when the DC bus voltage is below a predetermined threshold value to charge up the capacitor at a controlled rate by conducting current from the power stage rectifier or other local DC source through the impedance to limit the inrush current to the capacitor thereby protecting the capacitor and charging semiconductor devices against overcurrent conditions. In the illustrated embodiments, for instance, the shared resistor is sized so as to reduce the current spike upon charge up to a manageable level, and also to facilitate dynamic braking operation. The circuitry thus presents a significant advance over conventional multilevel inverters by providing both these functions with a minimal number of circuit elements. The techniques of the present disclosure, moreover, find utility in association with low-voltage as well as medium or high voltage power converter applications involving any number of cascaded power stages using on-board circuitry with a shared resistor sized for the power levels associated with the individual power cell or stage.
- An exemplary multilevel inverter motor drive
power conversion system 10 is shown inFig. 1 , in which the individual power cells orpower stages 100 incorporate precharging and dynamic braking circuitry employing a shared resistor. Thepower converter 10 includes a three-phasemultilevel inverter 40 with series-connected power stages 100-1, 100-2, 100-3, 100-4, 100-5, 100-6 for each of three sections orinverter legs motor load 50. Although the concepts of the present disclosure are shown in the context of a multiphase multilevel inverter driving a motor load, other embodiments are possible in which other forms ofload 50 are driven, including without limitation single phase AC loads, wherein the present disclosure is not limited to multiphase motor drive type power converters. In certain embodiments, moreover, the individual power stages 100 include an H-bridge switching circuit orinverter 40 with switching devices (e.g., Q1-Q4 with associated diodes D11-D14 inFig. 2 below), although any suitable form ofoutput switching circuit 40 may be provided in the individual power stages 100 with two or more switches forming a switching circuit for generating a power stage output having one of two or more possible levels according to switching control signals 62 provided by an inverter control component orcontroller 64 of apower converter controller 60. - The example of
Fig. 1 is a multiphase 13-level inverter 40 with six power cells orpower stages 100 for each of three motor load phases U, V and W (e.g., 100-U1, 100-U2, 100-U3, 100-U4, 100-U5 and 100-U6 forming a first inverter leg 102U for phase U; 100-V1, 100-V2, 100-V3, 100-V4, 100-V5 and 100-V6 forming asecond inverter leg 102V for phase V; and stages 100-W1, 100-W2, 100-W3, 100-W4, 100-W5 and 100-W6 forming athird inverter leg 102W for phase W). Each of the inverter legs 102 in this example, moreover, is connected between a power converter neutral point N and the corresponding motor lead U, V or W. The various aspects of the present disclosure may be implemented in association with single phase or multiphase multilevel inverter type power conversion systems having any integer number "N" power stages 100, where N is greater than one. In addition, although the illustrated embodiments utilize H-Bridge stages 100 cascaded to form multilevel inverter legs 102 for each output phase of themotor drive system 10, other types and forms of power stages 100 can be used, such as astage 100 with a switching circuit having more or less than four switching devices, wherein the broader aspects of the present disclosure are not limited to H-Bridge power cells 100 shown in the illustrated embodiments. For instance, embodiments are possible, in which theindividual cells 100 may include as few as two switching devices or any integer number of switches greater than or equal to two. - The
power converter 10 is supplied with multiphase AC input power from aphase shift transformer 30 having a multiphase primary 32 (a delta configuration in the illustrated embodiment) receiving three-phase power from anAC power source 20. Thetransformer 30 includes 18 three-phase secondaries 34, with six sets of three delta-configured three-phase secondaries 34, each set being at a different phase relationship. Although the primary 32 and thesecondaries 34 are configured as delta windings in the illustrated example, "Y" connected primary windings and/or secondary windings or other winding configurations can alternatively be used. In addition, while the transformer has three-phase primary andsecondary windings Fig. 1 is coupled to provide AC power to drive a three-phase rectifier 120 of acorresponding power stage 100 of the three-phasemultilevel inverter 40. Theinverter 40 in this example is a 13-level inverter with six cascaded H-Bridge power stages 100-U1 through 100-U6 having outputs 104-U1 through 104-U6 connected in series with one another (cascaded) between the neutral N and a first winding U of the three-phase motor load 50. Similarly, power stages 100-V1 through 100-V6 provide series connected voltage outputs 104-V1 through 104-V6 between the neutral N and the second winding V, and power stages 100-W1 through 100-W6 provide series connected voltage outputs 104-W1 through 104-W6 between the neutral N and the third winding W of themotor 50. - In operation, the
motor drive controller 60 providescontrol signals 62U to the power stages 100-U1 through 100-U6 associated with the first motor winding U, and also providescontrol signals 62V to the power stages 100-V1 through 100-V6 andcontrol signals 62W to the power stages 100-W1 through 100-W6. Although theinverter 40 shown inFig. 1 is a multiphase unit supplying output power to phases U, V and W to drive a three-phase motor 50, the concepts of the present disclosure are also applicable to single phase converters, for example, a three-phase-to-single phase converter receiving a three phase input from thesource 20, with a single series-connected group ofcells 100 providing power to a single phase motor or other single phase output load. Moreover, other multiphase outputs can be provided using corresponding series-connected groups of power stages 100 having more than three phases or inverter legs 102. - The
motor drive controller 60 and itscomponent 64 can be implemented using any suitable hardware, processor executed software or firmware, or combinations thereof, wherein an exemplary embodiment of thecontroller 60 includes one or more processing elements such as microprocessors, microcontrollers, FPGAs, DSPs, programmable logic, etc., along with electronic memory, program memory and signal conditioning driver circuitry, with the processing element(s) programmed or otherwise configured to generate the inverterswitching control signals 62 suitable for operating the switching devices of the power stages 100, as well as to perform other motor drive operational tasks to drive theload 50. -
Fig. 2 illustrates one possible implementation of an H-Bridge power stage 100 which can be replicated to form the cascaded power stages of single or multi-phasemultilevel inverters 40 such as that shown inFig. 1 . The power stage inFig. 2 includes a threephase AC input 108 withinput terminals transformer 30 inFig. 1 . Other implementations are possible in which the individual power stages orcells 100 receive single-phase AC input power, or in which the individual power stages 100 receive DC input power from an external DC source (not shown). In the illustrated example, AC input power is provided from thecell input 108 to arectifier circuit 120 having onboard rectifier diodes D1-D6 forming a three-phase rectifier 120 which receives three-phase AC power from the corresponding transformer secondary 34 and provides DC output power at output terminals 121 (+) and 122 (-) connected to aDC bus circuit 130. In this example, apassive rectifier 120 is used, but active rectifier circuits or other forms of rectifiers can be used, whether having a single or multi-phase AC input. - The
power stage 100 inFig. 2 also includes a DC link orbus circuit 130 and an output switching circuit 140 (e.g., H-Bridge inverter) providing an output voltage VOUT at a controlled one of a plurality of distinct output voltage levels to apower cell output 104 having first andsecond output terminals DC bus circuit 130 includes a DC bus capacitor C connected between an upper or first circuit branch extending between thepositive output node 121 of therectifier 120 and apositive input node 131 connected to theoutput switching circuit 140, and a second or lower circuit branch extending between thenegative output node 122 of therectifier 120 and thenegative input node 132 of theoutput switching circuit 140. As described further below, moreover, a precharge anddynamic braking circuit 200 is provided between therectifier 120 and theoutput switching circuit 140. - In normal operation, the
rectifier 120 provides DC power across the DC bus capacitor C. TheDC link circuit 130, in turn, provides an input to an H-Bridge inverter 140 formed by four switching devices Q1-Q4 configured in an "H" bridge circuit. Although the illustratedpower stage 100 operates based on DC power provided by aninternal rectifier circuit 120 driven by an AC input from the corresponding transformer secondary 34, any suitable form of a DC input can be provided to the power stages 100 in accordance with the present disclosure, and the power stages 100 may, but need not, include on-board rectification circuitry 120. In addition, any suitable switching circuit configuration can be used in the output switching circuits 140 (e.g., inverter) ofindividual stages 100 having at least two switching devices Q configured to selectively provide voltage at thestage output 104 of at least two distinct levels. Moreover, any suitable type of switching devices Q may be used in the power stages 100, including without limitation semiconductor-based switches such as insulated gate bipolar transistors (IGBTs), silicon controlled rectifiers (SCRs), gate turn-off thyristors (GTOs), integrated gate commutated thyristors (IGCTs), etc. - The illustrated four-switch H-Bridge
output switching circuit 140 advantageously allows selective switching control signal generation by thecontroller 60 to provide at least two distinct voltage levels at theoutput 104 in a controlled fashion. For instance, a voltage output VOUT is provided at theoutput terminals Bridge power stage 100 advantageously allows selection of two or more distinct output voltages, and the cascaded configuration of six such stages (e.g.,Fig. 1 ) allows selective switching control signal generation by theinverter control component 64 to implement 13 different voltage levels (line to neutral) for application to the corresponding motor phase U, V or W. This, in turn, allows for 25 different line to line voltage levels. It is noted that other possible switching circuitry may be used to implement a two, three, or K-level selectable output forindividual stages 100, where K is any positive integer greater than 1. Any suitable logic or circuitry in themotor drive controller 60 can be used for providing inverterswitching control signals 62 to a givenpower stage 100, such as carrier-based switching circuitry and/or digital logic implementing pulse width modulated switching control signals 62. In addition, thecontroller 60 may include signal level amplification and/or driver circuitry (not shown) to provide suitable drive voltage and/or current levels sufficient to selectively actuate the switching devices Q1-Q4, for instance, such as comparators, carrier wave generators or digital logic and signal drivers. - As further shown in
Fig. 2 , the individual power stages 100 also include a dual function precharge anddynamic braking circuit 200 which may be connected anywhere in the DC path between the rectifier 120 (or other DC input) and theoutput switching circuit 140. In the illustrated example, the precharge anddynamic braking circuit 200 is configured between therectifier 120 and the DC bus capacitance C, although other implementations are possible. In accordance with the present disclosure, moreover, the precharge anddynamic braking circuit 200 advantageously employs a single sharedresistor 206 operable both for controlled precharging of the DC link capacitor voltage as well as for dynamic braking operation. In addition, first andsecond switches circuit 200 for selective connection of theresistor 206 for both these purposes. In addition, a precharge and dynamicbraking control circuit 220 is provided within eachpower stage 100 to control the operation of thepower stage 100 in one of three distinct modes, as summarized in the table shown inFig. 2 . Specifically, thecontroller 220 selectively changes the switching states of the precharge anddynamic braking circuit 200 to implement a first mode for precharging the DC link capacitor C, as well as to implement a normal operating mode and a third mode for dynamic braking. In certain embodiments, moreover, thecontroller 220 selectively sets the operating mode at least partially according to the DC bus voltage in thecircuit 130. For example, as seen inFig. 2 , thecontroller 220 may receive one or more feedback signals indicative of the voltage across the DC bus capacitor C (VDC). Any suitable hardware, processor-executed firmware, processor-executed software, logic circuitry, FPGA, etc. may be used to construct the precharge anddynamic braking controller 220, and any suitable feedback signal or signals may be used by thecontroller 220 to selectively set the operating mode of thepower stage 120 as described herein. - As seen in the table of
Fig. 2 , at any given time, the exemplary precharge anddynamic braking controller 220 operates thepower stage 100 according to the sensed DC bus voltage of theintermediate DC circuit 130, and selectively places the precharge anddynamic braking circuit 200 in one of three distinct operating modes by comparison of the bus voltage with first and second thresholds. Other forms of operational mode switching may be based in various implementations, in whole or in part, on one or more other operating conditions of themotor drive 10 or thepower stage 100 thereof. In the illustrated example,circuit 200 includes aresistor 206 coupled between therectifier 120 and theoutput switching circuit 140, with thecontroller 220 operating thecircuit 200 in a first operating mode (precharge) to conduct current from therectifier 120 through theresistor 206 to the capacitor C. In a second (normal) operating mode, thecontroller 220 operates thecircuit 200 to bypass theresistor 206 thereby allowing current to flow directly from therectifier 120 to theswitching circuit 140. Dynamic braking is achieved in a third operating mode to connect theresistor 206 in parallel with the capacitor C. - As seen in
Fig. 2 , thefirst switch 202 is coupled in the first DC bus circuit branch between thenodes first control signal 222 from thecontroller 220 in a first state (open or non-conductive) to prevent current from flowing directly through theswitch 202 between therectifier 120 and theswitching circuit 140. Thefirst switching device 202 is also operable in a second state (closed or conductive) to allow current to flow through theswitch 202 according to thecontrol signal 222. Anysuitable switching device 202 may be used, such as a contactor, relay, or a semiconductor-based switching device (e.g., IGBT, SCR, GTO, IGCT, etc.), wherein theswitching device 202 is preferably sized to accommodate the maximum current flow required in normal operation. Although the embodiment ofFig. 2 provides thefirst switching device 202 in the upper or positiveDC circuit branch first switch 202 is alternatively provided in the lower DC circuit branch between thenodes diode 204 is connected across theswitch 202, with the anode terminal connected to the outputswitching circuit node 131 and the cathode connected to theoutput node 121 of therectifier 120. Thediode 204 allows regenerative current flow from theoutput switching circuit 140 to thenode 121, for example, during dynamic braking operation, but prevents or blocks forward current flow from thenode 121 to theoutput switching circuit 140 when theswitching device 202 is open or non-conductive. - The
resistor 206 and asecond diode 208 are connected in a circuit branch in parallel with the contacts of thefirst switching device 202, with theresistor 206 being connected between thenode 121 and aninternal node 209, with the anode of thesecond diode 208 being connected to thenode 209 and the cathode being connected to thenode 131 as shown. In addition, asecond switching device 210 is coupled between the second DC circuit branch atnodes internal node 209. Thesecond switch 210 operates according to a second control signal 224 from the precharge anddynamic braking controller 220, and can be any suitable type of switching device, including without limitation a contactor, relay, or a semiconductor-based switching device (e.g., IGBT, SCR, GTO, IGCT, etc.). Thecontroller 220 includes any suitable logic and signal conditioning and/or driver circuitry to provide the control signals 222 and 224 to properly operate the first andsecond switching devices - Referring also to
Figs. 3-6 ,Fig. 3 illustrates an exemplary process ormethod 300 for operating a power conversion system, which may be implemented using the precharge anddynamic braking controller 220 of individual power stages 104 three-mode operation thereof in accordance with various aspects of the present disclosure. Various aspects of the present disclosure further provide non-transitory computer readable mediums, such as an electronic memory operatively associated with thecontroller 220, which include computer executable instructions for performing the described methods, including the illustratedmethod 300 ofFig. 3 . Although themethod 300 is illustrated and described below in the form of a series of acts or events, it will be appreciated that the various methods of the disclosure are not limited by the illustrated ordering of such acts or events. In this regard, except as specifically provided hereinafter, some acts or events may occur in different order and/or concurrently with other acts or events apart from those illustrated and described herein in accordance with the disclosure. It is further noted that not all illustrated steps may be required to implement a process or method in accordance with the present disclosure, and one or more such acts may be combined. The illustratedmethod 300 other methods of the disclosure may be implemented in hardware, processor-executed software, or combinations thereof, such as in theexemplary controller 220 described herein, and may be embodied in the form of computer executable instructions stored in a tangible, non-transitory computer readable medium, such as in a memory operatively associated with thecontroller 220 in one example. - The illustrated
process 300 begins at 302 with application of power to theconversion system 10. As previously mentioned, the precharging features may be employed on initial power up of thesystem 10 and/or upon resumption of power after a temporary disruption. A determination is made by thecontroller 220 at 304 as to whether the DC bus voltage is less than a first (precharge) threshold THPC. In one possible implementation, the precharge threshold THPC can be set at or near the nominal DC bus voltage associated with normal operation of thepower stage 100. If the DC bus voltage is at or above the first threshold (NO at 304) theprocess 300 continues to 308 as described below. - Referring also to
Fig. 4 , if the bus voltage is less than the threshold THPC (YES at 304 inFig. 3 ), thecontroller 220 switches to a first operating mode at 306 for precharging the bus capacitor C. As shown inFig. 4 , thecontroller 220 provides thefirst control signal 222 in order to open the first (precharge)switch 202 and provides thesecond control signal 224 to keep thesecond switch 210 off (non-conductive). As seen inFig. 4 , current from therectifier 120 in this first precharge mode flows from thenode 121 through theresistor 206 and thediode 208 to thenode 131, and then through the DC bus capacitor C to the lower DC circuit branch atnode 132 to return to the negative rectifier terminal atnode 122. For this operation, theresistor 206 has a resistance value selected or designed according to the capacitance of the DC bus capacitor C to control the charging time of the capacitor C. In this regard, the resistance ofresistor 206 sets the limit to the inrush current, particularly for a fully discharged bus capacitor C, thereby protecting the semiconductor devices (e.g., a passive rectifier diodes and/or active rectifier switches) of therectifier 120 from over current conditions, and also protects the capacitor C from high inrush currents. As seen inFig. 3 , moreover, theprocess 300 returns to again assess the DC bus voltage level relative to the threshold THPC and continues the precharging operation at 304, 306 until the DC bus voltage is at the threshold level THPC. - When the DC bus voltage is at or above the first threshold level THPC (NO at 304), the
process 300 inFig. 3 proceeds to 308 where a determination is made (e.g., by the controller 220) as to whether the DC bus voltage exceeds a second (dynamic braking) threshold THDB, which is higher than the first threshold THPC. The second threshold THDB can be set to any desired level suitable for triggering dynamic braking in the power cell orstage 100, such as about 5% - 10% above the nominal DC bus voltage level in one non-limiting example. If the DC bus voltage is between the first and second thresholds (NO at 308), thecontroller 220 operates in a second or normal mode at 310, with the control signals 222 and 224 maintaining thefirst switch 202 in the closed or on (e.g., conductive) state and thesecond switch 210 in an open/off (e.g., non-conductive) state. This operation is further illustrated inFig. 5 , where the DC current flows from thepositive rectifier node 121 through the closedfirst switch 202 to theupper input node 131 of theoutput switching circuit 140, thereby maintaining the DC bus voltage across the capacitor C and allowing switching operation of theswitching circuit 140 according to theswitching control signals 62 from the power converter controller 60 (Fig. 1 above). - Returning again to
Fig. 3 , this normal mode operation continues at 304, 308 and 310 while the DC bus voltage is between the first and second thresholds. If, however, the DC bus voltage exceeds the second (upper) threshold THDB (YES at 308), theprocess 300 proceeds to 312 with thecontroller 220 entering a third (dynamic braking) mode. This dynamic braking operation is further illustrated inFig. 6 , with thecontroller 220 maintaining thefirst switch 202 in the closed or conductive state viacontrol signal 222, and selectively closing (rendering conductive) thesecond switch 210 viacontrol signal 224. In certain embodiments, thecontroller 220 may simply close theswitch 210 during the third (dynamic braking) operating mode. In other possible embodiments, moreover, thecontroller 220 may provide thecontrol signal 224 so as to pulse width modulate theswitch 210. In some implementations, for instance, the pulse width modulation operation of thecontrol signal 224 may be controlled at least in part according to the DC bus voltage level, for example, with thecontroller 220 increasing the pulse width for larger excursions of the DC bus voltage above the threshold THDB. For such pulse width modulated implementations, moreover, any suitable switching frequency may be used in controlling the operation of thesecond switch 210 via thecontrol signal 224. As seen inFig. 6 , moreover, the operation of thecontroller 220 in the dynamic braking mode provides a circuit path through theresistor 206 for conducting current from the outputswitching circuit node 131 back through the closed switch 202 (and/or through the blocking diode 204), and then through theresistor 206 and theswitch 210. - Thus, the operation of the
controller 220 in the dynamic braking mode provides an impedance via theresistor 206 to dissipate excess energy flowing back from theoutput switching circuit 140. In this regard, the resistance value of the sharedresistor 206 may be set according to a desired braking impedance value, in addition to the above-mentioned inrush current limiting function performed by theresistor 206 in the precharge operating mode. Theresistance 206 determines the braking torque, and thus the decelleration rate of a drivenmotor load 50, and the duty cycle of the pulse width modulatedswitch 210 determines the power rating of the braking resistor. In certain non-limiting embodiments, for example, theresistor 206 may be set to approximately 5Ω - 10Ω. - As seen in
Fig. 3 , moreover, theprocess 300 returns to again assess the DC bus voltage at 304 and 308 as described above, thereby implementing three-mode operation of thepower cell 100 for selectively precharging the bus capacitor C, operating in normal mode and/or providing dynamic braking. - The above examples are merely illustrative of several possible embodiments of various aspects of the present disclosure, wherein equivalent alterations and/or modifications will occur to others skilled in the art upon reading and understanding this specification and the annexed drawings. In particular regard to the various functions performed by the above described components (assemblies, devices, systems, circuits, and the like), the terms (including a reference to a "means") used to describe such components are intended to correspond, unless otherwise indicated, to any component, such as hardware, processor-executed software, or combinations thereof, which performs the specified function of the described component (i.e., that is functionally equivalent), even though not structurally equivalent to the disclosed structure which performs the function in the illustrated implementations of the disclosure. In addition, although a particular feature of the disclosure may have been disclosed with respect to only one of several implementations, such feature may be combined with one or more other features of the other implementations as may be desired and advantageous for any given or particular application. Also, to the extent that the terms "including", "includes", "having", "has", "with", or variants thereof are used in the detailed description and/or in the claims, such terms are intended to be inclusive in a manner similar to the term "comprising".
Claims (7)
- A power conversion system (10), comprising:a multilevel inverter (40), including at least one inverter leg (102) comprising a plurality of power stages (100), the individual power stages (100) comprising:a DC bus circuit (130) with a first DC circuit branch (121, 131) and a second DC circuit branch (122, 132),a rectifier circuit (120) providing a DC voltage to the DC bus circuit (130),an output (104); anda switching circuit (140) operable according to switching control signals (62) to provide an output voltage at the output (104) at one of a plurality of distinct output voltage levels, anda precharge and dynamic braking circuit (200) with a resistor (206) connected between the rectifier circuit (120) and the switching circuit (140), the precharge and dynamic braking circuit (200) operative in a first operating mode (precharge) to conduct current from the rectifier circuit (120) through the resistor (206) to charge a capacitor (C) of the DC bus circuit (130), in a second operating mode (normal) to bypass the resistor (206) and allow current to flow from the rectifier circuit (120) to the switching circuit (140), and in a third operating mode (dynamic braking) to connect the resistor (206) in parallel with the capacitor (C) of the DC bus circuit (130),the outputs (104) of the plurality of power stages of each of the at least one inverter legs (102) being coupled in series with one another, wherein the output (104) of a last power stage (100) of each of the at least one inverter legs (102) provides an output to drive a load (50); anda controller (60) operative to provide the switching control signals (62) to set the individual output voltage levels of the power stages (100) of the multilevel inverter (40), wherein the individual precharge and dynamic braking circuits (200) operate in the first operating mode if a DC bus voltage of the corresponding DC bus circuit (130) is less than a first threshold value (THPC), in the third operating mode if the DC bus voltage is greater than a second threshold value (THDB), and in the second operating mode (normal) if the DC bus voltage is between the first and second threshold values (THPC, THDB), the second threshold value (THDB) being greater than the first threshold value (THpc).
- The power conversion system (10) of claim 1, wherein the precharge and dynamic braking circuit (200) of the individual power stages (100) comprises:a first switching device (202) coupled in the first circuit branch (121, 131) of the DC bus circuit (130) between the rectifier (120) and the switching circuit (140), the first switching device (202) operative according to a first control signal (222) in a first state (open) to prevent current from flowing directly through the first switching device (202) between the rectifier (120) and the switching circuit (140), and in a second state (closed) to allow current to flow through the first switching device (202);a first diode (204) coupled in parallel with the first switching device (202), with a cathode connected to the rectifier (120) and an anode connected to the switching circuit (140);a second diode (208) coupled in series with the resistor (206) in a circuit branch parallel with the first switching device (202), the second diode (208) having an anode connected to the resistor (206) and a cathode connected to the switching circuit (140); anda power stage controller (220) providing the first control signal (222) to selectively place the first switching device (202) in the first state in the first operating mode, and to place the first switching device (202) in the second state in the second and third operating modes.
- The power conversion system (10) of claim 2, wherein the precharge and dynamic braking circuit (200) of the individual power stages (100) comprises:a second switching device (210) coupled between the second DC circuit branch (122, 132) and a first internal node (209) joining the second diode (208) and the resistor (206), the second switching device (210) operative according to a second control signal (224) in a first state (open) to prevent current from flowing between the first internal node (209) and the second DC circuit branch (122, 132), and in a second state (closed) to allow current to flow between the first internal node (209) and the second DC circuit branch (122, 132);wherein the power stage controller (220) provides the second control signal (224) to selectively place the second switching device (210) in the first state in the first and second operating modes, and to place the second switching device (210) in the second state for at least a portion of a time during which the precharge and dynamic braking circuit (200) is in the third operating mode.
- The power conversion system (10) of claim 3, wherein the power stage controller (220) provides the second control signal (224) to pulse width modulate the second switching device (210) in the third operating mode.
- The power conversion system (10) of claim 3, wherein the second switching device (210) is an insulated gate bipolar transistor (IGBT).
- The power conversion system (10) of claim 1, wherein the operating mode of the individual precharge and dynamic braking circuits (220) is determined at least partially according to a DC bus voltage of the DC bus circuit (130).
- A method (300) for operating individual power stages (100) in a multilevel inverter (40) according to claim 1, the method (300) comprising:if a DC bus voltage of a given power stage (100) is less than a first threshold value (THPC), precharging (306) a DC bus capacitance (C) of the given power stage (100) through a resistor (206);if the DC bus voltage of the given power stage is greater than a second threshold value (THDB), connecting (312) the resistor (206) in parallel with the capacitor (C) of the DC bus circuit (130) for dynamic braking of a load (50) driven by the multilevel inverter (40), the second threshold value (THDB) being greater than the first threshold value (THPC); andbypassing (310) the resistor (206) to allow current to flow from a rectifier circuit (120) to a switching circuit (140) of the given power stage (100) if the DC bus voltage is between the first and second threshold values (THPC, THDB).
Applications Claiming Priority (1)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
US13/858,187 US9083274B2 (en) | 2013-04-08 | 2013-04-08 | Power stage precharging and dynamic braking apparatus for multilevel inverter |
Publications (3)
Publication Number | Publication Date |
---|---|
EP2814161A2 EP2814161A2 (en) | 2014-12-17 |
EP2814161A3 EP2814161A3 (en) | 2015-11-25 |
EP2814161B1 true EP2814161B1 (en) | 2018-08-08 |
Family
ID=50442389
Family Applications (1)
Application Number | Title | Priority Date | Filing Date |
---|---|---|---|
EP14163824.7A Active EP2814161B1 (en) | 2013-04-08 | 2014-04-08 | Power stage precharging and dynamic braking apparatus for multilevel inverter |
Country Status (4)
Country | Link |
---|---|
US (1) | US9083274B2 (en) |
EP (1) | EP2814161B1 (en) |
CN (1) | CN104104219B (en) |
BR (1) | BR102014008470B1 (en) |
Cited By (1)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
CN108574427A (en) * | 2017-03-10 | 2018-09-25 | 西门子公司 | Transducer brake unit and frequency converter |
Families Citing this family (47)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
US9425705B2 (en) * | 2012-08-13 | 2016-08-23 | Rockwell Automation Technologies, Inc. | Method and apparatus for bypassing cascaded H-bridge (CHB) power cells and power sub cell for multilevel inverter |
CN104380586B (en) * | 2013-06-04 | 2017-12-12 | 东芝三菱电机产业系统株式会社 | Power conversion device |
KR101611010B1 (en) * | 2013-11-19 | 2016-04-08 | 엘에스산전 주식회사 | Pre-charging circuit of inverter |
KR102166362B1 (en) * | 2013-12-18 | 2020-10-15 | 오티스 엘리베이터 컴파니 | Bus capacitor bank configuration for a multi-level regenerative drive |
US9787212B2 (en) | 2014-05-05 | 2017-10-10 | Rockwell Automation Technologies, Inc. | Motor drive with silicon carbide MOSFET switches |
US9787210B2 (en) | 2015-01-14 | 2017-10-10 | Rockwell Automation Technologies, Inc. | Precharging apparatus and power converter |
CN104967303A (en) * | 2015-06-04 | 2015-10-07 | 中国科学院电工研究所 | Self-starting control apparatus for intelligent electric energy router DC unit and self-starting method |
JP6200457B2 (en) * | 2015-06-29 | 2017-09-20 | ファナック株式会社 | Motor driving device having means for detecting abnormal heat generation in initial charging circuit |
WO2017053443A1 (en) * | 2015-09-21 | 2017-03-30 | Lord Corporation | Improved actuator motion controller with regeneration compensation |
CN105119512B (en) * | 2015-09-23 | 2017-12-22 | 阳光电源股份有限公司 | A kind of electric capacity charging method of multi-electrical level inverter and its application circuit |
DE112016004548T5 (en) | 2015-10-05 | 2018-06-21 | Resilient Power Systems, LLC | Power management using synchronous shared coupling |
US10608545B2 (en) | 2015-10-05 | 2020-03-31 | Resilient Power Systems, LLC | Power management utilizing synchronous common coupling |
CN107078633B (en) * | 2015-10-23 | 2018-10-02 | 三菱电机株式会社 | Power-converting device |
US9917544B2 (en) * | 2016-02-13 | 2018-03-13 | Ge Aviation Systems, Llc | Method and power converter unit for operating a generator |
US10439431B2 (en) * | 2016-02-23 | 2019-10-08 | Vertiv Corporation | Method to reduce inrush currents in a transformer-less rectifier uninterruptible power supply system |
US10020755B2 (en) * | 2016-03-03 | 2018-07-10 | GM Global Technology Operations LLC | Apparatus for discharging a high-voltage bus |
CN107294438A (en) * | 2016-04-05 | 2017-10-24 | 德昌电机(深圳)有限公司 | Electric tool and its motor driven systems |
US9837924B1 (en) * | 2016-06-02 | 2017-12-05 | Rockwell Automation Technologies, Inc. | Precharge apparatus for power conversion system |
CN106230057B (en) * | 2016-08-18 | 2019-03-29 | 西北工业大学 | A kind of precharge of frequency converter and error protection integrated apparatus |
US10486537B2 (en) * | 2016-08-29 | 2019-11-26 | Hamilton Sundstrand Corporation | Power generating systems having synchronous generator multiplex windings and multilevel inverters |
DE102017201955A1 (en) * | 2017-02-08 | 2018-08-09 | Geze Gmbh | braking device |
US10381946B2 (en) * | 2017-02-10 | 2019-08-13 | Regal Beloit America, Inc. | Three-phase to single-phase converter module for electrically commutated motors |
GB2560195B (en) * | 2017-03-03 | 2020-01-08 | Ge Energy Power Conversion Technology Ltd | Electric circuits and power systems incorporating the same |
CN106763185B (en) * | 2017-03-07 | 2018-09-25 | 华中科技大学 | A kind of power electronic controller for multiaxis magnetic suspension bearing |
CN107707003B (en) * | 2017-09-08 | 2020-12-08 | 广州双穗电气设备有限公司 | PWM pulse width type constant-current charging type capacitor energy storage welding charging control system |
US11637503B2 (en) * | 2017-09-14 | 2023-04-25 | Siemens Aktiengesellschaft | Frequency converter, frequency converter assembly, and control method thereof |
EP3457550A1 (en) * | 2017-09-14 | 2019-03-20 | Siemens Aktiengesellschaft | Coupling between circuits in drive networks |
DE102019200181A1 (en) * | 2018-01-15 | 2019-07-18 | Continental Teves Ag & Co. Ohg | Method of control, drive circuit, brake system and use |
US11025052B2 (en) | 2018-01-22 | 2021-06-01 | Rockwell Automation Technologies, Inc. | SCR based AC precharge protection |
CN110071622A (en) * | 2018-01-23 | 2019-07-30 | 西门子公司 | The multi-functional pre-charge circuit and its control device and method and frequency converter of frequency converter |
CN108336763B (en) * | 2018-02-08 | 2021-01-15 | 澄瑞电力科技(上海)有限公司 | Active and reactive decoupling control-based parallel connection method of H-bridge cascaded shore power supply |
GB201803765D0 (en) * | 2018-03-09 | 2018-04-25 | Rolls Royce Plc | AC--AC Converter and method of operation |
US10158299B1 (en) | 2018-04-18 | 2018-12-18 | Rockwell Automation Technologies, Inc. | Common voltage reduction for active front end drives |
US10770987B2 (en) * | 2018-05-11 | 2020-09-08 | Hamilton Sunstrand Corporation | Motor drive architecture for variable frequency alternating current loads |
EP3618250B1 (en) * | 2018-08-29 | 2021-02-17 | FRIWO Gerätebau GmbH | Inrush current limiting device and power factor correction circuit |
CA3125620A1 (en) * | 2019-01-04 | 2020-07-09 | Siemens Aktiengesellschaft | Reducing input harmonic distortion in a power supply |
CN110034705A (en) * | 2019-04-09 | 2019-07-19 | 上海奇电电气科技股份有限公司 | Load-balancing method and braking system |
CN110138231A (en) * | 2019-05-10 | 2019-08-16 | 珠海格力电器股份有限公司 | Drive control circuit, control method thereof, drive control system and air conditioner |
CN110224644B (en) * | 2019-06-12 | 2020-12-11 | 上海艾为电子技术股份有限公司 | Control method and driving circuit for controlling current ripple based on offset feedback voltage |
US11142075B2 (en) * | 2019-08-08 | 2021-10-12 | Hamilton Sundstrand Corporation | Efficient regenerative electrical braking |
CN110460272A (en) * | 2019-09-16 | 2019-11-15 | 江苏科技大学 | High power permanent magnet synchronous motor energy bleeder and control method |
US11211879B2 (en) | 2019-09-23 | 2021-12-28 | Rockwell Automation Technologies, Inc. | Capacitor size reduction and lifetime extension for cascaded H-bridge drives |
CN110912467A (en) * | 2019-12-13 | 2020-03-24 | 浙江禾川科技股份有限公司 | Motor driving circuit |
CN113644829A (en) * | 2020-04-27 | 2021-11-12 | 台达电子企业管理(上海)有限公司 | Pre-charging method of cascade frequency converter and cascade frequency converter |
US20210359621A1 (en) * | 2020-05-14 | 2021-11-18 | Eaton Intelligent Power Limited | Drive system with common dc bus |
EP4020789A1 (en) * | 2020-12-23 | 2022-06-29 | Hamilton Sundstrand Corporation | Motor drive system |
US11342878B1 (en) | 2021-04-09 | 2022-05-24 | Rockwell Automation Technologies, Inc. | Regenerative medium voltage drive (Cascaded H Bridge) with reduced number of sensors |
Family Cites Families (61)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
US3757197A (en) | 1972-07-25 | 1973-09-04 | Gen Electric | Amping voltage on series compensating capacitor series parallel compensated current source inverter with means for cl |
US4039914A (en) | 1975-11-25 | 1977-08-02 | General Electric Company | Dynamic braking in controlled current motor drive systems |
JPS605151B2 (en) | 1978-04-05 | 1985-02-08 | 株式会社日立製作所 | Control method for multiplexed current source inverter |
US4230979A (en) | 1978-04-10 | 1980-10-28 | General Electric Company | Controlled current inverter and motor control system |
US4215304A (en) | 1978-10-02 | 1980-07-29 | General Electric Company | Motor/brake transitioning for an inverter driven a-c induction motor |
US4496899A (en) | 1983-06-28 | 1985-01-29 | General Electric Company | Control for a force commutated current source var generator |
US4545002A (en) | 1983-06-28 | 1985-10-01 | General Electric Company | Thyristor voltage limiter for current source inverter |
US4870338A (en) | 1988-09-26 | 1989-09-26 | Westinghouse Electric Corp. | Load commutated inverter (LCI) induction motor drive |
US4833389A (en) | 1988-09-26 | 1989-05-23 | Westinghouse Electric Corp. | Current source inverter control system for load commutated induction motor drive |
US5005115A (en) | 1989-07-28 | 1991-04-02 | Westinghouse Electric Corp. | Forced-commutated current-source converter and AC motor drive using the same |
US5041959A (en) | 1990-08-14 | 1991-08-20 | General Electric Company | Control system for a current source converter supplying an AC bus |
US5083039B1 (en) | 1991-02-01 | 1999-11-16 | Zond Energy Systems Inc | Variable speed wind turbine |
US5293308A (en) * | 1991-03-26 | 1994-03-08 | Auckland Uniservices Limited | Inductive power distribution system |
FR2735296B1 (en) | 1995-06-08 | 1997-08-22 | Sgs Thomson Microelectronics | CIRCUIT AND METHOD FOR CONTROLLING A CURRENT CALL LIMITER IN A POWER CONVERTER |
WO1997004521A1 (en) | 1995-07-18 | 1997-02-06 | Midwest Research Institute | A variable speed wind turbine generator system with zero-sequence filter |
JP3724523B2 (en) | 1996-12-20 | 2005-12-07 | 株式会社安川電機 | Inrush current prevention resistor protection method |
US5875281A (en) * | 1997-07-24 | 1999-02-23 | Cableform, Inc. | DC solid state series wound motor drive |
GB2330254B (en) | 1997-10-09 | 2000-10-18 | Toshiba Kk | Multiple inverter system |
US6058031A (en) * | 1997-10-23 | 2000-05-02 | General Electric Company | Five level high power motor drive converter and control system |
DE19756777B4 (en) | 1997-12-19 | 2005-07-21 | Wobben, Aloys, Dipl.-Ing. | Method for operating a wind energy plant and wind energy plant |
US5969957A (en) | 1998-02-04 | 1999-10-19 | Soft Switching Technologies Corporation | Single phase to three phase converter |
US6005362A (en) * | 1998-02-13 | 1999-12-21 | The Texas A&M University Systems | Method and system for ride-through of an adjustable speed drive for voltage sags and short-term power interruption |
US5933339A (en) | 1998-03-23 | 1999-08-03 | Electric Boat Corporation | Modular static power converter connected in a multi-level, multi-phase, multi-circuit configuration |
US6262555B1 (en) | 1998-10-02 | 2001-07-17 | Robicon Corporation | Apparatus and method to generate braking torque in an AC drive |
US6118676A (en) | 1998-11-06 | 2000-09-12 | Soft Switching Technologies Corp. | Dynamic voltage sag correction |
JP4284478B2 (en) * | 1998-12-28 | 2009-06-24 | 株式会社安川電機 | Inverter device |
US6166513A (en) | 1999-04-09 | 2000-12-26 | Robicon Corporation | Four-quadrant AC-AC drive and method |
US6377478B1 (en) | 1999-05-28 | 2002-04-23 | Toshiba International Corporation | Inverter device |
US6301130B1 (en) | 1999-09-01 | 2001-10-09 | Robicon Corporation | Modular multi-level adjustable supply with parallel connected active inputs |
US6166929A (en) | 2000-02-29 | 2000-12-26 | Rockwell Technologies, Llc | CSI based drive having active damping control |
EP1250741B1 (en) | 2000-11-30 | 2008-02-13 | Mitsubishi Denki Kabushiki Kaisha | Inrush current limiting circuit, power source device and power conversion device |
DE10119624A1 (en) | 2001-04-20 | 2002-11-21 | Aloys Wobben | Operating wind energy plant involves regulating power delivered from generator to electrical load, especially of electrical network, depending on current delivered to the load |
JP3535477B2 (en) | 2001-05-17 | 2004-06-07 | 株式会社日立製作所 | Inverter device, inverter conversion method, and initial charging method of inverter device |
US6714429B2 (en) | 2001-08-15 | 2004-03-30 | Astec International Limited | Active inrush current control for AC to DC converters |
TW539934B (en) | 2001-12-06 | 2003-07-01 | Delta Electronics Inc | Inrush current suppression circuit |
KR100465805B1 (en) * | 2002-12-23 | 2005-01-13 | 삼성전자주식회사 | Soft charging and dynamic braking device using motor |
KR100534107B1 (en) * | 2003-02-14 | 2005-12-08 | 삼성전자주식회사 | Power supply apparatus for motor |
US7233129B2 (en) | 2003-05-07 | 2007-06-19 | Clipper Windpower Technology, Inc. | Generator with utility fault ride-through capability |
KR100488528B1 (en) * | 2003-05-16 | 2005-05-11 | 삼성전자주식회사 | Power supply device for motor |
KR100566437B1 (en) | 2003-11-11 | 2006-03-31 | 엘에스산전 주식회사 | Inverter fault detection apparatus and method using phase shifting |
AT504818A1 (en) | 2004-07-30 | 2008-08-15 | Windtec Consulting Gmbh | TRANSMISSION TRAIL OF A WIND POWER PLANT |
US7158393B2 (en) | 2005-03-11 | 2007-01-02 | Soft Switching Technologies Corporation | Power conversion and voltage sag correction with regenerative loads |
US7173399B2 (en) | 2005-04-19 | 2007-02-06 | General Electric Company | Integrated torsional mode damping system and method |
US7508147B2 (en) | 2005-05-19 | 2009-03-24 | Siemens Energy & Automation, Inc. | Variable-frequency drive with regeneration capability |
MX2008002303A (en) | 2005-08-18 | 2008-03-14 | Siemens Energy & Automat | System and method for limiting ac inrush current. |
TW200713762A (en) | 2005-09-06 | 2007-04-01 | Acbel Polytech Inc | AC-DC converter capable of actively suppressing inrush current |
US7511385B2 (en) | 2005-11-11 | 2009-03-31 | Converteam Ltd | Power converters |
US7312537B1 (en) | 2006-06-19 | 2007-12-25 | General Electric Company | Methods and apparatus for supplying and/or absorbing reactive power |
US7402965B2 (en) | 2006-09-21 | 2008-07-22 | Rockwell Automation Technologies, Inc. | DC common bus self-protection method and system |
DE102006054768A1 (en) | 2006-11-16 | 2008-05-21 | Nordex Energy Gmbh | Method for operating a wind energy plant in power-limited operation |
JP4845904B2 (en) | 2008-02-08 | 2011-12-28 | 株式会社日立製作所 | Wind power generation system |
US7880343B2 (en) | 2008-04-07 | 2011-02-01 | Toshiba International Corporation | Drive isolation transformer controller and method |
US7965529B2 (en) | 2008-05-13 | 2011-06-21 | Eaton Corporation | Voltage source inverter and medium voltage pre-charge circuit therefor |
US8030791B2 (en) | 2008-07-31 | 2011-10-04 | Rockwell Automation Technologies, Inc. | Current source converter-based wind energy system |
CN202121500U (en) * | 2008-08-26 | 2012-01-18 | Abb技术公司 | Driving unit |
US7679208B1 (en) | 2008-09-18 | 2010-03-16 | Samsung Heavy Ind. Co., Ltd. | Apparatus and system for pitch angle control of wind turbine |
US7929323B2 (en) | 2008-09-26 | 2011-04-19 | Rockwell Automation Technologies, Inc. | Method and apparatus for pre-charging power converters and diagnosing pre-charge faults |
US8223515B2 (en) | 2009-02-26 | 2012-07-17 | TECO—Westinghouse Motor Company | Pre-charging an inverter using an auxiliary winding |
US8587160B2 (en) | 2009-09-04 | 2013-11-19 | Rockwell Automation Technologies, Inc. | Grid fault ride-through for current source converter-based wind energy conversion systems |
US8400085B2 (en) | 2009-09-04 | 2013-03-19 | Rockwell Automation Technologies, Inc. | Dynamic braking for current source converter based drive |
JP5627264B2 (en) * | 2010-03-27 | 2014-11-19 | 三洋電機株式会社 | Power supply device for vehicle and vehicle equipped with this power supply device |
-
2013
- 2013-04-08 US US13/858,187 patent/US9083274B2/en active Active
-
2014
- 2014-04-08 BR BR102014008470-3A patent/BR102014008470B1/en active IP Right Grant
- 2014-04-08 CN CN201410138168.9A patent/CN104104219B/en active Active
- 2014-04-08 EP EP14163824.7A patent/EP2814161B1/en active Active
Non-Patent Citations (1)
Title |
---|
None * |
Cited By (2)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
CN108574427A (en) * | 2017-03-10 | 2018-09-25 | 西门子公司 | Transducer brake unit and frequency converter |
CN108574427B (en) * | 2017-03-10 | 2022-06-28 | 西门子公司 | Frequency converter brake unit and frequency converter |
Also Published As
Publication number | Publication date |
---|---|
BR102014008470B1 (en) | 2021-05-18 |
US9083274B2 (en) | 2015-07-14 |
EP2814161A3 (en) | 2015-11-25 |
EP2814161A2 (en) | 2014-12-17 |
CN104104219B (en) | 2017-04-12 |
BR102014008470A2 (en) | 2015-11-03 |
CN104104219A (en) | 2014-10-15 |
US20140300298A1 (en) | 2014-10-09 |
Similar Documents
Publication | Publication Date | Title |
---|---|---|
EP2814161B1 (en) | Power stage precharging and dynamic braking apparatus for multilevel inverter | |
US9787213B2 (en) | Power cell bypass method and apparatus for multilevel inverter | |
US9007787B2 (en) | Method and apparatus for bypassing Cascaded H-Bridge (CHB) power cells and power sub cell for multilevel inverter | |
US10855168B2 (en) | Power conversion device having bypass circuit protection | |
US20190214899A1 (en) | Method and apparatus for bypassing cascaded h-bridge (chb) power cells and power sub cell for multilevel inverter | |
US9812990B1 (en) | Spare on demand power cells for modular multilevel power converter | |
US9748848B2 (en) | Modular multilevel DC/DC converter for HVDC applications | |
US8816625B2 (en) | Integrated regenerative AC drive with solid state precharging | |
KR102412845B1 (en) | In particular, a drive system for a vehicle and a method of heating the drive system | |
JP6174498B2 (en) | Power converter | |
US20050122082A1 (en) | Drive system | |
CN107046273B (en) | Electric power system | |
JP6440923B1 (en) | Power converter | |
JP6253850B2 (en) | AC rotating electrical machine control device | |
US11472305B2 (en) | Charging circuit for a vehicle-side electrical energy store | |
WO2019064705A1 (en) | Power conversion device | |
CN113165540A (en) | Vehicle side charging device | |
CN107852086B (en) | Multi-phase inverter | |
CN106992701B (en) | Propulsion device and circuit arrangement for operating an electric machine with the aid of two energy stores | |
CN112448603A (en) | Power conversion device | |
CN113661643A (en) | Method for limiting current in the event of transient voltage changes at the alternating current output of a multilevel inverter, and multilevel inverter | |
JP2020058178A (en) | Charging control method and charging control device | |
US11855555B2 (en) | Control device for an inverter, inverter for a vehicle, vehicle and method of operating an inverter | |
KR20170050605A (en) | Controlling circuit for multilevel inverter and controlling method thereof | |
SU1089736A1 (en) | Versions of three-phase a.c.voltage-to-a.c.voltage converter |
Legal Events
Date | Code | Title | Description |
---|---|---|---|
17P | Request for examination filed |
Effective date: 20140408 |
|
AK | Designated contracting states |
Kind code of ref document: A2 Designated state(s): AL AT BE BG CH CY CZ DE DK EE ES FI FR GB GR HR HU IE IS IT LI LT LU LV MC MK MT NL NO PL PT RO RS SE SI SK SM TR |
|
AX | Request for extension of the european patent |
Extension state: BA ME |
|
PUAI | Public reference made under article 153(3) epc to a published international application that has entered the european phase |
Free format text: ORIGINAL CODE: 0009012 |
|
RIC1 | Information provided on ipc code assigned before grant |
Ipc: H02M 5/453 20060101AFI20150618BHEP |
|
RIC1 | Information provided on ipc code assigned before grant |
Ipc: H02M 5/453 20060101AFI20150701BHEP |
|
PUAL | Search report despatched |
Free format text: ORIGINAL CODE: 0009013 |
|
AK | Designated contracting states |
Kind code of ref document: A3 Designated state(s): AL AT BE BG CH CY CZ DE DK EE ES FI FR GB GR HR HU IE IS IT LI LT LU LV MC MK MT NL NO PL PT RO RS SE SI SK SM TR |
|
AX | Request for extension of the european patent |
Extension state: BA ME |
|
RIC1 | Information provided on ipc code assigned before grant |
Ipc: H02M 5/453 20060101AFI20151022BHEP |
|
R17P | Request for examination filed (corrected) |
Effective date: 20160525 |
|
RBV | Designated contracting states (corrected) |
Designated state(s): AL AT BE BG CH CY CZ DE DK EE ES FI FR GB GR HR HU IE IS IT LI LT LU LV MC MK MT NL NO PL PT RO RS SE SI SK SM TR |
|
GRAP | Despatch of communication of intention to grant a patent |
Free format text: ORIGINAL CODE: EPIDOSNIGR1 |
|
STAA | Information on the status of an ep patent application or granted ep patent |
Free format text: STATUS: GRANT OF PATENT IS INTENDED |
|
RIN1 | Information on inventor provided before grant (corrected) |
Inventor name: NONDAHL, THOMAS Inventor name: LIU, JINGBO |
|
INTG | Intention to grant announced |
Effective date: 20180322 |
|
GRAS | Grant fee paid |
Free format text: ORIGINAL CODE: EPIDOSNIGR3 |
|
GRAA | (expected) grant |
Free format text: ORIGINAL CODE: 0009210 |
|
STAA | Information on the status of an ep patent application or granted ep patent |
Free format text: STATUS: THE PATENT HAS BEEN GRANTED |
|
AK | Designated contracting states |
Kind code of ref document: B1 Designated state(s): AL AT BE BG CH CY CZ DE DK EE ES FI FR GB GR HR HU IE IS IT LI LT LU LV MC MK MT NL NO PL PT RO RS SE SI SK SM TR |
|
REG | Reference to a national code |
Ref country code: GB Ref legal event code: FG4D |
|
REG | Reference to a national code |
Ref country code: CH Ref legal event code: EP Ref country code: AT Ref legal event code: REF Ref document number: 1028134 Country of ref document: AT Kind code of ref document: T Effective date: 20180815 |
|
REG | Reference to a national code |
Ref country code: IE Ref legal event code: FG4D |
|
REG | Reference to a national code |
Ref country code: DE Ref legal event code: R096 Ref document number: 602014029811 Country of ref document: DE |
|
REG | Reference to a national code |
Ref country code: NL Ref legal event code: MP Effective date: 20180808 |
|
REG | Reference to a national code |
Ref country code: LT Ref legal event code: MG4D |
|
REG | Reference to a national code |
Ref country code: AT Ref legal event code: MK05 Ref document number: 1028134 Country of ref document: AT Kind code of ref document: T Effective date: 20180808 |
|
PG25 | Lapsed in a contracting state [announced via postgrant information from national office to epo] |
Ref country code: GR Free format text: LAPSE BECAUSE OF FAILURE TO SUBMIT A TRANSLATION OF THE DESCRIPTION OR TO PAY THE FEE WITHIN THE PRESCRIBED TIME-LIMIT Effective date: 20181109 Ref country code: NO Free format text: LAPSE BECAUSE OF FAILURE TO SUBMIT A TRANSLATION OF THE DESCRIPTION OR TO PAY THE FEE WITHIN THE PRESCRIBED TIME-LIMIT Effective date: 20181108 Ref country code: BG Free format text: LAPSE BECAUSE OF FAILURE TO SUBMIT A TRANSLATION OF THE DESCRIPTION OR TO PAY THE FEE WITHIN THE PRESCRIBED TIME-LIMIT Effective date: 20181108 Ref country code: NL Free format text: LAPSE BECAUSE OF FAILURE TO SUBMIT A TRANSLATION OF THE DESCRIPTION OR TO PAY THE FEE WITHIN THE PRESCRIBED TIME-LIMIT Effective date: 20180808 Ref country code: AT Free format text: LAPSE BECAUSE OF FAILURE TO SUBMIT A TRANSLATION OF THE DESCRIPTION OR TO PAY THE FEE WITHIN THE PRESCRIBED TIME-LIMIT Effective date: 20180808 Ref country code: LT Free format text: LAPSE BECAUSE OF FAILURE TO SUBMIT A TRANSLATION OF THE DESCRIPTION OR TO PAY THE FEE WITHIN THE PRESCRIBED TIME-LIMIT Effective date: 20180808 Ref country code: PL Free format text: LAPSE BECAUSE OF FAILURE TO SUBMIT A TRANSLATION OF THE DESCRIPTION OR TO PAY THE FEE WITHIN THE PRESCRIBED TIME-LIMIT Effective date: 20180808 Ref country code: IS Free format text: LAPSE BECAUSE OF FAILURE TO SUBMIT A TRANSLATION OF THE DESCRIPTION OR TO PAY THE FEE WITHIN THE PRESCRIBED TIME-LIMIT Effective date: 20181208 Ref country code: RS Free format text: LAPSE BECAUSE OF FAILURE TO SUBMIT A TRANSLATION OF THE DESCRIPTION OR TO PAY THE FEE WITHIN THE PRESCRIBED TIME-LIMIT Effective date: 20180808 Ref country code: FI Free format text: LAPSE BECAUSE OF FAILURE TO SUBMIT A TRANSLATION OF THE DESCRIPTION OR TO PAY THE FEE WITHIN THE PRESCRIBED TIME-LIMIT Effective date: 20180808 Ref country code: SE Free format text: LAPSE BECAUSE OF FAILURE TO SUBMIT A TRANSLATION OF THE DESCRIPTION OR TO PAY THE FEE WITHIN THE PRESCRIBED TIME-LIMIT Effective date: 20180808 |
|
PG25 | Lapsed in a contracting state [announced via postgrant information from national office to epo] |
Ref country code: AL Free format text: LAPSE BECAUSE OF FAILURE TO SUBMIT A TRANSLATION OF THE DESCRIPTION OR TO PAY THE FEE WITHIN THE PRESCRIBED TIME-LIMIT Effective date: 20180808 Ref country code: HR Free format text: LAPSE BECAUSE OF FAILURE TO SUBMIT A TRANSLATION OF THE DESCRIPTION OR TO PAY THE FEE WITHIN THE PRESCRIBED TIME-LIMIT Effective date: 20180808 Ref country code: LV Free format text: LAPSE BECAUSE OF FAILURE TO SUBMIT A TRANSLATION OF THE DESCRIPTION OR TO PAY THE FEE WITHIN THE PRESCRIBED TIME-LIMIT Effective date: 20180808 |
|
PG25 | Lapsed in a contracting state [announced via postgrant information from national office to epo] |
Ref country code: EE Free format text: LAPSE BECAUSE OF FAILURE TO SUBMIT A TRANSLATION OF THE DESCRIPTION OR TO PAY THE FEE WITHIN THE PRESCRIBED TIME-LIMIT Effective date: 20180808 Ref country code: CZ Free format text: LAPSE BECAUSE OF FAILURE TO SUBMIT A TRANSLATION OF THE DESCRIPTION OR TO PAY THE FEE WITHIN THE PRESCRIBED TIME-LIMIT Effective date: 20180808 Ref country code: IT Free format text: LAPSE BECAUSE OF FAILURE TO SUBMIT A TRANSLATION OF THE DESCRIPTION OR TO PAY THE FEE WITHIN THE PRESCRIBED TIME-LIMIT Effective date: 20180808 Ref country code: ES Free format text: LAPSE BECAUSE OF FAILURE TO SUBMIT A TRANSLATION OF THE DESCRIPTION OR TO PAY THE FEE WITHIN THE PRESCRIBED TIME-LIMIT Effective date: 20180808 Ref country code: RO Free format text: LAPSE BECAUSE OF FAILURE TO SUBMIT A TRANSLATION OF THE DESCRIPTION OR TO PAY THE FEE WITHIN THE PRESCRIBED TIME-LIMIT Effective date: 20180808 |
|
REG | Reference to a national code |
Ref country code: DE Ref legal event code: R097 Ref document number: 602014029811 Country of ref document: DE |
|
PG25 | Lapsed in a contracting state [announced via postgrant information from national office to epo] |
Ref country code: SM Free format text: LAPSE BECAUSE OF FAILURE TO SUBMIT A TRANSLATION OF THE DESCRIPTION OR TO PAY THE FEE WITHIN THE PRESCRIBED TIME-LIMIT Effective date: 20180808 Ref country code: DK Free format text: LAPSE BECAUSE OF FAILURE TO SUBMIT A TRANSLATION OF THE DESCRIPTION OR TO PAY THE FEE WITHIN THE PRESCRIBED TIME-LIMIT Effective date: 20180808 Ref country code: SK Free format text: LAPSE BECAUSE OF FAILURE TO SUBMIT A TRANSLATION OF THE DESCRIPTION OR TO PAY THE FEE WITHIN THE PRESCRIBED TIME-LIMIT Effective date: 20180808 |
|
PLBE | No opposition filed within time limit |
Free format text: ORIGINAL CODE: 0009261 |
|
STAA | Information on the status of an ep patent application or granted ep patent |
Free format text: STATUS: NO OPPOSITION FILED WITHIN TIME LIMIT |
|
26N | No opposition filed |
Effective date: 20190509 |
|
PG25 | Lapsed in a contracting state [announced via postgrant information from national office to epo] |
Ref country code: SI Free format text: LAPSE BECAUSE OF FAILURE TO SUBMIT A TRANSLATION OF THE DESCRIPTION OR TO PAY THE FEE WITHIN THE PRESCRIBED TIME-LIMIT Effective date: 20180808 |
|
REG | Reference to a national code |
Ref country code: CH Ref legal event code: PL |
|
REG | Reference to a national code |
Ref country code: BE Ref legal event code: MM Effective date: 20190430 |
|
PG25 | Lapsed in a contracting state [announced via postgrant information from national office to epo] |
Ref country code: MC Free format text: LAPSE BECAUSE OF FAILURE TO SUBMIT A TRANSLATION OF THE DESCRIPTION OR TO PAY THE FEE WITHIN THE PRESCRIBED TIME-LIMIT Effective date: 20180808 Ref country code: LU Free format text: LAPSE BECAUSE OF NON-PAYMENT OF DUE FEES Effective date: 20190408 |
|
PG25 | Lapsed in a contracting state [announced via postgrant information from national office to epo] |
Ref country code: LI Free format text: LAPSE BECAUSE OF NON-PAYMENT OF DUE FEES Effective date: 20190430 Ref country code: CH Free format text: LAPSE BECAUSE OF NON-PAYMENT OF DUE FEES Effective date: 20190430 |
|
PG25 | Lapsed in a contracting state [announced via postgrant information from national office to epo] |
Ref country code: BE Free format text: LAPSE BECAUSE OF NON-PAYMENT OF DUE FEES Effective date: 20190430 |
|
PG25 | Lapsed in a contracting state [announced via postgrant information from national office to epo] |
Ref country code: TR Free format text: LAPSE BECAUSE OF FAILURE TO SUBMIT A TRANSLATION OF THE DESCRIPTION OR TO PAY THE FEE WITHIN THE PRESCRIBED TIME-LIMIT Effective date: 20180808 |
|
PG25 | Lapsed in a contracting state [announced via postgrant information from national office to epo] |
Ref country code: IE Free format text: LAPSE BECAUSE OF NON-PAYMENT OF DUE FEES Effective date: 20190408 |
|
PG25 | Lapsed in a contracting state [announced via postgrant information from national office to epo] |
Ref country code: PT Free format text: LAPSE BECAUSE OF FAILURE TO SUBMIT A TRANSLATION OF THE DESCRIPTION OR TO PAY THE FEE WITHIN THE PRESCRIBED TIME-LIMIT Effective date: 20181208 |
|
PG25 | Lapsed in a contracting state [announced via postgrant information from national office to epo] |
Ref country code: CY Free format text: LAPSE BECAUSE OF FAILURE TO SUBMIT A TRANSLATION OF THE DESCRIPTION OR TO PAY THE FEE WITHIN THE PRESCRIBED TIME-LIMIT Effective date: 20180808 |
|
PG25 | Lapsed in a contracting state [announced via postgrant information from national office to epo] |
Ref country code: MT Free format text: LAPSE BECAUSE OF FAILURE TO SUBMIT A TRANSLATION OF THE DESCRIPTION OR TO PAY THE FEE WITHIN THE PRESCRIBED TIME-LIMIT Effective date: 20180808 Ref country code: HU Free format text: LAPSE BECAUSE OF FAILURE TO SUBMIT A TRANSLATION OF THE DESCRIPTION OR TO PAY THE FEE WITHIN THE PRESCRIBED TIME-LIMIT; INVALID AB INITIO Effective date: 20140408 |
|
PG25 | Lapsed in a contracting state [announced via postgrant information from national office to epo] |
Ref country code: MK Free format text: LAPSE BECAUSE OF FAILURE TO SUBMIT A TRANSLATION OF THE DESCRIPTION OR TO PAY THE FEE WITHIN THE PRESCRIBED TIME-LIMIT Effective date: 20180808 |
|
P01 | Opt-out of the competence of the unified patent court (upc) registered |
Effective date: 20230404 |
|
PGFP | Annual fee paid to national office [announced via postgrant information from national office to epo] |
Ref country code: GB Payment date: 20240321 Year of fee payment: 11 |
|
PGFP | Annual fee paid to national office [announced via postgrant information from national office to epo] |
Ref country code: FR Payment date: 20240320 Year of fee payment: 11 |
|
PGFP | Annual fee paid to national office [announced via postgrant information from national office to epo] |
Ref country code: DE Payment date: 20240320 Year of fee payment: 11 |